TWI650899B - Hybrid serial high frequency signal distribution circuit - Google Patents
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- TWI650899B TWI650899B TW106144440A TW106144440A TWI650899B TW I650899 B TWI650899 B TW I650899B TW 106144440 A TW106144440 A TW 106144440A TW 106144440 A TW106144440 A TW 106144440A TW I650899 B TWI650899 B TW I650899B
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Abstract
本發明係為一種混合式串接高頻信號分佈電路,其係於基板設置傳輸線組。第一傳輸線包含第一矩形環繞段及第一橫伸段。第二傳輸線包含第二矩形環繞段及的第二橫伸段。第三傳輸線包含第三矩形環繞段及第三橫伸段。第一橫伸段二側延伸有第一延伸段及第二延伸段。第二橫伸段二側延伸有第三延伸段及第四延伸段。第三橫伸段二側延伸有第五延伸段及第六延伸段。第四傳輸線二側延伸有第七延伸段及第八延伸段。第三延伸段外側間隔設有第一導電塊。第五延伸段外側間隔設有第二導電塊。第四傳輸線一側間隔設有第三導電塊。第三延伸段與第一導電塊之間、第五延伸段與第二導電塊之間以及第四傳輸線一側與第三導電塊之間各自連接一負載元件,俾能運用不同功率分配比率枝幹耦合器以混合方式形成串接高頻信號之分佈電路。 The invention is a hybrid series-connected high-frequency signal distribution circuit. The transmission line group is arranged on a substrate. The first transmission line includes a first rectangular surrounding segment and a first transversely extending segment. The second transmission line includes a second rectangular surrounding section and a second transversely extending section. The third transmission line includes a third rectangular surrounding section and a third transverse extending section. A first extension section and a second extension section extend on both sides of the first transverse extension section. A third extension section and a fourth extension section extend on both sides of the second transverse extension section. A fifth extension section and a sixth extension section extend on both sides of the third transverse extension section. The fourth transmission line extends on both sides of a seventh extension and an eighth extension. First conductive blocks are spaced from the third extension. Second conductive blocks are spaced apart from the fifth extension. Third conductive blocks are spaced from one side of the fourth transmission line. A load element is connected between the third extension section and the first conductive block, between the fifth extension section and the second conductive block, and between the fourth transmission line side and the third conductive block, and different power distribution ratios cannot be used. The dry coupler forms a distributed circuit that connects high-frequency signals in a hybrid manner.
Description
本發明係有關一種混合式串接高頻信號分佈電路,尤指一種可以運用不同功率分配比率枝幹耦合器以混合方式形成串接高頻信號之分佈電路的枝幹耦合器技術。 The present invention relates to a hybrid series-connected high-frequency signal distribution circuit, and more particularly, to a branch coupler technology that can use branch couplers with different power distribution ratios to form a series-connected high-frequency signal distribution circuit in a hybrid manner.
隨著科技的蓬勃發展,連帶使得無線通訊系統之微波技術進展十分迅速及普遍,如早期的無線電到現今流行的物聯網系統、數位電視系統以及行動通訊系統,無線資訊傳輸系統確實已與現代人的生活緊密相連,而產品也朝向效能高、成本低、容易製作、輕薄短小的方向發展,以致寬頻、多頻段、縮小化以及可調結構已成為設計耦合器所需具備的要項。再者,在微波電路中枝幹耦合器如參考文獻[1-4]扮演很重要的角色,並且運用於許多方面,如功率放大器如參考文獻[5]、天線陣列如參考文獻[6-7]、輸出埠功率不等比如參考文獻[8-9]、功率分配如參考文獻[10]。 With the rapid development of science and technology, the microwave technology of wireless communication systems has progressed very quickly and widely. Life is closely connected, and products are also developing in the direction of high efficiency, low cost, easy production, thinness and shortness, so that broadband, multi-band, downsizing and adjustable structure have become necessary items for designing couplers. Furthermore, the branch coupler such as reference [1-4] plays an important role in microwave circuits, and is used in many aspects, such as power amplifiers such as reference [5], antenna arrays such as reference [6-7] ], Output port power varies, such as reference [8-9], power allocation as reference [10].
按,傳統枝幹耦合器為左右及上下對稱,並且含有輸入埠、輸出埠、耦合埠、隔離埠,其基本構造為傳輸線電氣長度為四分之一波長(θ=90°),其輸出埠|S 21|與耦合埠|S 31|輸出功率比由傳輸線阻抗值決定,兩輸出訊號相位差為90度,且輸入埠|S 11|與隔離埠|S 41|達-15dB以下。為因應不同環境的使用需求,使得現今耦合器之電路設計之輸入點及輸出點比率必須能有更多靈活變化,本文提出一可調輸出功率之混合式串接高頻信號分佈電 路設計,因此,如何開發出一套可調輸出功率之混合式串接高頻信號分佈電路的枝幹耦合器技術,實已成為相關產學業界所急欲解決與挑戰的技術課題。 According to the traditional branch coupler, which is symmetrical left and right and up and down, and contains input ports, output ports, coupling ports, and isolation ports, its basic structure is that the electrical length of the transmission line is a quarter wavelength (θ = 90 °), and its output port S 21 | and coupling port | S 31 | The output power ratio is determined by the impedance of the transmission line. The phase difference between the two output signals is 90 degrees, and the input port | S 11 | and the isolated port | S 41 | are below -15dB. In order to meet the requirements of different environments, the ratio of input points and output points of today's coupler circuit designs must be able to be more flexible. This article proposes a hybrid series high-frequency signal distribution circuit design with adjustable output power. How to develop a set of branch coupler technology that can adjust the output power of a hybrid series-connected high-frequency signal distribution circuit has become a technical issue eager to be solved and challenged by the relevant industry-academia industry.
依據目前所知,尚未有一種可調輸出功率之混合式串接高頻信號分佈電路的專利或是論文被提出,而且基於電子產業的迫切需求下,本發明創作人等乃經不斷的努力研發之下,終於研發出一套有別於上述文獻之技術概念的本發明。 According to the current knowledge, no patent or paper has been proposed for a hybrid series high-frequency signal distribution circuit with adjustable output power, and based on the urgent needs of the electronics industry, the creators of the present invention have made continuous efforts to develop As a result, a set of technical concepts different from the above-mentioned documents has finally been developed.
本發明主要目的,在於提供一種混合式串接高頻信號分佈電路,主要是運用不同功率分配比率枝幹耦合器以混合方式形成串接高頻信號之分佈電路,用於提供高頻信號之任意功率分配並具有向下級輸出功率之功能,進而得以一種電路實現多個且多種輸出比率之耦合器,在系統的建置上相當便利,並適用於多種不同中心頻率,電路具備高度的系統支援性,並能減少整個系統建置的成本支出。達成上述目的採用之技術手段,係於基板設置傳輸線組。第一傳輸線包含第一矩形環繞段及第一橫伸段。第二傳輸線包含第二矩形環繞段及的第二橫伸段。第三傳輸線包含第三矩形環繞段及第三橫伸段。第一橫伸段二側延伸有第一延伸段及第二延伸段。第二橫伸段二側延伸有第三延伸段及第四延伸段。第三橫伸段二側延伸有第五延伸段及第六延伸段。第四傳輸線二側延伸有第七延伸段及第八延伸段。第三延伸段外側間隔設有第一導電塊。第五延伸段外側間隔設有第二導電塊。第四傳輸線一側間隔設有第三導電塊。第三延伸段與第一導電塊之間、第五延伸段與第二導電塊之間以及第四傳輸線一側與第三導電 塊之間各自連接一負載元件。 The main object of the present invention is to provide a hybrid series-connected high-frequency signal distribution circuit, which mainly uses branch couplers with different power distribution ratios to form a series-connected high-frequency signal distribution circuit in a hybrid manner, and is used to provide arbitrary high-frequency signals The power is distributed and has the function of outputting power to the next stage, so that a circuit can realize multiple and multiple output ratio couplers, which is very convenient in the construction of the system, and is suitable for a variety of different center frequencies. The circuit has a high degree of system support , And can reduce the cost of the entire system construction. The technical means adopted to achieve the above-mentioned purpose is to set a transmission line group on the substrate. The first transmission line includes a first rectangular surrounding segment and a first transversely extending segment. The second transmission line includes a second rectangular surrounding section and a second transversely extending section. The third transmission line includes a third rectangular surrounding section and a third transverse extending section. A first extension section and a second extension section extend on both sides of the first transverse extension section. A third extension section and a fourth extension section extend on both sides of the second transverse extension section. A fifth extension section and a sixth extension section extend on both sides of the third transverse extension section. The fourth transmission line extends on both sides of a seventh extension and an eighth extension. First conductive blocks are spaced from the third extension. Second conductive blocks are spaced apart from the fifth extension. Third conductive blocks are spaced from one side of the fourth transmission line. Between the third extension and the first conductive block, between the fifth extension and the second conductive block, and on the fourth transmission line side with the third conductive Each block is connected with a load element.
10‧‧‧基板 10‧‧‧ substrate
20‧‧‧傳輸線組 20‧‧‧ Transmission line group
21‧‧‧傳輸線 21‧‧‧ transmission line
210‧‧‧第一矩形環繞段 210‧‧‧The first rectangular surrounding segment
211‧‧‧第一橫伸段 211‧‧‧The first horizontal stretch
211a‧‧‧第一延伸段 211a‧‧‧first extension
211b‧‧‧第二延伸段 211b‧‧‧second extension
211c‧‧‧第一直伸段 211c‧‧‧The first straight stretch
211d‧‧‧第一三角形段 211d‧‧‧first triangle segment
22‧‧‧第二傳輸線 22‧‧‧Second transmission line
220‧‧‧第二矩形環繞段 220‧‧‧Second rectangular surrounding segment
221‧‧‧第二橫伸段 221‧‧‧Second transverse extension
221a‧‧‧第三延伸段 221a‧‧‧third extension
221b‧‧‧第四延伸段 221b‧‧‧Fourth Extension
221c‧‧‧第二直伸段 221c‧‧‧Second straight extension
221d‧‧‧第二三角形段 221d‧‧‧Second Triangular Segment
23‧‧‧第三傳輸線 23‧‧‧Third transmission line
230‧‧‧第三矩形環繞段 230‧‧‧ the third rectangular surrounding segment
231‧‧‧第三橫伸段 231‧‧‧Third horizontal extension
231a‧‧‧第五延伸段 231a‧‧‧Fifth extension
231b‧‧‧第六延伸段 231b‧ Sixth Extension
24‧‧‧第四傳輸線 24‧‧‧ Fourth Transmission Line
240‧‧‧第七延伸段 240‧‧‧ seventh extension
241‧‧‧第八延伸段 241‧‧‧eighth extension
25‧‧‧第一導電塊 25‧‧‧The first conductive block
26‧‧‧第二導電塊 26‧‧‧Second conductive block
27‧‧‧第三導電塊 27‧‧‧ the third conductive block
R‧‧‧負載元件 R‧‧‧ load element
圖1係本發明混合式高頻信號分佈電路結構示意圖。 FIG. 1 is a schematic structural diagram of a hybrid high-frequency signal distribution circuit according to the present invention.
圖2係本發明三階混合式高頻信號分佈結構示意圖。 FIG. 2 is a schematic diagram of a distribution structure of a third-order hybrid high-frequency signal according to the present invention.
圖3係傳統枝幹耦合器的架構示意圖。 Figure 3 is a schematic diagram of the architecture of a traditional branch coupler.
圖4係枝幹耦合器阻抗比的對照示意圖。 Fig. 4 is a comparison diagram of the impedance ratio of the branch coupler.
圖5(a)係本發明三階混合式高頻信號分佈電路的示意圖。 FIG. 5 (a) is a schematic diagram of a third-order hybrid high-frequency signal distribution circuit according to the present invention.
圖5(b)係本發明第一階枝幹耦合器的電路分析示意圖。 FIG. 5 (b) is a schematic circuit analysis diagram of the first-stage branch coupler of the present invention.
圖5(c)係本發明第二階枝幹耦合器的電路分析示意圖。 FIG. 5 (c) is a schematic circuit analysis diagram of the second-stage branch coupler of the present invention.
圖5(d)係係本發明第三階枝幹耦合器的電路分析示意圖。 FIG. 5 (d) is a schematic diagram of a circuit analysis of a third-stage branch coupler according to the present invention.
圖6(a)係本發明三階混合式高頻信號分佈成型電路示意圖。 FIG. 6 (a) is a schematic diagram of a third-order hybrid high-frequency signal distribution forming circuit according to the present invention.
圖6(b)係本發明第一階枝幹耦合器的電路成型示意圖。 FIG. 6 (b) is a schematic diagram of circuit formation of the first-stage branch coupler of the present invention.
圖6(c)係本發明第二階枝幹耦合器的電路成型示意圖。 FIG. 6 (c) is a schematic diagram of circuit formation of the second-stage branch coupler of the present invention.
圖6(d)係本發明第三階枝幹耦合器的電路成型示意圖。 FIG. 6 (d) is a schematic diagram of circuit formation of the third-stage branch coupler of the present invention.
圖7係本發明三階混合式高頻信號分佈實體電路示意圖。 FIG. 7 is a schematic diagram of a third-order hybrid high-frequency signal distribution entity circuit according to the present invention.
圖8(a)係本發明由埠1進入後輸出到各埠的電路模擬及量測數據示意圖。 FIG. 8 (a) is a schematic diagram of circuit simulation and measurement data outputted to each port after entering from port 1 of the present invention.
圖8(b)係本發明由埠2進入後輸出到各埠的電路模擬及量測數據示意圖。 FIG. 8 (b) is a schematic diagram of circuit simulation and measurement data of the present invention and output to each port after entering from port 2.
圖8(c)係本發明由埠3進入後輸出到各埠的電路模擬及量測數據示意圖。 FIG. 8 (c) is a schematic diagram of circuit simulation and measurement data outputted to each port after entering from port 3 of the present invention.
圖8(d)係本發明由埠4進入後輸出到各埠的電路模擬及量測數據示意圖。 FIG. 8 (d) is a schematic diagram of circuit simulation and measurement data outputted to each port after entering from port 4 of the present invention.
圖8(e)係本發明由埠5進入後輸出到各埠的電路模擬及量測數據示意圖。 FIG. 8 (e) is a schematic diagram of circuit simulation and measurement data outputted to each port after entering from port 5 of the present invention.
為讓 貴審查委員能進一步瞭解本發明整體的技術特徵與達成本發明目的之技術手段,玆以具體實施例並配合圖式加以詳細說明: In order to allow your reviewers to further understand the overall technical features of the present invention and the technical means for achieving the purpose of the present invention, specific embodiments and drawings are described in detail below:
簡言之,本發明是一種運用不同功率分配比率枝幹耦合器, 以混合方式形成串接高頻信號的分佈電路,用於提供高頻信號之任意功率分配並具有向下級輸出功率之功能。電路分析是以能量守恆為基礎依照設計之需求可提供任意輸出埠數量及於輸出埠之任意功率比輸出。對於功率分配單元提出兩種型式之電路構造方便系統設計及運用。本發明文中是以三階混合式高頻信號分佈電路進行設計、模擬與實驗,實體電路以厚度1.6mm,相對介電質係數4.3的FR-4電路板進行製作。模擬與實驗結果於測試實驗範圍內非常一致,驗證本發明電路設計的正確性。 In short, the present invention is a branch coupler using different power distribution ratios, A distribution circuit for connecting high-frequency signals in a hybrid manner is used to provide arbitrary power distribution of high-frequency signals and has the function of outputting power to the next stage. Circuit analysis is based on energy conservation. According to the requirements of the design, it can provide any number of output ports and any power ratio output at the output ports. Two types of circuit structures are proposed for the power distribution unit to facilitate system design and use. In the present invention, a third-order hybrid high-frequency signal distribution circuit is used for design, simulation, and experiments. The solid circuit is manufactured with a FR-4 circuit board having a thickness of 1.6 mm and a relative dielectric constant of 4.3. The simulation and experimental results are very consistent within the scope of the test experiment, verifying the correctness of the circuit design of the present invention.
請配合參看圖6a~6d及圖7所示,為達成本發明主要目的之實施例,係於基板10覆設傳輸線組20,該傳輸線組20係包含一第一傳輸線21、一第二傳輸線22、一第三傳輸線23及一橫向延伸且連接在第一傳輸線21、第二傳輸線22及第三傳輸線23底緣的第四傳輸線24。第一傳輸線21包含一呈矩形環繞連接的第一矩形環繞段210及一連接在第一矩形環繞段210頂緣的第一橫伸段211。第二傳輸線22包含一呈矩形環繞連接的第二矩形環繞段220及一連接在第二矩形環繞段220頂緣的第二橫伸段221。第三傳輸線23包含一呈矩形環繞連接的第三矩形環繞段230及一連接在第三矩形環繞段230頂緣的第三橫伸段231。第一橫伸段211二側分別延伸有一第一延伸段211a及一第二延伸段211b。第二橫伸段221二側分別延伸有一第三延伸段221a及一第四延伸段221b。第三橫伸段231二側分別延伸有一第五延伸段231a及一第六延伸段231b。第四傳輸線24二側分別延伸有一第七延伸段240及一第八延伸段241。第三延伸段221a外側間隔設有一第一導電塊25,第五延伸段231a外側間隔設有一第二導電塊26。第四傳輸線24一側間隔設有一第三導電塊27。第三延伸段221a與第一導電塊 之間、第五延伸段231a與第二導電塊之間以及第四傳輸線24一側與第三導電塊之間各自連接一個負載元件R。 Please refer to FIGS. 6 a to 6 d and FIG. 7. In order to achieve the main purpose of the present invention, a transmission line group 20 is covered on the substrate 10. The transmission line group 20 includes a first transmission line 21 and a second transmission line 22. A third transmission line 23 and a fourth transmission line 24 extending laterally and connected to the bottom edges of the first transmission line 21, the second transmission line 22 and the third transmission line 23. The first transmission line 21 includes a first rectangular surrounding segment 210 connected in a rectangular surrounding and a first transversely extending segment 211 connected to a top edge of the first rectangular surrounding segment 210. The second transmission line 22 includes a second rectangular surrounding segment 220 connected in a rectangular surround and a second transversely extending segment 221 connected to the top edge of the second rectangular surrounding segment 220. The third transmission line 23 includes a third rectangular surrounding segment 230 connected in a rectangular surround and a third horizontally extending segment 231 connected to the top edge of the third rectangular surrounding segment 230. A first extension section 211a and a second extension section 211b are respectively extended on two sides of the first transverse extension section 211. A third extension section 221a and a fourth extension section 221b extend from two sides of the second transverse extension section 221, respectively. A fifth extension section 231a and a sixth extension section 231b are respectively extended on two sides of the third horizontal extension section 231. A seventh extension 240 and an eighth extension 241 are respectively extended on the two sides of the fourth transmission line 24. A first conductive block 25 is spaced from the outside of the third extension section 221a, and a second conductive block 26 is spaced from the outside of the fifth extension section 231a. A third conductive block 27 is disposed on one side of the fourth transmission line 24. The third extension section 221a and the first conductive block A load element R is connected between the fifth extension 231a and the second conductive block, and between the fourth transmission line 24 and the third conductive block.
具體來說,如圖5、8所示之實施例中,上述第一傳輸線21、第二傳輸線22該第三傳輸線23係為透過連接四傳輸線24所串接的三階枝幹耦合器。 Specifically, in the embodiments shown in FIGS. 5 and 8, the first transmission line 21, the second transmission line 22, and the third transmission line 23 are three-stage branch couplers connected in series by connecting four transmission lines 24.
具體的,如圖6a~6d及圖7所示,第二延伸段211b向上延伸有一第一直伸段211c,第一直伸段211c的長度W 3=5mm,線寬L 2=3.1mm。第四延伸段221b向上延伸有一第二直伸段221c,該第二直伸段221c的長度W 4=8.67mm,線寬L 3=3.1mm。 Specifically, as shown in FIGS. 6 a to 6 d and FIG. 7, the second extension section 211 b extends upwards with a first extension section 211 c , the length of the first extension section 211 c is W 3 = 5 mm, and the line width L 2 = 3.1 mm. The fourth extension section 221b extends upward with a second straight extension section 221c. The length W 4 of the second straight extension section 221 c is 8.67 mm, and the line width L 3 is 3.1 mm.
如圖6a~6d及圖7所示,第二延伸段211b與該第一直伸段211c銜接處具有一形成斜切邊第一三角形段211d。第四延伸段221b與第二直伸段221c銜接處具有一形成斜切邊第二三角形段221d。 As shown in FIGS. 6 a to 6 d and FIG. 7, a joint of the second extension segment 211 b and the first straight extension segment 211 c has a first triangular segment 211 d forming a chamfered edge. A joint of the fourth extension section 221b and the second straight extension section 221c has a second triangular section 221d forming a chamfered edge.
如圖6a~6d及圖7所示,第一橫伸段211包含第一延伸段211a及第二延伸段211b的長度L 1=65.89mm。第一延伸段211a的線寬W 1=3.1mm,長度L 3=9mm。第二延伸段211b的長度L 5=5mm,線寬W 1=3.1mm。第一傳輸線21橫向內邊長度L 4=40.08mm,縱向內邊長度W 5=40.57mm。第一傳輸線21加上該第一橫伸段211的線寬W 2=7.52mm。第一傳輸線21縱向外邊長度W 4=49.41mm。第四傳輸線24包含第七延伸段240及第八延伸段241的長度為181.23mm,線寬W 7=3.1mm。第一導電塊L7=2mm,寬度W 6=3.1mm。 As shown in FIGS. 6 a to 6 d and FIG. 7, the first transversely extending section 211 includes a length L 1 of the first extending section 211 a and a second extending section 211 b of 65.89 mm. The first extension 211a has a line width W 1 = 3.1 mm and a length L 3 = 9 mm. The length L 5 of the second extension segment 211 b is 5 mm, and the line width W 1 is 3.1 mm. The length of the inner side of the first transmission line 21 in the lateral direction is L 4 = 40.08 mm, and the length of the inner side in the longitudinal direction is W 5 = 40.57 mm. The line width W 2 of the first transmission line 21 plus the first transversely extending section 211 is 7.52 mm. The length of the longitudinal outer side of the first transmission line 21 W 4 = 49.41 mm. The fourth transmission line 24 includes a seventh extension section 240 and an eighth extension section 241 with a length of 181.23 mm and a line width W 7 = 3.1 mm. The first conductive block L 7 = 2 mm, and the width W 6 = 3.1 mm.
如圖6a~6d及圖7所示,第二橫伸段221包含第三延伸段221a及第四延伸段221b的長度L 2=53.84mm。第三延伸段221a的長度L 4=3mm。第四延伸段221b的長度L 6=5mm,線寬W 3=3.1mm。第二傳輸線 22橫向內邊長度L 5=40.99mm,縱向內邊長度W 6=42.34mm。第二傳輸線22加上該第二橫伸段221的線寬W 2=4.8mm。第二傳輸線22縱向外邊長度W 5=45.74mm。第二導電塊L 1=2mm,寬度W 1=3.1mm。 As shown in FIGS. 6 a to 6 d and FIG. 7, the second transversely extending section 221 includes a third extending section 221 a and a fourth extending section 221 b having a length L 2 = 53.84 mm. The length L 4 of the third extension 221 a is 3 mm. The fourth extension 221b has a length L 6 = 5 mm and a line width W 3 = 3.1 mm. The length of the inner side of the second transmission line 22 in the lateral direction L 5 = 40.99 mm, and the length of the inner side in the longitudinal direction W 6 = 42.34 mm. The line width W 2 of the second transmission line 22 plus the second transversely extending section 221 is 4.8 mm. The longitudinal outer side length W 5 of the second transmission line 22 is 45.74 mm. The second conductive block L 1 = 2 mm, and the width W 1 = 3.1 mm.
如圖6a~6d及圖7所示,第三橫伸段231包含第五延伸段231a及第六延伸段231b的長度L 2=51.5mm。第五延伸段231a的長度L 3=3mm。第六延伸段231b的長度L 5=5mm。第三傳輸線23橫向內邊長度L 4=41.41mm,縱向內邊長度W 4=43.66mm。第三傳輸線23加上第三橫伸段231的線寬W 2=3.91mm。第二傳輸線22縱向外邊長度W 3=45.27mm。第三導電塊L 1=2mm,寬度W 1=3.1mm。 As shown in FIGS. 6 a to 6 d and FIG. 7, the third transversely extending section 231 includes a fifth extending section 231 a and a sixth extending section 231 b having a length L 2 = 51.5 mm. The length L 3 of the fifth extension section 231 a is 3 mm. The length L 5 of the sixth extension 231 b is 5 mm. The length of the inner side of the third transmission line 23 in the lateral direction is L 4 = 41.41 mm, and the length of the inner side in the longitudinal direction is W 4 = 43.66 mm. The line width W 2 of the third transmission line 23 plus the third transversely extending section 231 is 3.91 mm. The longitudinal length W 3 of the second transmission line 22 is 45.27 mm. The third conductive block L 1 = 2 mm, and the width W 1 = 3.1 mm.
第一傳輸線21、第二傳輸線22及第三傳輸線23的功率輸出比為1:1:1時,第一傳輸線21的阻抗比為1:2.3,X軸阻抗Z1=27.38Ω,Y軸阻抗Z2=32.73Ω,第二傳輸線22的阻抗比為1.3:1,X軸阻抗為Z1=37.79Ω,Y軸阻抗Z2=57.73Ω,第三傳輸線23的阻抗比為1:0.3,X軸阻抗為Z1=43.3Ω,Y軸阻抗Z2=86.6Ω,如下之表1所示。 When the power output ratios of the first transmission line 21, the second transmission line 22, and the third transmission line 23 are 1: 1, the impedance ratio of the first transmission line 21 is 1: 2.3, the X-axis impedance Z 1 = 27.38Ω, and the Y-axis impedance Z 2 = 32.73Ω, the impedance ratio of the second transmission line 22 is 1.3: 1, the X-axis impedance is Z 1 = 37.79Ω, the Y-axis impedance Z 2 = 57.73Ω, and the impedance ratio of the third transmission line 23 is 1: 0.3, X The axial impedance is Z 1 = 43.3Ω, and the Y-axis impedance Z 2 = 86.6Ω, as shown in Table 1 below.
本發明電路是以串接的方式將多個枝幹耦合器串接組成,電路構造如圖1所示,其中,Pin代表輸入功率,#1、#2、#3分別代表不同功率輸出之第1階枝幹耦合器(即第一傳輸線)、第2階枝幹耦合器(即第二傳輸線)及第3階枝幹耦合器(即第三傳輸線)枝幹耦合器,a1、aj、aN為輸出點,Pout代表輸出至下級之功率,Matched load為匹配之負載用於吸收反射信號,其中Type1為P2(輸出埠)輸出信號、P3(隔離埠)輸出功率至下級,而Type2為P2(輸出埠)輸出功率至下級、P3(隔離埠)輸出信號。本發明電路優點為以一電路實現多個且多種輸出比率之耦合器,在系統的建置上相當便利,並適用於 多種不同中心頻率,電路具備高度的系統支援性,並能減少整個系統建置的成本支出。 The circuit of the present invention is composed of multiple branch couplers connected in series. The circuit structure is shown in FIG. 1, where P in represents input power, # 1, # 2, and # 3 represent different power outputs. The first-order branch coupler (that is, the first transmission line), the second-order branch coupler (that is, the second transmission line), and the third-order branch coupler (that is, the third transmission line) branch coupler, a1, aj, aN is the output point, P out is the power output to the lower stage, Matched load is the matched load for absorbing the reflected signal, where Type1 is the output signal of P2 (output port), P3 (isolated port) output power to the lower stage, and Type2 P2 (output port) outputs power to the lower stage, and P3 (isolated port) outputs signals. The advantage of the circuit of the invention is that a coupler with multiple output ratios can be realized by one circuit, which is quite convenient for system construction, and is suitable for a variety of different center frequencies. The circuit has high system support and can reduce the overall system construction. Cost of ownership.
在電路分析與設計的實施例中,本發明電路分析以三階混合式高頻信號分佈電路為例進行說明,其中#1採用Type1而#2採用Type2,如圖2,Pin代表輸入功率,#1、#2、#3分別代表不同功率輸出之之第1階枝幹耦合器(即第一傳輸線)、第2階枝幹耦合器(即第二傳輸線)及第3階枝幹耦合器(即第三傳輸線)枝幹耦合器,a1、a2、a3為輸出點,Pout代表輸出至下級之功率,Matched load則為上述負載元件;亦即匹配之負載,用於吸收反射信號。假設輸入功率正規化為1,輸出功率為p,而三階混合式功率分配電路有三個輸出點分別為a1、a2、a3,由能量守恆原則可知a1+a2+a3=1-p。若三個輸出點之輸出功率不為均勻分布而其總合為k,如式(1)所示,則各級枝幹耦合器之輸出埠P2及P3的輸出功率比可由式(2)、(3)、(4)計算可得到。 In the embodiment of circuit analysis and design, the circuit analysis of the present invention is described by taking a third-order hybrid high-frequency signal distribution circuit as an example, in which # 1 uses Type1 and # 2 uses Type2. As shown in FIG. 2, P in represents the input power. # 1, # 2, and # 3 represent the first-order branch coupler (that is, the first transmission line), the second-order branch coupler (that is, the second transmission line), and the third-order branch coupler with different power outputs. (Ie, the third transmission line) a branch coupler, a1, a2, a3 are output points, P out represents the power output to the lower stage, and Matched load is the above-mentioned load element; that is, a matched load is used to absorb reflected signals. Assume that the input power is normalized to 1, and the output power is p, and the third-order hybrid power distribution circuit has three output points, a1, a2, and a3, respectively. From the principle of energy conservation, we can know that a1 + a2 + a3 = 1-p. If the output power of the three output points is not uniformly distributed and its total is k, as shown in formula (1), the output power ratios of the output ports P2 and P3 of the branch couplers at all levels can be expressed by formula (2), (3), (4) can be calculated.
a1+a2+a3=k (1) a1 + a2 + a3 = k (1)
P設定混合式高頻信號分布電路為三階,輸入至下級之功率為0.1,#1採用Type1而#2採用Type2參考前述公式(1)、(2)、(3)、(4)可得到的參數如表格1,其中a1、a2、a3為三個輸出點的輸出比率,#13、#22、#33為各枝幹耦合器的P2及P3輸出功率比。傳統枝幹耦合器結構如圖3,Port1為輸 入埠,Port2為輸出埠,Port3為耦合埠,Port4為隔離埠、Z1及Z2為傳輸線阻抗,θ 1=θ 2為電氣長度(傳統電氣長度為90度),其中輸出埠與耦合埠的輸出比率是藉由Z1及Z2的傳輸線阻抗決定。圖4為枝幹耦合器的阻抗比,其中X軸為Z1的阻抗、Y軸為Z2的阻抗,例圖中最左點為P2:P3=1:10時Z1=15.07Ω、Z2=15.81Ω,圖中最右點為P2:P3=10:1時Z1=47.67Ω、Z2=158.11Ω,藉由帶入表格1當中的第一行可得到當a1:a2:a3=1:1:1時#1的阻抗比為1:2.3,阻抗為Z1=27.38Ω、Z2=32.73Ω,#2的阻抗比為1.3:1,阻抗為Z1=37.79Ω、Z2=57.73Ω,#3的阻抗比為1:0.3,阻抗為Z1=43.3Ω、Z2=86.6Ω,具體內容如下表1所示。 P sets the hybrid high-frequency signal distribution circuit to the third order, and the power input to the lower stage is 0.1. # 1 uses Type1 and # 2 uses Type2. Refer to the aforementioned formulas (1), (2), (3), and (4). The parameters are shown in Table 1, where a1, a2, and a3 are the output ratios of the three output points, and # 13, # 22, and # 33 are the output power ratios of the branch couplers P2 and P3. The structure of a traditional branch coupler is shown in Figure 3. Port1 is an input port, Port2 is an output port, Port3 is a coupling port, Port4 is an isolated port, Z 1 and Z 2 are transmission line impedances, and θ 1 = θ 2 is the electrical length (traditional electrical The length is 90 degrees). The output ratio of the output port to the coupling port is determined by the transmission line impedance of Z 1 and Z 2 . Figure 4 shows the impedance ratio of the branch coupler, where the X-axis is the impedance of Z 1 and the Y-axis is the impedance of Z 2. The leftmost point in the example is P2: P3 = 1:10 when Z 1 = 15.07Ω, Z 2 = 15.81Ω, the rightmost point in the figure is P2: P3 = 10: 1 Z 1 = 47.67Ω, Z 2 = 158.11Ω, which can be obtained when a1: a2: a3 is brought into the first line in Table 1. When = 1: 1: 1, the impedance ratio of # 1 is 1: 2.3, the impedance is Z 1 = 27.38Ω, Z 2 = 32.73Ω, the impedance ratio of # 2 is 1.3: 1, the impedance is Z 1 = 37.79Ω, Z 2 = 57.73Ω, the impedance ratio of # 3 is 1: 0.3, the impedance is Z 1 = 43.3Ω, Z 2 = 86.6Ω, the specific content is shown in Table 1 below.
使用模擬軟體製作三階混合式高頻信號分佈電路圖如圖5(a),其中帶入#1的參數Z1=27.38Ω、Z2=32.73Ω並設f0=0.915GHz、EL=90Deg可得到#1的枝幹耦合器電路圖,如圖5(b),帶入#2的參數Z1=37.79Ω、Z2=57.73Ω並設f0=0.915GHz、EL=90deg可得到#2的枝幹耦合器電路圖,如圖5(c),帶入#3的參數Z1=43.3Ω、Z2=86.6Ω並設f0=0.915GHz、EL=90deg可得到#3的枝幹耦合器電路圖,如圖5(d),上述各電路使用模擬軟體驗證電路後與預期結果十分符合。 Software to create a high frequency signal using an analog circuit diagram of a third order profile hybrid FIG. 5 (a), wherein the parameters into the # 1 Z 1 = 27.38Ω, Z 2 = 32.73Ω and set f 0 = 0.915GHz, EL = 90Deg may to obtain a circuit diagram of the coupler branches # 1, FIG. 5 (b), into the parameter # 2 Z 1 = 37.79Ω, Z 2 = 57.73Ω and set f 0 = 0.915GHz, EL = 90deg available # 2 coupler branches a circuit diagram, FIG. 5 (c), the parameter Z 3 into the # 1 = 43.3Ω, Z 2 = 86.6Ω and let f 0 = 0.915GHz, EL = 90deg obtained coupler branches # 3 The circuit diagram is shown in Figure 5 (d). The above circuits use simulation software to verify the circuits and they are in good agreement with the expected results.
本發明三階混合式高頻信號分佈電路經由電磁模擬軟體驗 證電路特性,選用板材為FR4(厚度1.6mm),相對介電係數4.3,結構經最佳化調整如圖6(a),其中#1電路如圖6(b),電路尺寸:L 1=65.89mm,W 1=3.1mm,L 2=3.1mm,W 2=7.52mm,L 3=9mm,W 3=5mm,L 4=40.08mm,W 4=49.41mm,L 5=5mm,W 5=40.57mm,L 6=5.9mm,W 6=3.1mm,L7=2mm,W 7=3.1mm,L8=62.39mm。#2電路如圖6(c),電路尺寸:L 1=2mm,W 1=3.1mm,L 2=53.84mm,W 2=4.8mm,L 3=3.1mm,W 3=3.1mm,L 4=3mm,W 4=8.67mm,L 5=40.99mm,W 5=45.74mm,L 6=5mm,W 6=42.34mm,L7=2.42mm,W 7=3.1mm,L8=61.84mm。#3電路如圖6(d),電路尺寸:L 1=2mm,W 1=3.1mm,L 2=51.5mm,W 2=3.91mm,L 3=3mm,W 3=45.27mm,L 4=41.41mm,W 4=43.66mm,L 5=5mm,W 5=3.1mm,L 6=1.04mm,L7=57mm,L8=5mm。經雕刻機加工後成品如圖7。 The third-order hybrid high-frequency signal distribution circuit of the present invention uses electromagnetic simulation software to verify the circuit characteristics. The sheet material is FR4 (thickness: 1.6mm) and the relative dielectric constant is 4.3. 1 circuit as shown in Figure 6 (b), circuit size: L 1 = 65.89mm, W 1 = 3.1mm, L 2 = 3.1mm, W 2 = 7.52mm, L 3 = 9mm, W 3 = 5mm, L 4 = 40.08 mm, W 4 = 49.41mm, L 5 = 5mm, W 5 = 40.57mm, L 6 = 5.9mm, W 6 = 3.1mm, L 7 = 2mm, W 7 = 3.1mm, L 8 = 62.39mm. # 2The circuit is shown in Figure 6 (c). The circuit size is: L 1 = 2mm, W 1 = 3.1mm, L 2 = 53.84mm, W 2 = 4.8mm, L 3 = 3.1mm, W 3 = 3.1mm, L 4 = 3mm, W 4 = 8.67mm, L 5 = 40.99mm, W 5 = 45.74mm, L 6 = 5mm, W 6 = 42.34mm, L 7 = 2.42mm, W 7 = 3.1mm, L 8 = 61.84mm. # 3The circuit is shown in Figure 6 (d). The circuit size is: L 1 = 2mm, W 1 = 3.1mm, L 2 = 51.5mm, W 2 = 3.91mm, L 3 = 3mm, W 3 = 45.27mm, L 4 = 41.41mm, W 4 = 43.66mm, L 5 = 5mm, W 5 = 3.1mm, L 6 = 1.04mm, L 7 = 57mm, L 8 = 5mm. The finished product after engraving machine processing is shown in Figure 7.
由網路分析儀量測實體電路,與模擬結果進行比較得電路模擬結果與實體電路頻率響應如圖8(a),量測頻率由0到2GHz,大小由0至-60dB,於工作頻段(f 0=0.915GHz)輸入點的反射係數|S11|在-15dB以下,輸出端a1、a2、a3之輸出功率比|S21|、|S31|與|S41|約為1:1:1,輸出至下級之功率|S51|約為-11dB。圖8(b)為由埠2進入後輸出到各埠的電路模擬及量測數據,其中|S12|為a1的輸出功率,於工作頻段(f 0=0.915GHz)時|S12|約為-5.2dB,各埠的反射係數如|S22|、穿透係數|S32|、|S42|、|S52|皆遠低於-15dB。圖8(c)為由埠3進入後輸出到各埠的電路模擬及量測數據,其中|S13|為a2的輸出功率,於工作頻段(f 0=0.915GHz)時|S13|約為-5.6dB,各埠的反射係數如|S23|、穿透係數|S33|、|S43|、|S53|皆遠低於-15dB。圖8(d)為由埠4進入後輸出到各埠的電路模擬及量測數據,其中|S14|為a3的輸出功率,於工作頻段(f 0=0.915GHz)時|S12|約為-5.6dB,各埠的反射係數如|S24|、穿透係數|S34|、|S44|、|S54|皆遠低於-15dB。圖 8(e)為由埠5進入後輸出到各埠的電路模擬及量測數據,其中|S15|為輸出至下級之功率,於工作頻段(f 0=0.915GHz)時|S15|約為-11dB,|S25|、穿透係數|S35|、|S45|、|S55|皆遠低於-15dB上述模擬與量測結果與預期相當接近。 A network analyzer measures the physical circuit and compares the simulation results with the simulation results. The frequency response of the circuit is shown in Figure 8 (a). The measurement frequency is from 0 to 2 GHz, and the size is from 0 to -60 dB. f 0 = 0.915GHz) The reflection coefficient | S 11 | at the input point is below -15dB, and the output power ratios of the output terminals a1, a2, and a3 | S 21 |, | S 31 |, and | S 41 | are about 1: 1 : 1, the power | S 51 | output to the lower stage is about -11dB. Figure 8 (b) is the circuit simulation and measurement data output to ports after entering from port 2, where | S 12 | is the output power of a1, at the working frequency band ( f 0 = 0.915GHz) | S 12 | It is -5.2dB, and the reflection coefficients of each port such as | S 22 |, transmission coefficients | S 32 |, | S 42 |, | S 52 | are all far below -15dB. Figure 8 (c) is the circuit simulation and measurement data output to ports after entering from port 3, where | S 13 | is the output power of a2, at the working frequency band ( f 0 = 0.915GHz) | S 13 | It is -5.6dB. The reflection coefficients of each port such as | S 23 |, transmission coefficients | S 33 |, | S 43 |, | S 53 | are all far below -15dB. Figure 8 (d) is the circuit simulation and measurement data output from ports 4 after entering to each port, where | S 14 | is the output power of a3, at the working frequency band ( f 0 = 0.915GHz) | S 12 | It is -5.6dB. The reflection coefficients of each port such as | S 24 |, transmission coefficients | S 34 |, | S 44 |, | S 54 | are all far below -15dB. Figure 8 (e) is the circuit simulation and measurement data output to ports after entering from port 5, where | S 15 | is the power output to the lower stage, at the operating frequency band ( f 0 = 0.915GHz) | S 15 | About -11dB, | S 25 |, transmission coefficients | S 35 |, | S 45 |, | S 55 | are all far lower than -15dB. The above simulation and measurement results are quite close to expectations.
經由上述具體實施例說明,本發明所提出之一種可任意功率分配的混合式串接高頻信號分配電路設計,電路是以傳統枝幹耦合器為架構,透過串接的方式將多個枝幹耦合器連接,可提供任意輸出埠數量、輸出埠之任意功率比輸出,文內以三階混合式高頻信號分佈電路進行實作電路設計,其中輸出功率比1:1:1,輸出至下級功率為0.1,模擬與實測結果相當接近,可知此電路的可行性,且能廣泛應用於不同中心頻率之功率分配系統。 According to the above specific embodiments, the present invention provides a hybrid series high-frequency signal distribution circuit design that can be distributed at any power. The circuit is based on a traditional branch coupler, and multiple branches are connected in series. Coupler connection can provide any number of output ports and output power at any power ratio. The circuit design is implemented by a third-order hybrid high-frequency signal distribution circuit. The output power ratio is 1: 1 and output to the lower level. The power is 0.1, and the simulation and actual measurement results are quite close. The feasibility of this circuit can be known, and it can be widely used in power distribution systems with different center frequencies.
以上所述,僅為本發明之可行實施例,並非用以限定本發明之專利範圍,凡舉依據下列請求項所述之內容、特徵以及其精神而為之其他變化的等效實施,皆應包含於本發明之專利範圍內。本發明所具體界定於請求項之結構特徵,未見於同類物品,且具實用性與進步性,已符合發明專利要件,爰依法具文提出申請,謹請 鈞局依法核予專利,以維護本申請人合法之權益。 The above description is only a feasible embodiment of the present invention, and is not intended to limit the patent scope of the present invention. Any equivalent implementation of other changes based on the content, characteristics and spirit of the following claims should be It is included in the patent scope of the present invention. The structural features specifically defined in the present invention are not found in similar items, and are practical and progressive. They have met the requirements for invention patents. They have filed applications in accordance with the law. I would like to request the Bureau to verify the patents in accordance with the law in order to maintain this document. Applicants' legitimate rights and interests.
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[2] J. Reed and G. J. Wheeler, “A Method of Analysis of Symmetrical Four-Port Networks,” IRE Trans. Microwave Theory and Techniques, vol. 4, no. 4, pp. 246-252, Oct. 1956. [2] J. Reed and GJ Wheeler, "A Method of Analysis of Symmetrical Four-Port Networks," IRE Trans. Microwave Theory and Techniques, vol. 4, no. 4, pp. 246-252, Oct. 1956.
[3] Tseng, C.-H. and Wu and C.-H., “Design of compact branch-line couplers using n-equivalent artificial transmission lines,” Microwaves, Antennas& Propagation, lET,, Vol. 6, pp.969-974, June 2012. [3] Tseng, C.-H. and Wu and C.-H., "Design of compact branch-line couplers using n-equivalent artificial transmission lines," Microwaves, Antennas & Propagation, ET,, Vol. 6, pp. 969-974, June 2012.
[4] S. Kumar, C. Tannous and T. Danshin, “Multisection Broadband Impedance Transform Branch line Hybrid,” IEEE Transactions. Microwave Theory Techniques, vol. 43, no.11, pp. 2517-2523, Nov. 1995. [4] S. Kumar, C. Tannous and T. Danshin, “Multisection Broadband Impedance Transform Branch line Hybrid,” IEEE Transactions. Microwave Theory Techniques, vol. 43, no. 11, pp. 2517-2523, Nov. 1995.
[5] I. D. Robertson,R. Herath,M. Gillickand J. Bharj, “Solid state power amplifier using impedance-transforming branch-line couplers for L-band satellite systems,” Microwave Conference, 1993. 23rd European, pp. 448-450, Sept. 1993. [5] ID Robertson , R. Herath , M. Gillick and J. Bharj , "Solid state power amplifier using impedance-transforming branch-line couplers for L-band satellite systems," Microwave Conference, 1993. 23rd European , pp. 448 -450, Sept. 1993.
[6] S. Cheng, E. Ojefors, P. Hallbjorner and A. Rydberg, “Compact reflective microstrip phase shifter for traveling wave antenna applications,” IEEE Microwave and Wireless Components Letters, vol. 16, no. 7, pp. 431-433, Jul. 2006. [6] S. Cheng, E. Ojefors, P. Hallbjorner and A. Rydberg, “Compact reflective microstrip phase shifter for traveling wave antenna applications,” IEEE Microwave and Wireless Components Letters , vol. 16, no. 7, pp. 431 -433, Jul. 2006.
[7] A. K. M. Baki and Nemai Chandra Karmakar, “Staircase power distribution of array antenna for UHF band RFID reader,” Electrical & Computer Engineering (ICECE), 2012 7th International Conference, pp. 854-857, Dec. 2012. [7] AKM Baki and Nemai Chandra Karmakar, “Staircase power distribution of array antenna for UHF band RFID reader,” Electrical & Computer Engineering (ICECE), 2012 7th International Conference , pp. 854-857, Dec. 2012.
[8] Chun-HanYu andYi-HsinPang, “Dual-BandUnequal-PowerQuadratureBranch-LineCoupler With Coupled Lines,” IEEE Microwave and Wireless Components Letters , Vol. 23,No. 1, pp.10-12, Dec. 2013. [8] Chun-HanYu and Yi-HsinPang , " Dual-BandUnequal-PowerQuadratureBranch-LineCoupler With Coupled Lines ," IEEE Microwave and Wireless Components Letters , Vol. 23, No. 1 , pp.10-12, Dec. 2013.
[9] Hyun-Tai Kim,Kwi-Soo Kim andJong-Sik Lim,Dal Ahn, “A Branch Line Hybrid having Arbitrary Power Division Ratio and Port Impedances,” Microwave Conference, 2006. APMC 2006. Asia-Pacific , pp. 1376-1379.1, Dec. 2006. [9] Hyun-Tai Kim , Kwi-Soo Kim and Jong-Sik Lim , Dal Ahn , "A Branch Line Hybrid having Arbitrary Power Division Ratio and Port Impedances," Microwave Conference, 2006. APMC 2006. Asia-Pacific , pp. 1376-1379.1, Dec. 2006.
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Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
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EP0317717A2 (en) * | 1987-11-26 | 1989-05-31 | ANT Nachrichtentechnik GmbH | Planar branch line coupler |
US6300848B1 (en) * | 1998-09-01 | 2001-10-09 | Matsushita Electric Industrial Co., Ltd. | Power splitter and power combiner using N-branch-line-shaped directional couplers |
US7084715B2 (en) * | 2002-09-27 | 2006-08-01 | Nokia Corporation | Coupling device |
TW201637279A (en) * | 2015-04-10 | 2016-10-16 | Nat Univ Chin Yi Technology | Branch line coupler operable to adjust output power ratio |
TW201714348A (en) * | 2015-10-13 | 2017-04-16 | Nat Chin-Yi Univ Of Tech | Generalized branch coupler capable of regulating output power ratio can be similar to simulated frequency response and can be applied in systems having different frequency bands |
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Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP0317717A2 (en) * | 1987-11-26 | 1989-05-31 | ANT Nachrichtentechnik GmbH | Planar branch line coupler |
US6300848B1 (en) * | 1998-09-01 | 2001-10-09 | Matsushita Electric Industrial Co., Ltd. | Power splitter and power combiner using N-branch-line-shaped directional couplers |
US7084715B2 (en) * | 2002-09-27 | 2006-08-01 | Nokia Corporation | Coupling device |
TW201637279A (en) * | 2015-04-10 | 2016-10-16 | Nat Univ Chin Yi Technology | Branch line coupler operable to adjust output power ratio |
TW201714348A (en) * | 2015-10-13 | 2017-04-16 | Nat Chin-Yi Univ Of Tech | Generalized branch coupler capable of regulating output power ratio can be similar to simulated frequency response and can be applied in systems having different frequency bands |
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