TWI712212B - Second-order high penetration coefficient output power ratio branch coupler - Google Patents
Second-order high penetration coefficient output power ratio branch coupler Download PDFInfo
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Abstract
本發明係為一種二階高穿透係數輸出功率比枝幹耦合器,其係於基板覆設傳輸線組、二第一電感及一第二電感。傳輸線組包含第一傳輸線及第二傳輸線。第一傳輸線二端各自設有一左右對稱的第一延伸段及第二延伸段。第二傳輸線二端各自設有左右對稱的第三延伸段及第四延伸段。第一傳輸線二端之底緣各自設有左右對稱的第一梯形段及第二梯形段。第二傳輸線二端之頂緣各自向上突設有第三梯形段及第四梯形段。第一傳輸線中段底緣與第二傳輸線中段頂緣各自設有呈上下對稱的第五梯形段及第六梯形段。其一第一電感電連接於第一梯形段與該第三梯形段之間;其二第一電感電連接於第二梯形段與第四梯形段之間。第二電感電連接於第五梯形段與第六梯形段之間,俾能利用電感來替代高阻抗值的旁枝幹傳輸線段,以減少電路使用集總元件的數目,除了使得整體電路設計非常容易之外,並可大幅縮小電路尺寸,因而具有輸出頻寬較寬與頻率響應平坦等特點。 The present invention is a second-order high-penetration coefficient output power ratio branch-to-stem coupler, which is arranged on a substrate with a transmission line group, two first inductors and a second inductor. The transmission line group includes a first transmission line and a second transmission line. Two ends of the first transmission line are respectively provided with a first extension section and a second extension section that are symmetrical. Two ends of the second transmission line are respectively provided with a third extension section and a fourth extension section that are symmetrical. The bottom edges of the two ends of the first transmission line are respectively provided with a first trapezoidal section and a second trapezoidal section symmetrical. The top edges of the two ends of the second transmission line respectively protrude upwards with a third trapezoidal section and a fourth trapezoidal section. The bottom edge of the middle section of the first transmission line and the top edge of the middle section of the second transmission line are respectively provided with a fifth trapezoidal section and a sixth trapezoidal section which are symmetrical up and down. One of the first inductors is electrically connected between the first trapezoidal section and the third trapezoidal section; the second of the first inductors is electrically connected between the second trapezoidal section and the fourth trapezoidal section. The second inductor is electrically connected between the fifth ladder section and the sixth ladder section, so that the inductance can be used to replace the high-impedance branch trunk transmission line section to reduce the number of lumped components used in the circuit. In addition to making the overall circuit design very Besides being easy, the circuit size can be greatly reduced, so it has the characteristics of wide output bandwidth and flat frequency response.
Description
本發明係有關一種二階高穿透係數輸出功率比枝幹耦合器,尤指一種可以讓使用者依使用需求而透過調整主枝幹角度及電感值即可完成不同高穿透係數比的枝幹耦合器技術。 The present invention relates to a second-order high penetration coefficient output power ratio branch coupler, especially a branch that allows users to complete different high penetration coefficient ratios by adjusting the angle of the main branch and the inductance value according to the use requirements Coupler technology.
按,傳統枝幹耦合器構造具有為左右及上下對稱性質的四埠電路,依使用方式各埠分為輸入埠、輸出埠、耦合埠、隔離埠。傳統枝幹耦合器基本構造為四條傳輸線,其電氣長度皆為四分之一波長(θ=90°),其中輸出埠|S 21|與耦合埠|S 31|輸出功率由傳輸線特性阻抗值決定,兩輸出訊號相位差為90度,且輸入埠|S 11|與隔離埠|S 41|達-15dB以下。為因應不同環境的使用需求,調整傳輸線的特性阻抗值使輸出埠及耦合埠輸出功率比例能有更多變化。 According to, the traditional branch coupler structure has a four-port circuit with left-right and top-bottom symmetrical properties, and each port is divided into an input port, an output port, a coupling port, and an isolation port according to the usage mode. The basic structure of the traditional branch coupler is four transmission lines, the electrical length of which is a quarter wavelength ( θ =90°), where the output port | S 21 | and the coupling port | S 31 | output power are determined by the characteristic impedance of the transmission line , The phase difference between the two output signals is 90 degrees, and the input port | S 11 | and the isolated port | S 41 | reach below -15dB. In order to meet the requirements of different environments, the characteristic impedance of the transmission line is adjusted so that the output power ratio of the output port and the coupling port can have more changes.
再者,隨著行動通訊時代的來臨,物聯網、雲端技術、大數據、行動裝置和社群媒體,是構建未來設會不可或缺的元素。其中物聯網是驅動所有需求最關鍵的力量,因為它與人們的生活關聯性最強,需求也是最高,對於人們在日常生活中已成為不可或缺的重要區塊。行動通訊系統頻段分布廣泛,所需要運用的各項主動、被動零組件也需要依不同頻段進行設計。由於傳統枝幹耦合器傳輸線電氣長度皆為四分之一波長,在縮小化如參考文獻[3-7]設計電路技術中,一般會利用到傳輸線轉換PI型或者 是T型等效電路如參考文獻[8],但是同時會產生並聯電容值。雖然二階枝幹耦合器具有輸出寬頻與平坦性如參考文獻[2]的優點;惟,在高穿透係數輸出功率比設計時則會有製作上的困難點,因此,如何開發出一套可以針對此項困難點進行創新電路設計的枝幹耦合器技術,實已成為相關產學業界所亟欲解決與挑戰的技術課題。 Furthermore, with the advent of the era of mobile communications, the Internet of Things, cloud technology, big data, mobile devices and social media are indispensable elements for the construction of future conferences. Among them, the Internet of Things is the most critical force driving all needs, because it has the strongest relevance to people's lives and the highest demand, and it has become an indispensable and important area in people's daily life. The frequency bands of mobile communication systems are widely distributed, and various active and passive components that need to be used also need to be designed according to different frequency bands. Since the electrical length of the traditional branch coupler transmission line is a quarter wavelength, in the design circuit technology of the reference [3-7], the transmission line is generally used to convert the PI type or It is a T-type equivalent circuit such as reference [8], but at the same time it will produce a parallel capacitance value. Although the second-order branch coupler has the advantages of wideband output and flatness as in reference [2]; however, there are difficulties in manufacturing when designing a high transmission coefficient output power ratio. Therefore, how to develop a set of In view of this difficult point, the branch coupler technology for innovative circuit design has actually become a technical topic that the relevant industry and academia industries urgently want to solve and challenge.
依據目前所知,尚未有一種可依使用需求調整主枝幹角度與電感值而實現不同高穿透係數比的枝幹耦合器的專利或是論文被提出,而且基於電子產業的迫切需求下,本發明人等乃經不斷的努力研發之下,終於研發出一套有別於上述技術文獻之技術概念的本發明。 According to what is currently known, there is no patent or paper on a branch coupler that can adjust the angle of the main branch and the inductance value according to the needs of use to achieve different high penetration coefficient ratios. Moreover, based on the urgent needs of the electronics industry, After continuous research and development efforts, the inventors have finally developed a set of the present invention which is different from the technical concept of the above-mentioned technical literature.
本發明主要目的,在於提供一種二階高穿透係數輸出功率比枝幹耦合器,主要是利用電感來替代高阻抗值的旁枝幹傳輸線段,以減少電路使用集總元件的數目,除了使得整體電路設計非常容易之外,並可大幅縮小電路整體面積尺寸,因而具有輸出頻寬較寬與頻率響應平坦等特點。達成上述目的採用之技術手段,係於基板覆設傳輸線組、二第一電感及一第二電感。傳輸線組包含第一傳輸線及第二傳輸線。第一傳輸線二端各自設有一左右對稱的第一延伸段及第二延伸段。第二傳輸線二端各自設有左右對稱的第三延伸段及第四延伸段。第一傳輸線二端之底緣各自設有左右對稱的第一梯形段及第二梯形段。第二傳輸線二端之頂緣各自向上突設有第三梯形段及第四梯形段。第一傳輸線中段底緣與第二傳輸線中段頂緣各自設有呈上下對稱的第五梯形段及第六梯形段。其一第一電感電連接於第一梯形段與該第三梯形段之間;其二第一電感電連接於第二梯形段與第四 梯形段之間。第二電感電連接於第五梯形段與第六梯形段之間。 The main purpose of the present invention is to provide a second-order high-penetration coefficient output power ratio branch coupler, which mainly uses inductance to replace high-impedance branch trunk transmission line segments to reduce the number of lumped components used in the circuit, in addition to making the overall The circuit design is very easy, and the overall area size of the circuit can be greatly reduced, so it has the characteristics of wider output bandwidth and flat frequency response. The technical means used to achieve the above objectives is to cover the transmission line group, two first inductors and a second inductor on the substrate. The transmission line group includes a first transmission line and a second transmission line. Two ends of the first transmission line are respectively provided with a first extension section and a second extension section that are symmetrical. Two ends of the second transmission line are respectively provided with a third extension section and a fourth extension section that are symmetrical. The bottom edges of the two ends of the first transmission line are respectively provided with a first trapezoidal section and a second trapezoidal section symmetrical. The top edges of the two ends of the second transmission line respectively protrude upwards with a third trapezoidal section and a fourth trapezoidal section. The bottom edge of the middle section of the first transmission line and the top edge of the middle section of the second transmission line are respectively provided with a fifth trapezoidal section and a sixth trapezoidal section which are symmetrical up and down. One of the first inductors is electrically connected between the first trapezoidal section and the third trapezoidal section; the second of the first inductors is electrically connected between the second trapezoidal section and the fourth trapezoidal section. Between trapezoidal segments. The second inductor is electrically connected between the fifth trapezoidal section and the sixth trapezoidal section.
10‧‧‧基板 10‧‧‧Substrate
20‧‧‧傳輸線組 20‧‧‧Transmission line group
21‧‧‧第一傳輸線 21‧‧‧The first transmission line
210‧‧‧第一延伸段 210‧‧‧First extension
210a,211a,220a,221a1‧‧‧平行四邊形段 210a,211a,220a,221a1‧‧‧Parallelogram segment
210b,211b,220b,221b‧‧‧矩形段 210b,211b,220b,221b‧‧‧rectangular segment
211‧‧‧第二延伸段 211‧‧‧Second extension
212‧‧‧第一梯形段 212‧‧‧First ladder section
213‧‧‧第二梯形段 213‧‧‧Second ladder section
214‧‧‧第五梯形段 214‧‧‧Fifth trapezoid section
22‧‧‧第二傳輸線 22‧‧‧Second transmission line
220‧‧‧第三延伸段 220‧‧‧third extension
221‧‧‧第四延伸段 221‧‧‧ Fourth extension
222‧‧‧第三梯形段 222‧‧‧Third trapezoidal section
223‧‧‧第四梯形段 223‧‧‧Fourth trapezoidal section
224‧‧‧第六梯形段 224‧‧‧The sixth trapezoidal section
30‧‧‧輸入埠 30‧‧‧Input port
31‧‧‧輸出埠 31‧‧‧Output port
32‧‧‧耦合埠 32‧‧‧Coupling port
33‧‧‧隔離埠 33‧‧‧Isolated Port
L1‧‧‧第一電感 L1‧‧‧First inductor
L2‧‧‧第二電感 L2‧‧‧Second inductor
圖1係本發明二階枝幹耦合器的電路架構示意圖。 Fig. 1 is a schematic diagram of the circuit structure of the second-stage branch coupler of the present invention.
圖2係傳統二階枝幹耦合器的電路架構示意圖。 Fig. 2 is a schematic diagram of the circuit structure of a traditional second-order branch coupler.
圖3係本發明二階枝幹耦合器進行PI型等效電路示意圖。 Figure 3 is a schematic diagram of the PI type equivalent circuit of the second-order branch coupler of the present invention.
圖4係本發明電路一的電路示意圖。 Fig. 4 is a circuit diagram of circuit one of the present invention.
圖5係本發明電路一的實體電路示意圖。
Fig. 5 is a schematic diagram of the physical circuit of
圖6係本發明電路一的電路頻率響應示意圖。 Figure 6 is a schematic diagram of the circuit frequency response of circuit one of the present invention.
圖7係本發明電路二的電路示意圖。
Fig. 7 is a circuit diagram of
圖8係本發明電路二的實體電路示意圖。 FIG. 8 is a schematic diagram of the physical circuit of the second circuit of the present invention.
圖9係本發明電路二的電路頻率響應示意圖。
Fig. 9 is a schematic diagram of the circuit frequency response of
為讓 貴審查委員能進一步瞭解本發明整體的技術特徵與達成本發明目的之技術手段,玆以具體實施例並配合圖式加以詳細說明: In order to allow your reviewer to further understand the overall technical features of the present invention and the technical means to achieve the purpose of the invention, a detailed description is given with specific examples and accompanying drawings:
本發明電路設計主要是以四埠網路進行分析,如參考文獻[1]。由於傳統枝幹耦合器傳輸線電氣長度皆為四分之一波長,在縮小化如參考文獻[3-7]設計電路技術中,一般皆會利用到傳輸線轉換PI型或者是T型等效電路,如參考文獻[8],但是同時也會產生並聯電容值的問題,於是本發明遂提出一種運用改變主枝幹傳輸線的電氣長度產生負並聯電容值與前述的並聯電容值相互抵消形成簡單又有效的創新電路。本發明所提出之二階高穿透係數輸出功率比枝幹耦合器之電路結構如圖1所示。在二階枝幹耦合器中設計高穿透係數如參考文獻[9-10]輸出功率比,旁枝幹阻抗值主 要影響耦合訊號至耦合埠的訊號量,所以穿透係數比越高,旁枝幹阻抗值也會愈高,微帶傳輸線的寬度可能會小於0.1mm,在製作上便會遇到困難點,故而本發明係使用傳輸線PI型等效轉換電路,利用電感來替代高阻抗值的旁枝幹傳輸線段,另外等效出正電容值的電容器藉由主枝幹拉長產生的等效負電容值的電容器兩者相互抵銷除達到電路設計的目標,同時減少電路使用集總元件的數目。而且設計者只需調整主枝幹角度及電感值,即可完成不同高穿透係數比的設計,因此,本發明整體電路設計非常容易並且大幅縮小電路整體面積為傳統尺寸的20%,輸出頻寬也非常寬,頻率響應也相當平坦,對於射頻電路的佈線與建置有相當大的助力。 The circuit design of the present invention is mainly analyzed by a four-port network, as in reference [1]. Since the electrical length of the traditional branch coupler transmission line is a quarter wavelength, in the design circuit technology of the reference [3-7], the transmission line is generally used to convert the PI type or the T type equivalent circuit. For example, reference [8], but at the same time, the problem of parallel capacitance value will also occur. Therefore, the present invention proposes a method of changing the electrical length of the main branch transmission line to generate a negative parallel capacitance value and the aforementioned parallel capacitance value to cancel each other to form a simple and effective Innovative circuit. The circuit structure of the second-order high penetration coefficient output power ratio branch coupler proposed by the present invention is shown in FIG. 1. Design high penetration coefficient in the second-order branch coupler, such as reference [9-10] output power ratio, the branch resistance value mainly To affect the amount of the coupled signal to the coupling port, the higher the penetration coefficient ratio, the higher the impedance value of the branch trunk. The width of the microstrip transmission line may be less than 0.1mm, and there will be difficulties in production. Therefore, the present invention uses a transmission line PI-type equivalent conversion circuit, which uses inductance to replace the high-impedance branch trunk transmission line segment. In addition, it is equivalent to the equivalent negative capacitance value generated by the positive capacitance value of the capacitor by the main branch lengthening. The two capacitors offset each other in addition to achieving the goal of circuit design, while reducing the number of lumped components used in the circuit. Moreover, the designer only needs to adjust the angle of the main branch and the inductance value to complete the design of different high penetration coefficient ratios. Therefore, the overall circuit design of the present invention is very easy and greatly reduces the overall area of the circuit to 20% of the traditional size. The width is also very wide, and the frequency response is also quite flat, which greatly assists the wiring and construction of radio frequency circuits.
請配合參看圖3~4所示,為達成本發明主要目的之實施例,係包含一基板10、一覆設於基板10上的傳輸線組20、二第一電感L1及一第二電感L2等技術特徵。該傳輸線組20包含二橫向並置的一第一傳輸線21及一第二傳輸線22。該第一傳輸線21二端各自設有一左右對稱且呈向下斜向延伸的一第一延伸段210及一第二延伸段211。該第二傳輸線22二端各自設有一左右對稱且呈向下斜向延伸的一第三延伸段220及一第四延伸段221。該第一傳輸線21二端之底緣各自向下突設有左右對稱的一第一梯形段212及一第二梯形段213。該第二傳輸線22二端之頂緣各自向上突設有左右對稱的一第三梯形段222及一第四梯形段223。該第三梯形段222及第四梯形段223分別與第一梯形段212及第二梯形段213呈上下對稱。該第一傳輸線21中段底緣附近與第二傳輸線22中段頂緣附近各自設有呈上下對稱的一第五梯形段214及一第六梯形段224。其一第一電感L1電性連接於第一梯形段212與第三梯形段222之間。其二第一電感L1電性連接於第
二梯形段213與第四梯形段223之間,該第二電感L2電性連接於第五梯形段214與第六梯形段224之間。
Please refer to Figs. 3~4. In order to achieve the main purpose of the present invention, the embodiment includes a
請配合參看圖4所示的一種實施例中,該第一傳輸線21與第二傳輸線22的長度皆為L3=99mm,其寬度皆為W2=3mm。該第一延伸段210末端至第二延伸段211末端以及第三延伸段220末端至第四延伸段221末端的距離皆為L6=123mm。該第一延伸段210頂緣至第三延伸段220底緣以及第二延伸段211的頂緣至第四延伸段221的底緣距離皆為W1=18.5mm。
Please refer to an embodiment shown in FIG. 4, the length of the
請配合參看圖7所示的另一種實施例中,該第一傳輸線21與第二傳輸線22的長度皆為L3=96.5mm,其寬度皆為W2=3mm。該第一延伸段210末端至第二延伸段211末端以及第三延伸段220末端至第四延伸段221末端的距離皆為L6=120.5mm。該第一延伸段210頂緣至第三延伸段220底緣以及第二延伸段211的頂緣至第四延伸段221的底緣距離皆為W1=18.5mm。
Please refer to another embodiment shown in FIG. 7, the length of the
具體的,如圖4、7所示,該第一傳輸線21與第二傳輸線22的間距為W3=2.5mm。該第一延伸段210、第二延伸段211、第三延伸段220及第四延伸段221各自包含一平行四邊形段210a,211a,220a,221a及一自平行四邊形段末端延伸的矩形段210b,211b,220b,221b。各矩形段的長度皆為L1=5mm。各平行四邊形段之二長邊的長度皆為L2=8.6mm。
Specifically, as shown in FIGS. 4 and 7, the distance between the
具體的,如圖4、7所示,該第一梯形段212、第二梯形段213、第三梯形段222及第四梯形段223相對的下底長度皆為L4=2mm。該第五梯形段214及第六梯形段224相對的上底的寬度皆為L5=0.5mm。該
第一梯形段212與第三梯形段222以及第二梯形段213與第四梯形段223之間的間距皆為W4=0.5mm。
Specifically, as shown in FIGS. 4 and 7, the length of the lower bottom of the first
請參看圖5、8所示,該第一延伸段210末端電性連接一輸入埠30,該第二延伸段211末端電性連接一輸出埠31,該第三延伸段220末端電性連接一隔離埠33,該第四延伸段221末端電性連接一耦合埠32,當輸出埠31與耦合埠32的輸出功率比為10:1時,該二第一電感L1之電感值介於50~60nH之間,該第二電感L2之電感值介於25~35nH之間。當輸出埠31與耦合埠32的輸出功率比為20:1時,該二第一電感L1之電感值介於70~85nH之間,該第二電感L2之電感值介於30~45nH之間。
Please refer to FIGS. 5 and 8, the end of the
此外,本發明主要是一種可以應用於物聯網頻段(915MHz)高穿透係數輸出功率比的二階枝幹耦合器設計,以傳統二階枝幹耦合器(如圖2所示)作為設計基底,當給定輸出功率比值P2:P3後,各傳輸線的特性阻抗值、Z1,Z2,Z3、可經由公式(1-3)求得。各傳輸線電氣長度θ 1、θ 2、θ 3均為90°。新式二階高穿透係數輸出功率比枝幹耦合器是以傳統二階枝幹耦合器各傳輸線段運用兩種PI型等效電路轉換而成。這兩種PI型等效電路分別為(1)C-TL-C;(2)C-L-C。C-TL-C等效電路應用於主枝幹傳輸線Z1,900;其轉換公式如式(4-5)所示,而C-L-C等效電路則應用於旁枝幹傳輸線Z2,900與Z3,900;其轉換公式分別對應如式(6-7)及如式(8-9)所示。為了使每段枝幹傳輸線透過PI型等效轉換後所產生的電容器能夠互相抵銷,並聯電容必須滿足式(10-12)。旁枝幹特性阻抗Z2公式(1)式、Z3公式(2)式及主枝幹特性阻抗Z1公式(3)式,枝幹旁枝幹傳輸線透過PI型等效後得電感L1公式(6)式及L2公式(8)式、電容器C1公式(7)式及C2公式(9)式,以及將主枝幹傳輸線透過PI型等效轉換後得 對應傳輸線阻抗Zo1及電容器Co1,如圖3所示,接著將四個對角Co1、C1電容器相加抵銷公式如(9)式,以及中間的兩個Co1電容器與一個C2電容器相加抵銷公式如(10)式,得電容器Co1可抵銷C1與C2電容值公式如(11)式,再計算主枝幹電氣長度θ o1如公式(13)式、主枝幹特性阻抗Zo1公式如(14)式。依上述設計流程可以完成應用於物聯網頻段915MHz高穿透係數輸出功率比之二階枝幹耦合器設計,其電路架構如圖1所示。本發明給定兩個輸出功率比率條件進行理論與實作以驗證設計流程之正確性,如表1所示。 In addition, the present invention is mainly a second-order branch coupler design that can be applied to the IoT frequency band (915MHz) with high penetration coefficient and output power ratio. The traditional second-order branch coupler (as shown in Figure 2) is used as the design basis. Given the output power ratio P2: P3, the characteristic impedance value of each transmission line, Z 1 , Z 2 , and Z 3 , can be obtained by formula (1-3). The electrical lengths θ 1 , θ 2 , and θ 3 of each transmission line are all 90 ° . The new second-order high-penetration coefficient output power ratio branch coupler is converted by using two PI-type equivalent circuits for each transmission line segment of the traditional second-order branch coupler. These two PI-type equivalent circuits are (1) C-TL-C; (2) CLC. C-TL-C equivalent circuit is applied to a main transmission line branches Z 1, 90 0; its conversion formula such as formula (4-5) as shown, and applied to CLC is an equivalent circuit of the transmission line branches off Z 2, 90 0 With Z 3 , 90 0 ; its conversion formulas correspond to formula (6-7) and formula (8-9) respectively. In order to make each branch of the trunk transmission line through the PI type equivalent conversion capacitors can cancel each other, the parallel capacitance must meet the formula (10-12). The characteristic impedance of branch trunk Z 2 formula (1), Z 3 formula (2) and the main branch characteristic impedance Z 1 formula (3), the branch trunk transmission line is equivalent to the inductance L 1 Formula (6) and L 2 formula (8), capacitor C 1 formula (7) and C 2 formula (9), and the main branch transmission line through PI type equivalent conversion to obtain the corresponding transmission line impedance Z o1 And capacitor C o1 , as shown in Figure 3, then add the four diagonal C o1 and C 1 capacitors to offset the formula as (9), and add the two C o1 capacitors in the middle and one C 2 capacitor to offset The pin formula is as formula (10), the capacitor C o1 can offset the capacitance of C 1 and C 2 as formula (11), and then the electrical length θ o1 of the main branch is calculated as formula (13), the characteristic impedance of the main branch The Zo1 formula is as (14). According to the above design process, the design of the second-order branch coupler applied to the 915MHz high penetration coefficient output power ratio of the Internet of Things frequency band can be completed, and the circuit architecture is shown in Figure 1. The present invention provides two output power ratio conditions for theory and practice to verify the correctness of the design process, as shown in Table 1.
θo1=cos-1(Co1×ω×Z1×sin θ1+cos θ1) (4) θ o1 =cos -1 (C o1 ×ω×Z 1 ×sin θ 1 +cos θ 1 ) (4)
Co1+C1=0 (10) C o1 +C 1 =0 (10)
Co1+Co1+C2=0 (11) C o1 +C o1 +C 2 =0 (11)
θo1=cos-1(Co1×ω×Z1×sin θ1+cos θ1) (13) θ o1 =cos -1 (C o1 ×ω×Z 1 ×sin θ 1 +cos θ 1 ) (13)
本發明二階高穿透係數輸出功率比枝幹耦合器設計,經分析調整後給定條件,取得不同輸出功率比的理論值,如表1所示。經電磁模擬軟體驗證其電路特性,選用板材FR-4厚度為1.6mm、相對介電常數為4.3,結構經最佳化調整後,電路尺寸由模擬軟體IE3D的LineGauge算出,其電路一如圖4所示,電路二如圖7所示。經雕刻機加工成型後,電路一之成品如圖5所示,電路二之成品如圖8所示,由Anritsu-MS46122B-010向量網路分析儀,量測頻率由1MHz到8GHz,並取得電路測量值,再與模擬數值進行比較,得到電路一輸出功率比10:1頻率響應如圖6所示,電路二輸出功率比20:1頻率響應如圖9所示。高穿透係數輸出功率比之二階枝幹耦合器於工作頻率915MHz中,輸入與隔離兩端訊號反彈量|S11|、|S41|皆在-15dB以下,輸出與耦合訊號兩端輸出功率比|S21|、|S31|維持於設計比率如表2所示,上述模擬與量測結果有相當大的一致性。 The second-order high-penetration coefficient output power ratio of the present invention is designed with a branch-to-stem coupler. After analysis and adjustment, given conditions, theoretical values of different output power ratios are obtained, as shown in Table 1. The circuit characteristics are verified by electromagnetic simulation software. The thickness of FR-4 is 1.6mm and the relative dielectric constant is 4.3. After the structure is optimized and adjusted, the circuit size is calculated by the LineGauge of the simulation software IE3D. The circuit is shown in Figure 4. As shown, circuit two is shown in Figure 7. After being processed by the engraving machine, the finished circuit of circuit one is shown in Figure 5, and the finished circuit of circuit two is shown in Figure 8. The Anritsu-MS46122B-010 vector network analyzer measures the frequency from 1MHz to 8GHz and obtains the circuit The measured value is compared with the analog value, and the frequency response of circuit one output power ratio of 10:1 is shown in Figure 6, and the frequency response of circuit two output power ratio of 20:1 is shown in Figure 9. The second-order branch coupler with high penetration coefficient and output power ratio at the working frequency of 915MHz, the rebound of the signal at the input and isolation ends |S 11 | and |S 41 | are both below -15dB, and the output power at both ends of the output and coupling signal The ratios |S 21 | and |S 31 | are maintained at the design ratios as shown in Table 2. The above simulation and measurement results are quite consistent.
經由上述具體實施例說明,本發明確實為一種二階高穿透係 數輸出功率比枝幹耦合器設計,高穿透係數輸出功率比,以微帶傳輸線製作於常見的板材(FR-4),高耦合係數輸出功率比設計基本上皆可順利實作出高穿透係數輸出功率比設計就會因傳輸線產生的高阻抗值會遇到許多製作困難處,因此本發明以電感來替代高阻抗值傳輸線,只需調整主枝幹電氣長度及電感值即可調整不同輸出功率比,且主枝幹阻抗可以維持於50Ω減少與連接埠間的不連續接點,其電路製作面積為傳統電路尺寸的20%,面積縮小程度很大。上述電路均經過電路模擬軟體模擬其設計可行性,使用板材FR-4,厚度為1.6mm、相對介電常數為4.3,電路結構均經過最佳化調整,模擬與實測結果相當接近,可知此電路的可行性,且能廣泛使用於其他不同中心頻率的應用之功率分配系統。 Through the above specific examples, the present invention is indeed a second-order high-penetration system Digital output power ratio. Branch-to-stem coupler design, high penetration coefficient output power ratio, made with microstrip transmission line on common board (FR-4), high coupling coefficient output power ratio design can basically achieve high penetration smoothly The coefficient output power ratio design will encounter many manufacturing difficulties due to the high impedance value generated by the transmission line. Therefore, the present invention replaces the high impedance transmission line with an inductance, and only needs to adjust the electrical length and inductance value of the main branch to adjust different outputs. The power ratio and the main branch impedance can be maintained at 50Ω to reduce the discontinuous contact with the port. The circuit production area is 20% of the traditional circuit size, and the area is greatly reduced. The above circuits are all simulated by circuit simulation software to simulate their design feasibility. Using sheet material FR-4, the thickness is 1.6mm, the relative permittivity is 4.3, and the circuit structure has been optimized and adjusted. The simulation results are quite close to the actual measurement results. It is feasible and can be widely used in other power distribution systems with different center frequency applications.
以上所述,僅為本發明之可行實施例,並非用以限定本發明之專利範圍,凡舉依據下列請求項所述之內容、特徵以及其精神而為之其他變化的等效實施,皆應包含於本發明之專利範圍內。本發明所具體界定於請求項之結構特徵,未見於同類物品,且具實用性與進步性,已符合發明專利要件,爰依法具文提出申請,謹請 鈞局依法核予專利,以維護本申請人合法之權益。 The above are only feasible embodiments of the present invention, and are not intended to limit the patent scope of the present invention. Any equivalent implementation of other changes based on the content, characteristics and spirit of the following claims shall be It is included in the scope of the patent of the present invention. The structural features of the invention specifically defined in the claim are not found in similar articles, and are practical and progressive, and have already met the requirements of an invention patent. The application is filed in accordance with the law. I would like to request the Bureau of Jun to approve the patent in order to protect this The legitimate rights and interests of the applicant.
[1] J. Reed, and G. J. Wheeler, "A Method of Analysis of Symmetrical Four-Port Networks," IRE Transactions on Microwave Theory and Techniques, vol. 4, no. 4, pp. 246-252, Oct. 1956. [1] J. Reed, and GJ Wheeler, "A Method of Analysis of Symmetrical Four-Port Networks," IRE Transactions on Microwave Theory and Techniques , vol. 4, no. 4, pp. 246-252, Oct. 1956.
[2]陳宣宇,具有高度平坦性的功率及相位頻寬之寬頻枝幹耦合器研究,碩±論文,通訊工程學系研究所,逢甲大學,民國99年. [2] Chen Xuanyu, Research on Broadband Trunk Coupler with Highly Flat Power and Phase Bandwidth, Master ± Thesis, Institute of Communication Engineering, Fengjia University, Republic of China 1999.
[3] Satoshi Kondo, Hajime Kondo, and Hitoshi Ishida, "A Reduced-Size and Tunable Branch-Line 3dB Hybrid," Microwave Conference Proceedings (APMC), pp. 37-40, Dec. 2011. [3] Satoshi Kondo, Hajime Kondo, and Hitoshi Ishida, "A Reduced-Size and Tunable Branch-Line 3dB Hybrid," Microwave Conference Proceedings (APMC) , pp. 37-40, Dec. 2011.
[4] Tsu-Wei Lin, Yi-Chyun Chiou, and Jen-Tsai Kuo, "Distributed and Lumped-Element Realizations of Wideband Branch-Line Hybrids with Arbitrary Power Division," Microwave Conference Proceedings (APMC), pp. 2112-2115, Dec. 2009. [4] Tsu-Wei Lin, Yi-Chyun Chiou, and Jen-Tsai Kuo, "Distributed and Lumped-Element Realizations of Wideband Branch-Line Hybrids with Arbitrary Power Division," Microwave Conference Proceedings (APMC) , pp. 2112-2115 , Dec. 2009.
[5] Yi-Chyun Chiang, and Chong-Yi Chen, "Design of a Wide-Band Lumped-Element 3-dB Quadrature Coupler," IEEE Transactions on Microwave Theory and Techniques, vol. 49, no. 3, pp. 476-479, Mar. 2001. [5] Yi-Chyun Chiang, and Chong-Yi Chen, "Design of a Wide-Band Lumped-Element 3-dB Quadrature Coupler," IEEE Transactions on Microwave Theory and Techniques , vol. 49, no. 3, pp. 476 -479, Mar. 2001.
[6] S. N. D. Azizi, S. K. A. Rahim, and M. I. Sabran, "Realization of a compact branch line couple using semi-lumped element," Wireless Technology and Applications (ISWTA), pp. 21-23, Sept. 2011. [6] SND Azizi, SKA Rahim, and MI Sabran, "Realization of a compact branch line couple using semi-lumped element," Wireless Technology and Applications (ISWTA), pp. 21-23, Sept. 2011.
[7] Chia-Hung Mou, and Chao-Hsiung Tseng, "A Bandwidth-Enhanced 3-dB Lumped-Element Branch-Line Coupler Based on Asymmetrical E-Equivalent Sections," Microwave Conference Proceedings (APMC), pp. 29-32, Dec. 2011. [7] Chia-Hung Mou, and Chao-Hsiung Tseng, "A Bandwidth-Enhanced 3-dB Lumped-Element Branch-Line Coupler Based on Asymmetrical E-Equivalent Sections," Microwave Conference Proceedings (APMC) , pp. 29-32 , Dec. 2011.
[8] W. I. Bowman, and J. M. McNamee, "Development of Equivalent Pi and T Matrix Circuits for Long Untransposed Transmission Lines," IEEE Transactions on Power Apparatus and Systems, vol. 83, no. 6, pp. 625-632, Jun. 1964. [8] WI Bowman, and JM McNamee, "Development of Equivalent Pi and T Matrix Circuits for Long Untransposed Transmission Lines," IEEE Transactions on Power Apparatus and Systems , vol. 83, no. 6, pp. 625-632, Jun. 1964.
[9] Henning Mextorf, and Reinhard Knöchel, "Ultra-wideband loose coupling directional couplers with high directivity," Microwave Conference (EuMC), pp. 294-297, Oct. 2013. [9] Henning Mextorf, and Reinhard Knöchel, "Ultra-wideband loose coupling directional couplers with high directivity," Microwave Conference (EuMC) , pp. 294-297, Oct. 2013.
[10] A. Abramowicz, A. Golaszewski, and L. Kowalczyk, "High Directivity Couplers Realized in Microstrip Line Technology," Electromagnetics in Advanced Applications (ICEAA), pp. 730-733, Sept. 2015. [10] A. Abramowicz, A. Golaszewski, and L. Kowalczyk, "High Directivity Couplers Realized in Microstrip Line Technology," Electromagnetics in Advanced Applications (ICEAA) , pp. 730-733, Sept. 2015.
20‧‧‧傳輸線組 20‧‧‧Transmission line group
21‧‧‧第一傳輸線 21‧‧‧The first transmission line
210‧‧‧第一延伸段 210‧‧‧First extension
210a,211a,220a,221a‧‧‧平行四邊形段 210a,211a,220a,221a‧‧‧parallelogram segment
210b,211b,220b,221b‧‧‧矩形段 210b,211b,220b,221b‧‧‧rectangular segment
211‧‧‧第二延伸段 211‧‧‧Second extension
212‧‧‧第一梯形段 212‧‧‧First ladder section
213‧‧‧第二梯形段 213‧‧‧Second ladder section
214‧‧‧第五梯形段 214‧‧‧Fifth trapezoid section
22‧‧‧第二傳輸線 22‧‧‧Second transmission line
220‧‧‧第三延伸段 220‧‧‧third extension
221‧‧‧第四延伸段 221‧‧‧ Fourth extension
222‧‧‧第三梯形段 222‧‧‧Third trapezoidal section
223‧‧‧第四梯形段 223‧‧‧Fourth trapezoidal section
224‧‧‧第六梯形段 224‧‧‧The sixth trapezoidal section
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