TWI594554B - Interleaved high efficiency high-step-up direct current transformer - Google Patents

Description

Interleaved high efficiency high boost DC converter

The invention relates to an interleaved high-efficiency high-boost DC converter, in particular to an interleaved operation, having the utility of chopping current cancellation, which can reduce the chopping current, thereby reducing the size of the filter component, and Amplizable voltage gain, when operating at higher voltage gains, does not have to operate at a very large conduction ratio, and can achieve zero voltage switching, reducing switching loss and conduction loss, and interleaving with more practical utility characteristics in its overall implementation. Innovative designer of high efficiency and high boost DC converters.

According to the recent global energy crisis and environmental awareness, the search for alternative energy sources has become an important issue. Many alternative energy sources such as solar energy, wind energy, hydropower, biomass and fuel cells are quite potential green. energy. In renewable energy power system applications, the technology development of solar power systems and fuel cell power generation systems is becoming more and more mature, often playing an important role in distributed generation systems. In general, solar modules and fuels The output voltage generated by the battery is a low voltage, generally not exceeding In order to meet the requirements of the grid-connected power generation system or the DC microgrid, the low-voltage DC-DC converter must be boosted to a high DC-row voltage to facilitate the full-bridge inverter. DC-AC conversion. In theory, a conventional boost converter operating at very high turn-on ratio can achieve high voltage gain, but in practice it is affected by parasitic components, and the voltage conversion ratio is limited to less than about 5 times, so when the voltage gain exceeds At five times the demand, it is necessary to develop a new high-efficiency power converter topology, which is a common research topic in the field of power electronics engineering in recent years.

Among them, as for the commonly used interleaved boost converter, please refer to the circuit diagram of the existing interleaved boost converter of the 33rd diagram, the interleaved boost converter (2) has processing High power, reduced input current chopping characteristics, and improved dynamic response, reduced magnetic component size and favorable heat dispersion; however, the interleaved boost converter (2) achieves a high boost ratio when It needs to operate at a very large conduction ratio.

Therefore, the development of a modified boost-return converter (3), please refer to the circuit diagram of the modified correction boost-return converter of the thirty-fourth figure, the modified rise Press-return converter (3) utilizes coupled inductor , And form a high boost converter with a voltage multiplying module.

However, the interleaved boost converter (2) and the modified boost-return converter (3) described above are found to be hard switching due to their power switches. There is no flexible switching performance, so that during the high-frequency switching process, the switching loss will cause the temperature of the power switching element to rise, reducing the service life of the power switching element, resulting in failure to achieve higher efficiency.

In view of this, the inventor has provided a kind of interleaved high-efficiency and high-boost DC converter with a view to the rich experience in design, development and actual production of the relevant industry for many years, and to provide an interleaved high-efficiency and high-boost DC converter. The purpose of good practical value.

The main object of the present invention is to provide an interleaved high-efficiency high-boost DC converter, which mainly utilizes an interleaved operation and has the utility of chopping current cancellation, which can reduce the chopping current, thereby reducing the size of the filter component. Moreover, the voltage gain can be amplified, and at a higher voltage gain, it is not necessary to operate at a very large conduction ratio, and can achieve zero voltage switching, reduce switching loss and conduction loss, and more practical performance characteristics in its overall implementation.

The main purpose and effect of the interleaved high efficiency and high-boost DC converter of the present invention are achieved by the following specific technical means:

Mainly to make the converter on the input power The positive pole is connected in parallel with the first coupled inductor primary side First side and second coupled inductor primary side The first end, at the input power The negative pole is connected in parallel with the first power switch Second end, second power switch Second end, third output capacitor Second end and load impedance The second end of the first coupling inductor The second end and the first power switch The first end is connected to the first auxiliary switch The second end of the second coupled inductor The second end and the second power switch The first end is connected to the second auxiliary switch The second end of the first auxiliary switch First end and the second auxiliary switch The first end is connected to the third output capacitor First end, first output capacitor Second end, first voltage doubled body The positive electrode, the first output capacitor First end and second output capacitor Second end, first coupled inductor secondary side The second end is connected to the first voltage doubler The negative pole and the second voltage doubled body The positive side and the second coupled inductor secondary side The second end of the first coupling inductor is connected The first end and the second coupled inductor secondary side The first end is connected to make the second output capacitor First end, the second voltage doubled body The negative pole is connected to the load impedance The first end.

The interleaved high efficiency high step-up DC converter of the present invention, wherein the first power switch And the second power switch Is a N-channel gold-oxygen field effect transistor [MOSFET], and the first power switch And the second power switch The first end is the drain [Drian] and the second end is the source [Sourse].

The interleaved high efficiency high-boost DC converter of the present invention, wherein the first auxiliary switch And the second auxiliary switch Is a N-channel gold-oxygen field effect transistor [MOSFET], and the first auxiliary switch And the second auxiliary switch The first end is the drain [Drian] and the second end is the source [Sourse].

The interleaved high efficiency high-boost DC converter of the present invention, wherein the first coupled inductor includes a first magnetizing inductance And first leakage inductance The second coupled inductor includes a second magnetizing inductance And second leakage inductance .

The interleaved high efficiency high-boost DC converter of the present invention, wherein the first coupled inductor is on the primary side Secondary side with the first coupled inductor Forming a first ideal transformer, the second coupled inductor primary side Secondary side with the second coupled inductor Forms a second ideal transformer.

The interleaved high efficiency high-boost DC converter of the present invention, wherein the first ideal transformer and the second ideal transformer have the same turns ratio.

For a more complete and clear disclosure of the technical content, the purpose of the invention and the effects thereof achieved by the present invention, it is explained in detail below, and please refer to the drawings and drawings:

First, referring to the first diagram of the circuit diagram of the present invention, the converter (1) of the present invention is mainly used for input power. The positive pole is connected in parallel with the first coupled inductor primary side First side and second coupled inductor primary side The first end, at the input power The negative pole is connected in parallel with the first power switch Second end, second power switch Second end, third output capacitor Second end and load impedance The second end, the first power switch And the second power switch Can be an N-channel gold oxide field effect transistor [MOSFET], and the first power switch And the second power switch The first end is a drain [Drian] and the second end is a source [Sourse], so that the first coupled inductor is on the primary side. The second end and the first power switch The first end is connected to the first auxiliary switch The second end of the second coupled inductor The second end and the second power switch The first end is connected to the second auxiliary switch The second end, the first auxiliary switch And the second auxiliary switch Can be an N-channel gold oxide field effect transistor [MOSFET], and the first auxiliary switch And the second auxiliary switch The first end is a drain [Drian] and the second end is a source [Sourse], so that the first auxiliary switch First end and the second auxiliary switch The first end is connected to the third output capacitor First end, first output capacitor Second end, first voltage doubled body The positive electrode, the first output capacitor First end and second output capacitor Second end, first coupled inductor secondary side The second end is connected to the first voltage doubler The negative pole and the second voltage doubled body The positive side and the second coupled inductor secondary side The second end of the first coupling inductor is connected The first end and the second coupled inductor secondary side The first end is connected to make the second output capacitor First end, the second voltage doubled body The negative pole is connected to the load impedance The first end.

Please refer to the second figure, which is an equivalent circuit diagram of the converter (1) of the first figure, the first coupled inductor may include a first magnetizing inductance And first leakage inductance , making the first coupled inductor primary side Secondary side with the first coupled inductor Forming a first ideal transformer, and the second coupled inductor may include a second magnetizing inductance And second leakage inductance , making the second coupled inductor primary side Secondary side with the second coupled inductor Forming a second ideal transformer, the first ideal transformer and the second ideal transformer have the same turns ratio; and because the first coupled inductor is on the primary side Primary side with the second coupled inductor Parallel connection, so that the total input current can be shared, and the interleaved operation can reduce the input current ripple; the first coupled inductor secondary side Secondary side with the second coupled inductor The series is connected so that the voltage gain can be increased.

The converter (1) is operated in a continuous conduction mode [CCM] during use, the conduction ratio is greater than 0.5, and the first power switch And the second power switch The first auxiliary switch is operated in an interleaved manner with a working phase difference of 180 ∘ And the second auxiliary switch With the first power switch And the second power switch Complementary operation. At steady state, the converter (1) is based on the first power switch And the second power switch And the first voltage doubled body And the second voltage doubled body In the ON/OFF state, the converter (1) can be divided into 16 operating phases in one switching cycle, and due to the symmetry of the converter (1) circuit, only the first eight phases are briefly analyzed. , assuming:

1. The first power switch And the second power switch And the first voltage doubled body And the second voltage doubled body The conduction voltage drop is zero;

2. The third output capacitor The first output capacitor And the second output capacitor Large enough, third output capacitor voltage First output capacitor voltage And second output capacitor voltage Can be regarded as a constant voltage, so the output voltage Can be regarded as a constant;

3. The first coupling inductor and the second coupled inductor have the same turns ratio ( And the first magnetizing inductance And the second magnetizing inductance equal( ), the first leakage inductance And the second leakage inductance equal( ), the first magnetizing inductance And the second magnetizing inductance Far greater than the first leakage inductance And the second leakage inductance ;

4. The first magnetizing inductance of the first coupled inductor The second magnetizing inductance of the second coupled inductor The current is operated in Continuous Conduction Mode (CCM).

The linear equivalent circuit and the main component waveforms of each linear phase are as follows. Please refer to the third diagram of the main component timing waveform diagram of the present invention as shown in the following figure:

The first stage[ ]:[First power switch :ON, second power switch :ON, the first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :OFF]: Please refer to the fourth diagram. The equivalent circuit diagram of the first operation stage of the present invention is shown in this figure. The first power switch And the second power switch All are ON [on], the first auxiliary switch And the second auxiliary switch All are OFF [cutoff]. The first voltage doubled body And the second voltage doubled body Both are reverse biased and cut off. Input power Across the first side of the first and second coupled inductors, that is, across the first magnetizing inductance The first leakage inductance The second magnetizing inductance The second leakage inductance The primary side current of the first and second coupled inductors rises linearly. when Second power switch Switch to OFF and proceed to the next stage.

second stage[ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :OFF]: Please refer to the fifth diagram. The equivalent circuit diagram of the second operation stage of the present invention is shown in this figure. The first power switch Keep ON, the second power switch Switch to OFF, the second leakage inductance Current The second power switch Parasitic capacitance Charging, the second power switch Cross pressure Fast rise from zero voltage because of the parasitic capacitance Very small, so this time is very short. when The second power switch Cross pressure Voltage rises to output third output capacitor voltage The second auxiliary switch The body diode is turned on, the second power switch Cross pressure Clamping at the third output capacitor voltage This phase ends.

The third stage[ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :OFF]: Please refer to the sixth diagram for the third phase of the invention, as shown in the equivalent circuit diagram. This phase begins at The second auxiliary switch The body diode is turned on, the second leakage inductance Current Via the second auxiliary switch Body diode to third output capacitor Charging, the second leakage inductance Current Falling, the first power switch Keep it ON. when The second voltage doubled body Turned to ON, this phase ends.

Fourth stage [ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :ON]: Please refer to the seventh diagram. The equivalent circuit diagram of the fourth operation stage of the present invention is shown in this stage. The second voltage doubled body Change to ON. Stored in the second magnetizing inductance Energy is transmitted to the secondary side by the second coupled inductor Via the second voltage doubled body Second output capacitor Charging. On the other hand, because of the secondary side of the second coupled inductor Current reflected to the first side of the ideal transformer of the first coupled inductor a first leakage inductance of the first coupled inductor Current , rise rapidly. At that time, the second auxiliary switch When switching to ON, this phase ends.

Fifth stage [ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :ON, the first voltage doubled body :OFF, second voltage doubled body :ON]: Please refer to the eighth diagram for the fifth phase of the invention, as shown in the equivalent circuit diagram. This phase begins at The second auxiliary switch Switch to ON. Because of this second auxiliary switch The body diode is turned on, so the second auxiliary switch The cross pressure is zero, so the second auxiliary switch Achieving zero voltage switching [ZVS] performance, at which time the current flowing through the body diode is transferred to the second auxiliary switch Third output capacitor Charging, the second leakage inductance Current Continue to drop, which in turn changes the direction of the current. At that time, the second auxiliary switch Switch to OFF and this phase ends.

Sixth stage [ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :ON]: Please refer to the ninth figure. The equivalent circuit diagram of the sixth operation stage of the present invention is shown in this stage. The second auxiliary switch Switch to OFF. The second magnetizing inductance The second leakage inductance And the second power switch Body capacitance Resonance, second power switch Cross pressure It begins to decline in the form of resonance. At that time, the second power switch Cross pressure Down to zero, the second power switch The body diode begins to conduct and this phase ends.

Seventh stage [ ]:[First power switch :ON, second power switch :OFF, first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :ON]: Please refer to the tenth figure. The equivalent circuit diagram of the seventh operation stage of the present invention is shown in this section. The second power switch The body diode is turned on, the second power switch Cross pressure Zero, second power switch The condition of zero voltage switching [ZVS] is established. At that time, the second power switch Switch to ON, the second power switch The ZVS performance is achieved and this phase ends.

The eighth stage [ ]:[First power switch :ON, second power switch :ON, the first auxiliary switch :OFF, second auxiliary switch :OFF, first voltage doubled body :OFF, second voltage doubled body :ON]: Please refer to the eleventh figure. The equivalent circuit diagram of the eighth operation stage of the present invention is shown in this section. The second power switch Switching to ON, and the first power switch Keep ON, this second leakage inductance Current Rapid rise, the second voltage doubled body Still conducting, the second magnetizing inductance Energy is transmitted to the secondary side by the second coupled inductor Continuously on the second output capacitor Charging. At that time, the second leakage inductance Current Rising to equal the second magnetizing inductance Current The second voltage doubled body Turned to OFF, this phase ends and enters the next half of the switching cycle.

In the 8 stages of the second half of the switching period of the converter (1), due to the symmetry of the circuit, the analysis of the operation of the last 8 stages is similar [please refer to the twelfth to the nineteenth pictures together], detail The analysis is omitted here.

The first power switch of the converter (1) And the second power switch All achieve ZVS performance, and the first auxiliary switch And the second auxiliary switch It has ZVS performance, so the converter (1) can improve switching losses.

Performing a steady-state characteristic analysis of the converter (1): to simplify the analysis, ignoring the first power switch And the second power switch And the first voltage doubled body And the second voltage doubled body Turn-on voltage drop and transient characteristics of very short time while ignoring the first leakage inductance And the second leakage inductance The third output capacitor The first output capacitor And the second output capacitor Large enough to ignore voltage chopping so that the capacitor voltage is constant.

Voltage gain:

Due to the third output capacitor The voltage can be regarded as the output voltage of the conventional boost converter, so the third output capacitor Output voltage Derivable

(1)

First and second output capacitor voltages on the secondary side of the first and second coupled inductors with It can be obtained by deriving the primary side voltage reflection voltage of the first and second coupled inductors. When the first power switch :OFF, second power switch :ON, and the first voltage doubled body When conducting [Twelfth stage], voltage for

(2)

When the first power switch :ON, second power switch :OFF, and the second voltage doubled body When conducting [fourth phase], voltage for

(3)

Total output voltage for

(4)

Therefore the voltage gain of the converter (1) is

(5)

From the above formula, the voltage gain is known to have the first and second coupled inductor turns ratio And conduction ratio Two design degrees of freedom. The converter (1) can achieve a high step-up ratio by appropriately designing the turns ratio of the first and second coupled inductors, and does not have to operate at a very large conduction ratio. Referring to the twentieth embodiment of the present invention, the coupled inductor turns ratio and the turn-on ratio of the voltage gain curve are shown in the schematic diagram, and the turn-on ratio is known. , When the voltage gain is 10 times; , At the time, the voltage gain is 30 times.

Voltage stress of the switching element:

The first power switch And the second power switch Voltage stress is

(6)

Because the power switching stress of the traditional interleaved boost converter is And the first power switch of the converter (1) And the second power switch The voltage stress is small, only 1/(2 n +1) times, so a low rated voltage with a low R _{ds (ON)} MOSFET can be used to reduce the switch conduction loss.

According to the above circuit action analysis results, the IsSpice simulation software and the implementation results are verified. Set the relevant parameters of the converter (1): input power 48V, output voltage 400V, maximum output power 500W, switching frequency 50kHz, The following is an examination of the characteristics of the converter (1) with analog waveforms and actual results [please refer to the twenty-first figure for the schematic diagram of the analog circuit of the present invention]:

A. Verification of steady-state characteristics: Please refer to the twenty-second diagram of the switch waveform driving signal, input power supply and output voltage of the present invention as shown in the analog waveform diagram to verify the steady-state characteristics of the converter (1), full load 500W When you know , , the conduction ratio is approximately , in accordance with the formula of (5) voltage gain.

B. Verifying the switch voltage stress: Please refer to the twenty-third figure for the switch drive signal and the switch voltage across the analog waveform diagram of the present invention, when the first power switch And the second power switch When all are OFF, the voltage across the switch is about 133.3V, which is only one-third of the output voltage of 400V. According to the analysis of (6), the switch of the converter (1) has the advantage of low voltage stress.

C. Verify that both the power switch and the auxiliary switch can achieve ZVS operation:

C1. Please refer to the driving signal and voltage-crossing analog waveform diagram of the power switch of the present invention, and the twenty-fifth figure. The analog waveform of the first power switch switching instant of the present invention is enlarged. FIG. 6 is an enlarged view of the analog waveform of the second power switch switching instant of the present invention, and the first power switch can be known when the load is 500 W at full load. And the second power switch The first power switch before switching to ON Cross pressure And the second power switch Cross pressure Both have dropped to zero, so ZVS operation is achieved.

C2. Please refer to the twenty-seventh figure for the driving signal and the voltage-crossing analog waveform diagram of the auxiliary switch of the present invention, and the twenty-eighth drawing, the analog waveform of the first auxiliary switch of the present invention, and the twentieth In the enlarged view of the analog waveform of the second auxiliary switch switching instant of the present invention, the first auxiliary switch can be known when the load is 500W. And the second auxiliary switch The first auxiliary switch before switching to ON Cross pressure And the second auxiliary switch Cross pressure Both have dropped to zero, so ZVS operation is achieved.

D. Verification of low input chopping current performance and CCM operation: Please refer to the thirty-fifth figure of the present invention for the leakage inductor current and total input current analog waveform diagram, which can be known as the first coupled inductor Leakage inductance Current And the second leakage inductance of the second coupled inductor Current The chopping current is about 19A, and the input current The chopping current is only about 1A, so the interleaved operation has the effect of reducing the input chopping current; please refer to the thirty-first figure of the magnetizing inductor current analog waveform diagram of the present invention, the first coupled inductor First magnetizing inductance The second magnetizing inductance of the second coupled inductor Verify that the operation is in continuous conduction mode [CCM].

E. Verifying the output capacitor voltage: Please refer to the voltage waveform diagram of the output capacitor of the present invention as shown in the thirty-second diagram. The third output capacitor is shown. Voltage The first output capacitor Voltage And the second output capacitor Voltage It is approximately equal to 133.3V, which is in accordance with the derivation results of (1)(2)(3).

From the above, the implementation description of the present invention shows that the present invention has the following advantages in comparison with the prior art means:

1. Interleaved operation: In high-power applications, it will result in high input current. Each group of coupled inductors only share one-half of the input average current, and the interleaved operation with 180° operating phase difference has a chopping current phase. The utility of the elimination can reduce the magnitude of the chopping current, thereby reducing the size of the filter component.

2. High voltage gain: The converter uses a coupled inductor and a switched capacitor to form a voltage multiplying module superimposed on the output side of the original interleaved boost converter, amplifying the voltage gain, and adjusting the turns ratio of the coupled inductor during design. This makes it unnecessary to operate at very high turn-on ratios when the converter is at a higher voltage gain.

3. High efficiency: The output diode is replaced by an auxiliary switch, so that both power switches and auxiliary switches can achieve zero voltage switching, reducing switching loss; since the voltage stress of the power switch is much smaller than the output voltage, it can be used low. A low-voltage MOSFET with on-resistance Rds(ON) reduces conduction losses; on the other hand. Therefore, the converter has the advantage of high efficiency.

While the invention has been described in connection with the preferred embodiments described above, it is not intended to limit the scope of the invention. The technical scope protected by the invention.

(1)‧‧‧ converter

(2) ‧‧‧Interleaved Boost Converter

(3) ‧‧‧Corrected Boost-Return Converter

First picture: converter circuit diagram of the present invention

Second figure: schematic diagram of the equivalent circuit of the converter of the present invention

Third figure: timing waveform diagram of main components of the present invention

Fourth figure: equivalent circuit diagram of the first operation stage of the present invention

Figure 5: Equivalent circuit diagram of the second operation stage of the present invention

Figure 6: Equivalent circuit diagram of the third operation stage of the present invention

Figure 7: Equivalent circuit diagram of the fourth operation stage of the present invention

Figure 8: Equivalent circuit diagram of the fifth operation stage of the present invention

Ninth diagram: equivalent circuit diagram of the sixth operation stage of the present invention

Figure 11: Equivalent circuit diagram of the seventh operation stage of the present invention

Eleventh figure: equivalent circuit diagram of the eighth operation stage of the present invention

Twelfth figure: equivalent circuit diagram of the ninth operation stage of the present invention

Thirteenth figure: equivalent circuit diagram of the tenth operation stage of the present invention

Figure 14: Equivalent circuit diagram of the eleventh operation stage of the present invention

Figure 15: Equivalent circuit diagram of the twelfth operation stage of the present invention

Figure 16: Equivalent circuit diagram of the thirteenth operation stage of the present invention

Figure 17: Equivalent circuit diagram of the fourteenth operation stage of the present invention

Figure 18: Equivalent circuit diagram of the fifteenth operation stage of the present invention

Figure 19: Equivalent circuit diagram of the sixteenth operation stage of the present invention

Figure 20: Schematic diagram of the voltage gain curve of the coupled inductor turns ratio and the turn-on ratio of the present invention

Figure 21: Schematic diagram of the analog circuit of the present invention

Twenty-second graph: analog waveform diagram of the switch drive signal, input power source and output voltage of the present invention

Twenty-third figure: analog waveform diagram of the switch drive signal and the switch across the voltage of the present invention

Figure 24: Driving signal and cross-voltage analog waveform diagram of the power switch of the present invention

Figure 25: enlarged waveform of the analog waveform of the first power switch switching instant of the present invention

Figure 26: enlarged waveform of the analog waveform of the second power switch switching instant of the present invention

Figure 27: Driving signal and cross-voltage analog waveform diagram of the auxiliary switch of the present invention

The twenty-eighth figure: an enlarged waveform of the analog waveform of the first auxiliary switch switching instant of the present invention

Twenty-ninth figure: an enlarged view of the analog waveform of the second auxiliary switch switching instant of the present invention

Figure 30: Analog waveform diagram of leakage inductance current and total input current of the present invention

The thirty-first figure: the waveform of the magnetizing inductor current of the present invention

Figure 32: Simulation diagram of the voltage waveform of the output capacitor of the present invention

Thirty-third picture: existing interleaved boost converter circuit diagram

Figure 34: Existing modified boost-return converter circuit diagram

(1)‧‧‧ converter

Claims (6)

An interleaved high-efficiency, high-boost DC converter that primarily converts the converter to an input power source The positive pole is connected in parallel with the first coupled inductor primary side First side and second coupled inductor primary side The first end, at the input power The negative pole is connected in parallel with the first power switch Second end, second power switch Second end, third output capacitor Second end and load impedance The second end of the first coupling inductor The second end and the first power switch The first end is connected to the first auxiliary switch The second end of the second coupled inductor The second end and the second power switch The first end is connected to the second auxiliary switch The second end of the first auxiliary switch First end and the second auxiliary switch The first end is connected to the third output capacitor First end, first output capacitor Second end, first voltage doubled body The positive electrode, the first output capacitor First end and second output capacitor Second end, first coupled inductor secondary side The second end is connected to the first voltage doubler The negative pole and the second voltage doubled body The positive side and the second coupled inductor secondary side The second end of the first coupling inductor is connected The first end and the second coupled inductor secondary side The first end is connected to make the second output capacitor First end, the second voltage doubled body The negative pole is connected to the load impedance The first end. The interleaved high efficiency high-boost DC converter according to claim 1, wherein the first power switch And the second power switch Is a N-channel gold-oxygen field effect transistor [MOSFET], and the first power switch And the second power switch The first end is the drain [Drian] and the second end is the source [Sourse]. The interleaved high efficiency high-boost DC converter according to claim 1, wherein the first auxiliary switch And the second auxiliary switch Is a N-channel gold-oxygen field effect transistor [MOSFET], and the first auxiliary switch And the second auxiliary switch The first end is the drain [Drian] and the second end is the source [Sourse]. The interleaved high efficiency high-boost DC converter according to claim 1, wherein the first coupled inductor includes a first magnetizing inductance And first leakage inductance The second coupled inductor includes a second magnetizing inductance And second leakage inductance . The interleaved high efficiency high-boost DC converter according to claim 1, wherein the first coupled inductor is on the primary side Secondary side with the first coupled inductor Forming a first ideal transformer, the second coupled inductor primary side Secondary side with the second coupled inductor Forms a second ideal transformer. The interleaved high efficiency high-boost DC converter according to claim 5, wherein the first ideal transformer and the second ideal transformer have the same turns ratio.