TWI466423B - High boost power converter - Google Patents

High boost power converter Download PDF

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TWI466423B
TWI466423B TW101102268A TW101102268A TWI466423B TW I466423 B TWI466423 B TW I466423B TW 101102268 A TW101102268 A TW 101102268A TW 101102268 A TW101102268 A TW 101102268A TW I466423 B TWI466423 B TW I466423B
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diode
capacitor
power switch
energy
boost
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TW201332269A (en
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Univ Chienkuo Technology
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高昇壓電源轉換器High boost power converter

本發明係關於一種高昇壓電源轉換器,特別是指結合耦合電感與電壓昇舉技術之高昇壓電源轉換器,主要是調整耦合電感的匝數比與利用電壓昇舉技術及倍壓電路來達成高昇壓比之目的。The invention relates to a high-boost power converter, in particular to a high-boost power converter combined with a coupled inductor and a voltage boosting technique, which mainly adjusts the turns ratio of the coupled inductor and utilizes a voltage boosting technique and a voltage doubler circuit. Achieve a high boost ratio.

按,高昇壓比直流-直流轉換器(High Step-up Ratio DC-DC Converter)廣泛應用於工業電器及市售產品中,如:電腦週邊電源供應、不斷電電源供應器(Uninterruptible Power Supply,UPS)及車用高強度放電燈(High Intensity Discharge Lamp,HID Lamp)等,皆需要具有高昇壓比及高效率之直流-直流電源供應。According to the High Step-up Ratio DC-DC Converter, it is widely used in industrial electrical appliances and commercially available products, such as computer peripheral power supply and uninterruptible power supply (Uninterruptible Power Supply, UPS) and High Intensity Discharge Lamp (HID Lamp) require a DC-DC power supply with high step-up ratio and high efficiency.

傳統的昇壓型轉換器(Boost Converter)即使合理的操作在極高工作週期之下,所得到的昇壓比還不能滿足所需求的高昇壓比,當轉換器開關操作於極高的工作週期,輸入電壓相對輸出側的高電壓使得輸出二極體逆向回復的問題相當嚴重,降低轉換器穩定度。The traditional boost converter (Boost Converter) can not meet the required high boost ratio even when the operation is under a very high duty cycle. When the converter switch operates at a very high duty cycle. The high voltage of the input voltage relative to the output side makes the problem of reverse recovery of the output diode quite serious, reducing the converter stability.

為了改善二極體逆向回復的問題,利用具耦合電感之昇壓型轉換器(Coupled Inductor with Boost Converter)來改善;當耦合電感之匝數比提高時,可改變轉換器的昇壓比; 然而利用耦合電感相對衍生出的問題,為漏電感能量釋放於開關上的寄生電容上,使開關上產生電壓突波、增加切換損失與降低轉換器效率。In order to improve the reverse recovery of the diode, a booster inductor with a coupled inductor (Coupled Inductor with Boost Converter) is used to improve; when the turns ratio of the coupled inductor is increased, the boost ratio of the converter can be changed; However, the relative problem derived from the coupled inductor is that the leakage inductance energy is released on the parasitic capacitance on the switch, causing voltage surge on the switch, increasing switching loss and reducing converter efficiency.

2005年T.J.Liang與K.C.Tseng所提出的整合型昇壓返馳式轉換器(Integrated Boost-Flyback Converter,IBFC),利用耦合電感技術將昇壓型轉換電路與返馳式轉換電路作整合,使轉換電路具有高效率、低電壓應力的功率開關及輸出電容。In 2005, TJLiang and KCTseng proposed an integrated Boost-Flyback Converter (IBFC), which uses a coupled inductor technology to integrate a boost converter circuit with a flyback converter circuit to convert The circuit has high efficiency, low voltage stress power switches and output capacitors.

如我國公開編號TW201117540 A1之「電源轉換裝置」,其中,第三實施例For example, the "power conversion device" of the Japanese Patent Publication No. TW201117540 A1, wherein the third embodiment

由此可見,上述習用物品仍有諸多缺失,實非一良善之設計者,而亟待加以改良。It can be seen that there are still many shortcomings in the above-mentioned household items, which is not a good designer and needs to be improved.

本案發明人鑑於上述習用高昇壓電源轉換器所衍生的各項缺點,乃亟思加以改良創新,並經多年苦心孤詣潛心研究後,終於成功研發完成本件高昇壓電源轉換器。In view of the shortcomings derived from the above-mentioned conventional high-boost power converters, the inventors of the present invention have improved and innovated, and after years of painstaking research, finally successfully developed and completed this high-boost power converter.

本發明之目的即在於提供一種高昇壓電源轉換器,具有低開關電壓應力之高昇壓電源轉換器,此高昇壓轉換器具有高昇壓比、高轉換效率與低開關電壓應力之特性,主要是利用耦合電感、電壓昇舉技術與倍壓電路來達到高昇壓比之功效。The object of the present invention is to provide a high-boost power converter with a high-boost power converter with low switching voltage stress, which has the characteristics of high step-up ratio, high conversion efficiency and low switching voltage stress, mainly utilizing Coupled inductors, voltage boosting technology and voltage doubling circuit to achieve high boost ratio.

本發明之次一目的係在於提供一種高昇壓電源轉換器,使儲存於耦合電感中之漏電感能量,可藉由功率開關在截止期間予以回收再生,因此轉換效率得以提升,並且能夠有效地箝制功率開關上的電壓突波。A second object of the present invention is to provide a high-boost power converter, so that the leakage inductance energy stored in the coupled inductor can be recovered and regenerated by the power switch during the cut-off period, thereby improving the conversion efficiency and effectively clamping Voltage surge on the power switch.

可達成上述發明目的之高昇壓電源轉換器,包括有:一高昇壓電源轉換電路,係由一輸入電源串接一功率開關與第一耦合電感,該第一耦合電感兩端分別串接第一電容與第一二極體,並連接於一擴展電壓增益電路;一擴展電壓增益電路,係由一箝制電感串接第二二極體與第二電容,並電性連接一濾波電路;一濾波電路,係由一第三二極體串接第一輸出電容,並電性連接一倍壓電路;一倍壓電路,係由第二耦合電感串接第四二極體與第五二極體,再串接第二、第三輸出電容,最後再並聯一負載電阻。The high-boost power converter capable of achieving the above object includes: a high-boost power conversion circuit, wherein an input power source is connected in series with a power switch and a first coupled inductor, and the first coupled inductor is respectively connected in series with the first end The capacitor and the first diode are connected to an extended voltage gain circuit; an extended voltage gain circuit is connected by a clamp inductor to the second diode and the second capacitor, and is electrically connected to a filter circuit; The circuit is connected by a third diode to the first output capacitor and electrically connected to the double voltage circuit; the double voltage circuit is connected by the second coupled inductor to the fourth diode and the fifth The pole body is connected in series with the second and third output capacitors, and finally a load resistor is connected in parallel.

請參閱圖1,本發明所提供之高昇壓電源轉換器,主要包括有:一高昇壓電源轉換電路1,係由一輸入電源Vin 串接一功率開關Q與第一耦合電感N1 ,該第一耦合電感N1 兩端分別串接第一電容C1 與第一二極體D1 ,並連接於一擴展電壓增益電路2;一擴展電壓增益電路2,係由一箝制電感Lc串接第二二極體D2 與第二電容C2 ,並電性連接一濾波電路4;一濾波電路4,係由一第三二極體D3 串接第一輸出電容Co1 ,並電性連接一倍壓電路3;一倍壓電路3,係由第二耦合電感N2 串接第四二極體D4 與第五二極體D5 ,再串接第二、第三輸出電容Co2 、Co3 ,最後再並聯一負載電阻RLReferring to FIG. 1 , a high-boost power converter provided by the present invention mainly includes: a high-boost power conversion circuit 1 , wherein an input power source V in is connected in series with a power switch Q and a first coupled inductor N 1 . The first coupling inductor N 1 is connected in series with the first capacitor C 1 and the first diode D 1 , and is connected to an extended voltage gain circuit 2; an extended voltage gain circuit 2 is connected in series by a clamp inductor Lc. The second diode D 2 and the second capacitor C 2 are electrically connected to a filter circuit 4; a filter circuit 4 is connected in series with the first output capacitor C o1 by a third diode D 3 , and is electrically connected Connecting the double voltage circuit 3; the voltage doubler circuit 3 is connected in series with the fourth diode D 4 and the fifth diode D 5 by the second coupling inductor N 2 , and then connected in series with the second and third outputs Capacitors C o2 , C o3 , and finally a parallel load resistor R L .

高昇壓電源轉換器一般適用於需較高輸出電壓的場合,依據架構的不同昇壓比而有所不同,昇壓比通常只能從調整耦合電感匝數比著手;當所需匝數比較大、功率較高或銅線數量較多時,需選用較大的線圈架與鐵芯,因此提出一具耦合電感與電壓昇舉技術結合之架構克服上述問題,並提高電路的昇壓比。High-boost power converters are generally suitable for applications requiring higher output voltages, depending on the different boost ratios of the architecture. The boost ratio can usually only be adjusted by adjusting the coupling inductance turns ratio; when the required turns are large When the power is high or the number of copper wires is large, a larger coil bobbin and iron core are required. Therefore, a structure combining the coupled inductor and the voltage lift technology is proposed to overcome the above problem and improve the boost ratio of the circuit.

本發明之高昇壓電源轉換器的架構,部份兼具箝制開關電壓作用,倍壓電路3透過功率開關Q或二極體導通將能量經由耦合電感儲存在輸出電容,以利提高昇壓比,至於輸出電容部份係由第一、第二與第三輸出電容Co1 、Co2 、Co3 串接而成,用以解決習知之昇壓電路架構,輸出電容耐壓規格選用不易的問題。The architecture of the high-boost power converter of the present invention partially functions as a clamp switch voltage, and the voltage doubler circuit 3 stores energy through the coupled inductor in the output capacitor through the power switch Q or the diode conduction to improve the boost ratio. The output capacitor portion is formed by connecting the first, second, and third output capacitors C o1 , C o2 , and C o3 in series to solve the conventional boost circuit architecture, and the output capacitor withstand voltage specifications are difficult to select. problem.

圖2為高昇壓電源轉換器主要波形圖,依照各工作狀態可將基本工作原理分為七個操作狀態:Figure 2 shows the main waveform of the high-boost power converter. According to each working state, the basic working principle can be divided into seven operating states:

Mode 1[t0 <t≦t1 ]:Mode 1[t 0 <t≦t 1 ]:

當t=t0 時,功率開關Q導通,其電路狀態如圖3所示,此時,第二二極體D2 與第四二極體D4 導通,第一二極體D1 、第三二極體D3 與第五二極體D5 截止,輸入電源Vin 經功率開關Q對漏電感Lk1 進行儲能,同時輸入電源Vin 也經第二二極體D2 對第一電容C1 與箝制電感Lc 進行儲能,第二電容C2 經功率開關Q釋放能量;此時激磁電感Lm 與漏電感Lk2 能量釋放儲存在第二輸出電容Co2 ,iLm 下降至初始值,負載RL 所需能量由三個輸出電容提供。When t=t 0 , the power switch Q is turned on, and its circuit state is as shown in FIG. 3. At this time, the second diode D 2 and the fourth diode D 4 are turned on, the first diode D 1 , the first The triode D 3 and the fifth diode D 5 are turned off, the input power source V in is stored by the power switch Q to the leakage inductance L k1 , and the input power source V in is also passed through the second diode D 2 The capacitor C 1 and the clamp inductor L c store energy, and the second capacitor C 2 releases energy through the power switch Q; at this time, the excitation inductance L m and the leakage inductance L k2 energy release are stored in the second output capacitor C o2 , i Lm drops to Initially, the energy required to load R L is provided by three output capacitors.

Mode 2[t1 <t≦t2 ]:Mode 2[t 1 <t≦t 2 ]:

當t=t1 時,功率開關Q導通,其電路狀態如圖4所示,此時,第二二極體D2 與第五二極體D5 導通,第一二極體D1 、第三二極體D3 與第四二極體D4 截止,輸入電源Vin 經功率開關Q對激磁電感Lm 與漏電感Lk1 進行儲能,同時輸入電源Vin 也經第二二極體D2 對第一電容C1 與箝制電感Lc 進行儲能,第二電容C2 經功率開關Q釋放能量;此時輸入電源Vin 藉由第一耦合電感N1 將能量傳遞至第二耦合電感N2 對漏電感Lk2 與第三輸出電容Co3 儲存能量,激磁電感電流iLM 由初始值增加,負載RL 所需能量由三個輸出電容提供。When t=t 1 , the power switch Q is turned on, and its circuit state is as shown in FIG. 4 . At this time, the second diode D 2 and the fifth diode D 5 are turned on, the first diode D 1 , the first thirty-two diode D 3 and the fourth diode D 4 is turned off, the input power source via the power switch Q V in the magnetizing inductance L m of the leakage inductance L k1 store energy while the power supply V in is also input via a second diode D 2 stores energy for the first capacitor C 1 and the clamp inductor L c , and the second capacitor C 2 releases energy through the power switch Q; at this time, the input power source V in transfers energy to the second coupling through the first coupled inductor N 1 The inductor N 2 stores energy to the leakage inductance L k2 and the third output capacitor C o3 , the magnetizing inductor current i LM is increased by an initial value, and the energy required for the load R L is provided by three output capacitors.

Mode 3[t2 <t≦t3 ]:Mode 3[t 2 <t≦t 3 ]:

當t=t2 時,功率開關Q導通,其電路狀態如圖5所示,此時,第五二極體D5 導通,第一二極體D1 、第二二極體D2 、第三二極體D3 與第四二極體D4 截止,輸入電源Vin 經功率開關Q對激磁電感Lm 與漏電感Lk1 進行儲能,第一電容C1 、第二電容C2 與箝制電感Lc 因第二二極體D2 截止無法傳遞能量;同時輸入電源Vin 藉由第一耦合電感N1 將能量傳遞至第二耦合電感N2 對漏電感Lk2 與第三輸出電容Co3 儲存能量,激磁電感電流iLm 增加至最高值,負載RL 所需能量由輸出電容提供。When t=t 2 , the power switch Q is turned on, and its circuit state is as shown in FIG. 5 . At this time, the fifth diode D 5 is turned on, the first diode D 1 , the second diode D 2 , and the first The diode D 3 and the fourth diode D 4 are turned off, and the input power source V in is stored by the power switch Q for the magnetizing inductance L m and the leakage inductance L k1 , and the first capacitor C 1 and the second capacitor C 2 are The clamp inductor L c cannot transfer energy due to the second diode D 2 cutoff; at the same time, the input power source V in transfers energy to the second coupled inductor N 2 to the drain inductor L k2 and the third output capacitor by the first coupled inductor N 1 C o3 stores energy, the magnetizing inductor current i Lm increases to the highest value, and the energy required to load R L is provided by the output capacitor.

Mode 4[t3 <t≦t4 ]:Mode 4[t 3 <t≦t 4 ]:

當t=t3 時,功率開關Q截止,其電路狀態如圖6所示,此時,第一二極體D1 、第三二極體D3 與第五二極體D5 導通,第二二極體D2 與第四二極體D4 截止,第一電容C1 經第一二極體D1 釋放能量給漏電感Lk1 ,輸入電源Vin 經激磁電感Lm 與漏電感Lk1 對功率開關Q的寄生電容Coss 進行儲能,也經第三二極體D3 對第二電容C2 與第一輸出電容Co1 儲存能量;同時輸入電源Vin 藉由第一耦合電感N1 將能量傳遞至第二耦合電感N2 對漏電感Lk2 與第三輸出電容Co3 儲存能量,激磁電感電流iLm 由最高值下降,負載RL 所需能量由輸出電容提供。When t=t 3 , the power switch Q is turned off, and the circuit state thereof is as shown in FIG. 6. At this time, the first diode D 1 , the third diode D 3 and the fifth diode D 5 are turned on, two diode D 2 and the fourth diode D 4 is turned off, the first capacitor C 1 via the first diode D 1 the release of energy to the leakage inductance L K1, input power V in by the magnetizing inductance L m and a leakage inductance L K1 stores energy to the parasitic capacitance C oss of the power switch Q, and also stores energy to the second capacitor C 2 and the first output capacitor C o1 via the third diode D 3 ; the input power source V in is coupled by the first coupled inductor N 1 transfers energy to the second coupled inductor N 2 to store energy to the leakage inductance L k2 and the third output capacitor C o3 , the magnetizing inductor current i Lm is decreased by the highest value, and the energy required to load the R L is provided by the output capacitor.

Mode 5[t4 <t≦t5 ]:Mode 5[t 4 <t≦t 5 ]:

當t=t4 時,功率開關Q截止,且寄生電容Coss 已儲能完畢,其電路狀態如圖7所示,此時,第一二極體D1 、第三二極體D3 與第四二極體D4 導通,第二二極體D2 與第五二極體D5 截止,第一電容C1 經第一二極體D1 釋放能量給漏電感Lk1 ,輸入電源Vin 藉由第三二極體D3 經激磁電感Lm 與漏電感Lk1 對第二電容C2 與第一輸出電容Co1 儲存能量;同時激磁電感Lm 與漏電感Lk2 能量釋放儲存在第二輸出電容Co2 ,激磁電感電流iLm 持續下降,負載RL 所需能量由三個輸出電容提供。When t=t 4 , the power switch Q is turned off, and the parasitic capacitance C oss has been stored, and the circuit state is as shown in FIG. 7 . At this time, the first diode D 1 and the third diode D 3 are a fourth diode D 4 is turned on, the second diode D 2 and the fifth diode D 5 is turned off, the first capacitor C 1 via the first diode D 1 the release of energy to the leakage inductance L k1, the input power supply V Is stored by the third diode D 3 via the magnetizing inductance L m and the leakage inductance L k1 to the second capacitor C 2 and the first output capacitor C o1 ; while the excitation inductance L m and the leakage inductance L k2 are released in energy storage The second output capacitor C o2 , the magnetizing inductor current i Lm continues to drop, and the energy required to load R L is provided by three output capacitors.

Mode 6[t5 <t≦t6 ]:Mode 6[t 5 <t≦t 6 ]:

當t=t5 時,功率開關Q截止,其電路狀態如圖8所示,此時,第一二極體D1 、第三二極體D3 與第四二極體D4 導通,第二二極體D2 與第五二極體D5 截止,第一電容C1 經第一二極體D1 釋放能量給漏電感Lk1 ,輸入電源Vin 藉由第三二極體D3 與第四二極體D4 經激磁電感Lm 與漏電感Lk1 對第二電容C2 與第二輸出電容Co2 儲存能量;同時激磁電感Lm 與漏電感Lk2 能量釋放儲存在第二輸出電容Co2 ,激磁電感電流iLm 持續下降,負載RL 所需能量由三個輸出電容提供。When t=t 5 , the power switch Q is turned off, and the circuit state thereof is as shown in FIG. 8. At this time, the first diode D 1 , the third diode D 3 and the fourth diode D 4 are turned on, two diode D 2 and the fifth diode D 5 is turned off, the first capacitor C 1 via the first diode D 1 the release of energy to the leakage inductance L k1, V in the input power by a third diode D 3 And the fourth diode D 4 stores the energy to the second capacitor C 2 and the second output capacitor C o2 via the magnetizing inductance L m and the leakage inductance L k1 ; while the excitation inductance L m and the leakage inductance L k2 are released in energy and stored in the second The output capacitor C o2 , the magnetizing inductor current i Lm continues to drop, and the energy required to load R L is provided by three output capacitors.

Mode 7[t6 <t≦t7 ]:Mode 7[t 6 <t≦t 7 ]:

當t=t6 時,功率開關Q截止,其電路狀態如圖9所示,此時,第四二極體D4 導通,第一二極體D1 、第二二極體D2 、第三二極體D3 與第五二極體D5 截止,所以輸入電源Vin 與漏電感Lk1 沒有傳遞路徑無法提供能量;同時激磁電感Lm 與漏電感Lk2 能量釋放儲存在第二輸出電容Co2 ,激磁電感電流iLm 持續下降,負載RL 所需能量由三個輸出電容提供。When t=t 6 , the power switch Q is turned off, and its circuit state is as shown in FIG. 9 . At this time, the fourth diode D 4 is turned on, the first diode D 1 , the second diode D 2 , and the first The triode D 3 and the fifth diode D 5 are turned off, so the input power source V in and the leakage inductance L k1 have no transmission path to provide energy; and the excitation inductance L m and the leakage inductance L k2 energy release are stored in the second output. Capacitor C o2 , the magnetizing inductor current i Lm continues to drop, and the energy required to load R L is provided by three output capacitors.

當功率開關Q導通時,由等效電路可得到以下關係式:VM =VLm =Vin ,VC2 =VC1 +Vin ,VN2 =Vo3 =(N2 /N1 )VLm =(N2 /N1 )Vin When the power switch Q is turned on, the following relationship can be obtained by the equivalent circuit: V M = V Lm = V in , V C2 = V C1 + V in , V N2 = V o3 = (N 2 / N 1 ) V Lm =(N 2 /N 1 )V in

當功率開關Q截止時,由等效電路可得到以下關係式:VLm =-VC1 ,Vo1 =VC1 +VC2 +Vin ,VN2 =-Vo2 When the power switch Q is turned off, the following relationship can be obtained by the equivalent circuit: V Lm = -V C1 , V o1 = V C1 + V C2 + V in , V N2 = -V o2

由上述式子可得知,輸出與輸入電壓關係為:Vo /Vin =2+(N2 /N1 )/1-DIt can be known from the above equation that the relationship between the output and the input voltage is: V o /V in =2+(N 2 /N 1 )/1-D

為驗證上述之動作原理,提出一較佳實施例之模擬與實驗結果,設定輸入電壓Vin 為直流12V,輸出規格為200V/150W,且切換頻率為50kHz:如圖10所示,為實作量測之功率開關驅動訊號VGS 、功率開關電壓VDS 及功率開關電流iDS 波形圖,由圖中可知,當具耦合電感與電壓昇舉技術之高昇壓電源轉換器輸出為滿載時,測量功率開關Q之切換頻率為fs =50kHz。To verify the operation principle of the above, the embodiment of the proposed simulation and experimental results a preferred embodiment, the input voltage V in is set to DC 12V, the output specifications of 200V / 150W, and the switching frequency is 50kHz: 10, for the implementation Measured power switch drive signal V GS , power switch voltage V DS and power switch current i DS waveform diagram, as shown in the figure, when the output of the high-boost power converter with coupled inductor and voltage lift technology is full load, the measurement The switching frequency of the power switch Q is f s = 50 kHz.

其中,實作所量測之功率開關電壓的突波大小為VDS =32V,開關電流峰值為iDS =24A高,轉換器工作週期為D=0.56。Among them, the magnitude of the power switch voltage measured by the implementation is V DS =32V, the peak of the switching current is i DS =24A high, and the converter duty cycle is D=0.56.

如圖11所示,為實作量測之功率開關驅動訊號VGS 、第一電容電流ic1 及第一二極體電流iD1 波形圖,由圖中可知,高昇壓電源轉換器之功率開關Q導通時,因輸入端能量從第一電容C1 流入,所以第一電容電流iC1 為儲能,此時第一二極體D1 逆偏截止;當高昇壓電源轉換器之功率開關Q截止時,第一電容C1 因第一二極體D1 順向導通形成流經漏電感Lk1 的路徑,此時第一電容電流ic1 為釋量。As shown in FIG. 11, the waveform diagram of the power switch drive signal V GS , the first capacitor current i c1 , and the first diode current i D1 measured for actual measurement, as shown in the figure, the power switch of the high-boost power converter when Q is turned on, due to energy flow from the input terminal of the first capacitor C 1, so the first current i C1 is the storage capacitor, a first diode D At this time, a reverse bias is turned off; when the power of the high-boost power converter switches Q when turned off, the first capacitor C 1 by the first diode D 1 forward conducting path is formed passing through the leakage inductance L k1, when the first capacitor is released an amount of current i c1.

其中,所量測之第一電容電流的峰值大小為ic1 =2.3A,第一二極體電流峰值為iD1 =9A。Wherein, the measured peak current of the first capacitor current is i c1 =2.3A, and the peak value of the first diode current is i D1 =9A.

如圖12所示,為實作量測之功率開關驅動訊號VGS 、箝制電感電流iLc 及第二二極體電流iD2 波形圖,由圖中可知,當高昇壓電源轉換器之功率開關Q導通時,箝制電感LC 因第二二極體D2 順向導通形成流經功率開關Q的路徑,此時箝制電感Lc為箝制功率開關電壓VDs 與第二二極體電流iD2As shown in FIG. 12, the waveform diagram of the power switch drive signal V GS , the clamp inductor current i Lc and the second diode current i D2 for actual measurement is shown in the figure, when the power switch of the high boost power converter is shown When Q is turned on, the clamp inductor L C forms a path through the power switch Q due to the second diode D 2 flowing forward. At this time, the clamp inductor Lc is the clamped power switch voltage V Ds and the second diode current i D2 .

其中,所量測之第二二極體電流為iD2 =2.5A,箝制電感電流為iLc =2.5A,兩者非常接近。Among them, the measured second diode current is i D2 = 2.5A, and the clamped inductor current is i Lc = 2.5A, which are very close.

如圖13所示,為實作量測之功率開關驅動訊號VGS 、第二電容電流ic2 及第三二極體電流iD3 波形圖,由圖中可知,當高昇壓電源轉換器之功率開關Q導通時,因第二二極體D2 順向導通形成第二電容C2 流經功率開關Q的路徑,所以第二電容電流iC2 為釋能,此時第三二極體D3 逆偏截止;當高昇壓電源轉換器之功率開關Q截止時,第二電容C2 因第三二極體D3 順向導通形成流經第一輸出電容Co1 的路徑,此時第二電容電流iC2 為儲能。As shown in FIG. 13, the power switch drive signal V GS , the second capacitor current i c2 , and the third diode current i D3 waveform are actually measured. As can be seen from the figure, when the power of the high boost power converter is when the switch Q is turned on, because the second diode D 2 is formed along a second conducting capacitor C 2 Q path flowing through the power switch, the second capacitor C2 is discharging current I, now the third diode D 3 Reverse bias cutoff; when the power switch Q of the high boost power converter is turned off, the second capacitor C 2 forms a path through the first output capacitor C o1 due to the third diode D 3 flowing forward, and the second capacitor Current i C2 is energy storage.

其中,所量測之第二電容電流的峰值大小為iC2 =5A,第三二極體電流峰值為iD3 =5A。Wherein, the measured peak value of the second capacitor current is i C2 = 5A, and the peak value of the third diode current is i D3 = 5A.

如圖14所示,為實作量測之功率開關驅動訊號VGS 、二極體電流iD4 及二極體電流iD5 波形圖,由圖中可知,當高昇壓電源轉換器之功率開關Q導通時,因第五二極體D5 順向導通對第三輸出電容Co3 儲能,此時第四二極體D4 逆偏截止;當高昇壓電源轉換器之功率開關Q截止時,因第四二極體D4 順向導通對第二輸出電容Co2 儲能,此時第五二極體D5 逆偏截止。As shown in FIG. 14, the waveform diagram of the power switch drive signal V GS , the diode current i D4 , and the diode current i D5 for actual measurement is shown in the figure, when the power switch Q of the high boost power converter is shown. When turned on, the fifth diode D 5 is stored in the third output capacitor C o3 by the conduction of the fifth diode D 5 , and the fourth diode D 4 is reverse biased off; when the power switch Q of the high boost power converter is turned off, Because the fourth diode D 4 stores the energy to the second output capacitor C o2 , the fifth diode D 5 is reverse biased.

其中,所量測之第四二極體電流的峰值大小為iD4 =2.4A,功率開關電流峰值為iDS =1.6A。Among them, the measured peak value of the fourth diode current is i D4 = 2.4A, and the peak value of the power switch current is i DS = 1.6A.

如圖15所示,高昇壓電源轉換器於輕載10W時轉換效率可達86.83%,轉換器大約於29W時高昇壓電源轉換器進入連續導通模式,當輸出功率約60W時可達到最高轉換效率99.01%,但是隨著輸出功率增大,功率開關Q之電流也隨之增大。As shown in Figure 15, the high-boost power converter achieves a conversion efficiency of 86.83% at 10W light load, and the high-boost power converter enters continuous conduction mode at approximately 29W converter. The maximum conversion efficiency can be achieved when the output power is about 60W. 99.01%, but as the output power increases, the current of the power switch Q also increases.

如圖10所示,當轉換器為滿載(150W)情況下,功率開關Q導通時之電流高達24A,因此轉換效率也隨之下降,但輸出功率為滿載(150W)情況下,仍有90.16%的高效率。As shown in Figure 10, when the converter is fully loaded (150W), the current of the power switch Q is up to 24A, so the conversion efficiency is also reduced, but the output power is full load (150W), still 90.16% High efficiency.

上列詳細說明係針對本發明之一可行實施例之具體說明,惟該實施例並非用以限制本發明之專利範圍,凡未脫離本發明技藝精神所為之等效實施或變更,均應包含於本案之專利範圍中。The detailed description of the preferred embodiments of the present invention is intended to be limited to the scope of the invention, and is not intended to limit the scope of the invention. The patent scope of this case.

綜上所述,本案不但在空間型態上確屬創新,並能較習用物品增進上述多項功效,應已充分符合新穎性及進步性之法定發明專利要件,爰依法提出申請,懇請 貴局核准本件發明專利申請案,以勵發明,至感德便。In summary, this case is not only innovative in terms of space type, but also can enhance the above-mentioned multiple functions compared with the customary items. It should fully meet the statutory invention patent requirements of novelty and progressiveness, and apply for it according to law. This invention patent application, in order to invent invention, to the sense of virtue.

1...高昇壓電源轉換電路1. . . High boost power conversion circuit

2...擴展電壓增益電路2. . . Extended voltage gain circuit

3...倍壓電路3. . . Voltage doubling circuit

4...濾波電路4. . . Filter circuit

Vin ...輸入電源V in . . . Input power

VGS ...功率開關驅動訊號V GS . . . Power switch drive signal

VDS ...功率開關電壓V DS . . . Power switch voltage

Q...功率開關Q. . . Power switch

N1 ...第一耦合電感N 1 . . . First coupled inductor

N2 ...第二耦合電感N 2 . . . Second coupled inductor

C1 ...第一電容C 1 . . . First capacitor

C2 ...第二電容C 2 . . . Second capacitor

Co1 ...第一輸出電容C o1 . . . First output capacitor

Co2 ...第二輸出電容C o2 . . . Second output capacitor

Co3 ...第三輸出電容C o3 . . . Third output capacitor

Coss ...寄生電容C oss . . . Parasitic capacitance

D1 ...第一二極體D 1 . . . First diode

D2 ...第二二極體D 2 . . . Second diode

D3 ...第三二極體D 3 . . . Third diode

D4 ...第四二極體D 4 . . . Fourth diode

D5 ...第五二極體D 5 . . . Fifth diode

Lm ...激磁電感L m . . . Magnetizing inductance

Lc...箝制電感Lc. . . Clamping inductance

Lk1 、Lk2 ...漏電感L k1 , L k2 . . . Leakage inductance

iLM ...激磁電感電流i LM . . . Magnetizing inductor current

iDS ...功率開關電流i DS . . . Power switch current

RL ...負載R L . . . load

圖1為本發明高昇壓電源轉換器之電路圖;1 is a circuit diagram of a high boost power converter of the present invention;

圖2為該高昇壓電源轉換器之波形圖;2 is a waveform diagram of the high boost power converter;

圖3為該高昇壓電源轉換器之t0 <t≦t1 電路狀態圖;3 is a circuit state diagram of t 0 <t≦t 1 of the high-boost power converter;

圖4為該高昇壓電源轉換器之t1 <t≦t2 電路狀態圖;4 is a circuit diagram of the circuit of t 1 <t≦t 2 of the high-boost power converter;

圖5為該高昇壓電源轉換器之t2 <t≦t3 電路狀態圖;Figure 5 is a circuit diagram of the t 2 <t≦t 3 circuit of the high-boost power converter;

圖6為該高昇壓電源轉換器之t3 <t≦t4 電路狀態圖;6 is a circuit diagram of the circuit of t 3 <t≦t 4 of the high-boost power converter;

圖7為該高昇壓電源轉換器之t4 <t≦t5 電路狀態圖;7 is a circuit state diagram of the t 4 <t≦t 5 of the high-boost power converter;

圖8為該高昇壓電源轉換器之t5 <t≦t6 電路狀態圖;Figure 8 is a circuit diagram of the circuit of t 5 <t≦t 6 of the high-boost power converter;

圖9為該高昇壓電源轉換器之t6 <t≦t7 電路狀態圖;Figure 9 is a circuit diagram of the circuit of t 6 <t≦t 7 of the high-boost power converter;

圖10為該高昇壓電源轉換器之實作量測之功率開關驅動訊號VGS 、功率開關電壓VDS 及功率開關電流iDS 波形圖;10 is a waveform diagram of a power switch drive signal V GS , a power switch voltage V DS , and a power switch current i DS of the high-boost power converter;

圖11為該高昇壓電源轉換器之實作量測之功率開關驅動訊號VGS 、第一電容電流ic1 及第一二極體電流iD1 波形圖;11 is a waveform diagram of the power switch drive signal V GS , the first capacitor current i c1 , and the first diode current i D1 of the high-boost power converter;

圖12為該高昇壓電源轉換器之實作量測之功率開關驅動訊號VGS 、箝制電感電流iLc 及第二二極體電流iD2 波形圖;12 is a waveform diagram of the power switch driving signal V GS , the clamped inductor current i Lc , and the second diode current i D2 of the high-boost power converter;

圖13為該高昇壓電源轉換器之實作量測之功率開關驅動訊號VGS 、第二電容電流ic2 及第三二極體電流iD3 波形圖;13 is a waveform diagram of the power switch drive signal V GS , the second capacitor current i c2 , and the third diode current i D3 of the high-boost power converter;

圖14為該高昇壓電源轉換器之實作量測之功率開關驅動訊號VGS 、二極體電流iD4 及二極體電流iD5 波形圖;以及14 is a waveform diagram of a power switch driving signal V GS , a diode current i D4 , and a diode current i D5 of the high-boost power converter; and

圖15為該高昇壓電源轉換器之量測效率圖。Figure 15 is a graph showing the measurement efficiency of the high-boost power converter.

1‧‧‧高昇壓電源轉換電路1‧‧‧High boost power conversion circuit

2‧‧‧擴展電壓增益電路2‧‧‧Extended voltage gain circuit

3‧‧‧倍壓電路3‧‧‧ double voltage circuit

4‧‧‧濾波電路4‧‧‧Filter circuit

Vin ‧‧‧輸入電源V in ‧‧‧Input power supply

Q‧‧‧功率開關Q‧‧‧Power switch

N1 ‧‧‧第一耦合電感N 1 ‧‧‧First coupled inductor

N2 ‧‧‧第二耦合電感N 2 ‧‧‧Second coupled inductor

C1 ‧‧‧第一電容C 1 ‧‧‧first capacitor

C2 ‧‧‧第二電容C 2 ‧‧‧second capacitor

Co1 ‧‧‧第一輸出電容C o1 ‧‧‧first output capacitor

Co2 ‧‧‧第二輸出電容C o2 ‧‧‧second output capacitor

Co3 ‧‧‧第三輸出電容C o3 ‧‧‧ third output capacitor

D1 ‧‧‧第一二極體D 1 ‧‧‧First Diode

D2 ‧‧‧第二二極體D 2 ‧‧‧Secondary

D3 ‧‧‧第三二極體D 3 ‧‧‧third diode

D4 ‧‧‧第四二極體D 4 ‧‧‧fourth dipole

D5 ‧‧‧第五二極體D 5 ‧‧‧ fifth dipole

Lc‧‧‧箝制電感Lc‧‧‧Clamping Inductors

RL ‧‧‧負載R L ‧‧‧load

Claims (3)

一種高昇壓電源轉換器,包括:一高昇壓電源轉換電路,係由一輸入電源串接一功率開關與一第一耦合電感,該第一耦合電感兩端分別串接一第一電容與一第一二極體,並連接於一擴展電壓增益電路;該擴展電壓增益電路,係由一箝制電感串接一第二二極體與一第二電容,並電性連接一濾波電路;一濾波電路,係由一第三二極體串接一第一輸出電容,並電性連接一倍壓電路;該倍壓電路,係由一第二耦合電感串接一第四二極體與一第五二極體,再串接一第二輸出電容、一第三輸出電容,最後再並聯一負載電阻;該功率開關導通後,該第二二極體與該第四二極體導通,該第一二極體、該第三二極體與該第五二極體截止,該輸入電源經該功率開關對漏電感進行儲能,同時該輸入電源也經該第二二極體對該第一電容與該箝制電感進行儲能,該第二電容經該功率開關釋放能量,此時激磁電感與漏電感能量釋放儲存在該第二輸出電,激磁電感電流下降至初始值,負載所需能量由三個輸出電容提供。 A high-boost power converter includes: a high-boost power conversion circuit: an input power supply is connected in series with a power switch and a first coupled inductor, and the first coupled inductor is connected in series with a first capacitor and a first a diode body is connected to an extended voltage gain circuit; the extended voltage gain circuit is connected by a clamp inductor to a second diode and a second capacitor, and is electrically connected to a filter circuit; a filter circuit a third diode is connected in series with a first output capacitor and electrically connected to a voltage doubler circuit; the voltage doubler circuit is connected by a second coupled inductor to a fourth diode and a a fifth diode, a second output capacitor and a third output capacitor are connected in series, and finally a load resistor is connected in parallel; after the power switch is turned on, the second diode is electrically connected to the fourth diode, The first diode, the third diode, and the fifth diode are turned off, and the input power source stores energy to the leakage inductance via the power switch, and the input power source is also passed through the second diode. a capacitor is stored with the clamped inductor, and the second capacitor is Energy release the power switch, then magnetizing inductance and leakage inductance energy stored in the second release output, the magnetizing inductor current drops to the initial value, the energy provided by the three required output capacitive load. 如申請專利範圍第1 項所述之高昇壓電源轉換器,其中 該第一二極體、該第三二極體與該第五二極體導通,該第二二極體與該第四二極體截止,該第一電容經該第一二極體釋放能量給該第一耦合電感之漏電感,輸入電源經激磁電感與漏電感對該功率開關的寄生電容進行儲能,也經該第三二極體對該第二電容與該第一輸出電容儲存能量,並將漏電感之能量回收,藉此提高轉換效率。The high-boost power converter of claim 1 , wherein the first diode, the third diode, and the fifth diode are turned on, the second diode and the fourth The pole body is cut off, the first capacitor releases energy to the leakage inductance of the first coupled inductor via the first diode, and the input power source stores energy of the parasitic capacitance of the power switch through the excitation inductor and the leakage inductance. The triode stores energy to the second capacitor and the first output capacitor, and recovers energy of the leakage inductance, thereby improving conversion efficiency. 如申請專利範圍第1 項所述之高昇壓電源轉換器,其中該功率開關導通時,因該第二二極體順向導通形成該第二電容流經該功率開關的路徑,所以該第二電容電流為釋能,此時該第三二極體逆偏截止;當高昇壓電源轉換器之該功率開關截止時,該第二電容因該第三二極體順向導通形成流經該第一輸出電容的路徑,此時該第二電容電流為儲能,藉此達到箝制該功率開關之電壓突波。The high-boost power converter according to claim 1 , wherein when the power switch is turned on, the second diode flows in a path to form a path of the second capacitor flowing through the power switch, so the second The capacitor current is the release energy, and the third diode is reverse biased off; when the power switch of the high-boost power converter is turned off, the second capacitor flows through the third diode due to the conduction of the third diode A path of the output capacitor, at which time the second capacitor current is energy storage, thereby achieving voltage surges that clamp the power switch.
TW101102268A 2012-01-19 2012-01-19 High boost power converter TWI466423B (en)

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CN103490622B (en) * 2013-09-16 2016-01-20 华南理工大学 A kind of Single-switch high-gain boost converter
TWI554014B (en) * 2015-06-01 2016-10-11 遠東科技大學 High step-up dc power converter

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TW201143267A (en) * 2010-05-31 2011-12-01 Univ Nat Cheng Kung Multi-winding high step-up DC-DC converter

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TW201143267A (en) * 2010-05-31 2011-12-01 Univ Nat Cheng Kung Multi-winding high step-up DC-DC converter

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