TWI399010B - Power supply - Google Patents

Description

Power supply unit

The present invention relates to a power supply device, and more particularly to a power supply device having a power supply that can be charged by an external power source.

Due to the high awareness of global environmental protection, in recent years, high-efficiency hybrid vehicles (Hybrid Car) are gaining popularity. The hybrid electric vehicle system includes a main battery for driving the traveling motor and an auxiliary battery for driving the auxiliary machine. When the batteries are charged by the commercial alternating current power source, the fuel consumption of the hybrid electric vehicle can be improved.

However, when a vehicle is equipped with a charging device that converts a commercial power source voltage into a DC voltage capable of battery charging, the weight of the vehicle increases.

Therefore, in Patent Document 1, it is shown that when the battery is charged, the existing equipment (inverter) that is not operating is used as a part of the charger, and the commercial power source is used while suppressing an increase in the weight of the vehicle. The aforementioned battery is charged.

Further, a power supply device that charges a battery by a commercial power source using an inverter is disclosed in Patent Documents 2 to 5.

[Previous Technical Literature]

[Patent Document 1] Japanese Patent Laid-Open Publication No. 2007-195336

[Patent Document 2] Japanese Patent No. 2695083

[Patent Document 3] Japanese Patent Laid-Open No. Hei 8-228443

[Patent Document 4] Japanese Patent Laid-Open Publication No. 2007-318970

[Patent Document 5] Japanese Patent Laid-Open Publication No. 2006-320074

In general, in order to reduce the size and efficiency of the power supply device, it is effective to use a switching element having a fast switching characteristic. However, in the conventional power supply device shown in Patent Documents 1 to 3, in order to downsize the power supply device, the current density of the inverter is set to be high.

However, in the case of a switching element, for example, an IGBT current density can be set to be high. However, when an element having a slow switching characteristic is used, the switching loss is increased, and the power conversion efficiency when charging from a commercial power source to the battery is lowered.

The present invention has been made in view of such problems, and provides a power supply device capable of charging a battery to be mounted with high efficiency while using a commercial power source while suppressing an increase in weight.

In order to solve the above problems, the present invention employs the means described below.

The first conversion circuit is provided with a first DC power supply connected to the DC side terminal, a primary winding of the transformer connected to the AC side terminal, and a second conversion circuit having the transformer connected twice at the AC side terminal thereof. a winding is connected to the DC-side terminal with a second DC power supply; and a control circuit that opens and closes the switching elements constituting the first and second conversion circuits, and supplies the AC to the AC-side terminal of the first conversion circuit. Power is supplied to the first or second DC power source.

Since the present invention has the above configuration, it is possible to charge the mounted battery with high efficiency while using a commercial power source while suppressing an increase in weight.

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings. In the present specification, the operation of transmitting power from the DC power source V1 to the DC power source V2 is referred to as a step-down operation. Conversely, the operation of transmitting power from the DC power source V2 to the DC power source V1 is referred to as a boosting operation. Further, the operation of transmitting power to the DC power source V1 and the DC power source V2 by the AC power source V3 is referred to as charging operation 1, and the operation of transmitting power to the DC power source V1 by the AC power source V3 and not transmitting power to the DC power source V2 is referred to as charging. Action 2.

[First Embodiment]

Fig. 1 is a view showing a circuit configuration of a power supply device according to a first embodiment of the present invention. The power supply device shown in Fig. 1 is connected to a DC power supply V1 to which a load R1 is connected, a DC power supply V2 to which a load R2 is connected, and an AC power supply V3, and the power is received between the DC power supplies V1 and V2. The AC power source V3 charges the DC power sources V1 and V2.

In Fig. 1, the smoothing capacitor C1 is connected to the DC power supply V1, and the smoothing capacitor C2 is connected to the DC power supply V2. The DC terminal of the conversion circuit 11 is connected to the smoothing capacitor C1 through the diode D. The diode D is connected to the DC power supply V1 by the conversion circuit 11, and vice versa, the DC power supply V1 is connected to the direction in which the conversion circuit 11 does not flow power, and the switch SW0 is connected in parallel to the diode D. Further, the DC terminal of the circuit 12 is connected to the smoothing capacitor C2.

The AC terminal of the converter circuit 11 is connected to the switch N11 through the switches SW11 and SW12 and the resonance capacitor Cr, and the AC power source V3 is connected to the boost inductors L1 and L2 and the switches SW21 and SW22. A winding N2 is connected to the AC terminal of the conversion circuit 12. Transformer 1 magnetically couples winding N1 to winding N2.

The conversion circuits 11, 12, the switches SW0, SW11, SW12, SW21, and SW22 are controlled by the control means 10. Voltage sensors 21, 22, and 23 and current sensors 31, 32, and 33 are connected to the control means 10.

Here, the step-down operation of the power supply device shown in Fig. 1 will be described. In the step-down operation, the switches SW0, SW11, and SW12 are kept in an on state, and the switches SW21 and SW22 are kept in an off state. Since both ends of the diode D are short-circuited, the DC terminal of the converter circuit 11 is formed in the same state as the case where the diode D is not directly connected to the smoothing capacitor C1. The control means 10 applies an alternating current voltage to the winding N1 while the switches SW0, SW11, and SW12 are kept in the on state and the switches SW21 and SW22 are kept in the off state, and the switching circuit 11 is switched. The conversion circuit 12 rectifies the induced voltage generated in the winding N2 to supply electric power to the DC power supply V2.

Next, the boosting operation of the power supply device shown in Fig. 1 will be described. In the boosting operation, the control means 10 applies the AC voltage to the winding N2 while the switches SW0, SW21, and SW22 are kept in the off state and the SW11 and SW12 are kept in the ON state while the switching circuit 12 is switched. The conversion circuit 11 rectifies the induced voltage generated in the winding N1 to supply electric power to the DC power supply V1.

Next, the charging operation 1 of the power supply device shown in Fig. 1 (power transmission of the DC power supply V1 and the DC power supply V2 by the AC power supply V3) will be described. In the charging operation 1, the switch SW0 is kept in the off state, and the SW11, SW12, SW21, and SW22 are kept in the on state. The switching circuit 11 is switched, and the boost inductors L1 and L2 are superimposed on the energy of the AC power source V3, and the power is supplied to the DC power source V1, and an AC voltage is applied to the winding N1. The conversion circuit 12 rectifies the induced voltage generated in the winding N2 to supply electric power to the DC power supply V2.

Next, the charging operation 2 of the power supply device shown in Fig. 1 (power transmission by the AC power supply V3 only to the DC power supply V1) will be described. In the charging operation 2, the switches SW0, SW11, and SW12 are kept in the off state, and the switches SW21 and SW22 are kept in the on state. Similarly to the charging operation 1, the switching circuit 11 is switched to supply electric power to the DC power supply V1. Since the switches SW11 and SW12 are in the off state, no voltage is applied to the winding N1, and no power is supplied to the DC power source V2.

In the charging operations 1 and 2, the input current from the AC power source V3 detected by the current sensor 33 is made to have the same waveform as the voltage of the AC power source V3 detected by the voltage sensor 23. The circuit 11 performs a switching operation whereby the power factor of the input power can be increased.

In the boosting operation and the charging operation 1 and 2, even if an element having a relatively low reverse recovery characteristic such as an intrinsic diode (parasitic diode) of a high withstand voltage MOSFET is used as the rectifying element constituting the conversion circuit 11, Also, since the diode D, which prevents the reverse recovery characteristic from being fast, is back-flowed from the DC power source V1 or the smoothing capacitor C1 to the conversion circuit 11, efficient power transmission can be performed.

Since the switch SW0 switches between the on state and the off state only during the operation switching, it is possible to use an IGBT having a slow operation or a mechanical switch like an electromagnetic relay. If an IGBT is used, if a package having an anti-parallel diode built in is used, the external diode D is not required, which is advantageous for miniaturization. If a mechanical switch is used, since the conduction loss is small, more efficient power transmission can be performed. Of course, in the case of the rectifying element constituting the conversion circuit 11, when the element having a relatively fast reverse recovery characteristic is used, the diode D and the switch SW0 are not required, and the DC terminal of the conversion circuit 11 can be directly connected to the smoothing. Capacitor C1.

[Second Embodiment]

Fig. 2 is a circuit configuration diagram of a power supply device according to a second embodiment of the present invention. The power supply device shown in Fig. 2 is connected to a DC power supply V1 to which a load R1 is connected, a DC power supply V2 to which a load R2 is connected, and an AC power supply V3, and power is supplied between the DC power supplies V1 and V2. The AC power source V3 charges the DC power sources V1 and V2.

In Fig. 2, the smoothing capacitor C1 is connected to the DC power supply V1, and the smoothing capacitor C2 is connected to the DC power supply V2. The first switching pin in which the switching elements H1 and H2 are connected in series is transmitted through the diode D to be connected to the smoothing capacitor C1. The diode D is connected to the DC power supply V1 by the first switching pin, and the DC power supply V1 is connected to the direction in which the first switching pin does not flow power, and the diode D is connected in parallel. Switch SW0. The second switching pin in which the switching elements H3 and H4 are connected in series is connected in parallel to the first switching pin.

Between the series connection point of the switching elements H1, H2 and the series connection point of the switching elements H3, H4, through the resonant inductor Lr, the switches SW11, SW12 and the resonant capacitor Cr and the winding N1 are connected in series, and the switch SW21 is connected in series , SW22 and boost inductors L1, L2 and AC power supply V3.

The transformer 2 magnetically couples the windings N1, N21, and N22. One end of the winding N21 is connected to one end of the winding N22, the other end of the winding N21 is connected to one end of the switching element S1, and the other end of the winding N22 is connected to one end of the switching element S2. The other end of the switching element S1 and the other end of the switching element S2 are connected to one end of the smoothing capacitor C2. The connection point of the windings N21 and N22 is connected to the other end of the smoothing capacitor C2 through the smoothing inductor L.

The anti-parallel diodes DH1 to DH4, DS1, and DS2 are connected to the switching elements H1 to H4, S1, and S2, respectively. Here, when a MOSFET is used as the switching element, an in-line diode of the MOSFET can be used as the anti-parallel diode. Wherein, the snubber capacitors may be connected in parallel in each of the aforementioned switching elements.

The switching elements H1 to H4, S1, S2, and the switches SW0, SW11, SW12, SW21, and SW22 are controlled by the control means 10. Voltage sensors 21, 22, and 23 and current sensors 31, 32, and 33 are connected to the control means 10.

(Buck action)

3A to 3E are views for explaining the step-down operation of the power supply device shown in Fig. 2. The following steps will be described in detail with reference to FIGS. 3A to 3E. Among them, the 3A to 3E drawings indicate modes a to e, respectively.

(mode a)

First, in mode a, switches SW0, SW11, SW12, switching elements H1, H4 are in an on state, switches SW21, SW22, switching elements H2, H3 are in an off state, and a voltage of a direct current power source V1 is transmitted through switches SW0, SW11, SW12. The switching elements H1, H4, the resonant inductor Lr, and the resonant capacitor Cr are applied to the winding N1.

The switching element S2 is in an off state, and the voltage generated in the winding N21 is applied to the DC power source V2 through the diode DS1 and the smoothing inductor L, and supplies energy to the DC power source V2. At this time, when the MOSFET is used as the switching elements S1 and S2, if the switching element S1 is turned on, the current flowing to the diode DS1 can be shunted toward the switching element S1, and the loss can be reduced. As described above, when the indirect diode of the diode or MOSFET connected in anti-parallel with the MOSFET flows through the forward current of the diode, the MOSFET is turned into an on state to reduce the loss, which is hereinafter referred to as synchronization. Rectification.

(mode b)

When the switching element H4 is turned off, the current flowing through the switching element H4, the DC power supply V1, and the switch SW0 is diverted to the diode DH3. At this time, the switching element H3 is turned on. The energy accumulated in the smoothing inductor L is supplied to the DC power source V2.

(mode c)

When the switching element H1 is turned off, the current flowing through the switching element H1 is diverted to the switch SW0 and/or the diode D, the direct current power source V1, and the diode DH2. At this time, the switching element H2 is turned on. The voltage of the DC power source V1 is applied to the resonant inductor Lr, and the current is gradually reduced. Along with this, the current flowing through the diode DS1 and the winding N21 is reduced, and the current flows through the diode DS2 and the winding N22. At this time, when the switching element S2 is turned on, synchronous rectification is performed.

(mode d)

Since the switching elements H2, H3 are in an on state, the current increases in the reverse direction after the current of the resonant inductor Lr reaches zero. Before the current through the winding N21 reaches zero, the switching element S1 is first turned off.

(mode e)

When the current passing through the winding N21 reaches zero, the voltage generated in the winding N22 is applied to the DC power source V2 through the diode DS2 and the smoothing inductor L, and energy is supplied to the DC power source V2.

This mode e is a symmetric action of mode a. Hereinafter, after the symmetrical operation of the modes b to d, the mode a is returned.

(Charging action 1)

4A and 4B are diagrams for explaining the charging operation 1 of the power supply device shown in Fig. 2 (the power is transmitted from the AC power source V3 to the DC power source V1 and the DC power source V2). Hereinafter, the charging operation 1 will be described in detail with reference to FIGS. 4A and 4B. 4A and 4B show modes a and b, respectively. A period in which the voltage of the AC power source V3 is positive toward the connection point of the switching elements H1 and H2 will be described.

(mode a)

First, in mode a, the switches SW11, SW12, SW21, SW22, and the switching elements H2 and H3 are in an on state, and the switch SW0 is in an off state, and the voltage of the alternating current power source V3 is transmitted through the switches SW21 and SW22, the switching elements H2 and H3, The diodes DH1 and DH4 and the resonant inductor Lr are applied to the boost inductors L1 and L2, and the energy of the AC power source V3 is accumulated in the boost inductors L1 and L2. At this time, when the switching elements H1 and H4 are turned on, synchronous rectification is performed.

On the other hand, the voltage of the resonant capacitor Cr is applied to the winding N1 through the switches SW11 and SW12, the switching elements H2 and H3, the diodes DH1 and DH4, and the resonant inductor Lr. The switching element S1 is in an off state, and the voltage generated in the winding N22 is applied to the DC power source V2 through the diode DS2 and the smoothing inductor L, and supplies energy to the DC power source V2. At this time, when the switching element S2 is turned on, synchronous rectification is performed.

(mode b)

When the switching elements H2 and H3 are turned off, the current flowing through the switching elements H2 and H3 is diverted to the diode D and the DC power source V1, and the boost inductors L1 and L2 release the accumulated energy to the DC power source V1. Supply energy. Similarly to the mode a, when the switching elements H1 and H4 are turned on, synchronous rectification is performed.

On the other hand, the voltage of the AC power supply V3 is applied to the winding N1 through the switches SW11, SW12, SW21, and SW22, the boost inductors L1 and L2, and the resonant capacitor Cr. The switching element S2 is in an off state, and the voltage generated in the winding N21 is applied to the DC power source V2 through the diode DS1 and the smoothing inductor L, and supplies energy to the DC power source V2. At this time, when the switching element S1 is turned on, synchronous rectification is performed.

When the switching elements H2 and H3 are turned on again, the diode D is turned off, and the operation returns to the mode a. At this time, the diode D is prevented from flowing back to the switching elements H1 to H4 by the DC power source V1.

As described above, when the voltage of the AC power supply V3 is positive toward the connection point of the switching elements H1 and H2, the modes a and b are repeated, and the switching elements H2 and H3 are turned on and off. In the case where the voltage of the AC power source V3 is reversed, the switching elements H1 and H4 may be turned on and off.

In the charging operation 1, it is conceivable that the switching frequency of the switching elements H1 to H4 is passed through the resonant capacitor Cr, and the commercial frequency of the AC power supply V3 is prevented, thereby preventing the magnetic saturation of the transformer 2.

(Charging action 2)

FIGS. 5A and 5B are diagrams for explaining the charging operation 2 of the power supply device shown in FIG. 2 (only the AC power supply V3 transmits power to the DC power supply V1). In the charging operation 2, the switches SW11 and SW12 are different in the off state as compared with the charging operation 1. Thereby, the application of the voltage to the winding N1 and the supply of the power to the DC power supply V2 are different from the charging operation 1. The operation of supplying electric power to the DC power supply V1 by the AC power supply V3 is the same as the charging operation 1.

As described above, in the power supply device shown in FIG. 2, when the charging operation 1 and 2 are performed, the diode D is prevented from flowing back to the switching elements H1 to H4 by the DC power supply V1, so that the switching element H1 to H1 can be performed. The operation of all the H4 is turned on, or the high-voltage MOSFET and its internal diode are used as the switching elements H1 to H4 and the diodes DH1 to DH4 to perform efficient operation.

As described above, the power supply device (second drawing) of the second embodiment can simultaneously charge the DC power supply V1 and the DC power supply V2 by using the energy of the AC power supply V3. At this time, whether or not the power is supplied to the DC power source V2 can be selected by the control of the switches SW11 and SW12. Further, if the switches SW21 and SW22 are turned off, power can be received between the DC power sources V1 and V2.

Further, in the power supply device shown in Fig. 2, the resonant inductor Lr may be inserted in series with the winding N1.

Further, in the example of the figure, the conversion circuits 11 and 12 are formed as a combination of a voltage type full bridge circuit and a current type intermediate tap circuit, but may be formed as a voltage type intermediate tap circuit or a current type full bridge circuit or multiple times. A combination of stream circuits.

[Third embodiment]

Fig. 6 is a view showing a power supply device of a third embodiment. The power supply device omits the diode D and the switch SW0, and the switching elements H1 and H3 are formed as switching elements H11 and H13, which will be described later, in comparison with the power supply device according to the second embodiment shown in FIG. Different.

In the power supply device shown in Fig. 6, for the switching elements H11 and H13 and the diodes DH1 and DH3, for example, a IGBT and a diode having a relatively fast reverse recovery characteristic are used. Further, in the case of the switching elements H2, H4, the diodes DH2, and DH4, an element having a fast switching characteristic such as a high withstand voltage MOSFET and an in-line diode thereof are used.

Next, the operation of the power supply device shown in Fig. 6 will be described. First, the step-down operation is the same as that of the power supply unit shown in Fig. 2.

Fig. 7A and Fig. 7B are diagrams for explaining the charging operation 1 of the power supply device shown in Fig. 6. Among them, the 7A and 7B drawings indicate modes a and b, respectively.

As shown in FIGS. 7A and 7B, the charging operation 1 of the power supply device shown in FIG. 6 (the power is transmitted from the AC power supply V3 to the DC power supply V1 and the DC power supply V2), as shown in FIGS. 4A and 4B. In the charging operation 1 of the power supply device according to the second embodiment, the period of the mode a is different. That is, in FIG. 4A, the switching element H3 is turned on and the current flows through the diode DH1 and the switching element H3, but in FIG. 7A, the switching element H13 is turned off and the diode DH1 and the switching element are turned off. H13 has no current flowing.

As shown in Fig. 7B, the operation when the switching element H2 is turned off in the mode b is the same as the operation of the mode b in Fig. 4B.

In the mode b shown in Fig. 7B, if the switching element H2 is turned on again, the diode DH1 is turned off, and the mode a is returned. At this time, in FIGS. 4A and 4B, although the diode D is prevented from flowing back power to the switching elements H1 to H4 by the DC power source V1, the diode DH1 prevents the diode DH1 in FIGS. 7A and 7B. Countercurrent, it is different at this point.

The charging operation 2 of the power supply device shown in Fig. 6 (only the AC power supply V3 transmits power to the DC power supply V1) is turned off by the switches SW11 and SW12 in the same manner as the charging operation 2 of the power supply device shown in Fig. 2 Broken, and the power supply to the DC power supply V2 is not supplied.

As described above, in the power supply device shown in Fig. 6, by using the elements having a relatively fast reverse recovery characteristic as the diodes DH1 and DH3, the second of the power supply devices shown in Figs. 1 and 2 can be omitted. Polar body D and switch SW0.

As described above, in the present embodiment, since the elements having high switching characteristics are used as the switching elements H2 and H4, the switching loss is small, and the conduction loss of the diode D can be reduced, and a highly efficient charging operation can be performed. . Of course, the same operation can be performed even if other types of elements are used as the switching elements H2, H4, or the switching elements H1, H3 and the switching elements H2, H4 are exchanged.

Further, in the present embodiment, the DC power of the DC power source V1 can be converted into AC power, and the power can be supplied to the AC power source V3. In this case, for example, while the current flowing through the boosting inductor L1 to the AC power supply V3, the switching element H11 and the switching element H4 are turned on and off while the switching element H11 is kept in the ON state. While the voltage is flowing through the AC power supply V3, the switching element H13 is kept in the ON state, and the switching element H11 and the switching element H2 are complementarily turned on and off. At this time, the presence or absence of power supply to the DC power source V2 can be selected by the control of the switches SW11 and SW12.

[Fourth embodiment]

Fig. 8 is a view for explaining a fourth embodiment. In Fig. 8, the power supply device 100 of the present invention is employed as the power supply system of the electric vehicle 111. The power supply device 100 is connected to an auxiliary battery 106 to which the electrical equipment 101 is connected, and a main battery 105 to which a DC-DC converter 102 for supplying power to the inverter 103 for driving the power motor 104 is connected, And a plug-in charging connector 108. Further, the main battery 105 is connected to the rapid charging connector 107, and the main battery 105 is charged by connecting an external DC power source such as a rapid charger.

The power supply device 100 is electrically connected between the main battery 105 and the auxiliary battery 106. Further, the power of the AC power source 109 connected to the plug-in charging connector 108 is supplied to the main battery 105 and the auxiliary battery 106. Further, the power of the main battery 105 is supplied to the alternating current power source 109. Of course, if the AC load 110 is connected to the plug-in charging connector 108, the power of the main battery 105 can be supplied to the AC load 110.

Fig. 9 is a view showing an example in which a double current circuit is used as the second conversion circuit.

As described above, according to the embodiment of the present invention, the main battery can be efficiently charged by the commercial power source while suppressing an increase in the weight of the vehicle (the weight of the power supply device). In addition, by using an element having a faster switching characteristic as a MOSFET as a switching element, the switching loss can be reduced, and the battery can be charged to the battery with high efficiency by a commercial power source.

1, 2. . . transformer

10. . . Control means

11,12. . . Conversion circuit

21, 22, 23. . . Voltage sensor

31, 32, 33. . . Current sensor

V1, V2. . . DC power supply

V3. . . AC power

R1, R2. . . load

C1, C2. . . Smoothing capacitor

L. . . Smoothing inductor

L1, L2. . . Boost inductor

Lr. . . Resonant inductor

Cr. . . Resonant capacitor

N1, N2, N21, N22. . . Winding

SW0, SW11, SW12, SW21, SW22. . . switch

H1～H4, H11, H13, S1, S2. . . Switching element

D, DH1 ~ DH4, DS1, DS2. . . Dipole

100. . . Power supply unit

101. . . Denso machine

102. . . DC-DC converter

103. . . Inverter

104. . . Power motor

105. . . Main battery

106. . . Auxiliary battery

107. . . Rapid charging connector

108. . . Plug-in charging connector

109. . . AC power

110. . . AC load

111. . . electric car

Fig. 1 is a view showing a circuit configuration of a power supply device according to a first embodiment.

Fig. 2 is a view showing a circuit configuration of a power supply device according to a second embodiment.

Fig. 3A is a view for explaining the step-down operation (mode a) of the power supply device shown in Fig. 2.

Fig. 3B is a view for explaining the step-down operation (mode b) of the power supply device shown in Fig. 2.

Fig. 3C is a view for explaining the step-down operation (mode c) of the power supply device shown in Fig. 2.

Fig. 3D is a view for explaining the step-down operation (mode d) of the power supply device shown in Fig. 2.

Fig. 3E is a view for explaining the step-down operation (mode e) of the power supply device shown in Fig. 2.

Fig. 4A is a view for explaining the charging operation 1 (mode a) of the power supply device shown in Fig. 2.

Fig. 4B is a view for explaining the charging operation 1 (mode b) of the power supply device shown in Fig. 2.

Fig. 5A is a view for explaining the charging operation 2 (mode a) of the power supply device shown in Fig. 2.

Fig. 5B is a view for explaining the charging operation 2 (mode b) of the power supply device shown in Fig. 2.

Fig. 6 is a view showing a power supply device of a third embodiment.

Fig. 7A is a view for explaining the charging operation 1 (mode a) of the power supply device shown in Fig. 6.

Fig. 7B is a view for explaining the charging operation 1 (mode b) of the power supply device shown in Fig. 6.

Fig. 8 is a view for explaining a fourth embodiment.

Fig. 9 is a view showing an example in which a double current circuit is used as the second conversion circuit.

1. . . transformer

10. . . Control means

11,12. . . Conversion circuit

21, 22, 23. . . Voltage sensor

31, 32, 33. . . Current sensor

V1, V2. . . DC power supply

V3. . . AC power

R1, R2. . . load

C1, C2. . . Smoothing capacitor

L1, L2. . . Boost inductor

Cr. . . Resonant capacitor

N1, N2. . . Winding

SW0, SW11, SW12, SW21, SW22. . . switch

D. . . Dipole

Claims (20)

A power supply device comprising: a first conversion circuit having a first DC power supply connected to a DC side terminal thereof, a primary winding of a transformer connected to an AC side terminal thereof, and a second conversion circuit having an AC side terminal thereof a secondary winding to which the transformer is connected, a second DC power supply connected to the DC side terminal thereof, and a control circuit that opens and closes the switching elements constituting the first and second conversion circuits, and supplies the first conversion to the first conversion The AC power of the AC side terminal of the circuit is supplied to the first or second DC power source. The power supply device of claim 1, wherein the resonant capacitor is inserted in series with the primary winding of the transformer. The power supply device according to claim 1, wherein the first switch that opens and closes between the AC side terminal of the first conversion circuit and the primary winding of the transformer is supplied to the first conversion When the AC power of the AC side terminal of the circuit is supplied to the first DC power source, the first switch is opened. The power supply device of the first aspect of the invention, wherein the first converter circuit is inserted between the DC-side terminal of the first converter circuit and the first DC power source, and the first DC power source is charged. The parallel circuit of the pole body and the second switch turns on the second open circuit when the first DC power source supplies power to the second DC power source. A power supply device according to claim 1, wherein a boosting inductor is inserted between an AC side terminal of the first converter circuit and an AC power source connected to the AC side terminal. The power supply device according to claim 1, wherein the control circuit includes a power factor improvement control means for controlling a current supplied to an AC power source of the AC side terminal of the first conversion circuit to be sinusoidal. The power supply device according to claim 1, wherein the first conversion circuit includes: a first switching pin that connects the first and second switching elements in series; and the third and fourth switching elements a second switching pin connected in series with the first switching pin, wherein both ends of the first switching pin are DC-side terminals, and a series connection point of the first and second switching elements is The series connection point of the third and fourth switching elements is a full bridge circuit of the AC side terminal. The power supply device according to claim 1, wherein the second conversion circuit includes: a smoothing inductor; a third switching pin that connects the fifth and sixth switching elements in series; and the seventh and the third a switching element is connected in series, and a fourth switching pin connected in parallel with the third switching pin is connected to one end of the smoothing inductor at one end of the third switching pin, and the smoothing inductor is The other end is the DC-side terminal between the other end of the third switching pin, and the series connection point of the series connection point of the fifth and sixth switching elements and the seventh and eighth switching elements is used as an AC side terminal. Full bridge circuit. The power supply device according to claim 1, wherein the secondary winding system includes a connection body of one end of the first secondary winding and one end of the second secondary winding, and the second conversion circuit is provided with a smoothing inductor, and fifth and sixth switching elements, wherein one end of the fifth switching element is connected to the other end of the first secondary winding, and the sixth switching element is connected to the other end of the second secondary winding One end of the fifth switching element is connected to the other end of the sixth switching element, and one end of the smoothing inductor is connected to a connection point of the first and second secondary windings to smooth the smoothing A connection point between the other end of the inductor and the fifth and sixth switching elements is used as a center tap circuit of the DC side terminal. The power supply device according to claim 1, wherein the second conversion circuit includes: a connection body of one end of the first smoothing inductor and one end of the second smoothing inductor; and a fifth switching element a connection body having one end and one end of the sixth switching element, the other end of the fifth switching element being connected to the other end of the first smoothing inductor, and the other end of the sixth switching element being connected to the second smoothing inductor At the other end, the other end of the fifth switching element and the other end of the sixth switching element are used as an AC side terminal, and the connection point between the first smoothing inductor and the fifth and sixth switching elements are connected. The point is used as a double current circuit of the DC side terminal. A power supply device according to claim 7 is characterized in that the anti-parallel diode connected to each of the first to fourth switching elements is connected in anti-parallel. A power supply device according to claim 7, wherein a snubber capacitor connected in parallel to each of the first to fourth switching elements is provided. The power supply device of claim 3, wherein the first open relationship is formed as an electromagnetic relay. The power supply device of claim 3, wherein the first open relationship is formed as a semiconductor switching element. The power supply device of claim 7, wherein the first to fourth switching elements are formed as MOSFETs. The power supply device of claim 7, wherein the two poles are compared with the in-line diodes of the first to fourth switching elements or the anti-parallel diodes connected in anti-parallel with the respective switching elements. The reverse response feature of the system is faster. The power supply device of claim 7, wherein the first and third switching elements are formed as IGBTs, and the second and fourth switching elements are formed as MOSFETs. The power supply device of claim 3, wherein the control circuit turns on the first switch when the voltage of the second DC power source is lower than a first predetermined value, and when the voltage ratio of the second DC power source is higher than When the second predetermined value of the first predetermined value is higher, the first switch is turned off. The power supply device of claim 1, wherein the first direct current power source supplies electric power to the alternating current power source. A vehicle characterized by being equipped with a power supply device as claimed in claim 1.