JP5412515B2 - Power supply - Google Patents

Description

  The present invention relates to a power supply device, and more particularly to a power supply device including a power supply that can be charged from an external power supply.

  In recent years, high-efficiency hybrid vehicles have been spreading due to the growing awareness of global environmental conservation. The hybrid vehicle includes a main battery for driving the traction motor and an auxiliary battery for driving the auxiliary machinery. If these batteries are charged from a commercial AC power source, the fuel efficiency of the hybrid vehicle can be improved.

  However, if a charging device that converts a commercial power supply voltage into a DC voltage that can be charged by a battery is installed in the vehicle, the vehicle weight increases.

  Therefore, in Patent Document 1, when the battery is charged, an existing facility (inverter) that is not in operation is used as a part of the charger, so that the battery is mounted using a commercial power source while suppressing an increase in vehicle weight. Shown to charge.

  Patent Documents 2 to 5 disclose power supply apparatuses that charge a battery from a commercial power supply using an inverter.

JP 2007-195336 A Japanese Patent No. 2695083 JP-A-8-228443 JP 2007-318970 A JP 2006-320074 A

  In general, in order to reduce the size and increase the efficiency of a power supply device, it is effective to use a switching element having a fast switching characteristic. However, in the conventional power supply devices disclosed in Patent Documents 1 to 3, in order to reduce the size of the power supply device, the inverter current density is often set high.

  However, the current density can be set high as a switching element, such as an IGBT, but if an element with slow switching characteristics is used, the switching loss increases, and the efficiency of power conversion when charging the battery from the commercial power supply decreases. .

  The present invention has been made in view of these problems, and provides a power supply device capable of charging a mounted battery with high efficiency using a commercial power supply while suppressing an increase in weight.

  In order to solve the above problems, the present invention employs the following means.

A first DC power source is connected to the DC side terminal via a parallel circuit of a diode and a second switch in a direction for charging the first DC power source, and a transformer is connected to the AC side terminal via the first switch. A first conversion circuit to which the primary winding is connected, and a second conversion in which the secondary winding of the transformer is connected to the AC side terminal and the second DC power source is connected to the DC side terminal. A boosting inductor inserted between a circuit, an AC side terminal of the first conversion circuit, and an AC power supply connected to the AC side terminal, and switching constituting the first and second conversion circuits A control circuit for controlling opening and closing of the element is provided, and AC power supplied to the AC side terminal of the first conversion circuit is supplied to the first or second DC power source.

  Since the present invention has the above-described configuration, it is possible to charge a mounted battery with high efficiency using a commercial power supply while suppressing an increase in weight.

It is a figure explaining the circuit structure of the power supply device which concerns on 1st Embodiment. It is a figure explaining the circuit structure of the power supply device which concerns on 2nd Embodiment. It is a figure explaining the pressure | voltage fall operation (mode a) of the power supply device shown in FIG. It is a figure explaining the pressure | voltage fall operation (mode b) of the power supply device shown in FIG. It is a figure explaining the pressure | voltage fall operation (mode c) of the power supply device shown in FIG. It is a figure explaining the pressure | voltage fall operation (mode d) of the power supply device shown in FIG. It is a figure explaining the pressure | voltage fall operation (mode e) of the power supply device shown in FIG. It is a figure explaining the charge operation 1 (mode a) of the power supply device shown in FIG. It is a figure explaining the charge operation 1 (mode b) of the power supply device shown in FIG. It is a figure explaining the charge operation 2 (mode a) of the power supply device shown in FIG. It is a figure explaining the charge operation 2 (mode b) of the power supply device shown in FIG. It is a figure explaining the power supply device which concerns on 3rd Embodiment. It is a figure explaining the charge operation 1 (mode a) of the power supply device shown in FIG. It is a figure explaining the charge operation 1 (mode b) of the power supply device shown in FIG. It is a figure explaining 4th Embodiment. It is a figure which shows the example which used the current doubler circuit as a 2nd conversion circuit.

  Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings. In this specification, the operation of transmitting power from the DC power source V1 to the DC power source V2 is referred to as a step-down operation, and the operation of transmitting power from the DC power source V2 to the DC power source V1 is referred to as a boost operation. The operation of transmitting power from the AC power supply V3 to the DC power supply V1 and the DC power supply V2 is referred to as charging operation 1, and the operation of transmitting power from the AC power supply V3 to the DC power supply V1 and not transmitting power to the DC power supply V2 is charging operation. 2 is called.

[First Embodiment]
FIG. 1 is a diagram illustrating a circuit configuration of the power supply device according to the first embodiment of the present invention. The power supply device shown in FIG. 1 is connected to a DC power supply V1 to which a load R1 is connected, a DC power supply V2 to which a load R2 is connected, and an AC power supply V3, and transfers power between the DC power supplies V1 and V2. The DC power sources V1 and V2 are charged from the AC power source V3.

  In FIG. 1, the smoothing capacitor C1 is connected to the DC power source V1, and the smoothing capacitor C2 is connected to the DC power source V2. The DC terminal of the conversion circuit 11 is connected to the smoothing capacitor C1 via the diode D. The diode D is connected in such a direction that power flows from the conversion circuit 11 to the DC power supply V1, and conversely no power flows from the DC power supply V1 to the conversion circuit 11, and the switch SW0 is connected in parallel to the diode D. . The DC terminal of the circuit 12 is connected to the smoothing capacitor C2.

  A winding N1 is connected to the AC terminal of the conversion circuit 11 via switches SW11 and SW12 and a resonance capacitor Cr, and an AC power supply V3 is connected via boost inductors L1 and L2 and switches SW21 and SW22. . A winding N <b> 2 is connected to the AC terminal of the conversion circuit 12. The transformer 1 magnetically couples the winding N1 and the winding N2.

  The conversion circuits 11 and 12 and the switches SW0, SW11, SW12, SW21, and SW22 are controlled by the control means 10. Voltage sensors 21, 22 and 23 and current sensors 31, 32 and 33 are connected to the control means 10.

  Here, the step-down operation of the power supply device shown in FIG. 1 will be described. During the step-down operation, the switches SW0, SW11, and SW12 are kept on, and the switches SW21 and SW22 are kept off. Since both ends of the diode D are short-circuited, the DC terminal of the conversion circuit 11 is in the same state as when directly connected to the smoothing capacitor C1 without passing through the diode D. The control means 10 switches the conversion circuit 11 while applying the switches SW0, SW11, and SW12 to the on state and the switches SW21 and SW22 to the off state, and applies an alternating voltage to the winding N1. The conversion circuit 12 rectifies the induced voltage generated in the winding N2 and supplies power to the DC power supply V2.

  Next, the boosting operation of the power supply device shown in FIG. 1 will be described. During the step-up operation, the control means 10 switches the conversion circuit 12 while applying the switches SW0, SW21, SW22 to the off state and SW11, SW12 to the on state, and applies an alternating voltage to the winding N2. The conversion circuit 11 rectifies the induced voltage generated in the winding N1 and supplies power to the DC power supply V1.

  Next, charging operation 1 (power transmission from AC power supply V3 to DC power supply V1 and DC power supply V2) of the power supply device shown in FIG. 1 will be described. During the charging operation 1, the switch SW0 is turned off, and SW11, SW12, SW21, and SW22 are kept on. The converter circuit 11 is switched to repeatedly store and release the energy of the AC power supply V3 to the boost inductors L1 and L2, supply power to the DC power supply V1, and apply an AC voltage to the winding N1. The conversion circuit 12 rectifies the induced voltage generated in the winding N2 and supplies power to the DC power supply V2.

  Next, the charging operation 2 (power transmission only from the AC power supply V3 to the DC power supply V1) of the power supply device shown in FIG. 1 will be described. During the charging operation 2, the switches SW0, SW11, and SW12 are kept off, and SW21 and SW22 are kept on. Similar to the charging operation 1, the conversion circuit 11 is switched to supply power to the DC power supply V1. Since the switches SW11 and SW12 are in the off state, no voltage is applied to the winding N1, and no power is supplied to the DC power supply V2.

  In the charging operations 1 and 2, by switching the circuit 11 so that the input current from the AC power source V3 detected by the current sensor 33 has the same waveform as the voltage of the AC power source V3 detected by the voltage sensor 23, The power factor of input power can be increased.

  In the boosting operation and the charging operations 1 and 2, even if an element having a relatively slow reverse recovery characteristic such as a body diode (parasitic diode) of a high voltage MOSFET is used as the rectifying element constituting the conversion circuit 11, the reverse recovery characteristic is obtained. Since the relatively fast diode D prevents the backflow of power from the DC power source V1 or the smoothing capacitor C1 to the conversion circuit 11, efficient power transmission is possible.

  Since the switch SW0 is switched between an on state and an off state only when the operation is switched, a relatively slow IGBT or a mechanical switch such as an electromagnetic relay can be used. When an IGBT is used, using a package with a built-in antiparallel diode eliminates the need for externally attaching the diode D, which is advantageous for downsizing. If a mechanical switch is used, since the conduction loss is small, more efficient power transmission becomes possible. Of course, when an element having a relatively fast reverse recovery characteristic is used as the rectifying element constituting the conversion circuit 11, the diode D and the switch SW0 are unnecessary, and the DC terminal of the conversion circuit 11 is directly connected to the smoothing capacitor C1. May be.

[Second Embodiment]
FIG. 2 is a diagram illustrating a circuit configuration of a power supply device according to the second embodiment of the present invention. The power supply device shown in FIG. 2 is connected to a DC power supply V1 to which a load R1 is connected, a DC power supply V2 to which a load R2 is connected, and an AC power supply V3, and transfers power between the DC power supplies V1 and V2. The DC power sources V1 and V2 are charged from the AC power source V3.

  In FIG. 2, the smoothing capacitor C1 is connected to the DC power source V1, and the smoothing capacitor C2 is connected to the DC power source V2. The first switching leg in which the switching elements H1 and H2 are connected in series is connected to the smoothing capacitor C1 through the diode D. The diode D is connected in such a direction that power flows from the first switching leg to the DC power supply V1, and conversely, no power flows from the DC power supply V1 to the first switching leg. It is connected. The second switching leg in which the switching elements H3 and H4 are connected in series is connected in parallel to the first switching leg.

  The switches SW11 and SW12, the resonance capacitor Cr, and the winding N1 are connected in series via the resonance inductor Lr between the series connection point of the switching elements H1 and H2 and the series connection point of the switching elements H3 and H4. In addition, switches SW21 and SW22, boost inductors L1 and L2, and an AC power supply V3 are connected in series.

  The transformer 2 magnetically couples the windings N1, N21, and N22. One end of the winding N21 and one end of the winding N22 are connected, the other end of the winding N21 is connected to one end of the switching element S1, and the other end of the winding N22 is connected to one end of the switching element S2. The other end of the switching element S1 and the other end of the switching element S2 are connected to one end of the smoothing capacitor C2. A connection point between the windings N21 and N22 is connected to the other end of the smoothing capacitor C2 via the smoothing inductor L.

  Antiparallel diodes DH1 to DH4, DS1 and DS2 are connected to the switching elements H1 to H4, S1 and S2, respectively. Here, when MOSFETs are used as these switching elements, MOSFET body diodes can be used as antiparallel diodes. A snubber capacitor can be connected in parallel to each of the switching elements.

  The switching elements H1 to H4, S1, and S2 and the switches SW0, SW11, SW12, SW21, and SW22 are controlled by the control unit 10. Voltage sensors 21, 22 and 23 and current sensors 31, 32 and 33 are connected to the control means 10.

(Step-down operation)
3A to 3E are diagrams for explaining the step-down operation of the power supply device shown in FIG. Hereinafter, the step-down operation will be described in detail with reference to FIGS. 3A to 3E. However, FIGS. 3A to 3E represent modes a to e, respectively.

(Mode a)
First, in mode a, the switches SW0, SW11, SW12, the switching elements H1, H4 are on, the switches SW21, SW22, the switching elements H2, H3 are off, and the voltage of the DC power supply V1 is It is applied to winding N1 via SW12, switching elements H1, H4, resonant inductor Lr, and resonant capacitor Cr.

  The switching element S2 is in an off state, and the voltage generated in the winding N21 is applied to the DC power source V2 via the diode DS1 and the smoothing inductor L, and energy is supplied to the DC power source V2. At this time, in the case where MOSFETs are used as the switching elements S1 and S2, if the switching element S1 is turned on, the loss may be reduced by dividing the current flowing through the diode DS1 to the switching element S1. In this way, when the forward current of the diode flows through the diode connected in reverse parallel to the MOSFET or the body diode of the MOSFET, the reduction of the loss by turning on the MOSFET is hereinafter referred to as synchronous rectification.

(Mode b)
When the switching element H4 is turned off, the current flowing through the switching element H4, the DC power supply V1, and the switch SW0 is commutated to the diode DH3. At this time, the switching element H3 is turned on. The energy stored in the smoothing inductor L is supplied to the DC power source V2.

(Mode c)
When the switching element H1 is turned off, the current flowing through the switching element H1 is commutated to the switch SW0 and / or the diode D, the DC power supply V1, and the diode DH2. At this time, the switching element H2 is turned on. The voltage of the DC power supply V1 is applied to the resonant inductor Lr, and this current decreases. As a result, the current passing through the diode DS1 and the winding N21 decreases, and the current flows through the diode DS2 and the winding N22. At this time, if the switching element S2 is turned on, synchronous rectification occurs.

(Mode d)
Since the switching elements H2 and H3 are on, the current increases in the opposite direction after the current of the resonant inductor Lr reaches zero. Before the current flowing through the winding N21 reaches zero, the switching element S1 is turned off.

(Mode e)
When the current through the winding N21 reaches zero, the voltage generated in the winding N22 is applied to the DC power source V2 via the diode DS2 and the smoothing inductor L, and energy is supplied to the DC power source V2.

  This mode e is a symmetrical operation of mode a. Thereafter, the mode b returns to the mode a after the symmetrical operation of the modes b to d.

(Charging operation 1)
4A and 4B are diagrams for explaining the charging operation 1 (power transmission from the AC power supply V3 to the DC power supply V1 and the DC power supply V2) of the power supply device shown in FIG. Hereinafter, the charging operation 1 will be described in detail with reference to FIGS. 4A and 4B. However, FIGS. 4A and 4B represent modes a and b, respectively. The period when the voltage of the AC power supply V3 is directed to the connection point of the switching elements H1 and H2 will be described.

(Mode a)
First, in mode a, the switches SW11, SW12, SW21, SW22, the switching elements H2, H3 are in the on state, the switch SW0 is in the off state, and the voltage of the AC power supply V3 is the switches SW21, SW22, the switching elements H2, H3, Applied to the boost inductors L1 and L2 via the diodes DH1 and DH4 and the resonant inductor Lr, the energy of the AC power supply V3 is accumulated in the boost inductors L1 and L2. At this time, if the switching elements H1 and H4 are turned on, synchronous rectification is performed.

  On the other hand, the voltage of the resonance capacitor Cr is applied to the winding N1 via the switches SW11 and SW12, the switching elements H2 and H3, the diodes DH1 and DH4, and the resonance inductor Lr. The switching element S1 is in an off state, and the voltage generated in the winding N22 is applied to the DC power source V2 via the diode DS2 and the smoothing inductor L, and energy is supplied to the DC power source V2. At this time, if the switching element S2 is turned on, synchronous rectification occurs.

(Mode b)
When the switching elements H2 and H3 are turned off, the current flowing through the switching elements H2 and H3 is commutated to the diode D and the DC power source V1, and the boost inductors L1 and L2 release the stored energy, and the DC power source V1 is discharged. Energy is supplied. Similar to mode a, synchronous rectification is performed when switching elements H1 and H4 are turned on.

  On the other hand, the voltage of the AC power supply V3 is applied to the winding N1 via the switches SW11, SW12, SW21, SW22, the boost inductors L1, L2, and the resonance capacitor Cr. The switching element S2 is in an off state, and the voltage generated in the winding N21 is applied to the DC power source V2 via the diode DS1 and the smoothing inductor L, and energy is supplied to the DC power source V2. At this time, if the switching element S1 is turned on, synchronous rectification occurs.

  When the switching elements H2 and H3 are turned on again, the diode D is turned off and the operation returns to the mode a. At this time, the diode D prevents power backflow from the DC power supply V1 to the switching elements H1 to H4.

  As described above, when the voltage of the AC power supply V3 is more positive when it is directed to the connection point of the switching elements H1 and H2, the modes a and b are repeated to turn the switching elements H2 and H3 on and off. Note that the switching elements H1 and H4 may be turned on and off during the period in which the voltage of the AC power supply V3 is reversed.

  In this charging operation 1, the resonance capacitor Cr may be considered to block the commercial frequency of the AC power supply V3 and prevent the magnetic saturation of the transformer 2 while allowing the switching frequency of the switching elements H1 to H4 to pass.

(Charging operation 2)
5A and 5B are diagrams for explaining the charging operation 2 (power transmission only from the AC power supply V3 to the DC power supply V1) of the power supply device shown in FIG. The charging operation 2 is different from the charging operation 1 in that the switches SW11 and SW12 are in an off state. This is different from the charging operation 1 in that voltage application to the winding N1 is blocked and power is not supplied to the DC power supply V2. The operation of supplying power from the AC power supply V3 to the DC power supply V1 is the same as the charging operation 1.

  In this way, in the power supply device shown in FIG. 2, the diode D prevents the power from flowing back from the DC power supply V1 to the switching elements H1 to H4 during the charging operations 1 and 2, so that the switching elements H1 to H4 are all turned on. As the switching elements H1 to H4 and the diodes DH1 to DH4, for example, high voltage MOSFETs and their body diodes can be used, and efficient operation is possible.

  As described above, the power supply apparatus (FIG. 2) according to the second embodiment can charge the DC power supply V1 and the DC power supply V2 at the same time using the energy of the AC power supply V3. At this time, whether or not power is supplied to the DC power supply V2 can be selected by controlling the switches SW11 and SW12. Further, when the switches SW21 and SW22 are turned off, power can be exchanged between the DC power sources V1 and V2.

  In the power supply device shown in FIG. 2, the resonant inductor Lr may be inserted in series with the winding N1.

  In the example of this figure, the conversion circuits 11 and 12 are a combination of a voltage type full bridge circuit and a current type center tap circuit, but may be a combination of a voltage type center tap circuit, a current type full bridge circuit, or a current doubler circuit. Good.

[Third Embodiment]
FIG. 6 is a diagram for explaining a power supply device according to the third embodiment. This power supply apparatus is different from the power supply apparatus according to the second embodiment shown in FIG. 2 in that the diode D and the switch SW0 are omitted and the switching elements H1 and H3 are replaced with switching elements H11 and H13 described later.

  In the power supply device shown in FIG. 6, as the switching elements H11 and H13 and the diodes DH1 and DH3, for example, IGBTs and diodes having relatively fast reverse recovery characteristics are used. Further, as the switching elements H2 and H4 and the diodes DH2 and DH4, for example, an element having a fast switching characteristic such as a high breakdown voltage MOSFET and its body diode are used.

  Next, the operation of the power supply device shown in FIG. 6 will be described. First, the step-down operation is the same as that of the power supply device shown in FIG.

  7A and 7B are diagrams for explaining the charging operation 1 of the power supply device shown in FIG. However, FIGS. 7A and 7B represent modes a and b, respectively.

  As shown in FIGS. 7A and 7B, the charging operation 1 (power transmission from the AC power supply V3 to the DC power supply V1 and the DC power supply V2) of the power supply device shown in FIG. 6 is performed in the second embodiment shown in FIGS. 4A and 4B. Compared with the charging operation 1 of the power supply device according to the embodiment, it differs in the period of mode a. That is, in FIG. 4A, the switching element H3 is turned on and a current flows through the diode DH1 and the switching element H3, but in FIG. 7A, the switching element H13 is turned off and no current flows through the diode DH1 and the switching element H13. .

  As shown in FIG. 7B, the operation when the switching element H2 is turned off in mode b is the same as the operation in mode b in FIG. 4B.

  In the mode b shown in FIG. 7B, when the switching element H2 is turned on again, the diode DH1 is turned off and the operation returns to the mode a. At this time, in FIG. 4A and FIG. 4B, the diode D prevented the backflow of power from the DC power supply V1 to the switching elements H1 to H4, but the point that the diode DH1 prevents this backflow is different in FIG. 7A and FIG.

  The charging operation 2 (power transmission only from the AC power supply V3 to the DC power supply V1) shown in FIG. 6 is performed by turning off the switches SW11 and SW12 in the same manner as the charging operation 2 of the power supply device shown in FIG. The power is not supplied to V2.

  As described above, in the power supply device shown in FIG. 6, the diode D and the switch SW0 in the power supply device shown in FIGS. 1 and 2 can be omitted by using elements having relatively fast reverse recovery characteristics as the diodes DH1 and DH3. .

  As described above, in this embodiment, since the switching elements H2 and H4 are elements having fast switching characteristics, the switching loss is small, and the conduction loss of the diode D can be reduced, and a highly efficient charging operation is possible. It is. Of course, it is natural that the same operation can be performed even if other types of elements are used as the switching elements H2 and H4, or the roles of the switching elements H1 and H3 and the switching elements H2 and H4 are exchanged.

  In the present embodiment, the DC power of the DC power supply V1 can be converted into AC power and supplied to the AC power supply V3. In this case, for example, in a period in which a current flows from the boost inductor L1 to the AC power supply V3, the switching element H13 and the switching element H4 are complementarily turned on and off while the switching element H11 is kept on, and the boost inductor L2 exchanges AC. In the period in which the current flows to the power supply V3, the switching element H11 and the switching element H2 may be turned on and off in a complementary manner while the switching element H13 is kept on. Also in this case, the presence / absence of power supply to the DC power supply V2 can be selected by the control of the switches SW11 and SW12.

[Fourth Embodiment]
FIG. 8 is a diagram for explaining the fourth embodiment. In FIG. 8, the power supply device 100 according to the present invention is adopted as the power supply system of the electric vehicle 111. The power supply apparatus 100 includes an auxiliary battery 106 to which the electrical equipment 101 is connected, a main battery 105 to which a DC-DC converter 102 that supplies power to the inverter 103 that drives the power motor 104 is connected, and a plug-in charging connector 108. And connected to. In addition, a quick charge connector 107 is connected to the main battery 105 in order to charge the main battery 105 by connecting an external DC power source such as a quick charger.

  The power supply apparatus 100 transmits and receives power between the main battery 105 and the supplementary battery 106. In addition, the power of the AC power supply 109 connected to the plug-in charging connector 108 is supplied to the main battery 105 and the supplementary battery 106. Further, the power of the main battery 105 is supplied to the AC power source 109. Of course, if the AC load 110 is connected to the plug-in charging connector 108, the power of the main battery 105 can be supplied to the AC load 110.

  FIG. 9 is a diagram illustrating an example in which a current doubler circuit is used as the second conversion circuit.

  As described above, according to the embodiment of the present invention, the main battery can be charged from the commercial power source with high efficiency while suppressing an increase in vehicle weight (weight of the power supply device). Further, by using an element having a fast switching characteristic such as a MOSFET as the switching element, the switching loss can be reduced and the battery can be charged from the commercial power source with high efficiency.

1, 2 Transformer 10 Control means 11, 12 Conversion circuit 21, 22, 23 Voltage sensor 31, 32, 33 Current sensor V1, V2 DC power supply V3 AC power supply R1, R2 Load C1, C2 Smoothing capacitor L Smoothing inductor L1, L2 Boost Inductor Lr Resonant inductor Cr Resonant capacitor N1, N2, N21, N22 Winding SW0, SW11, SW12, SW21, SW22 Switches H1-H4, H11, H13, S1, S2 Switching elements D, DH1-DH4, DS1, DS2 Diode 100 Power supply device 101 Electrical equipment 102 DC-DC converter 103 Inverter 104 Power motor 105 Main battery 106 Auxiliary battery 107 Quick charge connector 108 Plug-in charge connector 109 AC power supply 110 AC negative 111 Electric power Automobile

Claims (19)

A first DC power source is connected to the DC side terminal via a parallel circuit of a diode and a second switch in a direction for charging the first DC power source, and a transformer is connected to the AC side terminal via the first switch. A first conversion circuit to which a primary winding of
A second conversion circuit in which a secondary winding of the transformer is connected to the AC side terminal, and a second DC power source is connected to the DC side terminal;
A step-up inductor inserted between the AC side terminal of the first conversion circuit and an AC power source connected to the AC side terminal ;
A control circuit for controlling opening and closing of the switching elements constituting the first and second conversion circuits;
A power supply apparatus that supplies AC power supplied to an AC side terminal of the first conversion circuit to the first or second DC power supply. The power supply device according to claim 1, wherein
A power supply device comprising a resonance capacitor inserted in series with a primary winding of the transformer. The power supply device according to claim 1, wherein
A power supply apparatus comprising: opening the first switch when supplying AC power supplied to an AC terminal of the first conversion circuit to the first DC power supply. The power supply device according to claim 1, wherein
A power supply apparatus comprising: closing the second switch when supplying power from the first DC power supply to the second DC power supply. The power supply device according to claim 1, wherein
The power supply apparatus according to claim 1, wherein the control circuit includes power factor correction control means for controlling the current of the AC power source supplied to the AC side terminal of the first conversion circuit in a sine wave form. The power supply device according to claim 1, wherein
The first conversion circuit includes a first switching leg in which first and second switching elements are connected in series, a third switching element and a fourth switching element in series, and a parallel connection to the first switching leg. Second switching legs, both ends of the first switching legs being DC side terminals, and a series connection point of the first and second switching elements and a series of the third and fourth switching elements. A power supply device comprising a full bridge circuit having a connection point as an AC side terminal. The power supply device according to claim 1, wherein
The second conversion circuit includes a smoothing inductor, a third switching leg in which fifth and sixth switching elements are connected in series, a seventh and eighth switching elements in series, and the third switching circuit. A fourth switching leg connected in parallel to the leg, one end of the smoothing inductor is connected to one end of the third switching leg, and the other end of the smoothing inductor and the other end of the third switching leg Between the DC side terminals, and a full bridge circuit in which the series connection point of the fifth and sixth switching elements and the series connection point of the seventh and eighth switching elements are AC side terminals. A featured power supply. The power supply device according to claim 1, wherein
The secondary winding includes a connection body of one end of the first secondary winding and one end of the second secondary winding, and the second conversion circuit includes a smoothing inductor, fifth and sixth Switching element, one end of the fifth switching element is connected to the other end of the first secondary winding, and the other end of the second secondary winding is connected to the sixth switching element. One end is connected, the other end of the fifth switching element is connected to the other end of the sixth switching element, and one end of the smoothing inductor is connected to a connection point of the first and second secondary windings. A power supply apparatus, comprising: a center tap circuit that is connected and has a DC side terminal at the other end of the smoothing inductor and a connection point of the fifth and sixth switching elements. The power supply device according to claim 1, wherein
The second conversion circuit includes a connection body between one end of the first smoothing inductor and one end of the second smoothing inductor, and a connection body between one end of the fifth switching element and one end of the sixth switching element. The other end of the first smoothing inductor is connected to the other end of the fifth switching element, the other end of the second smoothing inductor is connected to the other end of the sixth switching element, The other end of the fifth switching element and the other end of the sixth switching element are AC side terminals, the connection point of the first and second smoothing inductors and the connection point of the fifth and sixth switching elements, A power supply device characterized by being a current doubler circuit having a DC side terminal.   7. The power supply apparatus according to claim 6, further comprising an antiparallel diode connected in antiparallel to each of the first to fourth switching elements.   7. The power supply device according to claim 6, further comprising a snubber capacitor connected in parallel to each of the first to fourth switching elements.   4. The power supply device according to claim 3, wherein the first switch is an electromagnetic relay.   4. The power supply device according to claim 3, wherein the first switch is a semiconductor switching element.   7. The power supply apparatus according to claim 6, wherein the first to fourth switching elements are MOSFETs. 7. The power supply device according to claim 6, wherein the diode in the direction of charging the first DC power supply is a body diode of the first to fourth switching elements or an antiparallel diode connected in antiparallel to each switching element. The power supply device is characterized by a fast reverse recovery characteristic.   7. The power supply device according to claim 6, wherein the first and third switching elements are IGBTs, and the second and fourth switching elements are MOSFETs.   4. The power supply apparatus according to claim 3, wherein the control circuit turns on the first switch when the voltage of the second DC power supply is lower than a first predetermined value, and the second DC power supply. The power supply device is characterized in that the first switch is turned off when the voltage is higher than a second predetermined value higher than the first predetermined value.   The power supply apparatus according to claim 1, wherein power is supplied from the first DC power supply to the AC power supply. The power supply apparatus according to claim 1, wherein the power supply apparatus is mounted on a vehicle .

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