TW201611469A - Charging structure - Google Patents

Abstract

A charging structure including a power supply device, a charging battery and a charging management device are provided. The charging structure is configured to switch the corresponding charging mode according to the voltage level of a positive end of the charging battery and stop charging action when a charging current for charging the charging battery is reduced to a preset current value.

Description

Charging architecture

The present invention relates to a charging architecture, and more particularly to a charging architecture having an analog smoothing conversion circuit and a charge termination circuit.

In this era of green energy technology, electronic products must be connected to the environment, and batteries are no exception, so the charger must master this principle when charging the battery. A battery is used in the frequency of about 500 to 1000 times, and its capacity will be less and less with the number of times of charging and discharging. Further, in the case of a general linear lithium ion charger, due to internal resistance in the battery, when When the system operates between the conversion of each mode, such as a small current conversion current or a constant current conversion voltage mode, if the relevant circuit conversion mechanism is not performed, the oscillation phenomenon occurring during the circuit conversion will be caused, thereby jeopardizing the charging. And battery.

In addition, after the battery is fully charged, if the charger fails to turn off the charging action in time, it will also cause the battery to overcharge, which greatly reduces the battery life. If you do not deliberately do the mechanism to protect the battery, it is easy to the battery. The huge damage caused, on the one hand, the battery capacity is no longer as large as before, on the other hand, the battery replacement rate is also increased, and the excessive battery replacement will also cause garbage problems and environmental pollution. Dyeing and other issues.

The invention provides a charge management device with an analog smooth transition circuit (ASTC) and an end of charge circuit (EOC), which can make the overall charging architecture between the various charging mode transitions. Stable switching to prevent the oscillation effect from harming the circuit. On the other hand, it can instantly judge the charging state of the battery and stop charging, ensuring that the battery will not overcharge.

A charging architecture of the present invention includes: a power supply device, a rechargeable battery, and a charging management device. A power supply device is used to provide a system voltage. The charging management device is configured to switch the corresponding charging mode according to the voltage level of the positive terminal of the rechargeable battery. When the charging current for charging the rechargeable battery drops to a preset current value, the charging operation is terminated.

In an embodiment of the invention, the charging management device includes: a power switch, a smoothing conversion circuit, and a charging termination circuit. The power switch has a first end, a second end and a gate terminal. The first end of the power switch receives the system voltage, and the second end of the power switch is coupled to the positive end of the rechargeable battery to obtain the output voltage level. The smoothing conversion circuit is coupled to the gate terminal of the power switch for adjusting the voltage level of the gate terminal of the power switch according to the voltage level of the output terminal of the second end of the power switch. The charging termination circuit senses the charging current through the second current sensing circuit, and when the charging current drops to a preset current value, starts the charging termination circuit and terminates the charging operation.

In an embodiment of the invention, the smoothing conversion circuit includes: a bias current source, a first current mirror, a second current mirror, a third current mirror, and a first transistor. A bias current source is used to provide a bias current. The first current mirror is coupled to the bias current source for receiving the bias current and providing the first current according to the bias current. The second current mirror is connected in series with the first current mirror. The third current mirror is coupled to the first current mirror and adjusts the first control current according to the first control bias. The first transistor has a first end, a second end, and a gate terminal, the first end of the first transistor receives the system voltage, and the gate terminal of the first transistor receives the second control bias, and according to the second control bias The second control current is adjusted, wherein a current sum between the first control current and the second control current is equal to the first current, and the smoothing conversion circuit adjusts the voltage level of the gate terminal of the power switch according to the current.

In an embodiment of the invention, the charge termination circuit includes: a disconnect current source, a fourth current mirror, a fifth transistor, a fifth current mirror, a sixth current mirror, a second current sensor, and a seventh current mirror. A trip current source is used to provide a reference current. The fourth current mirror receives the reference current to provide a second current in accordance with the reference current. The fifth transistor has a first end, a second end and a gate terminal, the first end of which is coupled to the fourth current mirror, and the gate terminal is coupled to the mode selection circuit for determining the second current according to the level of the set voltage The conduction state of the path. The fifth current mirror is coupled to the second end of the fifth transistor for receiving the second current and generating the third current according to the second current. The sixth current mirror is connected in series with the fifth current mirror for receiving and transmitting the third current. The second current sensor is configured to sense a level of the positive terminal of the rechargeable battery to generate a second sensing current. The seventh current mirror is coupled to the second current sensor for receiving the second sensing current and according to The second sensing current generates a fourth current, wherein the charging termination circuit determines a node voltage level between the sixth current mirror and the seventh current mirror according to a current difference between the third current and the fourth current.

In an embodiment of the invention, the charging termination circuit further includes: an inverter having an input end and an output end, wherein the input end is coupled between the sixth current mirror and the seventh current mirror, and the output thereof is The end is coupled to the sixth transistor for outputting an inverted result according to a node voltage level between the sixth current mirror and the seventh current mirror.

In an embodiment of the invention, the charging management device further includes a sixth transistor (M _C ) having a first end, a second end, and a gate terminal, and the first end of the sixth transistor is coupled to the system voltage The second end of the sixth transistor is coupled to the gate terminal of the power switch, the gate terminal of the sixth transistor is coupled to the charge termination circuit, and the conduction state is determined according to the reverse phase result.

Based on the above, the present invention proposes a charging architecture with a smooth conversion circuit and a charge termination circuit. On the one hand, the present invention realizes continuous output voltage regulation by interleaving the switching mode by the smooth conversion circuit, thereby easing the voltage level of the output terminal and improving the chain. Wave voltage, on the other hand, in this case, the charge termination circuit accurately fills the battery capacity, and directly senses the current through the transistor to reduce the error in the judgment, thereby enabling the charging process to be more accurately turned off. Therefore, the charging structure proposed by the present invention can neither damage the battery nor accurately charge the lithium battery, greatly improving the charging quality and prolonging the life of the battery.

The above described features and advantages of the invention will be apparent from the following description.

10‧‧‧Charging architecture

100‧‧‧Charging management device

102‧‧‧Rechargeable battery

104‧‧‧Power supply unit

110‧‧‧Smooth conversion circuit

112~116‧‧‧current mirror

120‧‧‧ mode selection circuit

122, 124‧‧‧Voltage comparator

130‧‧‧Charging termination circuit

131~134‧‧‧current mirror

135, 140‧‧‧ current sensor

136‧‧‧Inverter

M _P ‧‧‧Power switch

M1~M4, M _CAP1 , M _CAP2 , M _P1 ~M _P4 , M _N1 ~M _N4 , M _EN , M _E , M _EOC , M _F , M _S , M _C , M _D , M _VA , M _L , M _N ‧‧‧O crystal

Vc‧‧‧ node voltage

Vdd‧‧‧ system voltage

Vss‧‧‧ Grounding voltage

Vo‧‧‧ output voltage

V _G ‧‧‧ gate voltage

Vset‧‧‧Set voltage

V _eoc ‧‧‧Control bias

Vcom, VI, Vref‧‧‧ reference voltage

R _sen ‧‧‧resistance resistor

R _set1 , R _set2 , R _{set3 ‧‧‧Set} resistor

R _fb1 , R _fb2 ‧‧ ‧ voltage divider resistor

I1, I2, I3, I4, I _H , I _L ‧‧‧ current

I _CC , I _CV ‧‧‧Control current

ID1, ID2‧‧‧ sense current

I _cut-off ‧‧‧break current source

I _BIAS ‧‧‧ bias current source

t _cut-off ‧‧‧ deadline

V _L , V _n ‧‧‧Preset voltage level

V _STOP ‧‧‧voltage level

Asen‧‧‧Voltage Comparator

Acc, Acv‧‧‧ error amplifier

1 is a waveform diagram of a charging flow of a charge management device according to an embodiment of the present invention.

2 is a circuit diagram of a charge management device according to an embodiment of the present invention.

3 is a block diagram of a charging architecture in accordance with an embodiment of the present invention.

The exemplary embodiments of the present disclosure will now be described in detail with reference to the accompanying drawings. In addition, wherever possible, the elements and/

First, FIG. 3 is a block diagram of a charging architecture according to an embodiment of the present invention. Referring to FIG. 3 , the charging architecture 10 includes a power supply device 104 , a charging management device 100 , and a rechargeable battery 102 . In the present embodiment, the power supply device 104 may be a charger having at least a power output function, a mobile power source, or a fuel cell module, etc., but is not limited thereto. In addition, the charge management device 100 and the rechargeable battery 102 may be disposed in different types of terminal devices, such as electric vehicles or handheld devices (eg, smart phones, tablets, etc.), but are not limited thereto.

In this embodiment, when the charging battery is connected to the power supply device 104 when there is a charging demand, the charging management device 100 is based on the positive charging battery 102. The extreme voltage level adjusts the corresponding charging mode, and when the charging current for charging the rechargeable battery 102 drops to the preset current value, the charging management device 100 terminates the charging operation. In the embodiment, the rechargeable battery may be a lithium battery, but is not limited thereto.

1 is a waveform diagram of a charging flow of a charge management device according to an embodiment of the present invention. Please refer to FIG. 1 and FIG. 3 simultaneously. The constant current (CC) charging mode and the constant voltage (CV) charging mode used in a general lithium battery are the most widely used charging methods today. In the embodiment, the charging management device 100 can be divided into four charging modes for the charging process of the rechargeable battery 102, namely, a small current charging (TC) mode, a CC mode, a CC-CV mode, a CV mode, and a cutoff charging mode. Where the dashed curve represents the battery voltage, the right vertical axis represents the charging voltage, the solid line represents the battery current, the left vertical axis represents the charging current, and the horizontal axis represents the charging time.

In the TC mode, since the battery voltage is low due to overdischarge of the rechargeable battery, the charging management device 100 first charges with a small current, and when the battery voltage level of the rechargeable battery 102 is charged to the preset voltage level V _L , the charging management Device 100 then switches the charging mode to CC mode. It is worth mentioning that, since the charging management device 100 initially charges the battery with a small current, it can avoid charging the battery directly with a large current (or called a constant current), causing the battery temperature to rise or causing the battery to be damaged, thereby achieving charging safety. The effect. In the present embodiment, the switching point of the TC mode to the CC mode, that is, the preset voltage level V _{L is} approximately between 2.8V and 3.2V, but not limited thereto.

Next, in the CC mode, the charge management device 100 charges the rechargeable battery 102 with a constant current _IH . As the battery voltage of the rechargeable battery 102 gradually increases to the preset voltage level V _n , the constant current loop (not shown) in the charge management device 100 gradually fails, and gradually becomes a constant voltage loop in the charge management device 100. Replaced (not shown). In other words, at this time, the charging current of the charging management device 100 for the rechargeable battery 102 gradually decreases as the battery voltage increases, and the charging management device 10 also enters a mixed mode of CC-CV, that is, as shown in FIG. The transition point between CC mode and CV mode. In this embodiment, the preset voltage level Vn _is approximately 4.2V at the voltage of the rechargeable battery, but is not limited thereto.

In addition, it should be noted that the smooth conversion circuit (not shown) in the charging management device 100 adopts the state of interleaving control, switching the CC mode and the CV mode back and forth to stabilize the output voltage of the charging management device 100. Referring to FIG. 2 further, the ripple voltage generated during the mode switching is reduced to achieve a smooth transition effect. Then the circuit gradually enters the CV mode, at which time the output voltage will rise slowly and the charging current will drop rapidly. Finally, when the charging current of the charging management device 100 for charging the rechargeable battery 102 is lower than the breaking current value (for example, I _cut-off ), the charging management device 100 switches from the CV mode to the cut-off charging mode (refer to the rear reference map). 2 for further explanation).

For the sake of clarity, the components in the charging management device 100 of FIGS. 1 and 2 described above are provided below to explain the specific operational flow of the charging management device 100 of the present invention.

2 is a circuit diagram of a charge management device according to an embodiment of the present invention. Referring to FIG. 2, the charging management device 100 includes at least a power switch M _P , an Smooth Smooth Transition Circuit (ASTC) 110 , a mode selection circuit 120 , an End Of Charge Circuit (EOC) 130 , and a current sense. The measuring circuit 140, wherein the first end of the power switch M _P is coupled to the system voltage Vdd, and the second end of the power switch M _P is coupled to the mode selecting circuit 120, the charging termination circuit 130, and the current sensing circuit 140, and the power switch The second end of the M _P can be used as the output voltage terminal of the charging management device 100 , and the gate terminal of the power switch M _P is coupled to the smoothing conversion circuit 110 , the charging termination circuit 130 , and the current sensing circuit 140 .

In an embodiment, the mode selection circuit 120 includes: a transistor M _L , a set resistor R _SET1 , a set resistor R _SET2 , a set resistor R _SET3 , a voltage comparator 122 , a voltage comparator 124 , and a transistor M _N , wherein the transistor M _L in a PMOS transistor as an example, the NMOS transistors to transistors M _L as an example. M _L transistor having a first end, a second end, and a gate terminal, a first terminal of the transistor M _L coupled to the system voltage Vdd, its gate terminal coupled to the output terminal of the voltage comparator 122, _L of the first transistor M The two ends output the set voltage.

As for the portions of the resistors R _SET1 , R _SET2 , and R _SET3 , the set resistor R _SET1 has a first end and a second end, and the first end of the set resistor R _SET1 is coupled to the second end of the transistor M _L . Setting resistor R _SET2 having a first end and a second end, setting a first terminal of the resistor R _SET2 is set to the second terminal of the resistor R _SET1. The set resistor R _SET3 has a first end and a second end. The first end of the set resistor R _SET3 is coupled to the second end of the set resistor R _SET2 , and the second end of the set resistor R _SET3 is coupled to the ground voltage Vss. In this embodiment, the number of the set resistors R _SET1 , R _SET2 , and R _SET3 can be adjusted according to design choices, and is not limited thereto.

In addition, the voltage comparator 122 in the mode selection circuit 120 has a positive input terminal, a negative input terminal, and an output terminal. The positive input terminal of the voltage comparator 122 is coupled to the second terminal of the set resistor R _{SET1 and} the first resistor of the set resistor R _SET2 . At one end, the negative input terminal of the voltage comparator 122 is coupled to the reference voltage VI for locking the voltage of the node between the set resistor R _SET1 and the set resistor R _SET2 . In addition, the voltage comparator 124 has a positive input terminal, a negative input terminal and an output terminal. The positive input terminal of the voltage comparator 124 receives the output terminal voltage Vo, and the negative input terminal of the voltage comparator 124 receives the reference voltage Vcom for comparing the output terminals. The voltage Vo is compared with the reference voltage Vcom to output a control bias voltage V _eoc . In this embodiment, the reference voltage Vcom is about 3V, but is not limited thereto. The transistor M _N in the mode selection circuit 120 has a first end, a second end, and a gate terminal. The first end of the transistor M _N is coupled to the first end of the set resistor R _SET3 , and the second end of the transistor M _N setting resistor coupled to the second terminal R _SET3, M _N of the transistor gate terminal coupled to the output terminal of the voltage comparator 124, for determining a conduction state control bias V _eoc.

More specifically, the mode selection circuit 120 can determine the charging mode of the charging management device 100 to be the TC mode or the CC mode according to the voltage level of the output terminal voltage Vo. For example, when the output terminal voltage Vo is less than the reference voltage Vcom, the voltage comparator 124 outputs a low-level (eg, 0V) control bias voltage V _eoc , causing the transistor M _{N to} turn off, then flowing through the transistor M _L The current flows along the path of the set resistors R _SET1 , R _SET2 , and R _SET3 , and the module selection circuit 120 outputs a corresponding set voltage Vset (for example, Vset1 ). At this time, the charge management device 100 charges the battery in the TC mode. Charge it. When the output terminal voltage Vo is greater than the reference voltage Vcom, the voltage comparator 124 outputs a high-level control bias voltage V _eoc , causing the transistor M _{N to be} turned on, and the current flowing through the transistor M _L follows the set resistance R _SET1 , R The path of the _SET2 and the transistor M _N flows, and the module selection circuit 120 outputs a corresponding set voltage Vset (for example, Vset2). At this time, the charge management device 100 switches to the CC mode to charge the rechargeable battery.

On the other hand, when the charge management device 100 is in the TC mode or the CC mode, the current sensor 140 in the charge management device 10 is used to sense the current flowing through the power switch _PT , thereby generating the sense current ID1.

In an embodiment, the charge management device 100 includes a sense resistor R _sen and an error amplifier Acc. The sensing resistor R _sen has a first end and a second end, the first end of which is coupled to the current sensor 140 and the second end of which is coupled to the ground voltage Vss for generating a sensing voltage according to the sensing current ID1. The error amplifier Acc has a positive input terminal and a negative input terminal. The positive input terminal is coupled to the first end of the sensing resistor R _sen , and the negative input terminal is coupled to the mode selection circuit 120 for receiving and comparing the sensing voltage and The voltage Vset is set to generate a first control bias to the smoothing conversion circuit 110, as shown in FIG.

In an embodiment, the charge management device 100 further includes a voltage dividing resistor R _fb1 , a voltage dividing resistor R _{fb2 ,} and an error amplifier Acv. The voltage dividing resistor R _fb1 has a first end and a second end, the first end of which is coupled to the output terminal voltage Vo. The voltage dividing resistor R _fb2 has a first end and a second end, the first end of which is coupled to the first end of the voltage dividing group R _fb1 , and the second end of which is coupled to the ground voltage Vss . The error amplifier Acv has a positive input terminal and a negative input terminal, and the positive input terminal is coupled to the second end of the voltage dividing resistor R _{fb1 and} the first end of the voltage dividing resistor R _fb2 to receive the divided voltage, and the negative input terminal receives the reference voltage Vref is used to receive and compare the divided voltage with the reference voltage Vref to generate a second control bias to the smoothing conversion circuit 110, as shown in FIG.

With continued reference to FIG. 2, the smoothing conversion circuit 110 in the charge management device 100 includes a bias current source I _BIAS , a current mirror 114 , a current mirror 112 , a current mirror 116 , and a transistor M _VA , wherein the transistor M _{VA is} a PMOS transistor. As an example. A bias current source I _{BIAS is} used to provide a bias current. The current mirror 114 includes transistors M1 and M3. The transistors M1 and M3 are exemplified by an NMOS transistor. The current mirror 114 is coupled to a bias current source I _BIAS for receiving a bias current and providing a current I1 according to the bias current. . The current mirror 112 includes transistors M2, M4, and the transistors M2, M4 are exemplified by an NMOS transistor, and the current mirror 112 is connected in series with the current mirror 114. The current mirror 116 includes transistors M _CAP1 and M _CAP2 , wherein M _CAP1 and M _CAP2 are exemplified by a PMOS transistor, and the current mirror 116 is coupled to the current mirror 114 and adjusted according to the first control bias generated by the error amplifier Acc. Controls the magnitude of the current I _CC . As for the transistor M _VA in the smoothing conversion circuit 110 having the first end, the second end and the gate terminal, the first end of the transistor M _VA receives the system voltage Vdd, and the gate terminal of the transistor M _VA is received and according to the error amplifier Acv The generated second control bias adjusts the magnitude of the control current I _CV .

More specifically, since the bias current source I _BIAS generates the current I1 through the current mirrors 114, 112, and also because the current I1 is in the same path as the control current I _CC and the control current I _CV , the control current I _CC and the control current I The current between the _CV and the current will be locked by the current I1, so the smoothing conversion circuit 110 is between the CC mode and the CV mode, and can be adjusted according to the current and the interleaving between the control current I _CC and the control current I _CV (similar to a current) Pulling changes) to alleviate the voltage level of the gate voltage V _G of the power switch M _P , thereby achieving a continuous output voltage regulation function, thereby improving the voltage level at the output terminal and reducing the chain voltage.

In an embodiment, the charge termination circuit 130 includes: an open circuit current source I _cut-off , a current mirror 131, a transistor M _EN , a current mirror 133 , a current mirror 132 , a current mirror 134 , a current sensor 135 , and an inverter 136, wherein the transistor M _EN is exemplified by an NMOS transistor. The open current source I _{cut-off is} used to provide a reference current. The current mirror 131 in the charge termination circuit 130 includes a transistor M _N3 and a transistor M _N4 , wherein the transistor M _N3 and the transistor M _N4 are exemplified by an NMOS transistor, and the current mirror 131 receives a reference current to provide a reference current. Current I2. The transistor M _EN has a first end, a second end and a gate terminal, the first end of the transistor M _EN is coupled to the current mirror 131, and the gate terminal of the transistor M _EN is coupled to the mode selection circuit 120 for controlling according to the control bias voltage level V _eoc determine the conductive state of the transmission path of the current I2.

More specifically, when the voltage level of the control bias voltage V _eoc pulled out by the output terminal of the voltage comparator 124 in the mode selection circuit 120 is a low level (for example, 0 volt), the transistor is turned off. M _EN , the transmission path of the shutdown current I2. When the voltage level of the control bias voltage V _eoc pulled out by the output terminal of the voltage comparator 124 in the mode selection circuit 120 is at a high level, the conduction path of the transistor M _EN , that is, the conduction current I2 is turned on.

Referring to FIG. 2, the current mirror 133 in the charge termination circuit 130 includes a transistor M _P2 and a transistor M _P4 , wherein the transistor M _P2 and the transistor M _P4 are exemplified by a PMOS transistor, and the current mirror 133 is coupled to the transistor. The second end of M _EN . Current mirror 132 comprises transistor M _P1 and M _P3 transistor, wherein the transistor M _P1 and M _P3 transistor in PMOS transistor as an example, a current mirror 132 and current mirror 133 connected in series. When the transistor M _{EN is} turned on, the current mirror 132 is used to receive and generate a current I3 based on the current I2. The current mirror 133 is used to receive and transmit a current I3, wherein the current I2 is equal to the current I3.

On the other hand, the current sensor 135 in the charge termination circuit 130 is used to sense the voltage level of the positive terminal of the rechargeable battery to generate the sense current ID2. The current mirror 134 in the charge termination circuit 130 includes a transistor M _N1 and a transistor M _N2 , wherein the transistor M _N1 and the transistor M _N2 are exemplified by an NMOS transistor, and the current mirror 134 is coupled to the current sensor 135. The current I4 is generated by receiving the sense current ID2 and according to the sense current ID2, wherein the sense current ID2 is equal to the current I4. The input terminal of the inverter 136 in the charge termination circuit 130 is coupled between the current mirror 133 and the current mirror 134, and the output of the inverter 136 is coupled to the gate terminal of the transistor M _c . Since the current I3 is a fixed current value and is located on the same transmission path as the current I4, the voltage level of the node voltage Vc between the current mirror 133 and the current mirror 134 can be determined according to the current difference between the current I3 and the current I4. . In other words, when the value of the current I4 rises, the voltage level of the node voltage Vc decreases; on the contrary, when the value of the current I4 decreases, the voltage level of the node voltage Vc rises. Then, the inverted result is output via the inverter 136.

In this embodiment, the charging management device 100 further includes a transistor M _c having a first end, a second end, and a gate terminal, and the first end of the transistor M _c is coupled to the system voltage Vdd, and the transistor M _c is The two ends are coupled to the gate terminal of the power switch M _P , the gate terminal of the transistor M _c is coupled to the inverter 136 of the charge termination circuit 130 , and switches the conduction state according to the inverted result output by the inverter 136 , wherein The transistor M _c is exemplified by a PMOS transistor. When the result of the inverted transistor M _c gate terminal of the received level is high, the voltage level is turned on and the gate voltage V _G M _P of the power switch is pulled, causing the power switch is turned off M _P The charging current for the rechargeable battery drops to a preset current value (for example, I _cut-off ), so that the charging management device 100 enters the cut-off charging mode and terminates the charging operation. Thereby, the charging termination circuit 130 can accurately determine that the battery is fully charged, and close the charging process in time to prevent overcharging of the battery, thereby achieving the purpose of protecting the lithium ion charger circuit and the battery.

In summary, the present invention provides a charging architecture with a smooth conversion circuit and a charge termination circuit. On the one hand, the present invention achieves a continuous output voltage regulation function by smoothly switching the switching mode to switch the charging mode, thereby easing the voltage level of the output terminal and Improve the chain voltage; on the other hand, the case accurately fills the battery capacity through the charge termination circuit, and directly senses the current through the transistor to reduce the error in the judgment, thereby enabling the charging process to be more accurately turned off. Therefore, the charging structure proposed by the present invention can neither damage the battery nor accurately charge the lithium battery, greatly improving the charging quality and prolonging the life of the battery.

Although the present invention has been disclosed in the above embodiments, it is not intended to limit the present invention, and any one of ordinary skill in the art can make some changes and refinements without departing from the spirit and scope of the present invention. The scope of the invention is defined by the scope of the appended claims.

10‧‧‧Charging architecture

100‧‧‧Charging management device

102‧‧‧Rechargeable battery

104‧‧‧Power supply unit

Claims (10)

A charging architecture includes: a power supply device for providing a system voltage; a rechargeable battery connected in parallel to the power supply device; and a charging management device connected in parallel to the power supply device and the rechargeable battery for positively charging the rechargeable battery The extreme voltage level switches the corresponding charging mode, and when the charging current for charging the rechargeable battery drops to the preset current value, the charging operation is terminated. The charging architecture of claim 1, wherein the charging management device comprises: a power switch having a first end, a second end, and a gate terminal, the first end of the power switch receiving the system voltage, and the power source a second end of the switch is coupled to the positive terminal of the rechargeable battery to obtain an output voltage level; a smoothing conversion circuit is coupled to the gate terminal of the power switch for determining the voltage level of the output terminal according to the second end of the power switch Adjusting a voltage level of a gate terminal of the power switch; and a charging termination circuit coupled to the second end of the power switch for sensing the charging current through the second sensing circuit therein, and reducing the charging current When the preset current value is reached, the charging action is terminated. The charging architecture of claim 2, wherein the smoothing conversion circuit comprises: a bias current source for providing a bias current; a first current mirror coupled to the bias current source for receiving the bias current and providing a first current according to the bias current; a second current mirror connected in series with the first current mirror; a third current mirror, Coupling to the first current mirror, and adjusting the first control current according to the first control bias; and the first transistor having a first end, a second end, and a gate terminal, the first end of the first transistor receiving The system voltage, and the gate terminal of the first transistor receives the second control bias, and adjusts the second control current according to the second control bias, wherein the first control current and the second control current are The current sum is equal to the first current, and the smoothing conversion circuit adjusts the gate voltage level of the gate terminal of the power switch according to the current. The charging architecture of claim 2, wherein the charging termination circuit comprises: an open current source for providing a reference current; and a fourth current mirror receiving the reference current to provide a second current according to the reference current a fifth transistor having a first end, a second end, and a gate terminal, the first end of the fifth transistor being coupled to the fourth current mirror, the gate terminal being coupled to the mode selection circuit for The level of the set voltage determines a conduction state of the path of the second current; the fifth current mirror is coupled to the second end of the fifth transistor for receiving the second current and generating a third according to the second current Current a sixth current mirror serially connected to the fifth current mirror for receiving and transmitting the third current; the second current sensor for sensing a current level of the positive terminal of the rechargeable battery to generate a second current Sensing a current; and a seventh current mirror coupled to the second current sensor for receiving the second sensing current and generating a fourth current according to the second sensing current, wherein the charging termination circuit is configured according to the first The current difference between the three currents and the fourth current determines a node voltage level between the sixth current mirror and the seventh current mirror. The charging architecture of claim 4, wherein the charging termination circuit further comprises: an inverter having an input end and an output end, the input end of which is coupled to the sixth current mirror and the seventh current mirror The output end is coupled to the sixth transistor for outputting an inverted result according to a node voltage level between the sixth current mirror and the seventh current mirror. The charging management device further includes: a sixth transistor having a first end, a second end, and a gate terminal, wherein the first end of the sixth transistor is coupled to the charging structure The system voltage, the second end of the sixth transistor is coupled to the gate terminal of the power switch, the gate terminal of the sixth transistor is coupled to the charge termination circuit, and the conduction state is determined according to the reverse phase result. The charging structure of claim 2, further comprising: a first current sensor coupled to the power switch and the smoothing conversion circuit And sensing an output voltage level of the second end of the power switch to generate a first sensing current. The charging management device further includes: a mode selection circuit, configured to determine a charging mode according to the voltage level of the output terminal, and output a set voltage, including: a first setting resistor, The first end and the second end have a first end coupled to the second end of the third transistor; the second set resistor has a first end and a second end, the first end of which is coupled to the first end Setting a second end of the resistor; the third set resistor has a first end and a second end, the first end of which is coupled to the second end of the second set resistor, the second end of which is coupled to the ground voltage; The voltage comparator has a positive input terminal, a negative input terminal and an output terminal, the positive input terminal of which is coupled to the second end of the first set resistor and the first end of the second set resistor, and the negative input terminal thereof is coupled to a third reference voltage for receiving and comparing the third reference voltage and a voltage division between the first set resistor and the second set resistor; the third transistor having a first end, a second end, and a gate terminal, The first end is coupled to the system voltage, The gate terminal is coupled to the output end of the first voltage comparator and outputs the set voltage by the second terminal thereof; the second voltage comparator has a positive input terminal, a negative input terminal and an output terminal, wherein the positive input terminal receives The output terminal voltage, the negative input terminal receives the first reference voltage, and compares the output terminal voltage with the first reference voltage to generate a third control bias And a fourth transistor having a first end, a second end, and a gate terminal, the first end of which is coupled to the first end of the three set resistors, and the second end of which is coupled to the third set resistor The second terminal has a gate terminal coupled to the output end of the first voltage comparator for determining a conduction state according to the third control bias voltage. The charging management device further includes: a sensing resistor having a first end and a second end, the first end of which is coupled to the first current sensor, the first The second end is coupled to the ground voltage for generating a first sensing voltage according to the first sensing current; and the first error amplifier has a positive input end and a negative input end, the positive input end of which is coupled to the sensing The first end of the resistor is coupled to the mode selection circuit for receiving and comparing the first sensing voltage and the set voltage to generate the first control bias. The charging management device further includes: a first voltage dividing resistor having a first end and a second end, the first end receiving the output terminal voltage; the second voltage dividing resistor a first end and a second end, the first end of which is coupled to the first end of the first divided piezoelectric group, the second end of which is coupled to the ground voltage; and the second error amplifier has a positive input end And a negative input terminal, the positive input end of which is coupled to the second end of the first voltage dividing resistor and the first end of the second voltage dividing resistor to receive the Pressing, the negative input thereof receives the second reference voltage for receiving and comparing the divided voltage with the second reference voltage to generate the second control bias.