TW200904040A - Apparatus and method for computing maximum power reduction for a UMTS signal - Google Patents

Abstract

A method and apparatus are provided for controlling transmit power with an estimated value of cubic metric (CM) and/or peak-to-average ratio (PAR). Preferably, the method is applied in determining a value for Maximum Power Reduction (MPR) for computing maximum-MPR or minimum-MPR, by estimating CM and/or PAR from signal parameters. The method of estimating CM and/or PAR is applicable to any multicode signal.

Description

200904040 IX. Description of the Invention: [Technical Field] The present application relates to wireless communication. [Prior Art]

In practical amplifier circuits, such as amplifier circuits used in the Transmit Chain of the Universal Mobile Telecommunications System (UMTS) Wireless Transmitting and Receiving Unit (WTRu), spectral regeneration is induced due to nonlinear amplifier characteristics. The term spectral regeneration describes the "additional non-linear amplification II effect generated by the energy of the extra-domain signal in the round-off. (4) Spectral regeneration is mainly generated in the frequency adjacent to the desired chirp. For the power amplifier It is necessary to use the +/·5ΜΗζ_ 赖道韵 ratio (ACLR) of Qiangu·channel. The following are the voltage gain characteristics of the amplifier: complex v. (0 m (') + heart '2+g3 · V, +·. + Vi (〇„ Equation (1) /, the linear gain of the gl.v(9)疋 amplifier, the rest (ie, t v'w +g3'w+_..+g”.vi(0„) Nonlinear gain. If the signal is tuned, the third generation partner (3GPP) radio frequency (RF)' = as a result of the father's distortion will produce a silky term, which will result in an in-band missing term and f External distortion 'in-band distortion will be error vector magnitude (£士士) plus ~ external distortion will cause an increase in ACLR. Both will cause a decrease in modulation quality. Medium"'] such as UMTS version 5 and version 6 The multi-code signal is increasing at the peak-to-average power = this will produce a larger dynamic signal change. These increases, the ^ change requires a stronger amplification. This will result in greater power consumption for 200904040. Recent results have shown that dB is sent directly for fat (ie, the ratio of peak power to average power of the signal, also known as peak-to-average ratio (pAR is for amplifier power attenuation) It is not effective. Analysis of the spectrum regeneration of the amplifier shows that the third-order nonlinear gain term ("cubic gain,") is the main reason for the increase of ACLR. The total energy of the vertical term depends on the statistical distribution of the input signal. The introduction of Uplink Packet Access (HSUPA) introduced a new method for eliminating amplifier power attenuation in Release 6, called the cubic metric (CMXM is based on the cubic gain portion of the amplifier. CM describes the observed The ratio of the cubic part of the signal to the μ s speech interference signal. CJV [simultaneously applicable to High Speed Downlink Packet Access (HSDPA) and HSUPA uplink recording. Scale analysis shows that the power derating based on CM is estimated Compared with the 99.9% tender power derating, it shows a difficult error distribution, where the error distribution refers to the difference between the actual power derating and the estimated power derating. 3GPP specifies the maximum power attenuation (sharp test, which indicates that the maximum transmit power is greater than or equal to _ maximum transmit power, but less than the total amount of so-called maximum MPR) where the maximum MpR is a function of the CM of the transmitted signal. To correct the power amplifier, the manufacturer can decide that the device needs to limit its maximum power to some amount, referred to herein as "minimum MPR, which is less than the maximum tape size, but compatible with 3Gpp aclr. Although taking small MPR can be defined It is a function of (10) 'but can also be substituted for the special score of A 妓 PAR. Use the minimum MPR instead of the maximum bribe to limit the maximum power, so that wtru can transmit at a greater maximum power' Minimum MPR of 200904040

The WTRU manufacturer has a more advantageous voice. It is also possible that a WTRU's design can include a maximum and a minimum MPR, and choose between the two. Regardless of riding a large MPR wire small MPR ride, the riding problem is that the WTRU must know the value of CM and/or pAR to calculate the selected MPR and if necessary (ie if wtru is operating near the highest rate), Finally use the above values to actually send the slave power. Any = multi-code signal (characterized by the transmitted physical channel, its channelization code, and the weight called the item) has its specific CM and PAR. In ancient times, the signal, as well as CM and PAR, can vary in every 2 or leap seconds of transmission time interval (TTI). It can be seen that the combination of more than 200,000 for the gamma (10) = this 6' with the channel parameters and the quantified (four) is called the possible health. The large number of possible signals makes it possible to form a strict-to-the CM or PAR dare lookup table as a function of the k-characteristic, which is impractical for immediate applications; especially for small operations operating at UMTS f-rate Low power handheld, medium. After understanding that the WTRU cannot simply look up the CM or PAR, it is measured or estimated from the characteristic parameters of the signal within the error of the QoS. > 4CM or PAR is known from the actual signal. The important difference is that the signal must be generated first to make the measurement. Since the transmission power is finally = will be set as the CM and / or pAR training疋 Power will need to generate a signal portion of Wei or at least for a period of time before transmission. The axis is theoretically feasible, and the delay requirement between 200904040 and the actual storage of UMTS is not feasible. A variant of the above method is to generate and start transmitting a signal at the calculated power level from the "guess" of the CM or PAR, and adjust the transmit power to the second power in the entire time slot remaining in the subsequent ΤΏ level. The first and second power_combinations are calculated and the average power level is close to the power level selected by the CM or PAR before the start of m. In UMTS, there are 15 time slots in a 10 millisecond TTI, but there are only three time slots in a 2 millisecond TTI. Assuming, for example, that the measurement of (10) or pAR requires some portion of a time slot of, for example, 10 milliseconds, the initial power level will be set to be used only for the first time slot, while the remaining 14 time slots are used. The second value. For a 2 millisecond πι, the initial power level will be set to use the first time slot, which is one-third of the TTI, and the remaining two-thirds of the TTI will use the second value. Obviously the method is not - in particular, in the case of a 2 millisecond TTI. Therefore, a method is needed to be able to determine the CM or PAR before starting to transmit a signal to determine the maximum mpr and/or minimum MpR, and the final transmit power. SUMMARY OF THE INVENTION A method and apparatus for controlling transmission power using estimated values of CM or PAR are provided. This method, as opposed to directly measuring CM or PAR, can be applied to determine the maximum power attenuation value (MpR) or minimum MPR used to calculate the maximum MPR by estimating CM or pAR from the signal parameters. The method of estimating s ten CM or PAR is applicable to any multi-code signal. 200904040 [Embodiment] The term "wireless transmission (rTRU)", including but not limited to user equipment _, mobile unit 7, reading, mobile phone, personal digital assistant (10) 、), electric thief Other user devices that can operate in a closed environment.

The term "base station" as used hereinafter includes, but is not limited to, a node, a site controller, an access point (ΑΡ), or any other type of peripheral device capable of operating in a wireless environment.

FIG. 1 is a block diagram of a WTRU 120 configured to perform the methods disclosed below. In addition to the components contained within a typical WTRu, the WTRU 120 also decomments a processor 125' configured to perform the disclosed method, a receiver 126 that communicates with the processing n 125, and a transmitter 127 that communicates with the hard (2); Receiver 126 and transmitter 127 communicate to implement the transmission of the wire data and the absence of antenna 128. The WTRU communicates wirelessly with the base: 110. The transmission CM and/or PAR for estimating the signal based on the configuration parameters of the signal and using the estimated value to calculate the mpR's configuration parameters including the number and type of the channel and the configuration will be described below. The configuration can be defined as a combination of channelization code and channel weight (called no), best used for in-phase (I) and quadrature channel (Q) partial codes. The channel weight (for a given service and data rate), other parameters, the so-called "configuration" below, and all combinations above are determined according to the specification 200904040 defined by 3(}1>1> A combination of a channel and a unit. Each possible signal must be in at least one configuration. The definition can be extended. For example, 'may include some or all of the 5 or more physical channels including the configuration. A subset or a limited range of terms. Identification of the smallest subset of configuration conditions 疋 subjective 'this configuration specifies the minimum CM and/or PAR estimation error that can be received, and the CJV [and/or par estimation error is used in turn Estimating the error in MPR. An example of a set of 11 configuration cases is shown in Table 1. These configuration cases are limited to allowing up to one DPDCH. It will be appreciated by those skilled in the art that the configuration is not limited thereto. However, it may not be ideal. Empirical results indicate that the resulting less acceptable estimation error, especially the maximum maximum MPR estimation error, is less than or equal to udB. Table 1 shows the configuration. The situation is usually defined by three main characteristics: 1) the maximum number of DPDCHs (Nmax DPDCH); 2) whether to start high speed (HS); and 3) the number of E-DPDCHs and the spreading factor (SF) (E-DPDCiUi@SF ). Table 2 shows an alternative mapping method. Table 2 shows the division of some of the conditions originally defined in Table ^ into a number of cases, which can produce less error than the mapping of the table. In particular, it indicates that the maximum maximum MpR estimation error is less than or equal to 1.0 dB. Referring back to Table 1, the HSChan code block involves a specific "SF and orthogonal variable length (〇v) weight for HS-DPCCH, please note that 兕 is usually 256 'and for OVSF, two codes are used ( One of 33 and 64). When the third column (ie, Hs) shows no ("N") Hs, the shed 200904040 is expressed as "unavailable" (n/a).

E DPDCH 1, 3 I or Q block indicates that 'I or q, E-DPDCH channels #1 and #3 are displayed in this section, which are used according to the condition of the column. S E-DPDCH 1,3 Chan code block 'if any' relates to SF and OVSF codes for E-DPDCH involving channels #1 and #3. For example, the configuration case has two E_DPDCHs, labeled #ι and #3, and the rest of the block is either none (not available) or one (default is ζ') "#1". Most of the configuration There is only one E-DPDcjj. The E-DPDCH 2,4 Chan code column is similar to the above, for the case of having two or more E-DPDCHs. The I and Q columns indicate the/5 items in the I and Q parts. In configuration case 6, β& relates to E-DPDCH channels #1 and #2, and 々ed3/4 relates to E-DPDCH channels #3 and #4. Table 1 Γ --- Configure Nmax HS E-DPDCH HS e-dpdch E-DPDCH E-DPDCH IQ situation dpdch Lin SF Chan code Ui or Q l, 3Chan code 2, 4Chan code 0 1 N 0 N/AN/AN/AN/A βά A 1 0 Y 1@SF>=4 256, 33 I SF, SF/4 N/A 2 0 N 1@SF>=4 N/AIN/AN/AA 3 0 Y 0 256, 33 I SF, SF/4 · N/AN/A βζβ)Λ& 4 0 Υ / 2@SF>=4 256, 33 I SF, 4,1 Ν SF/4=4,1 ββά 5 0 Υ/ 2@SF>=2 256, 33 I 2,1 2,1 Ac^ed Οοβ)α&, Ν β&ά 6 0 Υ/ 4@SF>= 256, 33 I(#D 2, 1(#1) 2, 1(#1) Ac^ed, β<^β\ί5. 11 200904040 N 2/4/2/4 1(#3) 4, 1(# 3) 4, 1(#3) Ad3/4 force ed, Ad3/4 7 1 Y 〇, or 256, 64 I SF, SF/2 N/A βά„β&ζ, βζ,β\& 1@ SF>=4 Ad, 8 1 Υ / 2@SF>=4 256, 64 if SF, 4, 2 βά”β sink, β^β)Ά&, Ν HS=T SF/2=4, 2 , then I, otherwise Q 9 1 Υ / 2@SF>=2 256, 64 If SF, 4, 2 βά,, β^ζ, Ν HS=”Y” SF/2=4, 2 •Aed, βξίά , then I, otherwise Q 10 1 Ν 1@SF>=4 N/AQ SF, SF/2 N/A βά,, β^ζ, βζ, β^ά

Table 2 Configuration situation Nmax DPDCH HS E-DPDC H code @8? Additional state 0 1 N 0 N/A 1 0 Y 1@SF>=4 N/A 2 0 N 1@SF>=4 N/A 3 0 Y 0 N/A 4 0 Y/N 2@SF=4 N/A 5 0 Y/N 2@SF=2 N/A 6 0 Y/N 4@SF= 2/4/2/4 N/A 7a 1 Y 〇, or 1 @SF>-4 fic-βά >0 7b fic - βά 彡0 8a 1 Y/N 2@SF=4 fic - βά >0 15*Aed=5 12 200904040 8b fic - Βά >0 15*Α^~=5 8c fic -βά 彡0 15*Aed=5 8d fic -βά 彡0 9a 1 Y/N 2@SF=2 β〇-βά >0 9b Α -βά 彡0 15*Aed=5 9c βα ~βά 彡0 15^^-5 10 1 N 1 @SF>=4 Ν/Α The configuration in Table 1 and Table 2 is a known general case where zero maximum is required. For this configuration case, instead of using the calculation method for all other configuration cases, the maximum MPR and/or minimum MPR is simply set to zero. Referring to Figure 2, a simple version of the offline process 2〇〇 is shown. A more detailed description is also provided below in conjunction with FIG. 3, which ultimately calculates and stores the parameters of the threat WTRU to produce a maximum (10) 卩 and/or minimum MPR value. In UMTS, each combination of physical channels and parameters and quantized values is a possible signal. The quantized value is based on the configuration of the signal. First, all possible signals are mapped to a set of configuration conditions (21〇). By using the information (1 and Q) given by the two rightmost blocks of Table 1, a quantized value (22 〇) can be generated for all possible signals. The CM and/or par (230) for all possible signals is measured by transmitter simulation. Measurements of CM and PAR are described in more detail below in 200904040. The pre-calculated term a is optimally determined 240 by using the transmitter simulation 23 turns out. Optimally for each of the configuration scenarios defined above, a set of alpha terms for the CM and/or a set of alpha terms for the PAR calculated according to Equation 7 below are determined. For each configuration, the transmitter simulates 23 测量 measuring CM and PAR' for all possible signals (the mathematical derivation of the estimation of cM and/or PAR will be derived in detail below), where the signal is defined as All possible combinations of the summons 220 are quantified in 3GPP. You can use a least squares fit method to determine pre-computed terms for a particular configuration from all possible signals in the configuration case, or from a typical subset of them. The alpha term, the configuration, and the calculated adjustment factor for a ten nose are calculated (240). These values are then written to the WTRU 400 by firmware, software or hardware. Figure 3 is a flow chart of the offline initial configuration process (3〇〇). This process 300 calculates the alpha term for both CM and PAR and determines the adjustment factor for the configuration. These values are stored in the WTRU (400) for estimating CM and PAR for a given signal. A detailed version of the offline process 300 is shown with reference to FIG. First, at 310, the configuration is defined according to the characteristics of the physical channel. For example, as shown in configuration case 9 in Table 1, DPCCH, one DPDCH (the largest one DPDCH), HS-DPCCH (AACK and ACQI are set equal; always send an acknowledgement (ACK) and channel quality indicator are defined.

(CQI) ), E-DPCCH and 2SF@=2 (The two e_dpdcH 14 200904040 in SF use the information in the rightmost two blocks of Table 1 (1 and the desired single, square and component cross //5). The symbol from Equation 5 is required to be described below.) ed ^ ec ^ ed {:q:/"q3} is called "~(特;4: 疋疋任思的). Sixteen such items are defined in Table 3: Stone, 曰

k Hu must, βάϊ, V β'

Ur β^βά, 3ci3hs, β (ίβ&ά and all possible signals of the subsequent slave configuration (ie, all combinations of the items used for lining) (320). Each 3Gpp, , , : value pair Thirty kinds of implicit combinations, the obvious value of Ahs=, the nine values of ΑΠ/Α and the thirty values of ^' or the scale riding each of his sentimental 72_ wealth of letters Wei He. There is no List these 72,900 combinations. ~, 'Use transmitter simulation to measure CM and measure 99% PAR (330) for all 729 (8) possible signals for each configuration. The 145,800 values measured are not listed here. Using the 7290 possible signals of the parent configuration and its linear CM and linear PAR measurements, use Equation 7 to calculate the sixteen pre-computed alpha values used to estimate the CM and the sixteen pre-estimates used to estimate the PAR. § The alpha value of the calculation (340). The symbol term is given in Equations 8 to 7; the numerical value of the α term is given in Table 3. Although only one of the 729 combinations may be used. a small subset, but assume that in the next step you need a matrix X' with 72,900 lines, then use the entire 72,900 combinations. Set 15 200904040 Table 3 for calculating a configuration. Table 3 Functions of the β term aCM ^PAR _ Ac -1.53154 -0.0333305 β〇ά -1.04303 +1.97253 βά -1.88422 -0.691914 _ β〇-1.10666 -1.24791 /^ Hs ~~------ -0.851261 -0.642072 Λ--------- +2.7545 +2.3413 __Jed_ __ +3.39477 +1.35334 Jd2 ^ ')-- +2.85157 +2.61758 ...β〇Λ0 · +2.47229 +2.86022 +2.37892 +2.63543 -JlPO .Ped ___ +2.33816 +1.72716 ——^ec βά __ +2.18533 +1.27585 Ad +2.95673 +2.75154 As +1.75287 +1.80679 AA +2.05286 +3.06353 Where.Ah +1.59968 +2.07734

For each possible signal, the linear CM and linear PAR (350) are estimated using the models depicted in Equations 5 and 6 (described below). The calculation in the form of a matrix is given in Equation 12. The matrix X is a sub-element of Equation 5 and includes a normalization function for a single cold term. The matrix Y is the line f CM and the linear par measurement is multiplied by the denominator of Equation 5; the model of Equation 6 uses a similar form. The estimated error of the mouth and mouth is 〇6〇). For the further description, the distribution of the CM estimation error (in dB) is given in Figure 6A and Figure 6. In the 7th and 7th Guanxian County, the shape of the handle was distributed. Figures ^ and 7A show the model described in Equation 5, and Figure 200904040 shows the model described in Equation 6. The required adjustment factor (370) is then determined. It can be seen from the inspection that for the model of Equation 5, the adjustment factor for the maximum MPR, the maximum amplitude positive error in Figure 6A is about 0.54 dB or 1/0.883. Such as

If the minimum MPR is the desired result, then the s-round factor of the CM for the minimum MPR and the maximum amplitude negative error in Figure 6A are about _〇.71 dB.

The adjustment factor using PAR for the minimum MpR and the maximum value of the negative value in Figure 7A are approximately _〇.4idB. As can be seen from Fig. 6B and Fig. 7B, the corresponding values for the model of Equation 6 are _054 dB, _ 〇〇 8 〇 dB * - 0.57 dB. The distribution of the maximum MPR error is determined by using the adjustment factor (380), which, as calculated above, agrees to be 〇 54 dB. Looking at Figure 5A and Figure 5B, the distribution of the maximum mpr error shows that for the two models, the maximum maximum MPR error is 15 and if it is considered to be small enough (in this case), then theoretically Both models can be used. - As a second criterion 'should note' the frequency of occurrence of the maximum error of the model of the equation 5 as shown in the SAg and the figure, ie 9/72900, which is lower than the model of Equation 6, ie 72_. Therefore, the model of equation $ is selected and (10) and adjustment factor (10) are configured in the WTRU (400). The model of Equation 6 is estimated to require less multiplication, and if this is a significant factor, then the model can be chosen. The derivation of the estimated CM and/or PAR is now described. After the channel weights have been used, but with the hybrid raised cosine and other filters 17 200904040, the par of the uplink signal is determined according to Equation 2. PAR = 101og(^w) = 1 〇i〇g where; (N, \2 (NQΣβυ + \Μ ) W'=1 Nj % ηΣα/+Σ~2 j=\ Household 1 Equation (2) /5 / is the channel weight for the physical channel in the I part; is the channel weight for the physical channel in the Q part; the outer is the number of physical channels in the I part; and the outer is the number of physical channels in the Q part. Embodiments, 'the best CMW, (linear rather than dB form of CM, and no 0.5 dB quantization of 3GPP method) for a given configuration case as a pre-ship RU with Equation 2

Where; is used for each entity. The weighting factor η is the integer used to define the sum of the number of meters is the order of the arbitrary polynomial 'and the function makes 2) the value of the normalized function and the yS of any ratio Nothing. It is also possible to use the same function as in Equation 3 to estimate the filter rotation of 200904040, which has a value different from that of Lin. : Any possible signal for a given configuration, using Equation 3 to estimate and tear "_4 words usually produces an error between the estimated value and the measured value, which is called the estimated error. Although the heart* is deducted as any positive, in an embodiment eight is for example =*=2. The empirical results show that the range of estimation errors for all possible signals by using * ―' is for determining the maximum tenderness and the minimum tenderness __ by _®. Therefore, choosing a value greater than 2 would be complicated and there would be no obvious = advance. Therefore, when the ~ coffee is set to 2, etc. Σ^οΑ, ν>

Equation (4) Extends Equation 4 to produce Equation 5 iaAj CMlim Equation (5) Weight (CM/ί described by the equation for the inner product of the root term α term) is basically equal to a single square plus for weighting ), cross-sections in the component/5 and 19,04004040, which are not yet known, are just the form of the value-weighted term of the term. The formula also applies to the bold ", different. It is expressed in Equation 6 as described in Equation 5. The replacement model, the model removes the single item and the last item of the molecular towel related to the normalization function 2. The empirical result (4), for some configurations, the model will produce a model more than Equation 5 Less estimated error ^ CM CM, linear ' ϊβ:·-1βΰ; Μ ;-1

Equation (6)

For a given configuration, the value of the alpha term can be broken from the following. D uses the transmitter simulation (230) to measure all or a small number of typical 可14__ and/or / 3⁄4凡·除; and 2) using the known least squares fitting method, given in the form of a matrix in Equation 7: Equation (7) α={χτχ)χχτγ where; X疋 matrix (known For design or Vandermode matrices, each letter line, where each element in a row is a square, a single weight, or a numerical value that crosses /5 items within the component. This is determined by replacing the symbols cold I and /3Q in Equation 5 or Equation 6 with the β term for a particular channel; for a case with two or four E-DPDCHs, each single and squared cold Ed should only occupy one line of X 'instead of two or four lines; and Y is a column vector' with one element per signal, each of which is measured 〇4_ or dressed as ear. Assuming that the alpha term for the 200904040 estimated CM or the alpha term for estimating PAR is to be calculated, multiply by the signal weighting factor in the denominator of Equation 5 or Equation 6. Alternatively, assuming that the α term for estimating CM and PAR is to be calculated at the same time, Υ may be a matrix having two such columns: one for CM/Z„ear and the other for P^^linear° below A symbol term (rather than its numerical value) for calculating the alpha term for this example in equation (7) is provided:

C Ζ = βά\ +Pea +2Αλ2 +β〇1 +PhA«+2心2« Equation (8) 2 2 2 2 2 _ is 72900 +Ac72900 +2久?72900 + Han 72900 +Α^72900 4ί: ^βά\ +ββΛ +^ed\ +β〇1 +fihs\ -jβά2 ^βεΛ +,1ββά2 +β〇2 +β}ιΛ Equation (9) \ /3⁄4 2 2 72900 + where 72900 + 2 where / 7 2900 2 2 2 + is 72900 + where ^ 2900 C. ΧΓ 丨 1 1 1 ^C^AACA „111111_ ^ΧΊΛ,Λ,ΟΙ^. Also A ^ ^ Α ^ ^ ^

Pec 72900 Αί/72900 fidT29QQ A: 72900 A5 72900. ^ec72900 2 72900 rt 2 々72900 〇2 ^72900 Aw 72900 Ac72000^ 72900 Arc 7290〇/^ 72900 βεά129〇αβά12900 ☆ 72900"/« 72900 ^c7290〇/^erf 72900 ^/«72900^72900. 'diagi^fE) Equation (10) 21 200904040 CMjineaf PAR-lineaf* Y^diagly CMJineai PARJinea^ PAR"ifwci^9QQ_ Equation (12) err = l〇l〇g(7 )_i〇i〇g(7) equation (13)

The reduced set of possible signals referenced in the above example relates to the situation where the number of signals required to reliably calculate a CC term may be orders of magnitude less than the number of all possible signals. However, using Equations 12 and 13, the matrix X with all possible signals is used to calculate the estimation error. By limiting the number of signals used in X to calculate the alpha term, no significant savings are produced in the off-line processor 200. Ο Equation (11), as specified in Equations 5 and 6, is used to construct the weighting factors of the matrices 乂 and 分别, the digital power (the denominator of Equation 5 and Equation 6, respectively), and the mean square of each signal. The root amplitude (the root mean square term in the numerator of Equation 5) may be the same or substantially the same for all signals in a particular embodiment. In this case, it may not be necessary to calculate each signal. However, the two weighting factors can be constants common to all signals. If the ratio of the number β term in the transmitter simulation used to measure CM and/or PAR and then calculate the alpha term is equal to the ratio of the digit β term in the WTRU, the weighting factor can also be removed from Equations 5 and 6. And effectively combined into the alpha term. By using the processes of Figures 2 and 3, the alpha term for all defined configuration cases, the adjustment factor for each configuration case, and the ability to minimize the maximum MPR & minimum MPR profile, already scaled 5 and The two models described in 6 22 200904040 are calculated. The model that minimizes the maximum and minimum MPR is calculated as follows: η For the case of the maximum MPR, there are three _ squares to determine the model that can minimize the maximum MPR estimation error. The first alternative is that the estimate from equation 5 or 6 (iv) should be adjusted so that the adjusted estimated CM is not greater than the value obtained from the actual measurement of the CM. The adjustment factor should be the most significant positive error for a particular configuration; this factor should be subtracted from the actual estimate. The purpose of this adjustment error is to prevent overestimation of any signal. A second alternative is that the estimate from Equation 5 or 6 should be adjusted such that the determined maximum MPR from the adjusted estimate is no greater than the maximum MpR obtained from the actual CM measurement. The purpose of adjusting the error in this way is to prevent the maximum MPR from being overestimated for any signal. The following is a method of determining the adjustment factor: 1) For each signal in the configuration, the estimated CM is used to determine the estimated MPR (MPR-estimated) and the actual MPR (MPR_tme) is determined from the actual CM of the known simulation. 2) Calculate the MPR error (MPR_error) according to Equation 14: MPR_error = MPR true-MPR_estimated #^((14) 3) From the signal with the MPR error less than 〇, select the original adjustment factor (adjustment_factor_raw) according to Equation 15: adj-ustmenLfactor—mw= mso(CM-estimated-cei(CM”η^0·5))·, Equation (15) where (10) ίο·5) means round up to the nearest 0·5. 4) The final adjustment value is the value of Equation 15 plus a small amount, ε, 23 200904040 to ensure that the signal with the largest size in Equation 15 is not rounded up until after using the adjustment factor. One 〇 5dB. In other words, use the special 16 to adjust the factor (a(jjustment_fact〇r), where the largest of the signals with MPR towns less than zero is selected. _estimated_ceiKCM less _ "special second alternative is to use The smaller the adjustment factor used by the other alternatives, the selected amount is compromised as a design (for example, to prevent overestimating the CM only for specific signals in the configuration). Calculate the minimum MPR to determine the minimum minimum In the case of a model of MPR estimation error, the estimated CM or PAR should be adjusted such that the adjusted CM or PAR is not less than the actual measured value of the CM or PAR. The adjusted factor should be the maximum amplitude for a particular configuration. Negative CM or PAR estimation error; it should be subtracted from the actual estimate. The purpose of using the adjustment factor in this way is to prevent C1V [or PAR from being underestimated for any signal. Alternatively, a smaller amplitude can be used. The negative adjustment factor, the selected amount is used as a design compromise (for example, to prevent CM from being underestimated only for specific signals in the configuration case). For each configuration case, After using the adjustment factor by either method, it is necessary to perform 5 parity for whether the error is small enough for both models. In Figures 5A, 5B, 6A, 6B, 7A, and 7B The distribution of measurement errors for a particular configuration is given. Figure 5, Figure 6A and Figure 7A show the model described in Equation 5; Figure 5B, Figure 6B and Figure 7B show Equation 6. Models described. Figures 5A and 5B show the maximum mpr estimation error for a particular case. 24 200904040 ^ Distribution. In Figure 5A and the first map, due to the top-of-the-range (cez7) operation The distribution is highly quantified. Figures 6A and 6B show the intensity of the CM estimation error. Figure 6A has a narrower intensity than Figure 6B. Distribution in the 6a and the first map and the 7th The distribution in Figure and Figure 7B is substantially continuous. Figures 7A and 7B show the error strength of the estimated PAR. The maximum MpR error for calculating the maximum MPR' should be within the desired limits. Alternatively The difference between the expected CM error can be used as a standard. However, It is better to use the maximum maximum MPR error. In order to use CM or (10) to calculate the minimum MPR 'limit positive and 贞 measurement error _ difference should be within the required range. For the maximum MPR, according to g - the square is extremely The result of the factor is that no signal has an overestimated MpR, but some signals have an underestimated MPR. The result of the adjustment of the second alternative is that the signal has no overestimated CM, but some signals The CM with too low estimation is that the signal with the largest positive CM error will have a correctly estimated CM, and the signal with the negative CM error of the largest amplitude will have a difference due to the difference between the positive and negative (10) errors of the maximum amplitude. For low estimated CM, other signals will have a CM that is too low estimate due to some smaller ^. The result of using the adjustment factor for the minimum MPR' is that no signal will have a CM or PAR that is underestimated; some signals are overestimated CM or PAR. In particular, the signal 25 200904040 with the largest positive CM $ pAR error will have a correctly estimated CM or PAR; the 彳 § with the largest amplitude positive cm or PAR error will be due to the maximum amplitude between the positive and negative cm errors Poorly over-estimated CM or PAR. There are two possible problems with estimating the error: First, due to the intentional underestimation and overestimation of CM and PAR, the calculated minimum MPR may exceed the calculated maximum MPR. In this case, the WTRU may not be able to select a value for the MPR that is guaranteed to meet the requirements of the standard MPH and aclr, e.g., 3 Gpp. Secondly, the greater the difference between the positive and negative estimates of the maximum amplitude, the minimum and the hypothesis obtained according to the method are measured by the small MPR of the Saki thief, thereby reducing the maximum transmit power that can be achieved. Two possible measures for the above problems are: 1) the above compromise can be used by selecting the adjustment factor, so that the MpR for the different possible woods is not applicable; and 2) the specific The configuration is divided into two or more configuration flights, so the estimation error of the students is even smaller. For example, 'If the analysis is on a specific physical channel, the largest; 5 members produce the largest estimated error' then use these $ items to establish the configuration. Once the group configuration has been defined and has been calculated for all configuration scenarios, the items and Na's are best placed in the WTRU's table. Your h reference indicates WTRU4〇〇. At the beginning of each TTI, the appropriate configuration is used to configure the media provided by the transport block, and the data provided by the J layer. In order to define the set of conditions set forth in Table 1, the selection is based on the combination of physical channels used to transmit the transport block, and possibly the Ε-DPDCH spreading factor. Regardless of whether the MPR computing device (430) calculates the maximum MPR, the minimum MPR, or both, and if the device calculates the minimum MPR using PAR, then Equation 17 is estimated according to Equation 17, Equation 6 is Equation 5 and Equation 6. Simplified form: Equation (17) where 'N and D are the numerator and denominator of Equation 5 or Equation 6, respectively, and use the CM α term of the configuration above. Use the equation η to estimate ^^!inear , but replace CAilinear with 丨inea/a and use the PAR 〇: entry for the configuration case. After that, the words and/or the points will be converted into the JR form.

If the MPR metering device (430) calculates the maximum mpr, the selected adjustment factor (in dB) for calculating the maximum MpR is subtracted from the estimate of the CM in dB form. This gives the CM value used to calculate the maximum MPR. If the MPR computing device (430) uses the CM to calculate the minimum MPR, the selected adjustment factor (in dB) for calculating the minimum MPR is subtracted from the estimate of the CM in dB form. The result of this is that the minimum MPR is calculated using C1V [value. If the MPR computing device (430) uses PAR to calculate the minimum MPR' then subtract the selected = PAR to calculate the minimum [VtPR] adjustment factor (dB) from the estimate of the PAR in dB form, the result is used for 27 200904040 minimum calculation MPR. If the MPR computing device (430) calculates the maximum MPR, the maximum MPR is preferably calculated from 3GPP. If the MPR calculation device calculates the minimum MPR, the minimum MPR is optimally calculated according to the specifications of the power amplifier. If the device calculates the maximum MPR or the minimum MPR, instead of the same, the maximum MPR or the minimum MPR that the bell is out of is the output of the MPR value used to set the transmission power. Devices that calculate both the maximum MpR and the minimum MPR can select an intermediate value as the MPR value used to set the transmit power and remain consistent with the standards and manufacturer's recommendations. Actually, it is not necessary to fully estimate the value of C1V [and only need to detect whether the estimated CM value is higher or lower than one or more threshold values. A possible critical value test can be provided by slightly modifying Equation 17, such as Equation 18, which has the advantage of avoiding the division operation in Equation 17.

CMlinearT.D<N Equation (18) where the specific critical price of 疋; < operator is a critical value test, if the inequality is "true", then * is greater than

HinearT Table 4 is derived from the table oa of 3GPP TS 25_1〇1, which shows an efficient algorithm given in the form of C language, which sets the value of max-MPR-dB and the critical value. Select the adjustment factor: line ^ equivalent value to calculate the maximum MPR. Table 4

200904040 1 10Λ(1.5/10)-1.412538 0.5 2~~ 10Λ(2.0/10)-1.584893 10 10Α(2.5/10)-1.778279 .---- 1.5 4~~~ 10Λ(3.0/10)=1.995262 2.0 The special device algorithm used to calculate the minimum MPR is similar to the calculation of the maximum MPR. 'Depending on the specific number, it is likely that there is only one critical value for cm and/or PAR, and a similar algorithm can be used for the calculation.

Returning to Fig. 4, Fig. 4 is a wtru 400 configured for wireless communication, in which digital user data and control data are received and processed by a scaling circuit 45 to digitally scale the data and set its relative transmit power. The digital user profile can be encoded into a channel such as a Dedicated Physical Data Channel (DPDCH) or an Enhanced DPDCH (E-DPDCH). The control data can be encoded into a channel such as a Dedicated Physical Control Channel (DPCCH), a High Speed DPCCH (HS_DPCCH), or an Enhanced DPCCH (E-DPCCH). The scaling circuit 450 operates in each of these channels. The scaled data is filtered by filter device 460, and the filtered data is converted to an analog signal by analog to digital converter (DAC) 470 and transmitted by radio transmitter 480 through antenna (Tx) 490. The WTRU's transmitter has an adjustable (i.e., power controllable) overall transmit power, and a scalable single channel input, as represented by the analog gain term and the digital gain term, respectively, in FIG. Other forms of controllable transmission equipment can also be used. According to the procedure defined in 3GPP, the transmission power and the overall transmission power of a single channel are set by the transmission power control unit 44A. The nominal maximum transmit power is determined by the WTRU power level or the network. The WTRU power level 29 200904040 Maximum transmit power is defined in 3GPP. The WTRU may automatically limit its maximum transmit power using a maximum MPR or a smaller device-specific minimum MpR, which is a value within the range defined by 3GPP. The transmit power control unit 440 uses a plurality of parameters to set the transmit power. One of these parameters is MPR. In order to calculate the mpr, the configuration is first defined according to the offline configuration parameters, which are obtained according to the descriptions of Figs. 2 to 3 above (41〇). For the identified case, the adjusted estimated CM and/or PAR (420) is calculated based on the following. The mpr (430) is set according to the value for the maximum MPR and/or the minimum mpr. Optimally, the maximum MPR and/or the minimum mpr are calculated by the processing device "o based on the adjusted CM and/or PAR estimate (420)' or the adjusted MpR estimate. If calculated from the adjustment of MpR, then The CM and/or PAR are no longer adjusted. The WTRU 400 may be configured to calculate either or both of the MPRs to be different; and to calculate the minimum MPR from either CM or PAR, such that any combination may be selected for use. The estimate of CM and/or PAR may be a function of a pre-calculated value, represented by a term, or a function of the desired correlated channel power (beta term) of the transmitted signal, where The function is based on a particular entity parameter of the signal. The adjustment to the estimate may be from a pre-computed term. To calculate one or two MpRs in the WTRU 400, first, for a TTI 'in the configuration example of the signal, its MAC_es The channel weight is no. =15' y3d = 6'Ahs= 30 200904040 15/15 ' AeCH =15/15 ' Aed,=^ed/ec= 95/15. An example of this signal is at R4- 060176, 3GPP TSG Signal U in RAN 4 Meeting #38. Second, through Using digital scaling, the WTRU 400 calculates the following digital channel weights: ^c = 22, cold d = 9, stone hs = 22, ySec = 22, /3 ed = 200. These weights take up the desired ratio and their sum of squares For the required constants. Third, by using ^:(10) and cold in Table 3, and using Equation 5, calculate the weight of the digital channel and the estimate of CM plus ear, which is 丨.0589, which is equal to 〇.2487dB ° fourth, The CM estimate is adjusted by subtracting 0.54 dB, which is known to be approximately -0.29 dB. Alternatively, in linear form, the estimate is adjusted by multiplying 1.0589 by 0.883, yielding approximately 〇93. 弟五' CM The linear adjustment estimate of 0.94 is less than the first linear threshold in Table 4. Therefore, the maximum MPR is calculated as 〇 dB. As summarized in Figure 8, the process of setting the transmit power by the WTRU 400 to calculate the MPR is shown. Depending on the configuration, the adjustment factor and the pre-calculated alpha value are determined and processed in the offline processing benefit (810). These values are stored in WTRIMOO to assist the WTRU 4 to identify the configuration (820). Once the configuration is determined. , then calculate the adjusted estimate CM and / or P AR (830). By using these adjusted estimates, calculate the maximum MPR and the minimum mpr (84〇) and set the MPR. Combine the mpr, theoretical maximum power and power control commands (850) to set the transmit power. (86〇). 31 200904040 The sum of the components, the good implementation of the invention describes the special features of the invention::::== ‘ The method of supply is Qiansi. The computer firmware or the firmware executed by the computer or the processor is tangible; wherein the computer program, software or readable storage =:::==, the computer memory, the cache Clock, semiconductor storage, / hard disk and mobile _ magnetic bamboo, magneto-optical media and cd_r〇m disc and digital surface (DVD) _ optical media. . For example, proper duties include processor and dedicated processing. , conventional processor, digital signal processor (DSP), multiple micro-stoves, one or more microprocessors associated with the DSP core, controllers, microcontrollers, dedicated integrated circuits (ASICs), on-site Programmable Gate Array (FPGA) circuit, any other type of integrated circuit (5)) and/or state machine. The software-related processor can be used to implement a radio frequency transceiver for use in a wireless transmit receive unit (WTRU), user equipment (Ug), terminal, base station, radio network controller (RNC), or any host computer. The WTRU may be used in conjunction with modules implemented in hardware and/or software, such as cameras, camera modules, video phones, speaker phones, vibration devices, speakers, microphones, television transceivers, hands-free headsets, keyboards, Bluetooth 8 32 200904040 Module, FM radio unit, liquid crystal display (LCD) display unit, organic light emitting diode (OLED) display unit, digital music player, media player, video game module, internet access And / or any wireless local area network (WLAN) module. BRIEF DESCRIPTION OF THE DRAWINGS A more detailed understanding of the present invention will be apparent from the following description of the preferred embodiments. 1 is a functional block diagram of a wireless transmit receive unit (WTRU) invented by Gen counties; FIG. 2 is a block diagram of a simplified version of an offline processor, and FIG. 3 is a detailed flowchart of an offline initial configuration process; 4 is a block diagram of a WTRU according to an embodiment; FIGS. 5A and 5B are two diagrams of a model for Equation 5 and a model of Equation 6 respectively representing a distribution of maximum MPR estimation errors; 6A and 6B are two diagrams of the model for Equation 5 and the model for Equation 6, respectively, showing the distribution of CM estimation errors; Figures 7A and 7B are models for Equation 5, respectively. Two diagrams of the model of Equation 6 and the distribution of the PAR estimation error; and Figure 8 is a flow chart of the method of setting the transmission power. 34 200904040 [Major component symbol description] 110 base station 120, 400, WTRU radio transmission receiving unit 125 processor 126 receiver 127 transmitter 128 antenna 200 offline process 300 offline initial configuration process 440 transmission power control unit 450 scaling circuit 460 Device 470, DAC analog-to-digital converter 480 radio transmitter 490, Tx antenna CM cubic metric MPR maximum power attenuation PAR peak-to-average ratio 35

Claims (1)

200904040 X. Patent Application Range: 1. A method for calculating a maximum power attenuation (MPR) implemented in a wireless transmit and receive unit (WTRU), the method comprising: from a feature of a received signal from a Identifying a configuration situation in a group of predefined configuration scenarios; adjusting an estimated cubic metric (CM) by a pre-configured adjustment factor 'where the CM is based on a transmit power amplifier cubic gain term, and the estimated QV is Stored in the WTRU in an initial configuration; calculate the MPR based on the adjusted estimated CM; and use the MPR to set transmit power. 2. The method of claim 1, wherein the transmit power is set using the calculated MPR with a nominal maximum power limit and at least one power control command. 3. The method of claim 1, wherein the configuration is a channelization code of the received signal and an in-phase (I) channel code and an orthogonal channel of the received signal. The channel weight of the code is defined. 4. A wireless transmit receive unit (WTRU) comprising a processor, the processor configured to: identify a configuration condition from a set of predefined configuration conditions based on a characteristic of a received signal; The adjustment factor to adjust an estimated cubic metric (cm) 'where the αν [based on a transmit power amplifier cube increases 36 200904040 benefit, and the estimated αν [stored in WTRu from an initial configuration; The estimated αν[to calculate the mpr; and use the MPR to set the transmit power. 5. The WTRU as claimed in claim 4, wherein the transmit power is set using the calculated MPR with a nominal maximum power limit and at least one power control command. 6. The WTRU as claimed in claim 4, wherein the configuration is a channelization code of the received signal and an in-phase (I) channel code and an orthogonal channel of the received signal. The (Q) code is defined by a channel weight. 7. The WTRU' as described in claim 4, wherein the processor is further configured to: set an adjustment factor that is a maximum amplitude positive error for a configuration of a channel. 8. The WTRU as described in claim 7 wherein a smaller amplitude adjustment factor is selected. 9. The WTRU of claim 4, wherein the processor is further configured to calculate a weighted form of the CM as a inner product of a squared weighted, component-inscribed P term. Where β represents the signal strength. 10. The WTRU as claimed in claim 4, wherein the processor is further configured to calculate the CM as a weighted form of a inner product of squared weighted, zero-crossings within the component, The 37 200904040 /5 item includes a single (four) that is not within the composition of the homing, where the signal strength of the trait. 11. The WTRU as claimed in claim 4, wherein the processor is further configured to: determine an adjustment factor for minimizing a maximum MPR estimation error by: for each of the configuration scenarios A signal determines an estimated MPR and an actual MPR; an MPR error is calculated by subtracting the estimated MPR from the actual MPR; and the adjusted factor value is selected by a signal having an MPR error less than zero. 12. WTru as described in the scope of the patent application, wherein a smaller amplitude adjustment factor is selected. 13. The WTRU as claimed in claim 4, wherein the processor is remotely configured to: set an adjustment factor that is a maximum amplitude negative error of a configuration case. 38