CN104768212B - The method and device of signal metric is provided for transmitter - Google Patents
The method and device of signal metric is provided for transmitter Download PDFInfo
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- CN104768212B CN104768212B CN201510107103.2A CN201510107103A CN104768212B CN 104768212 B CN104768212 B CN 104768212B CN 201510107103 A CN201510107103 A CN 201510107103A CN 104768212 B CN104768212 B CN 104768212B
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04W—WIRELESS COMMUNICATION NETWORKS
- H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
- H04W52/04—TPC
- H04W52/06—TPC algorithms
- H04W52/16—Deriving transmission power values from another channel
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04W—WIRELESS COMMUNICATION NETWORKS
- H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
- H04W52/04—TPC
- H04W52/52—TPC using AGC [Automatic Gain Control] circuits or amplifiers
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Abstract
The present invention, which provides, a kind of provides the method for signal metric for transmitter, transmitter provides each of multiple first phase elements according to the summation of multiple corresponding first channel elements, and wherein each first channel element corresponds to product of one of the multiple symbol amplitudes with one of multiple zoom factors；Each corresponding performance number in multiple performance numbers is provided according to one of multiple first phase element；And the signal metric is calculated according to multiple performance numbers.The device of signal metric is provided the present invention also provides a kind of for transmitter.
Description
Technical field
The present invention relates to the transmitters for communication system to provide the method and device of signal metric, more particularly to provides calculating
The method and device of the nonlinear properties measurement of complexity reduction.
Background technique
Communication system, especially wireless communication system have become the important component of modern society.In general, in nothing
In line communication system, the radio wave that base station is established covers a unit, therefore a terminal (such as user equipment (user
Equipment, referred to as UE)) can by flow through the radio communication channel between base station and terminal signal transmit and base station
Communication.It is combined by different messaging parameter, such as the combination of different modulation schemes and/or encoding scheme, so that being related to wireless communication
The communication channel of number environment propagated and medium can be divided into multiple physical channels of multiple access.Under part physical channel executes
Row channel is to realize the transmission from base station to terminal, and other physical channels are assigned as up channel then to realize from terminal to base
The transmission stood.For other side, part physical channel is transmitted for data, and other physical channels are then used to control letter
Breath transmission, the control information is for initializing, managing, transferring and/or terminating the communication channel.
In a wireless communication system, terminal equipped with one be used to form and send uplink signal to base station transmitter,
The transmitter includes that a power amplifier (power amplifier, hereinafter referred to as PA) is transmitted for signal.Since power is put
The linear characteristic of big device, peak-to-average power ratio (Peak-to-Average of the maximum transmission power of transmitter by transmitted waveform
Power Ratio, hereinafter referred to as PAPR) limitation.For example, passing through in the third generation (3G) wideband code division multiple access (WCDMA) standard
Multi-code transmission techniques can support higher message transmission rate in the upstream direction.Up channel can be advised in Release 6 simultaneously
It is established in model, for example, setting up 4 E-DPDCHs (enhanced dedicated physical data channel), 1 E-DPCCH (enhanced dedicated object
Manage control channel), 1 DPCCH (Dedicated Physical Control Channel) and 1 HS-DPCCH (High-Speed Dedicated Physical Control Channel).And
And, it is well known that due to will lead to higher PAPR using complicated amplitude modulation system, and therefore it is required that the bigger PA range of linearity
To obtain with root mean square root (root-mean-square, hereinafter referred to as RMS) power.Prevent power amplifier requirements more High Linear
The method of degree first is that requirement to maximum transmission power is reduced, to keep terminal that there is reasonable cost and power consumption.In addition, such as
Fruit transmission power is more than the maximum power with linear characteristic, it may appear that the interference in non-linear distortion and formation band and outside band
Source.In the technical specification 25.101 of third generation partner program (3GPP), definition cubic measure (cubic metric, with
Lower abbreviation CM) come determine third order intermodulation distortion quantity and close to transmission signal PAPR.Value based on CM, passes through maximum
Power reduce (maximum power reduction, hereinafter referred to as MPR) reduction amount (back-off), it may be determined that MPR and
The maximum transmission power of reduction, to reduce nonlinear effect to the greatest extent.Therefore, maximum power is changed by dynamic, can not considered
Physical channel configuration and the characteristics of PAPR in the case where make full use of the range of linearity of PA.The calculation formula of the CM and MPR are as follows:
V=rI+j*rQ, vnorm=v/ | v | -- (eq1)
MPR=max (CM-1,0) -- (eq3)
MPR_unq=max (CM_unq-1,0)
Wherein, v is to be propagated (spreading), zoom factor scaling, IQ mapping 12 (IQ mapping), scrambling code
(scrambling) and the filtered propagation waveform of shaping pulse；CM_unq is a non-quantized CM, and MPR_unq is one
A non-quantized MPR；Vnorm be standardize version waveform v, function | v | be the absolute value of v；Function (*) rms is input ginseng
Several root-mean-square values；C1 and c2 is two constants depending on physical channel configuration, including number of physical channels (Nphch), spread spectrum
The factor, channel code etc. are also relied on the normalization of the CM based on reference waveform.And promote integer function CEIL0.5dB(*) is then used for will
Input parameter be promoted to it is minimum between be divided into 0.5dB closest to numerical value, this is more than or equal to the input parameter closest to numerical value.Citing
For, lifting function CEIL0.5dB0.35dB can be promoted to 0.5dB by (*), perhaps by 0.15dB be promoted to 0.5dB or
- 0.45dB is promoted to 0dB, etc..
MPR is for controlling transmission power to judge permitted maximum power.That is, MPR must be generated in waveform
It calculates before, and is heavily dependent on physical channel configuration.In 3 gpp, channel configuration can change in each time slot
Become twice (time slot is a scheduled time interval, about 11/15 millisecond) so that MPR handle the time by
To limitation.And CM calculates the practical CM before must predicting transmitted waveform formation, and works under critical time constraints.It is another
A difficulty is that CM calculating is related to cube operation and is related to the high dynamic range in fixed-point implementation.
Summary of the invention
The invention discloses a kind of reduction time restriction and can to reduce difficulty in computation be that transmitter provides the side of signal metric
Method and device.
A method of signal metric, summation of the transmitter according to multiple corresponding first channel elements are provided for transmitter
The each of multiple first phase elements is provided, wherein each first channel element corresponds to one of multiple symbol amplitudes
With the product of one of multiple zoom factors；It is provided according to one of multiple first phase element every in multiple performance numbers
One corresponding performance number；And the signal metric is calculated according to multiple performance numbers.
A kind of to provide the device of signal metric for transmitter, which includes accumulated unit and computing unit.Cumulative unit
Summation according to multiple corresponding first channel elements provides each of multiple first phase elements, wherein each first letter
Road element corresponds to product of one of the multiple symbol amplitudes with one of multiple zoom factors；And computing unit foundation
One of multiple first phase element provides each corresponding performance number in multiple performance numbers, and according to multiple function
Rate value calculates the signal metric.
The above-mentioned method and device for providing signal metric for transmitter combines wheel stream calculation cubic metric (CM) according to scaling,
Rather than cubic metric is calculated by time-domain integration (temporal integration) operation, so as to be effectively reduced
Cost and resource (time, power, computing hardware etc.) needed for calculating.
Detailed description of the invention
Fig. 1 is the structural schematic diagram for the transmitter that an embodiment of the present invention provides.
Fig. 2 is the power value comparison table that an embodiment of the present invention provides.
Fig. 3 is the schematic diagram of the metric calculation module of the transmitter of Fig. 1.
Fig. 4 to fig. 6 is the regulation coefficient selection scheme of the adjustment selector of the metric calculation module of Fig. 3 referring to figure.
Specific embodiment
Some vocabulary is used in this specification and claims to refer to specific component.The skill of this field
Art personnel are, it is to be appreciated that hardware manufacturer may call same component with different nouns.This specification and right are wanted
In a manner of asking not using the difference of title as differentiation component, but using the difference of component functionally as the criterion distinguished.
Mentioned "comprising" is an open term throughout the specification and claims, thus should be construed to " include
But it is not limited to ".In addition, " coupling " word includes any direct and indirect electrical connection herein.Therefore, if being retouched in text
It states first device and is coupled to second device, then second device can be directly electrically connected in by representing first device, or by other
Device or connection means are electrically connected indirectly to second device.
Referring to FIG. 1, it is the transmitter 10 that an embodiment of the present invention provides.The transmitter 10 can be applied to wirelessly
Communication system terminal, such as: being applied in the subscriber terminal equipment (UE) for the mobile communication system for meeting 3GPP standard/specification.By
The bit of data and/or information that transmitter 10 transmits is grouped as multiple modules (such as transmission module), and multiple module can
It is arranged to one or more channels (such as physical channel), specifically, such as from channel CH (1), CH (2) ..., CH (n) to letter
Road CH (Nphch).In present embodiment, those channels can be respectively a DPDCH, a DPCCH, a HS-DPCCH,
One E-DPCCH and four E-DPDCHs.The bit of each channel CH (n) is multiplied by corresponding channel code cs (n) and by corresponding
Zoom factor bt (n) is zoomed in and out to be propagated, and then passes through an IQ mapping 12 and in-phase component and/or orthorhombic phase part
It is mapped.Wherein, the result of IQ mapping 12, which is often expressed as one, has real part (corresponding to in-phase component) and imaginary part (corresponding
In orthorhombic phase part) plural number.The channel code of different channels can be different, and the zoom factor of different channels can different or phase
Together.The number (i.e. Nphch) of channel can be specifically arranged according to different application scenarios.For example, basic in order to support
WCDMA function needs to distribute channel DPDCH and DPCCH；And in order to support advanced HSDPA (high-speed slender body theory letter
Road), it needs simultaneously using three channels: DPDCH, DPCCH and HS-DPCCH.For using HSDPA and more advanced HSUPA
The application scenarios of (high speed ascending grouped access channel), can establish five to seven channels, including a DPDCH, a DPCCH,
One HS-DPCCH, an E-DPCCH and one to four E-DPDCH (s).Different application scenarios can mutually switch, example
Such as, time slot (slot) switches in turn.
The result of each IQ mapping 12 of channel CH (1) to CH (Nphch) is overlapped by an adder 14, is folded
The summation added is mixed (scrambled) by a scrambling code scr (for example, a complicated scrambling code), is then further led to
It crosses a real part extractor 16a and an imaginary part extractor 16b is decomposed into real and imaginary parts two parts.One shaping pulse filter
Wave device 18a forms a digital signal waveform to transmit the real part, and another pulse shaping filter 18b forms another number
Signal waveform is to transmit the imaginary part.The digital signal waveform of the real and imaginary parts respectively by two DAC (digital analog converter) 20a and
20b is converted into corresponding analog signal waveform.Resulting analog signal waveform pass through respectively two low-pass filter 22a and
22b is filtered, and is amplified respectively by two controllable amplifiers 26a and 26b of an amplifier module 24.Then, two
A amplified waveform is modulated into a modulated signal according to phase appropriate and carrier frequency by a uplink frequency converter 28.
The modulated signal, which carries, represents bit symbol to be sent, and is amplified by a controllable amplifier (PA) 30, then leads to
Antenna 32 is crossed to travel in air.
The PA 30 sets signal power level appropriate, to guarantee to be properly received the signal strength of base station signal.In order to
The amplitude of modulated signal is limited in the range of linearity of PA 30, which further includes 36 He of metric calculation module
One power control module 34.The power control module 34 is before the uplink frequency converter 28 by judging gain setting distribution
After or, to determine actual emission power.
Although multi-code transmission can provide higher message transmission rate, also imply that if using having larger PAPR
The physical channel of (Peak-to-Average Power Ratio) configures, then obtainable RMS (root- in terminal 10
Mean-square) power can be smaller.And the terminal 10 needs to guarantee the non-linear distortion that peak power will not cause PA 30, and
Lesser RMS power is unable to satisfy this condition.It is therefore desirable to have power control appropriate.It is suitable in order to realize in present embodiment
When power control, which is configured according to physical channel and/or the CM that is provided by metric calculation module 36
(cubic metric) judges maximum power loss (compared with the amplitude peak of a reference waveform).
The metric calculation module 36 generates it in transmission signal (such as analog signal waveform of low-pass filter 22a and 22b)
It is preceding that the function of prediction MPR is provided.According to equation eq1 and eq2 (please referring to background technique), a kind of side calculating cubic metric CM
Method is to generate time domain waveform (temporal waveform) v for operating on multiple chip rates (chip rate) to characterize this
The effect of pulse shaping filter 18a and 18b, and pass through numerical value time-domain integration (numerical temporal
Integration the root mean square (root-mean-square) of waveform v) is calculated.But such calculation method is time-consuming and extremely complex.
The present invention calculates the CM according to the random expected value in whole signal amplitudes, rather than by that will be transmitted
The time domain waveform of signal calculate CM.Since the signal (hereinafter referred to as ve) that will be transmitted can be by sinusoidal carrier signal tune
System, the amplitude (for example, peak amplitude of signal envelope) of signal ve can control its root mean square.In any spy of given application scene
(for example, in period of transmission signal code) is carved in timing, and signal ve carries one or more synchronizing symbols, the synchronizing symbol point
Not Dui Ying it is one or more it is different (co-existing) channel coexists, in this way, the amplitude of signal ve can be according to coexisting channel
Synchronizing symbol determine.Wherein, the symbol amplitude of each synchronizing symbol is zoomed in and out by the zoom factor of respective channels.It is right
In each symbol, symbol amplitude is multiple symbols according to value of symbol from conformation mapping (constellation mapping)
It is selected in amplitude alternative, and zoom factor is selected from multiple zoom factor alternatives according to channel configuration.
The symbol amplitude alternative of the synchronizing symbol and the zoom factor alternative that channel coexists combine, and shape
Alternative is combined at scaling.A performance number (power terms) A (i) is defined as representing a scaling knot wherein as a result,
Close the amplitude of the signal ve under alternative:
Wherein, element i indicates that one of scaling combines alternative, which is combined symbol vibration
The set of width alternative and zoom factor alternative.RI (i) and rQ (i) be correspond respectively to signal ve in-phase component and
Two phases of orthorhombic phase part.Element x indicates that each synchronization (or coexisting) channel carried by in-phase component, element y indicate
It each of is carried by orthorhombic phase part and channel coexists.Al (i, x) (or al (i, y)) represents the multiple symbols for being selected from respective channels
One symbol amplitude of one of amplitude alternative, the channel index (indexed) by x (or y).Bt (x) (or bt (y))
It is that the zoom factor come is selected from multiple zoom factor alternatives of respective channels, the channel is by x (or y) rope
Draw (indexed).
It is appreciated that in some embodiments, one of rI (i) and rQ (i) are possible to be equal to zero, at this point, performance number A
(i) it only needs to be calculated according to the rI (i) of non-zero or rQ (i).
Referring to FIG. 2, it is an embodiment of the performance number A (i).Assuming that two channels are (by ch1 and ch2
Index) by same Xiang Zaibo, without quadrature channel, then phase parameter rI (i) is by two channel parameter al (i, ch1) * bt
(ch1) it is mutually added up with al (i, ch2) * bt (ch2), and eliminates (vanishes) phase parameter rQ (i).In present embodiment, al
Any one symbol amplitude in (i, ch1) and al (i, ch2) is selected from alternative { 1,3 }, and zoom factor bt (ch2) is then
From selection one in alternative { bt_ch2 ,-bt_ch2 }.Therefore, eight (from A (0) to A (7)) covering parameter al be can get
The performance number of all alternatives of (i, ch1), al (i, ch2) and bt (ch2).
It is modulated generally, for the QPSK (quadrature phase shift keying) for being equivalent to BPSK (binary phase shift keying), same
In one of phase branch and orthorhombic phase branch, the correspondence symbol amplitude for conformation mapping is from two alternatives { 1, -1 }
It chooses.For being equivalent to the 16-QAM (quadrature amplitude modulation) of 4-PAM (pulse amplitude modulation), in phase branch and orthorhombic phase
In one of branch, symbol amplitude crosses over (spans) four alternatives { 1, -1,3, -3 }.For in each same phase and just
64-the QAM with 8-AM in Jiao Xiang branch, the symbol amplitude have eight alternatives { 1 ,-1,3 ,-3,5 ,-5,7 ,-7 }.
For certain channels, zoom factor crosses over two alternatives a: positive value and a negative value.Due to symbol amplitude alternative
Quantity with zoom factor alternative is 2 power, therefore the quantity of performance number A (i) is also 2 power.For example, it is assumed that having
3 channels with non-zero zoom factor are phase branch, and 4 channels with non-zero zoom factor are orthorhombic phase branch, and
All channels are all transmitted using BPSK, then the quantity of performance number A (i) will be 32, it may be assumed that from A (0) to A (31).Specific calculating process
Are as follows: assuming that described 3 channels with non-zero zoom factor are respectively a, b, c, then combination includes: a (±) b (±) c tetra-
Kind, it is assumed that described 4 channels with non-zero zoom factor are respectively d, e, f, g, then combination includes: d (±) e (±) f
Eight kinds of (±) g, then the quantity of the performance number A (i) is 4*8=32.The all of signal amplitude are covered in view of performance number A (i)
Possibility, the CM can be obtained according to signal metric M3, and the signal metric M3 of the third order distortion of the estimation signal ve passes through following
Formula calculates:
Wherein, 2K is the total number of performance number A (i), and function E [*] provides random expected value, which can root
It is estimated according to performance number A (i).For example, 3 powers of the quadratic sum of in-phase component rI and orthorhombic phase part rQ can be by each
The average value of 3 powers of performance number A (i) is estimated.It note that the CM can also be obtained by equation eq2 by measurement M3.Namely
It says, in the case where not by the numerical value time-domain integration of waveform root mean square, the CM can also be obtained easily (MPR is similarly).
It is appreciated that in some embodiments,With
One of be possible to be equal to zero, at this point, signal metric M3 can be calculated according only to the part not equal to zero.Referring to FIG. 3, it is
The metric calculation module 36 that an embodiment of the present invention provides.The metric calculation module 36 includes one cumulative unit 38, one
Computing unit 40 and a map unit 46.The cumulative unit 38 includes one or more power modules 44, each power module
44 correspond to a performance number A (i) and including two both phase integrators 42a and 42b.Both phase integrator 42a corresponds to same
Phase branch by integrating channel parameter al (i, x) the * bt (x) that channel coexists for corresponding to phase branch, and generates
Phase parameter rI (i).Similarly, both phase integrator 42b corresponds to orthorhombic phase branch, by that will correspond to orthorhombic phase branch
Channel parameter al (i, y) the * bt (y) that channel coexists is integrated, and generates phase parameter rQ (i).Both phase integrator 42a shape
At one can for each performance number A (i) provide phase parameter rI (i) phase module, and both phase integrator 42b formed it is another
It is a the phase module of phase parameter rQ (i) to be provided for each performance number A (i).Joined according to the phase of each performance number A (i)
Number rI (i) and rQ (i), the computing unit 40 can calculate the performance number A (i) and signal metric M3.
Signal metric M3 can also be adjusted further to obtain the CM.The map unit 46 provides a mapping function 50
To measurement M3.In the embodiment of fig. 3, which executes a Linear Mapping, which passes through function: ym
=a*xm+b will input xm and be mapped in corresponding output ym, wherein a is gain adjustment factor, and b is offset regulation coefficient.It should
Therefore the output of mapping function 50 is quantified by a quantifying unit 52, which executes the lifting function in equation eq2
(ceiling function)。
It adjusts selector 48 and regulation coefficient a and b is provided.Specifically, the adjustment selector 48 according to channel configuration and/or
Other relevant parameters (as indicated the bit of how many chip during spread spectrum spreading factor encoded), from multiple alternatives
One group of suitable regulation coefficient (a, b) of middle selection.In the present embodiment, the regulation coefficient (a, b) of various combination can be according to logical
Believe protocol/standard classification.
It is appreciated that in some embodiments, one of a and b are possible to be equal to zero, at this time, it is only necessary to according to being not zero
A or b.
Referring to FIG. 4, it is selected for the regulation coefficient to be followed up by adjustment selector 48 that an embodiment of the present invention provides
Process 100.If signal only by WCDMA transmission, selects first group of regulation coefficient (a, b).If signal will be by
WCDMA and HSDPA (but not being HSUPA) transmission, then select second group of regulation coefficient (a, b).If signal will be by
WCDMA, HSDPA and HSUPA transmission then select third group regulation coefficient (a, b).That is, there is 3 groups of different adjustment
Coefficient (a, b) is respectively suitable for: only being supported WCDMA, supports WCDMA+HSDPA and is supported the application of WCDMA+HSDPA+HSUPA
Scene is selected with specific reference to used application scenarios.The regulation coefficient selects process 100 can be in a new CM value quilt
Start to execute when calculating.
Referring to FIG. 5, it is second of regulation coefficient selection mode that another embodiment of the present invention provides.According to active
Code digit, it is known that the quantity of used channel, and therefore can be according to the channel quantity for communication to determine
It need to select regulation coefficient.For example, first group of regulation coefficient (a, b) is selected, if active generation if source code number is 0
Yardage word is 1, then selects second group of regulation coefficient (a, b), etc..Referring to Fig. 6, it is provided for a further embodiment of this invention
Another regulation coefficient select process 300, which is executed by the adjustment selector 48.The process 300 includes following step
It is rapid:
It step 302, whether is 0 according to corresponding zoom factor, it is to be understood that whether E-DPDCH is not used by.If E-
DPDCH is not used by, then enters step 304, otherwise enter step 314.
Step 304, whether it is equal to 0 according to another associated zoom factor, it is to be understood that whether HS-DPCCH is not used.
If be not used, 306 are entered step, otherwise enters step 310.
Step 306, whether it is equal to 0 according to another corresponding zoom factor, it is known that whether E-DPCCH is not sharp
With.If unutilized, 308 are entered step, otherwise enters step 310.
Step 308, since HSDPA and HSUPA are not applied, 0 directly is set by the CM.
Step 310, whether it is arranged to 1 according to a corresponding parameter, it is to be understood that whether DPDCH is set to use.If
DPDCH is set to use, then enters step 312, otherwise enter step 322.
Step 312, first group of regulation coefficient (a, b) is selected.
Step 314, if DPDCH is set to use, 316 is entered step, otherwise enters step 324.
Step 316, if the quantity of E-DPDCH is 1,318 is entered step, otherwise enters step 320.
Step 318, the 7th group of regulation coefficient (a, b) is selected for mapping function 50.
Step 320, the 8th group of regulation coefficient (a, b) is selected.
Step 322, second group of regulation coefficient (a, b) is selected.
Step 324, if the spreading factor of the first E-DPDCH is greater than or equal to 2,332 are entered step, otherwise enters step
Rapid 326.
Step 326, if only one E-DPDCH is used, 328 is entered step, otherwise enters step 330.
Step 328, third group regulation coefficient (a, b) is selected for mapping function 50.
Step 330, third group regulation coefficient (a, b) is selected.
Step 332, if two E-DPDCH are used, 334 is entered step, otherwise enters step 336.
Step 334, the 5th group of regulation coefficient (a, b) is selected.
Step 336, the 6th group of regulation coefficient (a, b) is selected.
Process 300 is demonstrated in view of by the type of adopted channel, the quantity of channel and by the spread spectrum of use
Because the regulation coefficient of the period of the day from 11 p.m. to 1 a.m selects.The adjustment selector 48 can determine one group of tune appropriate according to process 100,200 and 300
Integral coefficient (a, b), to adapt to different application scenarios.The values of difference group regulation coefficient (a, b) can be according to simulation and/or specific
The statistics of experiment is calibrated.For example, the measurement M3 and corresponding CM in each application scenarios can be estimated by simulating and/or testing
It calculates, so as to obtain the M3-CM mapping of each scene.Therefore, different M3-CM mapping can be respectively by different regulation coefficients
Characterization.And the scene with similar M3-CM mapping can be grouped to share same group of regulation coefficient.Although being appreciated that figure
3 embodiment uses Linear Mapping, and in various embodiments, other kinds of mapping (such as Nonlinear Mapping) can also be with
It is used.
The metric calculation module 36 can be realized by hardware, firmware and/or software.For example, transmitter 10 can be by one
Controller control (not shown), which, which executes the program instruction being stored in memory (volatibility or non-volatile), comes in fact
The function of existing metric calculation module 36.Different regulation coefficients (a, b) can store as multiple catalogues of an inquiry table.In addition to
M3 is measured, which, which can also be generalized further by signal metric M (n), calculates high-order (for example, n rank) distortion, tool
Body formula are as follows:
That is, signal metric M (n) can be according to the sum of n times side of each performance number A (i) and performance number A
(i) the n times side of summation calculates.For certain PA 30, the influence of (modeled) high-order distortion can be moulded well
(effect), and its performance can preferably be controlled according to the understanding to high-order measurement M (n).In conclusion the present invention tries root
Wheel stream calculation CM is combined according to scaling, rather than CM is calculated by time-domain integration (temporal integration) operation, from
And cost and resource (time, power, computing hardware etc.) needed for calculating can be effectively reduced.Although the present invention with reference to
WCDMA/HSDPA/HSUPA is to be best understood from content discussed above, however, the present invention, which may extend to, needs to estimate the non-of signal
Any transmitter and/or communication system of linear measurement.
Although the present invention is disclosed above in a preferred embodiment thereof, however, it is not to limit the invention, any affiliated skill
Technical staff in art field can do some changes without departing from the scope of the present invention, but belong to protection of the invention
In range.
Claims (16)
1. a kind of provide the method for signal metric for transmitter, which is characterized in that this method comprises:
Transmitter provides corresponding first phase element according to the summation of the first channel element of the first quantity, wherein described first
The first channel element of each of first channel element of quantity corresponds to one of multiple symbol amplitudes and multiple scalings
The product of one of the factor；
Corresponding second phase element is provided according to the summation of the second channel element of the second quantity, wherein each second channel
Element corresponds to product of one of the multiple symbol amplitudes with one of multiple zoom factors；
Performance number is provided according to the first phase element and the second phase element；And
The signal metric is calculated according to the performance number.
2. providing the method for signal metric as described in claim 1 for transmitter, which is characterized in that according to the first phase
Element and the second phase element provide performance number
The performance number is calculated according to the quadratic sum of the first phase element and the second phase element.
3. providing the method for signal metric as claimed in claim 2 for transmitter, which is characterized in that
For the performance number, this according to one of multiple symbol amplitude and one of multiple zoom factor multiplies
Product, provides the first channel element of corresponding first quantity and the second channel element of corresponding second quantity.
4. providing the method for signal metric as described in claim 1 for transmitter, which is characterized in that according to the performance number meter
Calculating the signal metric includes:
According to the n times side of performance number and calculate the signal metric.
5. providing the method for signal metric as described in claim 1 for transmitter, which is characterized in that according to the performance number meter
Calculating the signal metric includes:
The signal metric is calculated according to the n times side of performance number summation.
6. providing the method for signal metric as described in claim 1 for transmitter, which is characterized in that further comprise:
The signal metric is weighted and deviated by a regulation coefficient, which includes that an adjust gain and an adjustment are inclined
At least one of shifting amount person.
7. for transmitter providing the method for signal metric as claimed in claim 6, which is characterized in that the of first quantity
One channel element is related to the first channel of the first quantity respectively, and the second channel element of second quantity is counted with second respectively
The second channel of amount is related, and this method further comprises:
The regulation coefficient is determined according to channel configuration.
8. for transmitter providing the method for signal metric as claimed in claim 6, which is characterized in that the transmitter is according to being selected from
One parameter of multiple parameters alternative emits signal, and this method further comprises:
The regulation coefficient is determined according to selected parameter.
9. a kind of provide the device of signal metric for transmitter, which is characterized in that the device includes:
Cumulative unit, which includes first phase module and second phase module, for each performance number, first phase
Position module provides corresponding first phase element according to the summation of the first channel element of the first quantity, wherein first quantity
The first channel element of each of the first channel element correspond to one of multiple symbol amplitudes and multiple zoom factors
The product of one of them；And second phase module provides corresponding the according to the summation of the second channel element of the second quantity
Two phase element, wherein each second channel element corresponds to one of multiple symbol amplitudes with multiple zoom factors wherein
One of product；And
Computing unit provides performance number according to the first phase element and the second phase element, and according to the function
Rate value calculates the signal metric.
10. providing the device of signal metric as claimed in claim 9 for transmitter, which is characterized in that
The computing unit provides the performance number according to the quadratic sum of the first phase element and the second phase element.
11. providing the device of signal metric as claimed in claim 10 for transmitter, which is characterized in that
For each performance number, the first phase module also according to one of multiple symbol amplitude and multiple scaling because
The product of one of son, provides the first channel element of first quantity；And
For each performance number, the second phase module also according to one of multiple symbol amplitude and multiple scaling because
The product of one of son, provides the second channel element of second quantity.
12. for transmitter providing the device of signal metric as claimed in claim 9, which is characterized in that the computing unit is into one
N times side and the calculating signal metric of the step according to performance number.
13. for transmitter providing the device of signal metric as claimed in claim 9, which is characterized in that the computing unit is into one
Step calculates the signal metric according to the n times side of performance number summation.
14. providing the device of signal metric as claimed in claim 9 for transmitter, which is characterized in that further comprise one
Map unit, the map unit are weighted and are deviated the signal metric by a regulation coefficient, which includes that adjustment increases
At least one of benefit and adjustment offset person.
15. providing the device of signal metric as claimed in claim 14 for transmitter, which is characterized in that first quantity
First channel element is related to the first channel of the first quantity respectively, and the second channel element of second quantity is respectively with second
The second channel of quantity is related, which further judges the regulation coefficient according to channel configuration.
16. providing the device of signal metric as claimed in claim 14 for transmitter, which is characterized in that the transmitter is according to choosing
Emit signal from a parameter of multiple parameters alternative, and the map unit is further determined according to selected parameter
The regulation coefficient.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US13/113,311 US9161321B2 (en) | 2010-09-20 | 2011-05-23 | Method and apparatus providing signal metric for transmitter |
| US13/113,311 | 2011-05-23 | ||
| CN201110432419.0A CN102801440B (en) | 2011-05-23 | 2011-12-21 | Method and device for supplying signal measurement to emitter |
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| Application Number | Title | Priority Date | Filing Date |
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| CN201110432419.0A Division CN102801440B (en) | 2011-05-23 | 2011-12-21 | Method and device for supplying signal measurement to emitter |
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| CN104768212A CN104768212A (en) | 2015-07-08 |
| CN104768212B true CN104768212B (en) | 2019-03-15 |
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| CN201510107103.2A Expired - Fee Related CN104768212B (en) | 2011-05-23 | 2011-12-21 | The method and device of signal metric is provided for transmitter |
| CN201110432419.0A Expired - Fee Related CN102801440B (en) | 2011-05-23 | 2011-12-21 | Method and device for supplying signal measurement to emitter |
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101180790A (en) * | 2005-03-18 | 2008-05-14 | 纳维尼网络公司 | Active gain control system of communication receiver |
| US20080305824A1 (en) * | 2007-04-20 | 2008-12-11 | Interdigital Technology Corporation | Apparatus and method for computing maximum power reduction for a umts signal |
| TW201101897A (en) * | 2008-12-16 | 2011-01-01 | Nokia Corp | Calculating a non-linearity metric |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| TWI429214B (en) * | 2007-04-20 | 2014-03-01 | Interdigital Tech Corp | Apparatus and method for computing maximum power reduction for a umts signal |
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2011
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Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101180790A (en) * | 2005-03-18 | 2008-05-14 | 纳维尼网络公司 | Active gain control system of communication receiver |
| US20080305824A1 (en) * | 2007-04-20 | 2008-12-11 | Interdigital Technology Corporation | Apparatus and method for computing maximum power reduction for a umts signal |
| CN101669295A (en) * | 2007-04-20 | 2010-03-10 | 交互数字技术公司 | Be used to calculate the apparatus and method of the maximum power decay of UMTS signal |
| TW201101897A (en) * | 2008-12-16 | 2011-01-01 | Nokia Corp | Calculating a non-linearity metric |
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| CN102801440B (en) | 2015-04-15 |
| CN104768212A (en) | 2015-07-08 |
| CN102801440A (en) | 2012-11-28 |
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