SU1030961A1 - R.f. pulse sequence shaper - Google Patents

Abstract

1. RADIO IMPULSE SEQUENCE FORMER containing a multi-tap delay line, the taps of which are connected to the inputs of the switching matrix, the control inputs of which are connected to the outputs of the control unit, N non-verse delay lines, the inputs of which are connected to the corresponding outputs of the switching matrix, a. The taps of each nonius delay line are connected to the input of the corresponding electronic switches, the control inputs of which are connected to the corresponding outputs of the control unit, and the outputs are connected to each other, as well as the accumulator of radio pulses, so as to reduce distortion | 1 spectrum of generated radio pulses while improving the accuracy of regulating their temporary positions :, serially connected sensors of the phase shift keying code, the output of which is connected to the input of the unit, are entered into it ION and multidrop input delay line, and a clock pulse generator, one output of which is connected to a control input multidrop delay line, and the second - with the control inputs. the first and second quadrature channels, the same-name control inputs which are combined and connected to the connection points of the outputs of the corresponding electronic keys, the information inputs are connected to the corresponding outputs of the control unit, the output to the inputs of the radio pulse adder, and the series-connected harmonic generator oscillations and a phase-shifting circuit, the output of which is connected to the signal input of the second quadrature channel, while the signal input of the first quadrature channel connected to the output: harmonic oscillator. 2. Fа1 1 armature according to claim 1, which is indicated by the fact that each quadrature channel contains N identical circuits including (L serially connected first inverter, first adder and key, as well as a pulse interpreter, the output of which is connected to It drives the key input, with the first input of the first inverter, the second, the first adder input and the pulse maker input are interconnected and their connection point is the control input of the quadrature channel, the second input of the first inverter is informational an input quadrature unit, successively connected by a second inverter, m inputs of a single connection e m outputs of the second adder®, a third adder and an attenuator, the output of the second is called the output of the wedding channel, and the phase shifter whose input is connected to the output of the quadrature channel, and the output is connected to the second input of the attenuator, while (t + 1) -th output of the second adder is connected to the control input of the phase shifter, controlling the 5 input of the second inverter, and the second input of the third cyhSMaaropa, and the inputs to the outputs of the keys Ni Entichnyh chains.

Description

The invention relates to radio engineering and can be used to form sequences of broadband phase-shift keyed radio pulses with adjustable parameters, for example, in radar simulators to simulate the signals reflected from group objects in transmitters of response interference.

A radio pulse sequence former is known, based on the use of ultrasonic multiturn delay lines, in which radio pulse sequences are formed by switching taps of the main - and vernier delay line using switching matrices 3 However, when forming sequences of broadband radio pulses, a known device is observed to distort the spectrum of the generated signals, due to limited bandwidth of multi-drop lines holders.

The closest to the proposed one is a radio pulse pulse generator containing a multi-tap delay line whose taps are connected to the inputs of the switching matrix, the control inputs of which are connected to the outputs of the control unit, N nonius delay lines, the inputs of which are connected to the corresponding outputs; the switching matrices, and the taps of each vernier delay line are connected to the inputs of the corresponding electronic switches whose control inputs are connected to the corresponding outputs of the unit UP the outputs, and the outputs are interconnected, as well as the adder of radio pulses 2,

However, in the known generator of radio pulse sequences, while regulating the temporal position of the broadband radio pulses in the sequence being formed, carried out by connecting the corresponding branches. Dangers of the spectra of radio pulses and errors in setting their temporal position caused by limited bandwidth of delay lines connected in series, which further reduces their total bandwidth, as well as nonidentity of the amplitude-frequency characteristics of the channels, including the Vernier delay line and radio pulse envelope converter.

The purpose of the invention is to reduce the distortion of the spectrum of the generated radio pulses while at the same time improving the accuracy of adjusting their temporal position.

The goal is achieved by the fact that a shaper of radio pulse sequences containing a multi-drop delay line, whose taps are connected to the inputs of the switching matrix, whose control inputs are connected to the outputs of the control unit, N

Vernier delay lines, the inputs of which are connected to the corresponding outputs of the switching matrix, and the tapping of each Vernier line

The delays are connected to the inputs of the corresponding electronic switches, the control inputs of which are connected to the corresponding outputs of the control unit, and the outputs are interconnected, as well as an adder of radio pulses, a serially connected code of the phase shift keying code, the output of which is connected to the input of the control unit and the input multichangeal

5 delay lines, and a clock pulse generator, one output of which is connected to the control input of the multi-drop delay line, and the second to the control inputs of the vernier delay lines,

the first and second quadrature channels, of the same control inputs of which are combined and connected to the connection points of the outputs

5 corresponding electronic keys, informational inputs are connected to the corresponding outputs of the control unit, outputs are connected to the terminal, radio accumulator accumulators,

as well as series-connected harmonic oscillations and a phase-shifting circuit, which is connected to the signal input of the second quadrature channel, while the signal input of the first quadrature channel is connected to the output of the harmonic oscillator.

In addition, each quadrature channel contains N identical circuits, including a first inverter connected in series, a first adder and a key, as well as a pulse shaper, the output of which is connected to the control input of the key, the first input of the first inverter, the second input of the first adder and the input of the driver the pulses are interconnected and their connection point is the control input of the quadrature channel; the second input of the first inverter is the information input of the quadrature channel; nnye second inverter, m whose inputs are connected to m, vyhodaivHi second adder, a third adder and attenuator vosod koto cerned is. A quadrature input channel, as well as a phase shifter, which is the input of the quadrature channel, and the output is connected to the second input of the attenuator, while the (t + 1) -th output of the second sum of the torus is connected to the control of the input of the phase shifter, the control input of the second inverter and SECOND input of the third adder, and inputs with outputs of keys N identical to the chain. FIG. 1 shows the structure. The turntable electrical circuit forms a sequence of radio pulses; in FIG. 2 - time diagrams that show his work. The shaper of a sequence of radio pulses contains a phase shift keying sensor 1, a multi-lead delay line 2, a switching matrix 3, a control block 4, N vernier delay lines, electronic keys b, an adder 7, a harmonic oscillator 8, a phase-shifting circuit 9, the first 10 and the second 11, quadrature channels, a clock generator 12, The first 10 and second 11 quadrature channels contain N identical circuits including the first inverter 13, the first adder key 15 and the driver 16 pulses, as well as the second total p 17, second inverter 18, a third adder 19, attenuator 20, phase rotator 21, of sequences of RF pulse shaper operates as follows. in the initial state, the registers -22, -22pj Ps1mti, included in control block 4, are in the zero state, there are no control codes on the information inputs of the first 10 and second 11 quadrature channels, and decoder outputs 23 on the outputs. - 22f of control block 4; there are no control signals and all switches 24 of switching matrix 3 and keys b, i connected to vernier lines 5 - 5 | delays are in the closed state. The output signal from the generator 8 harmonic oscillations goes to the signal input of the first quadrature channel 10 and through the phase-moving (L / 2) circuit 9 to the signal input of the second quadrature channel 11, C outputs of the phase rotator 21 of each of the quadrature channels 10, 11 signal It is located at the input of the attenuator 20. Since the amplitude codes in the information inputs of the quadrature channels 10, 11 are absent in the initial state, the attenuators 20 are closed and prevent the passage of radio signals to the output of the sequence equalizer; diodes, Sensor 1 of the phase manipulation code generates a periodic mode, deocode with a period T, determines the law of intrapulse phase modulation of the generated radio pulses, at the times preceding the generation of the next code of phase manipulation using the sensor 1 code. The 25 control codes, included in the 6th | by 4 controls, generate codes defining the mutual temporal position of the Fovmir 5 e, my radio pulses, as well as their X amplitudes for each quadrature channel 10 and 11, which with the help of KONB The vjyTaTOpa 26 control unit 4 codes are written to its memory registers 22. Codes that determine the amplitudes of modulated signals from the outputs of registers 22–22 of the memory are sent to the corresponding information inputs of the corresponding from quadrature channels 10 and 11. Coya, which determine the mutual radio pulse from the registers of 22 memory rots to the corresponding decrypt | ry 23;, - 23r, which produce control potentials and control the operation; keys 24 commuting matrix 3 and keys b vernier line 5.- 5 delays. Moreover, the leading bits of the temporary position code are used to control the key and 24 switching matrix 3, and the lower ones - to control keys of the delay vernier 5f keys. In accordance with the values of the control banks, the decoders 23 of the switch matrix 24 of the switching matrix 3 and keys b nonius lines 5 delay, Video code. phase manipulation generated by the sensor of the phase manipulation code 1 is fed to the generator 12 clock pulses to synchronize it and to the input of the multi-branch delay line 2, to the control input of which clock pulses come from the generator of the 12 clock pulses defining the discreteness of the code delay adjustment phase shift keying in a 2-way delay line 2. At the output of the switching matrix 3, a sequence of N video codes of phase shift keying is formed, the temporal position of which is divided by the values of the control codes of the target indication. Further, these phase-shift keying codes arrive at the corresponding delay of 5–5 | h from the Vernier lines, where their mutual temporal position is refined with discreteness determined by the frequency of the clock pulses arriving at the control inputs of the Vernier 5 of the delay of the generator 12 clock pulses The delayed video codes of phase manipulation through public keys of 6 nonius delay lines arrive at the corresponding control inputs of the first 10 and second 11 quadrature channels. Consequently, sequences of phase shift keying video codes with independent discrete regulation of their temporal position are formed at the N control inputs of the quadrature channels. The N information inputs of the first quadrature channel 10 from the second outputs of the memory registers 22 of the control unit 4 receive codes that determine the amplitudes of the signals generated in this channel, and the information inputs of the second quadrature channels from the third outputs of memory registers 22, block 4 Controls are received that determine the amplitudes of the signals generated in this quadrature channel. At the same time, the codes supplied to the informational inputs of the same name for quadrature channels 10 and 11 are independent and can vary from that to the tact arbitrarily in accordance with the hypothesis of amplitude and phase of the corresponding forms. mimic signal. With binary phase shift keying (when phase to high frequency filling changes to Tf), the phase shift keying video code is a sequence of pulses whose edges and cuts determine the moments of the phase change of the O-vJT signal,. For each; From the N control inputs of the quadrature channels 10, 11, this video code comes. : Shaper 16 pulses, which can be used with a multivibrator, generates a video pulse with a duration equal to the duration of the received glad pulse, and opens the key 15, resolving the passage of information to the corresponding input of the second adder 17. The amplitude code of this generated radio pulse received by the corresponding information input of the quadrature channel 10 Or, 11 through the first inverter 13, the first adder 14 and the key 15 goes to the corresponding input of the matrix 17. In this case, if the code of the phase shift keying at the control input of quadrature channels 10, 11 corresponds to the phase of high-frequency filling of the formed radio pulse equal to zero, then the amplitude code of this signal passes to the input of adder 17 without changing. If the control code of phase shift keying corresponds to phase J, then the information code of amplitude A with the help of control The first inverter 13 is converted into the reverse A and fed to the controlled adder 14, where 1 is added to the lower digit of the reverse code, i.e. the amplitude code is converted in the adder 14 to an additional input to the input of the adder 17. In FIG. Figure 2 depicts diagrams explaining the process of summing the delayed video codes of phase shift keying for the case when the amplitude of the individual generated signals is determined by the amplitude of their phase shift key codes. Let the number of single-type circuits in each of the quadrature channels 10 and 11, and, consequently, the number of radio pulses in the generated sequence N 3. The relative amplitudes and delays of the phase-shift code for each of the radio pulses generated are shown in FIG. 2 (diagrams a. B, 6). The result of the linear summation of video codes in one of the quadrature channels is shown in FIG. 2 (plot 1). However, taking into account that the implementation of a linear summation of a large number of codes varying in amplitude in the required dynamic range is not technically feasible, in the proposed shaper of radio pulse sequences information on the amplitude of the generated signals is not in the amplitude of the phase-shift keying codes, as considered above, and posts to the information inputs of quadrature channels in the form of binary codes from the corresponding outputs of memory registers 22. In this case, the delayed phase-shift keying codes carry information only on O. points of the phase change of the high-frequency filling of the generated radio pulses, i.e. about the sign of their amplitude. Otherwise, when the code of phase manipulation corresponds to the phase of the signal equal to O, then its amplitude is specified by a positive number as a binary direct code, and if the code of phase manipulation corresponds to a phase of the signal that is equal to MH, then its amplitude is specified by a negative number as a binary additional code. Consider the process of forming the sum code of amplitude modulation and phase shift keying for the entire generated sequence of radio pulses. Let the number of generated radio pulses in subsequence No. 3, and their relative amplitudes be U, and 3, respectively, out of 4 k, 22 memory with five-bit binary codes are written into registers: U A 000 00011, and AZ 00100, where. four bits of the binary code carry information about the amplitude of the signal being formed, and the fifth (left bit) contains information. When translating these codes, respectively, in the return, and then into additional codes we will have: D 11110, Aldr 11111, D2 11100.2.00 11101, D noil, 11100. At the moment -f :, (Fig. 2), the first overlapping and the second generated radio pulses AUt Ah, + D 00001 + 00011 00100. Here, the zero in the sign bit of the total code indicates that at this time the phase of the total signal is O, and the relative amplitude is four. The summation is performed as follows. Since, at the considered time, the phase manipulation codes of the generated radio pulses correspond to the phase O, the amplitude codes specified in the form of direct binary codes pass through the corresponding serial circuit consisting of the first inverter 13, the first adder 14 and the key 15, without changes to hits on the second adder 17. At the output of adder 1, a summary code is formed, m of significant bits of which carry information about the amplitude, and (m + l) -ft the discharge carries information about the moments of change of the phase of the total oscillation; is the summary code of phase shift keying. At time 12 (FIG. 2), the value of the first phase shift code corresponds to the phase of the signal J, the second to phase J7, and the third to phase 0. Therefore, the amplitude codes of the first and second generated signals pass through the controlled first inverter 13 and first adder 14 is converted into additional ones, and the amplitude code of the third signal is fed to the input of the second adder 17 without identification. Then the output of the second from the Lmator 17 at time tp will be: 2 O LL.OP additional 11111 + 11101 + 00100 00000, t. e. the signals are mutually compensated at a given point in time, as from the plot of the city (Fig. 2). At other times, it will be (Fig. 2) i A..A.- AOP 2 3 11111 + 00011 + 00100 00110, i.e. the value of the relative sum, amplitude at this time instant is equal to six, and the oscillation phase is equal to O. Ayt gA + A, l-A i-lop AOP 11111 + 11101 + 11100 11000,. .. -. О Supplementary 11101 + 11100 11001 At units of time tc, in units of significant bits, the Kodal of the total signal has units. This indicates that the phase of the sum signal at these moments is equal to JT. In addition, units in sign bits indicate that information bits that carry information about the amplitude of the total signal are represented by an additional code. For the uniqueness of the digital-to-analog conversion of the received codes to the signal amplitudes, it is necessary to convert the information bits of the additional summary codes (having a unit in the sign bit) into a direct amplitude code. For this, m information bits of the total code from the output of the second adder 17 are fed to the input of the second inverter 18 and through it to the third adder 19, the control inputs of the KOTOIXJX receive the (m + l) bit of the total code, carrying information about the law of change of the total phase radio pulse sequences. At the moments when O is in (m + i) bit, the data bits of the code pass through the second inverter 18 and adder 19 without change, but if a bit appears in (m + l) bit, then the info dation bit The code dips are inverted in the second inverter 18n to the 4th digit of the inverted code is added one in the third adder 19. Thus, the second inverter 18 and the third regulator 19, controlled

summary code phase manipulation, convert additional codes of the total amplitude of the generated signals to direct. For example, for times t and i, the output of the third adder 19 will have the following amplitude codes:

AE-t ШОО + 1 1000,

those. relative signal amplitude is eight

AlZt 1001 + 10111,

those. The relative amplitude of the signal at this moment is seven (Fig. 2). From the output of the second adder 17, the sign (m + 1) -th bit of the total code is fed to the control input of the discrete phase shifter 21, which real-time phase-controls the harmonic signal received at its signal input. The amplitude code (envelope) of the generated sequence of radio pulses is fed to the control input of the attenuator 20, where the envelope of the sequence of radio pulses is formed in real time. Thus, a complex signal is generated at the output of the attenuator 20 (in the case of a sequence of overlapping photomanipulated radio pulses), the envelope of which also the law of phase manipulation depends on the mutual time delay of the radio pulses generated, as well as on the 5 values of the codes determining the amplitudes of the signals generated in -rto sequence. Similarly to the above, the second quadrature channel 11 works, but its signal input receives a harmonic oscillation through the α-phase-shifting circuit 9 at jr / 2. From the outputs of attenuators 20 of both quadrature channels 10 and 11, signals are received

5 at the output adder 7, - at the output of which a sequence of radio pulses is formed, the temporal position of which, amplitudes and phases can be set arbitrarily from beat to beat.

In the proposed shaper of radio pulse sequences, the errors of controlling the delay of the generated radio pulses are determined by the error of the following period.

 clock pulses from the clock pulse outputs, and the main elements influencing the spectrum of the generated signals are the phase shifter

0 is an attenuator, which allows the formation of radio pulse sequences with reduced spectrum distortion while improving the accuracy of controlling their temporal position.

Y ht

L ..

i42f

/eight

-J

7

P

T,

w

/ 7

f3

18

Lj

FIG. 2

Claims (2)

(54) (57) 1. RADIO PULSE SEQUENCE FORMER, comprising a multi-tap delay line, the taps of which are connected to the inputs of the switching matrix, the control inputs of which are connected to the outputs of the control unit, N non-tapered delay lines, the inputs of which are connected to the corresponding outputs of the switching matrix, and the taps each vernier delay line is connected to the inputs of the corresponding electronic keys, the control inputs of which are connected to the corresponding outputs of the control unit, and the outputs are interconnected, as well as an adder of radio pulses, which is due to the fact that, in order to reduce the distortion of the spectrum of the generated radio pulses while improving the accuracy of regulation of their temporal position, a phase-shift key code sensor is introduced into it, the output of which is connected to the input of the unit control and the input of the multi-tap delay line, and a clock generator, one output of which is connected to the control input of the multi-tap delay line, and the second to the control inputs. vernier delay lines, the first and second quadrature channels, the control inputs of the same name are combined and connected to the connection points of the outputs of the corresponding electronic keys, the information inputs are connected to the corresponding outputs of the control unit, the outputs are connected to the inputs of the radio pulse adder, as well as the harmonic oscillation generator and a phase-shifting circuit whose output is connected to the signal input of the second quadrature channel, wherein the signal input of the first quadrature channel single with output; harmonic oscillator. 2. Shaper pop. 1, characterized in that each quadrature channel contains N identical circuits, including a first inverter, a first adder and a key, and a pulse shaper, the output of which is connected to the control input of the key, the first input of the first inverter, the second the input of the first adder and the input of the pulse former are interconnected and the point of their connection is the control input of the quadrature channel, the second input of the first inverter is the information input of the quadrature channel **, followed by The second inverter, the “n” inputs of which are connected to the m outputs of the second adder, the third adder and attenuator, whose output is the output of the quadrature channel, and also the phase shifter, whose input is the input of the quadrature channel, and the output is connected to the second input of the attenuator, are (t + 1) -th output of the second adder is connected to the control input of the phase shifter, the control input of the second inverter, and the second input of the third adder, and the inputs are with the outputs of the keys N identical circuits.