RU54679U1 - RADAR STATION - Google Patents

Abstract

The utility model relates to the field of radar and can be used in ship (ship) or ground radar stations (radars) designed to detect surface and coastal targets and measure their coordinates. The technical result of using the utility model is to increase the resolution. The essence of the utility model consists in the fact that in a radar station containing a synchronizer, transmitter, antenna switch and antenna connected in series to the third arm of the antenna switch, an echo signal receiver, the transmitter comprising a frequency tuning unit, a driver, a phase manipulator and a power amplifier, connected in series, and also a phase shift key generator and pulse modulator, and the echo signal receiver contains a series-connected high-frequency amplifier, mixer, amplifier an intermediate frequency separator and a phase detector block, the first and second quadrature outputs of which are connected to the corresponding inputs of the video amplifier block, as well as a secondary information processing and display unit, the output of the local oscillator frequency of the pathogen being connected to the local oscillator input of the mixer, the output of the phase shift code generator and the output of the pulse modulator connected, respectively, with the control inputs of the phase manipulator and power amplifier, the output of the clock pulses of the repetition frequency of the synchronizer soy dinene with the control inputs of the pulse modulator and phase shift code generator, the clock output of the synchronizer is connected to the second input of clock pulses of the phase shift code generator, and the output of the antenna angle code is connected to the information input of the secondary processing and information display unit, the radio emission receiver is connected in series and a detection and measurement unit, serially connected control unit, a code-frequency converter and a frequency offset unit, as well as ok intra-period processing, and the output of the reference frequency of the pathogen is connected to the input of the reference frequency of the phase detector unit through the frequency offset unit, the information inputs of the control unit are connected, respectively, the first to the information output of the frequency adjustment unit, the fourth to the output of the antenna angular position code, and the second and the third is the input of the input of the own speed of the carrier of the radar station and the input of the speed setting of the detected target, respectively,

the control signal outputs of the control unit are connected, respectively, the second is connected to the power amplifier power control input, the third is connected to the synchronizer input and the video amplifier band control input, the fourth is connected to the antenna drive control input, the fifth is to the frequency channel switching input of the secondary processing unit, and display and control input of the detection and measurement unit, and the sixth - with the antenna switching input, the first and second quadrature outputs of the video amplifier unit are connected to the corresponding the input inputs of the intra-period processing unit, the signal output of which is connected to the first signal input of the secondary processing and display unit, the output of the detection and measurement unit is connected to the second signal input, the signal input of the radio emission receiver is connected to the output of the radio emission signals of the antenna, the output of the phase shift code generator is connected also with the input of the intra-period processing unit codes, and the outputs of the synchronization pulses of the repetition frequency and the clock pulses of the synchronizer are also connected to the corresponding inputs of the intra-period processing unit and the secondary processing and display unit, an auxiliary antenna device for the passive channel, an auxiliary receiver for the passive channel, the outputs of which are connected to the second input of the display and measurement unit, a carrier frequency selection and measurement unit, and a second input are control the input - which is connected to the corresponding bits of the seventh output of the control unit, and the first input - signal input - is connected to the output of signals p radio emission antenna, and the first output of the device for selection and measurement of the carrier frequency is connected to the second input of the receiver of radio emissions, and the second output of the device for selection and measurement of the carrier frequency is connected to the third input of the detection and measurement unit.

Description

The utility model relates to the field of radar and can be used in ship (ship) or ground radar stations (radars) designed to detect surface and coastal targets and measure their coordinates.

Currently, shipborne radars designed to detect surface and coastal targets use simple pulsed signals with high duty cycle (Q≅10 ³ ) and relatively high pulsed power (units and tens of kilowatts per pulse), constructed according to an incoherent scheme - with a transmitter on based on a magnetron generator and a superheterodyne type receiver with a local local oscillator based on a reflective klystron, the oscillation frequency of which is tuned manually or using an automatic frequency adjustment circuit (AP ) (See., E.g., [1], str.95-105). The disadvantage of this radar is the low noise immunity in relation to natural and organized interference, associated with both low stealth of the probing signals and the impossibility of quickly tuning parameters, primarily the carrier frequency, as well as the impossibility of organizing an operating mode with high coherence.

Another radar is known according to US patent No. 4.338.604, IPC GO 1 S 13/24, publication 06.07.82 [2]. The radar uses signals with intrapulse phase shift keying (FM signals) with a significantly lower duty cycle than pulsed at a lower pulse power and the same pulse energy and allows the carrier frequency to be tuned from pulse to pulse according to a random law over a wide range. It is built on a coherent principle and contains a serially connected synchronizer, transmitter, antenna switch and antenna, a receiver and an output display device connected to the third arm of the antenna switch, the transmitter being made on the basis of a series-connected exciter, phase manipulator and power amplifier controlled by a frequency tuning unit, a code generator and a pulse modulator, respectively, and the receiver contains a high-frequency amplifier, a decoding device, first mixer and a second mixer (phase detector), the frequency adjustment unit is connected to the control input of the exciter code generator is coupled to the control inputs of the phase manipulator and a decoding device, exciter output heterodyne frequency is connected to the mixer local oscillator input, and an output reference frequency exciter

- with the input of the reference frequency of the phase detector.

Due to the use of complex FM signals with the tuning of the carrier frequency from pulse to pulse, this radar has a higher noise immunity and stealth. However, the disadvantage of this radar is the introduction of a device for compressing FM signals (a "decoding device") into the receiver and turning it on directly behind the high-frequency amplifier, so that the compression of the FM signals in the prototype is performed at the frequency of the received signals, this limits its implementation to relatively small durations of complex signals (up to 10 ÷ 15 μs). Another disadvantage of this radar, which also does not allow the use of FM signals with long pulse durations T _And , is the lack of consideration of both the speed of the ship-carrier radar and the speed of detected surface targets. Meanwhile, as you know, the mutual movement of the radar and the target along the line connecting them leads to a shift in the frequency of the received signals by the Doppler frequency

where V _r is the radial velocity delivering target relative to the radar,

λ is the wavelength

f is the carrier frequency,

c is the speed of light

Further, the device for compressing FM signals, regardless of its implementation, has a frequency selectivity for the Doppler frequency, its frequency response has the form

(see, for example, [4], p. 103, table 4.1)

and the half-width of the strip at the level of 0.7 is

Therefore, if, for example, the radar is located on board a ship developing a speed of up to 60 knots relative to the target (30 m / s, i.e. 108 km / h), then the corresponding Doppler shift of the carrier frequency of the reflected signals at the carrier frequency

f = 15 GHz is F _∂o ≅3 kHz, so that with such a frequency shift the received signals fall into the frequency band of the compression device, the duration of the applied FM signals should not exceed

A similar situation occurs when signals from targets moving relative to the Earth with a sufficiently high speed are detected using a radar installed on board a stationary carrier, etc.

Thus, the need to detect radar signals from targets moving relative to the radar at a high speed makes it necessary to limit the duration T _{AND of the} probing signals in the radar analogue, that is, it does not allow for a sufficient decrease in the duty cycle Q, and, consequently, an increase in stealth.

Finally, it should be noted that the radar analogue does not provide for the possibility, with the aim of further increasing the secrecy of radiation, to reduce the power of probing signals when signals are detected from closely spaced or highly reflective targets (i.e. targets with a large effective scattering surface (EPR), for example, σ _C > 10 ⁴ m ² ), while at the same time reducing the duration of the probing signals T _AND as the range R decreases to detectable targets in accordance with the obvious ratio

as well as the transition to the passive mode of the radar when detecting targets that are both active sources of radio emissions (IR).

The closest in technical essence and selected as a prototype is a radar station according to the patent of the Russian Federation No. 214221, IPC G 01 S 13/42, publication 12/27/98 ([3]).

The radar prototype comprises a serially connected synchronizer, transmitter, antenna switch and antenna, an echo signal receiver connected to the third arm of the antenna switch, the transmitter comprising serially connected frequency tuning unit, exciter, phase manipulator and amplifier

power, as well as a phase-shift keying code generator and a pulse modulator, and the echo signal receiver contains a high-frequency amplifier, a mixer, an intermediate-frequency amplifier and a phase detector unit, the first and second quadrature outputs of which are connected to the corresponding inputs of the video amplifier unit, as well as the secondary processing unit and display information, moreover, the output of the local oscillator frequency of the pathogen is connected to the local oscillator input of the mixer, the outputs of the generator of phase shift codes and imp An ice modulator is connected, respectively, to the control inputs of the phase manipulator and the power amplifier, the synchronization pulse repetition clock synchronization output is connected to the control inputs of the pulse modulator and phase manipulation code generator, the synchronizer clock output is connected to the second input - clock pulses - phase manipulation code generator, and the output the code of the angular position of the antenna is connected to the information input of the secondary processing and display unit, sequentially with the remote radio emission receiver and the detection and measurement unit, the control unit, the code-frequency converter and the frequency offset unit, as well as the intra-period processing unit, the output of the reference frequency of the pathogen connected to the input of the reference frequency of the phase detector unit via the frequency offset unit, information the inputs of the control unit are connected, respectively, the first - with the information output of the frequency adjustment unit, the fourth - with the output of the antenna angular position code, and the second and third are with the input of the input of the own speed of the carrier of the radar station and the input of the speed setting of the detected target, respectively, the outputs of the control signals of the control unit are connected, respectively, the second is connected to the power control input of the power amplifier, the third is connected to the synchronizer input and the control input of the video amplifier block band, the fourth is with drive control input (Ex. pref.) antennas, the fifth - with the combined switching inputs of the frequency channels of the secondary processing and display unit and the detection and measurement unit, and the sixth - with the switching input (Comm.) of the antenna, the first and second quadrature outputs of the video amplifier unit are connected to the corresponding inputs of the intra-period processing unit the signal output of which is connected to the first signal input of the secondary processing and display unit, to the second signal input of which the output of the detection and measurement unit is connected, the signal input receiver radio emissions

is connected to the output of the radio emission signals (Signal radio emission) of the antenna, the output of the phase-shift code generator is also connected to the input of the codes of the intra-period processing unit, and the outputs of the clock pulses of the repetition frequency and the clock pulses of the synchronizer are also connected to the corresponding inputs of the intra-period processing unit and the secondary processing unit and display

In the radar, a passive mode of operation is carried out - detection of IR, then radiation of sounding signals with a low duty cycle and low pulse power with an in-pulse FM with adjustable power and pulse duration, with processing of the received FM signals at a video frequency in quadrature channels, compensation for the Doppler frequency shift resulting from own speed of the radar carrier in the directions to the observed targets, and search by Doppler frequency to detect speed targets.

The disadvantage of the prototype is the low resolution of the signals at the carrier frequency in the blocks of the frequency selection of the receiver of radio emissions, which are sets of microwave filters ("filter comb"). The low resolution is due to the fact that the resolution is determined by the discreteness of the bands passing filters. This leads to errors in determining the types of IRs and the classes of their carriers, as well as the disadvantage of the prototype is also possible errors in determining the bearing on the IR due to the inability to distinguish the situation when the background or the side lobe of the radiation pattern of its antenna coincides with the main lobe of the radiation pattern of the IR antenna and the situation when the main lobe of the radiation pattern of its antenna necessarily represent the background or sidelobe antenna pattern TS.

The objective of the utility model is to increase the resolution.

The essence of the utility model is that in a radar containing a serially connected synchronizer, transmitter, antenna switch, and antenna connected to the third arm of the antenna switch, an echo signal receiver, the transmitter comprising a series-tuned frequency tuning unit, an exciter, a phase manipulator, and a power amplifier, and also a phase-shift key generator and pulse modulator, and the echo signal receiver contains a series-connected high-frequency amplifier, mixer, amplifier divisor intermediate frequency unit and the phase detector, the first and second quadrature outputs of which are connected to respective inputs video amplifier unit, and

a secondary information processing and display unit, the output of the local oscillator frequency of the pathogen being connected to the heterodyne input of the mixer, the output of the phase-shift code generator and the output of the pulse modulator connected, respectively, to the control inputs of the phase manipulator and power amplifier, the synchronization output of the synchronizer repetition frequency connected to the control inputs of the pulse modulator and phase manipulation code generator, the synchronizer clock output is connected to the second input - the clock pulses - a phase-shift code generator, and the output of the antenna angular position code is connected to the information input of the secondary processing and information display unit, the radio emission receiver and the detection and measurement unit are connected in series, the control unit, the code-frequency converter and the frequency offset unit are connected in series, as well as an intra-period processing unit, wherein the output of the reference frequency of the pathogen is connected to the input of the reference frequency of the phase detector unit through the frequency offset unit, information the ion inputs of the control unit are connected, respectively, the first to the information output of the frequency tuning unit, the fourth to the output of the antenna angular position code, and the second and third are the input of the carrier’s own speed input for the radar station and the speed setting of the target being detected, respectively, the control signal outputs of the control unit, respectively, the second is connected to the power control input of the power amplifier, the third is connected to the synchronizer input and the strip control input video amplifier unit, the fourth with the input of the antenna drive control input, the fifth with the frequency channel switching input of the secondary processing and display unit and the control input of the detection and measurement unit, and the sixth with the antenna switching input, the first and second quadrature outputs of the video amplifier unit are connected to the corresponding inputs inter-period processing unit, the signal output of which is connected to the first signal input of the secondary processing and information display unit, to the second signal input of which The output of the detection and measurement unit is clear, the signal input of the radio emission receiver is connected to the output of the radio emission signals of the antenna, the output of the phase-shift code generator is also connected to the input of the codes of the intra-period processing unit, and the outputs of the synchronization pulses of the repetition frequency and the clock pulses of the synchronizer are also connected to the corresponding inputs of the intra-period processing unit and a secondary processing unit and

display, additionally introduced an auxiliary antenna device of the passive channel, an auxiliary receiver of the passive channel, the outputs of which are connected to the second input of the display and measurement unit, a device for selecting and measuring the carrier frequency, the second input is the control input - which is connected to the corresponding bits of the seventh output of the control unit, and the first input, the signal input, is connected to the output of the radio emission signals of the antenna, and the first output of the device for selecting and measuring the carrier frequency is connected to the second input house receiver radio signals, and the second output of carrier frequency selection and measurement device coupled to the third input of the detection unit and measurement.

The essence of the utility model is illustrated by a further description and drawings, which show:

figure 1 - structural diagram of the radar;

figure 2 - structural diagram of the antenna;

figure 3 is a structural diagram of a power amplifier;

figure 4 - structural diagram of the pathogen;

5 is a structural diagram of a frequency adjustment unit;

6 is a structural diagram of an intra-period processing unit;

Fig.7 is a structural diagram of a receiver of radio emissions;

Fig. 8 is a block diagram of a detection and measurement unit;

Fig.9 is a structural diagram of a block of secondary processing and display;

figure 10 is a structural diagram of a control unit;

11 - waveforms of control signals at the outputs of the synchronizer;

Fig - structural diagram of the synchronizer;

Fig - structural diagram of a device for selection and measurement of the carrier frequency;

Fig. 14 is a block diagram of a signal processing unit;

In figure 1, the following notation:

1 - antenna (A), the structural diagram of which is presented in figure 2;

2 - antenna switch (AP), made in the form of a ferrite Y-circulator;

3 - power amplifier (PA), a structural diagram of which is presented in figure 3;

4 - phase manipulator (FM), performed according to the scheme given in [2], moreover, segments of a strip waveguide switched by microwave diodes, which are controlled by pulses from

generator 9 phase-shift keying codes (see below), and in the absence of control pulses, the microwave diodes are locked, which also provides pulsed modulation of microwave oscillations;

5 - pathogen (B), the structural diagram of which is presented in figure 4;

6 - block frequency adjustment (BFC), a structural diagram of which is presented in figure 5;

7 - synchronizer (C), the structural diagram of which is presented in Fig.12, and Fig.11 shows the waveforms of the signals at its outputs;

8 - pulse modulator (IM), which can be implemented according to one of the schemes given in [5], pp. 103-107, Fig. 43-45;

9 - phase-shift code generator (GC), which can be performed according to the scheme given in [5], p. 421, Fig. 17;

10 - high frequency amplifier (UHF), implemented as a transistor microwave amplifier;

11 - mixer (SM), made in the form of a balanced mixer (see [5], p. 144);

12 - intermediate frequency amplifier (UPCH);

13 is a block of phase detectors (BFD), consisting of two identical phase detectors, the signal inputs of which are combined, and the inputs of the voltage of the reference frequency are connected through a 90 ° phase shifter;

14 - block video amplifiers (BVI), consisting of two identical parallel-connected video amplifiers, the bandwidth of which can be regulated, for example, by switching capacitors that determine the cutoff frequency;

15 is a block of intra-period processing (BVPO), the structural diagram of which is presented in Fig.6;

16 is a code-frequency converter (PCC), which can be made in the form of a serial connection of a pulse generator, a controlled repetition frequency divider (based on a counter), the division coefficient of which is determined by the Doppler frequency code, and a low-pass filter that selects the first harmonic;

17 - a frequency offset unit (BSC), which can be performed on the basis of a mixer with suppression of the mirror channel (see [5], p. 144, Fig. 3c);

18 is a receiver of radio emissions (PR), the structural diagram of which is presented in Fig.7;

19 is a block detection and measurement (BOI), a structural diagram of which is presented in Fig;

20 - block secondary processing and display (BVOO), a structural diagram of which is presented in Fig.9;

21 is a control unit (BU), a structural diagram of which is presented in figure 10,

92 - auxiliary antenna device of the passive channel,

93 - auxiliary receiver of the passive channel;

98 - device selection and measurement of the carrier frequency.

In the diagram of Fig. 1, a synchronizer 7, a frequency tuner 6, a driver 5, a phase manipulator 4, a power amplifier 3, an antenna switch 2 and an antenna 1 are connected in series, a high-frequency amplifier 10, a mixer 11, an intermediate-frequency amplifier 12 are connected in series, the phase detector unit 13, the video amplifier unit 14 and the intra-period processing unit 15 are connected in two lines, the signal input of the phase detector unit 13 being connected to the output of the intermediate frequency amplifier 12, and the output of the intraperiod unit 15 one processing unit is connected to the first signal input of the secondary processing and display unit 20, the output of the radio emission signals (Signal radio emission) of the antenna 1 is connected through a series-connected radio emission receiver 18 and the detection and measurement unit 19 to the second signal input of the secondary processing and display unit 20, the second the output of the synchronizer 7 is connected, respectively, through a pulse modulator 8 and a phase manipulation code generator 9 with the control inputs of the power amplifier 3 and the phase manipulator 4, and also with the third the course of the intra-period processing unit 15 combined with the sixth input of the secondary processing and display unit 20, the fourth input of the intra-period processing unit 15 combined with the second input of the clock frequency of the phase shift keying generator 9 and the fifth input of the clock frequency of the secondary processing and display unit 20 connected to the third output of the synchronizer 7, and the output of the generator 9 phase-shift keying codes is also connected to the fifth input - codes - block 15 intra-period processing.

The second output of the heterodyne frequency of the pathogen 5 is connected to the heterodyne input of the mixer 11, and the third output of the reference frequency of the pathogen 5 through the frequency offset unit 17 is connected to the reference frequency input of the phase detector unit 13.

The second input of the Doppler frequency of the frequency offset unit 17 through the code-frequency converter 16 is connected to the first output of the Doppler frequency code of the control unit 21, the second output of the power code of the control unit 21 is connected to the third - information - input of the power amplifier 3 , the third output is connected to the control input of the synchronizer 7 and the input of the block 14 of video amplifiers, the fourth output is the drive control is connected to the input of the drive control (Ex. privilege) of antenna 1, the fifth output is switching frequency channels is connected to the control inputs of the detection and measurement unit 19 and the fourth input of the secondary processing and display unit 20, and the sixth output — the antenna switching signal — is connected to the switching control input (Comm.) of the antenna 1.

The first input of the control unit 21 is connected to the information output of the frequency adjustment unit 6, the second and third inputs are connected to the sensors of the carrier’s own speed of the radar and the radial speed of the target, respectively, the fourth input, combined with the third input of the secondary processing and display unit 20, is connected to the output of the angle codes Positions (Position Code) - Antennas 1.

The auxiliary antenna device 92 of the passive channel is an omnidirectional or quasi-omnidirectional antenna (a rapidly rotating antenna that provides azimuthal viewing in the range 0-360 ° for a time of the order of 0.1 s).

The auxiliary receiver 93 of the passive channel is multi-channel and for each frequency channel contains a series-connected high-frequency amplifier, a block of amplitude detectors and a block of video amplifiers.

The output of the auxiliary antenna device 92 is connected to the input of the auxiliary receiver 93 of the passive channel, the output of which is connected to the second input of the detection and measurement unit 19.

The second input of the carrier frequency selection and measurement device 98 — the control input — is connected to the corresponding bits of the seventh output of the control unit 21, and the first input, the signal input, is connected to the output of the radio emission signals of the antenna 1, and the first output of the carrier frequency selection and measurement device 98 is connected to the second input of the radio emission receiver 18, and the second output of the carrier frequency selection and measurement device 18 is connected to the third input of the detection and measurement unit 19.

In figure 2, the following notation:

22 - antenna unit (BA);

23 - antenna active channel (AA);

24 ₁ , ..., 24 _n - passive channel antennas (AP ₁ , ..., AP _n );

25 - switch (K);

26 - antenna drive (PA).

In the diagram of figure 2, the antenna 23 of the active channel through the switch 25 is connected to the signal input-output of the antenna 1, the outputs of the antennas 24 ₁ , ..., 24 _{n of the} passive channel and the corresponding output of the switch 25 form the output of the radio emission signals (Signal radio emission) antenna 1, the control input of the switch 25 forms the switching control input (Comm.) antenna 1 ,. Antennas 23 and 24 ₁ , ..., 24 _{n are} mechanically combined into an antenna block 22, which is kinematically connected to the antenna drive 26, the information output of the latter is connected to form the output of the angular position code of the antenna 1, and the drive control input forms the antenna drive control input 1.

In figure 3, the following notation:

27 - the first switch (K ₁ );

28 - preliminary amplifier (U ₁ );

29 - the second switch (K ₂ );

30 - output amplifier (U ₂ );

31-32 - the first and second key blocks, respectively (Cl ₁ , Cl ₂ );

33 - output switch (KB).

In the diagram of FIG. 3, the first switch 27, the pre-amplifier 28, the second switch 29 and the output amplifier 30 are connected in series, the signal input of the first switch forms the first input of the power amplifier 3, its second input, respectively, through the first and second key blocks 31, 32 is connected to the pulse modulation inputs of the pre-amplifier 28 and the output amplifier 30, the control inputs of the switches 27, 29, the key blocks 31, 32 and the output switch 33 form the third input of the power amplifier 3, the second outputs of the switches 27, 29 and output amplifier 30 Exit connected respectively to the first, second and third signal inputs of the output switch 33, and the last output constituting the output of the power amplifier 3.

In figure 4, the following notation:

34 ₁ , ..., 34 _l - crystal oscillators (KG ₁ , ..., KG _l );

35 ₁ , ..., 35 _l - amplifiers (CSS ₁ , ..., CSS _l );

36 - frequency multiplier (Smart);

37 - signal frequency oscillation amplifier (USS);

38 - mixer (cm);

39 - generator oscillations of the reference frequency (GOCH);

40 - oscillator frequency oscillator (USg);

41 - amplifier oscillations of the reference frequency (USO).

In the diagram of Fig. 4 l chains of series-connected crystal oscillators 34 ₁ , ..., 34 _l and amplifiers 35 ₁ , ..., 35 _{l are} connected in parallel, the outputs of the latter are combined, the combined output is connected to the input of the multiplier 36, the output of which connected to the input of the amplifier 37 of the oscillation of the frequency of the signal, the output of which is the first output of the exciter 5, the output of the multiplier 36 is also connected to the input of the mixer 38, the output of the latter is connected to the input of the amplifier 40 of the oscillator frequency oscillator, the output of which is the second output of the exciter 5, and the second the mixer stroke is connected to the first output of the reference frequency oscillation generator 39, the other output of which is connected to the output of the reference frequency oscillation amplifier 41, the output of which is the third output of the exciter 5, and the control inputs of the amplifiers 35 ₁ , ..., 35 _l form the first input of the exciter 5 .

In figure 5, the following notation:

42 - noise generator (GS);

43 - amplifier-limiter (UO);

44 - counter (MF);

45 - element I (I);

46 - register (P);

47 - decoder (DS).

In the diagram of FIG. 5, a noise generator 42, a limiter amplifier 43, a counter 44, an AND element 45, a register 46 and a decoder 47 are connected in series, the output of which forms the first - control - output of the frequency tuning unit 6, and the input is connected to the second - information - the output of the frequency adjustment unit 6, the second input of the AND element 45 forms the input of the frequency adjustment unit 6.

Figure 6 adopted the following notation:

48 ₁ , ..., 48 _m - multipliers of the first (sine) quadrature (V _1s , ..., V _ms );

49 ₁ , ..., 49 _m - multipliers of the second (cosine) quadrature (У _1с , ..., У _mc );

50 - shift register of the first (sinus) quadrature (CP _S );

51 - shift register of the second (cosine) quadrature (CP _C );

52 - key block (C);

53 ₁ , ..., 53 _m - accumulating adders of the first (sine) quadrature (H _1s , ..., H _ms );

54 ₁ , ..., 54 _m - accumulating adders of the second (cosine) quadrature (H _1c , ..., H _mc );

55 ₁ , ..., 55 _m - blocks combining quadratures.

In the diagram of FIG. 6, the first inputs of the multipliers 48 ₁ , ..., 48 _{m of the} first (sine quadrature) are connected to the corresponding bits of the shift register 50, the outputs of these multipliers through the corresponding accumulating adders 53 ₁ , ..., 53 _{m are} connected to the first the inputs of the respective quadrature combining units 55 ₁ , ..., 55 _m , and the second inputs of the multipliers 48 ₁ , ..., 48 _m are interconnected and connected to the first signal input of the intra-period processing unit 15. Similarly, the first inputs of the multipliers 49 ₁ , ..., 49 _{m of the} second (cosine) quadrature are connected to the corresponding bits of the shift register 51, the outputs of these multipliers through the accumulating adders 54 ₁ , ..., 54 _{m are} connected to the second inputs of the corresponding blocks 55 ₁ , ..., 55 _{m of} combining quadratures, and the second inputs of multipliers 49 ₁ , ..., 49 _m are interconnected and connected to the second signal input of block 15. The third input (clock pulses) of block 15 is connected to the combined zero-setting inputs of all 2m accumulator - 53 _1, ..., 53 _m and 54 _1, ... 54 _m, a m also with the control input of the key block 52, the signal input of the latter is the input 4 (clock pulses) of the block 15, and the output is connected to the combined clock inputs of the shift registers 50 and 51, their signal inputs are also combined and connected to the fifth input (phase shift codes) block 15, and the outputs of blocks 55 ₁ , ..., 55 _m combining quadratures form the m-channel output of block 15.

In Fig.7, the following notation:

56 ₁ , ..., 56 _{n + 1} - high-frequency amplifiers (UHF ₁ , ..., UHF _{n + 1} );

57 ₁ , ..., 57 _{n + 1} - frequency selection blocks (BChS ₁ , ..., BChS _{n + 1} ), consisting of band-pass filters with adjacent frequency characteristics;

58 ₁ , ..., 58 _{n + 1} - blocks of amplitude detectors (DB ₁ , ..., DB _{n + 1} );

59 ₁ , ..., 59 _{n + 1} - blocks of video amplifiers (BVU ₁ , ..., BVU _{n + 1} ),

94 ₁ , ..., 94 _{n + 1} - controlled attenuators.

In the diagram of Figure 7 are connected in parallel n + 1 identical circuits consisting of series-connected amplifiers 56 _i, the high frequency blocks of frequency selection 57 _i, 58 _i blocks of amplitude detectors 59 and block _i (i = 1, 2, ... , n + 1) video amplifiers each. The inputs of the amplifiers 56 ₁ , ..., 56 _{n + 1} form the combined n + 1-channel input of the receiver 18 of radio emissions, the outputs of the blocks 59 ₁ , ..., 59 _{n + 1} video amplifiers form a combined M-channel output

where m _i is the number of frequency channels (filters) in the i-th frequency range of the receiver 18 radio emissions.

The control inputs _{of the} video amplifier units 59 ₁ , ..., 59 _{n + 1} form the video amplifier control input of the radio emission receiver 18, to which strobes are supplied from the first output of the signal processing unit 102 of the device 98, in the absence of which the video amplifiers are turned off. Amplification of signals in video amplifiers of blocks 59 ₁ , ..., 59 _{n + 1 of} video amplifiers is performed only in the presence of gates.

In Fig.8, the following notation:

60 ₁ , ..., 60 _{n + 1} - quantization blocks (BC ₁ , ..., BC _{n + 1} );

61 - storage device (memory);

62 - register of signs of receiving the main lobe,

95 ₁ , ..., 95 _{n + 1} - blocks of quantization of the auxiliary passive channel, 96 ₁ , ..., 96 _{n + 1} - blocks of formation of signs of reception of the main lobe.

In the diagram of Fig. 8, the combined multi-channel inputs _of quantization units 60 ₁ , ..., 60 _{n + 1} form the first M-channel signal input of the detection and measurement unit 19, the outputs _of quantization units 60 ₁ , ..., 60 _{n + 1 are} connected with the corresponding inputs of the storage device (memory) 61, the output of which forms the output of the block 19, and the control input of the memory 61 is the control input of the block 19. The second signal input of the detection and measurement block 19 is formed by the inputs of the blocks 95 ₁ , ..., 95 _{n + 1} quantization of the auxiliary passive channel. The outputs _of quantization units 60 ₁ , ..., 60 _{n + 1 are} also connected to the first inputs of feature formation units 96 ₁ , ..., 96 _{n + 1}

receiving the main lobe, the second inputs of which are connected to the outputs of blocks 95 ₁ , ..., 95 _{n + 1} quantization of the auxiliary passive channel. Blocks 96 ₁ , ..., 96 _{n + 1 of the} formation of signs of receiving the main lobe can be made in the form of comparators. The comparison results are indicated by the comparators but the corresponding inputs of the main lobe reception register 62, the output of which is connected to the input of the memory 61. The third input of the detection and measurement unit 19 is formed by the input of the memory 61. The memory 61 can be made in the form of a device containing random access memory, a microprocessor and I / O adapters. The inputs and outputs of the input-output adapters form the inputs and outputs of the memory 61. The microprocessor, for example, via a serial channel to the control input of the memory 61 from the control unit 21, controls the reception of data (write to the memory 61) from blocks 60 ₁ , ... , 60 _{n + 1} quantizations, from the register 62 of the reception signs of the main lobe, from the signal processing unit 102 of the device 98 for selecting and measuring the carrier frequency, as well as the output of this data from the memory 61 to the secondary processing and display unit 20.

In Fig.9, the following notation:

63 ₁ , ..., 63 _m - amplitude quantizers (AK ₁ , ..., AK _m );

64 ₁ , ..., 64 _m - shift registers (CP ₁ , ..., CP _m );

65 ₁ , ..., 65 _m - multi-input adders (Σ ₁ , ..., Σ _m );

66 - the first switch (K ₁ );

67 - key block (C);

68 - monitor (M);

69 - counter (MF);

70 - the first digital-to-analog converter (DAC ₁ );

71 - the second digital-to-analog converter (DAC ₂ );

72 - the first decoder (DS ₁ ),

73 - the second switch (K ₂ );

74 - the second decoder (DS ₂ );

75 - luminescent scoreboard (LT);

76 - the third decoder (DS ₃ ).

In the diagram of Fig. 9, the first - signal - m-channel input of the secondary unit 20

processing and displaying through the corresponding amplitude quantizers 63 ₁ , ..., 63 _{m is} connected per channel to the signal inputs of the corresponding shift registers 64 ₁ , ..., 64 _m each of which is connected with the outputs of all its bits to the corresponding inputs of the corresponding multi-input adder 65 _i ( i = 1, 2, ..., m), the outputs of all m adders 65 _i (i = 1, 2, ..., m) are connected to the corresponding inputs of the first switch 66, and the output of the latter is connected to the signal input of the monitor 68.

The clock inputs of all m shift registers 64 ₁ , ..., 64 _{m are} combined and connected to the sixth input - repetition frequency clock pulses - block 20, the control input of the key block 67, the signal input of which is connected to the fifth input, is also connected to the same point pulses of the clock frequency - block 20, and the output - with the control input of the switch 66, and also through the counter 69 and the first digital-to-analog converter 70 - with the second input - vertical voltage - monitor 68, the third input - horizontal scan - which is connected through the second The first digital-to-analog converter 71 with a third input — antenna azimuth codes — is block 20, which, through a third decoder 76, is also connected to the azimuth indication input of the fluorescent display 75.

The second signal input of block 20 through the first decoder 72 is connected to the signal input of the second switch 73, the control input of which through the second decoder 74 is connected to the fourth input - the number of the frequency channel - block 20, and the multi-channel output of the switch 73 is connected channel to channel with the corresponding inputs of the lines of the luminescent panel 75 .

Figure 10 adopted the following notation:

77 - the first graphic information display device (SOGI);

78 - the second UOGI;

79 - the first electronic control panel;

80 - second electronic control panel;

81 - the first electronic computer (computer);

82 - second computer;

83 - the third computer;

84 - fourth computer;

97 - control panel.

The first and second UOGI 77 and 78 are graphical displays that provide

display of all necessary data: radar situation, navigation data, data on the status and operating modes of the radar, etc. The first and second UOGI can be made in the form of displays based on liquid crystal matrices.

The first and second electronic control panels 79 and 80 are panels containing SOGI and a pointing device. On the screens of the UOGI images of controls are displayed. As a pointing device can be used manipulators such as "TrackBall" or "mouse". Coordinate-pointing devices are used to control cursors on the screens of the UOGI.

The first, second, third and fourth computers 81, 82, 83 and 84 are equipped with input-output devices for receiving and sending data through the inputs and outputs of the control unit 21. The first, second, third and fourth computers 81, 82, 83 and 84 are connected by communication channels, for example, communication channels of a local network and form a single computing complex.

The first, second, third and fourth computers 81, 82, 83 and 84 are configured to perform the functions of a power control unit, a synchronizer control unit, an antenna control unit, a frequency channel interrogation unit, a mode switch, and an attenuator control unit. The functions of these blocks are carried out programmatically, and through the input-output devices of the computer issue and receive the appropriate commands and signals through the outputs and inputs of the control unit 21.

In Fig.11, the following notation:

85 is an oscillogram of pulses with a duration of τ ₀ that are ahead of the moment of the beginning of the probe pulses by t ₀ , with a repetition period T _P , where t ₀ ≪T _P , τ ₀ ≪t ₀ - to control the frequency tuning unit 6 - at the first output of the synchronizer 7;

86 is an oscillogram of clock pulses with a duration of T _AND and a repetition period of T _P for controlling a pulse modulator 8, a phase shift keying generator 9, and also blocks 15 and 20 at the second output of the synchronizer;

87 is an oscillogram of pulses of a clock frequency f _T with a repetition period

and duration τ _T ≪Т - to control the generator 9 phase-shift keying codes, and also - blocks 15 and 20 - at the third output of the synchronizer 7.

On Fig adopted the following notation:

88 - clock generator (GTI);

89 - controlled frequency divider (UD);

90 - block RS-flip-flops (BTR) with decoders;

91 - pulse shaper (FI).

In the diagram of FIG. 12, a clock pulse generator 88, a controlled frequency divider 89, a trigger unit 90 with decoders and a pulse generator 91, the output of which is the first output of the synchronizer 7, the second output of the trigger unit 90 forms the second output of the synchronizer 7, the input of the block 90 are connected in series flip-flops is connected to the output of the controlled frequency divider 89, which is also connected to the third output of the synchronizer 7, and the control input of the controlled divider 89 is the input of the synchronizer 7.

In Fig.13, the following notation:

108 ₁ , ..., 108 _{n + 1} - high-frequency amplifiers (UHF ₁ , ..., UHF _{n + 1} );

99 - the fourth switch (K);

100 - frequency transponder (TFC);

101 - meter instantaneous frequency (MFI);

102 - signal processing unit (BOS).

In the diagram of FIG. 13, the inputs _{of the} high-frequency amplifiers 108 ₁ , ..., 108 _{n + 1} form the first input of the (n + 1) -channel device for selecting and measuring the carrier frequency, the outputs of the amplifiers 108 ₁ , ..., 108 _{n +1} high-frequency are connected to the inputs of the fourth switch 99, the output of which is connected via a frequency transformer 100 to the input of the instantaneous frequency meter 101, the output of which is connected to the input of the signal processing unit 102, the first and second outputs of which are the outputs of the device 98, and the second input of the block 102 is the second input of device 98, the third and fourth you the strokes of the signal processing unit 102 are connected to control inputs of a frequency transponder 100 and a fourth switch 99, respectively.

On Fig adopted the following notation:

103 - device comparison codes;

104 - digital signal processor (DSP);

105 - long-term reprogrammable memory device;

106 - controller serial channels;

107 - digital-to-analog converter (DSP);

In the diagram of FIG. 14, the input of the code comparison device 103 is the input of the signal processing unit 102. The code comparison device 103, the digital signal processor 104, the long-term reprogrammable memory 105, the serial channel controller 106 are interconnected via a system interface bus. The inputs and outputs of the controller 106 of the serial channels are respectively formed by the second input and second output of the signal processing unit 102, the first output of which is formed by the output of the digital-to-analog converter 107, and the third and fourth outputs are formed by the outputs of the digital signal processor 104, the digital-to-analog converter 107 is connected to a digital the signal processor 104. The device 103 code comparison is based on a programmable logic chip (programmable logic matrix), long-term reprogrammable the storage device 105 is made on the basis of elements of an electro-reprogrammable memory (flash memory).

In accordance with the considered structural diagram (figure 1), the proposed radar operates as follows.

At the first stage, the radar operates in a passive mode, while receiving and detecting radio emissions, evaluating their intensities and measuring the azimuths of their sources. In this mode, according to the code signal coming from the control unit 21, through the second output of the block 21 to the third input of the power amplifier 3 (Fig. 3), the first switch 27 is brought into a position in which the signal from the first input of the power amplifier 3 goes directly to the first the input of the output switch 33 and through it to the output of the power amplifier 3, and the key blocks 31 and 32 open the circuit between the second input of the power amplifier 3 and the modulation inputs of the amplifiers 28 and 30, removing high voltage from them. At the same time, the control unit 21 provides a signal for switching the antenna 23 of the active channel (Fig. 2) through the switch 25 to the first output of the antenna 1, which is achieved by supplying a control signal through the sixth output of the control unit 21 and the second input of the antenna 1 to the control input of the switch 25. Next , according to the signal arriving through the fourth output of block 21 and the third input of antenna 1 to drive 26 of the antenna, a sectorial review of the space in the horizontal plane is performed. Signals of radio frequency sources

the range of antennas 23 and (or) 24 ₁ , ..., 24 _n , fall into the corresponding high-frequency amplifier 56 _{i of the} radio receiver 18 (Fig. 7), and then enter the corresponding block 57 _i (i = 1, 2,. .., n + 1) of frequency selection. After amplification and filtering by high frequency, the received signals are detected by amplitude and amplified by video frequency in multi-channel detector units 58i and video amplifier units 59i, respectively, and pass from the output of the radio emission receiver 18 to the input of the detection and measurement unit 19 (Fig. 8).

The radio emission signals received by the antenna 1 from the multi-channel output of the radio emission signals are fed to the multi-channel input of the carrier frequency selection and measurement device 98, in which, after amplification in high-frequency amplifiers 108 ₁ , ...., 108 _{n + 1} are fed to the inputs of the fourth switch 99,

From the seventh output of the control unit 21, the codes of the range number and channel number, in which the frequency selection block 57 does not provide separation of the signals of several radio emissions whose frequencies fall into the band of one filter, are fed to the input of the controller 106 serial channels of the signal processing unit 102 and then to the digital signal processor 104, from the second output of the digital signal processor 104, the range code is supplied to the control input of the fourth switch 99, which in accordance with this code connects its output (connect connects to the transponder 100 frequency) with its input corresponding to a given range. The control input of the frequency transponder 100 from the third output of the signal processing unit 102 (from the second input of the digital signal processor 104) receives the average value of the range of transposable frequencies (the average frequency of the selected channel), which the digital signal processor 104 receives from the long-term reprogrammable memory 105 range and channel codes received from the control unit 21.

The instantaneous frequency meter 101 measures the frequency of the transposed signal and transmits the measured frequency code via a twelve-bit interface to the first input of block 102, in which this code is input to the code comparison device 103. Through the system interface bus, the code comparison device 103 receives the values of the channel strip boundaries extracted from the long-term reprogrammable memory 105 in the same codes that are used by the instantaneous frequency meter 101. The device 103 compares the codes coming from the instantaneous frequency meter 101 and the band boundary codes

channel received from the processor 104. As a result of the comparison, it is determined whether the frequency value received from the meter 101 is in the range of this channel. If the value is in this range, a signal is generated that is transmitted through the system interface line to the processor 104 and then to a digital-to-analog converter 107, the output of which is a strobe that is fed to the second input of the radio emission receiver 18, which is formed by the interconnected control the inputs of blocks 59 ₁ , ..., 59 _{n + 1} video amplifiers. In the absence of gates, the video amplifiers of blocks 59 ₁ , ..., 59 _{n + 1 of the} video amplifiers are closed. Thus, from the outputs of blocks 59 ₁ , ..., 59 _{n + 1} video amplifiers, the inputs of blocks 60 ₁ , ..., 60 _{n + 1} quantization receive signals selected from the carrier frequency from the radio emission source, which allows to reduce the measurement errors of the parameters and errors in determining the bearing. When narrowing the bandwidth of the frequency channel, the boundaries of which are recorded in the long-term reprogrammable memory 105, the command from the control unit 21 narrows the band of selectable signals and increases the accuracy of measurement of parameters and bearing. The values of the frequency codes measured by the instantaneous frequency meter 101 and falling into the channel frequency band from the code comparison device 103 are supplied to a digital signal processor 104, where they are converted into the frequency codes of the received signal (before transposition) and fed to the second output of the block 102 through the controller 106 of serial channels and through the corresponding communication channel to the input of the detection and measurement unit 19, where it is included in the radiation source form. When sequentially changing the codes of the range number and codes of the frequency band of the channel coming from the control unit 21 to the second input of the signal processing unit 102 in the device 98, the signal parameters of all radio sources received by the antenna 1 are measured.

The radio emission signals received at the input of the detection and measurement block 19, in each of the frequency ranges, are sent along m _i lines to the corresponding quantizer block 60 _i (i = 1, 2, ..., n + 1), which, in turn, contains , m _{i of} multilevel quantizers (by the number of frequency selection channels in the i-th band). In blocks 60 _{i of} quantizers, signals were detected - by exceeding the first quantization level selected from the condition for the admissible probability of false alarm - and their intensity was estimated by the number of the highest quantization level,

exceeded the amplitude of the received signal. Further, this information, that is, the encoded values of the amplitude, enters the memory 61, where it is recorded in the cell, the address of which is determined by the numbers of the range and the frequency selection channel in this range.

At the same time, radio emissions are received by the omnidirectional or quasi-omnidirectional antenna of the auxiliary antenna device 92 of the passive channel. The signals from the auxiliary antenna device 92 of the passive channel are fed to the auxiliary receiver 93 of the passive channel, which operates similarly to the receiver 18 of radio emissions.

In the detection and measurement unit 19 in all frequency channels, the signal levels received by the antenna 1 and the radio receiver 18 are compared with the signal levels received by the auxiliary antenna device 92 of the passive channel and the auxiliary receiver 93 of the passive channel. Based on this comparison, the conclusion is made about the reception of the main or side lobe of the radiation pattern and the blocks 96 ₁ , ..., 96 _{n + 1 of the} formation of the signs of receiving the main lobe generate the corresponding signs, information about which is also recorded in the memory 61.

In this case, the sensitivity of the auxiliary channel (consisting of the auxiliary antenna device 92 of the passive channel and the auxiliary receiver 93 of the passive channel) is selected so that it exceeds the sensitivity of the main channel (consisting of the antenna 1 and the receiver 18 of radio emissions) when the side lobe receives the radiation pattern, i.e. differ from the sensitivity of the main channel by no more than 15-20 dB. Reading information from the memory 61 occurs according to the polling signal received from the fifth output of the control unit 21 through the second input of the detection and measuring unit 19 to the control input of the memory 61 periodically, and the period of the polling signals must be significantly less than the scanning time of one azimuthal direction T _φ , determined by the width antenna patterns in azimuth φ _0.5 and angular scan rate ω _φ , i.e. .

Information from the memory 61 comes through the output of the block 19 detection and measurement

to the second input of the secondary processing and display unit 20 (Fig. 9) in the form of intensity codes and enters through the decoder 72 to the switch 73 controlled by the same polling signals of the frequency channels coming from the control unit 21 (Fig. 10) through the fourth input of the unit 20 (Fig. 9) and a decoder 74 to the control input of the switch 73. After passing the switch 73, the values of the intensity of the radio emission signals are displayed on the luminescent panel 75 in the form of a table, the line number in which corresponds to the number of the frequency range and the frequency channel in this range e. In the corner of the table, the corresponding antenna azimuth value is displayed, which falls on the luminescent display 75 through the decoder 76 (Fig. 9) and the third input of block 20 from the second output of the antenna 1 (Fig. 2).

After detecting the sources of radio emissions in the passive mode, and also, if necessary, dictated by a tactical task, the radar switches to active mode. Moreover, in the control unit 21 (FIG. 10) it gives a signal through its sixth output and the second input of the antenna 1 (FIG. 2) to the control input of the switch 25, which ensures that the antenna 23 of the active channel is switched to the first input of the antenna 1. In this case, the reception of radio emissions in other ranges it can be made still.

The operation of the radar in active mode is as follows.

The causative agent 5 (Fig. 4) of the transmitting device generates fluctuations in the frequency of the signal f _ci , the local oscillator f _Gi and the reference frequency f _OP , while the frequencies f _ci , f _{Gi are} highly stable during one repetition period T _{P of the} radar probe pulses, but change abruptly from the period to the period according to a random law under the action of block 6 of the frequency adjustment, taking one of i values (i = 1, 2, ..., l), and so that the relation always holds

f _OP = | f _ci -f _Гi | = const

The causative agent 5 works as follows (figure 4).

Crystal oscillators 34 ₁ , ..., 34 _l generate oscillations, each at its own frequency f _ki . These oscillations pass through gated amplifiers 35 ₁ , ..., 35 _l, respectively, of which only one is open in a given repetition period, namely the one at the control input of which from the input of the exciter 5 receives a single nonzero discharge of a parallel l-bit code generated in frequency tuning unit. These oscillations are multiplied by the frequency in the multiplier 36 by n ₁ , and thus

the oscillations of the signal frequency f _ci = n ₁ f _ki , which are amplified by the amplifier 37 and pass to the first output of the pathogen 5. Simultaneously, the oscillations of the frequency n ₁ f _ki arrive at the mixer 38, to the other input of which the oscillations of the frequency f _OP generated by the reference oscillator 39 frequency.

After mixing at the mixer output, oscillations of the local oscillator frequency are formed

f _Gi = f _ci -f _OD ,

which ensures the fulfillment of the above relation. From another output of the generator 39 of the reference frequency, the oscillations of the frequency f _OP pass through the amplifier 41 of the oscillations of the reference frequency to the third output of the pathogen 5.

The _{tuning of the} frequencies f _ci and f _{Gi is} performed using the frequency tuning unit 6, which operates as follows (Fig. 5).

A noise generator (GS) 42, built, for example, on the basis of a noise diode, generates noise oscillations with a spectrum width Δf _Ш significantly exceeding the repetition frequency F _P , then these oscillations are amplified and limited in the amplifier-limiter 43 and fed to the counter 44, which counts, for example, positive fronts modulo n _f and thus has n _f equiprobable states. At the moment determined by the pulses arriving through the repetition period from the first output of the synchronizer 7 with a lead time t ₀ relative to the beginning of the next probing pulse, the readings of the counter 44 through the And 45 element are recorded in register 46 and converted in the decoder 47 into a parallel code with the number of bits n _f , where nonzero is only one of the n _f bits, which is stored during one repetition period and determines the values of the frequencies f _ci and f _Гi in the next repetition period. This code is supplied to the first output of the frequency adjustment unit 6 and, further, to the input of the exciter 5. At the same time, the code of the carrier frequency number in the next repetition period is transmitted through the second output of the frequency adjustment unit 6 to the first input of the control unit 21 (see below).

Fluctuations in the frequency of the signal f _ci arrive at the phase manipulator 4, where they are phase-controlled by a binary multi-bit code (with the number of bits N) generated in the generator 9 of phase-shift code codes, amplified by power in

a power amplifier 3 generating probing signals under the influence of a pulse modulator 8 controlled by clock pulses coming from the second input of the synchronizer 7.

At the beginning of the active mode, it is advisable to work with a minimum pulse power and the duration of the probing signals, when the highest secrecy is ensured. In this case, according to the code signal coming from the control unit 21 through its second output (Fig. 10) to the third input of the power amplifier 3, the first switch 27 (Fig. 3) of the power amplifier 3 is in a position when the signal from the first input of the power amplifier 3 directly to the first input of the output switch 33 and through it to the output of the power amplifier 3, and the key blocks 31 and 32 open the circuit between the second input of the power amplifier 3 and the modulation inputs of the amplifiers 28 and 30 (pulse modulation is carried out, as mentioned above, phase 4).

The change in the pulse duration T _AND = Nτ _{AND is} carried out by changing the duration of the discretes τ _AND , determined by the clock frequency f _T , so that

This is done according to the signal from the control unit 21, which passes through the third output of the control unit 21 to the input of the synchronizer 7, which leads to a change in the clock frequency of the pulses at the third output of the synchronizer 7. While maintaining the compression ratio N, the duration of the probe pulses T _AND changes proportionally to τ _AND , simultaneously the repetition period T _P changes with a constant duty cycle Q = T _P / T _AND . At the beginning of the active stage of the radar operation, the discrete duration τ _И , and, therefore, Т _И = Nτ _И and Т _П = QT _И (N = const, Q = const) take the minimum values, providing the ability to observe targets at short ranges ( ), while achieving high secrecy. Further, if necessary, the pulse power P _{AND of the} probing signals increases, while the durations of τ _I , T _I, and T _P also increase, which makes it possible to detect targets at long ranges. Power increase

the probing signals P _{AND are} produced by a code signal coming from the control unit 21 (Fig. 10), the first switch 27 (Fig. 3) of the power amplifier 3 is transferred to the position when the signal from the first input of the power amplifier 3 is supplied to the input of the pre-amplifier 28, and the second switch 29 connects the output of this amplifier to the second signal input of the output switch 33, which, under the action of a code signal at the control input of the output switch 33, is connected to the output of the latter, at the same time the key unit 31 is closed, and the speech unit 32 remains in the open state, which ensures the operation of the preliminary amplifier 28 with the output amplifier 30 switched off (medium power mode). Finally, the highest power mode is provided when the first (27) and second (29) switches are in the position at the code signal coming from the control unit 21, at which the signal from the first input of the power amplifier 3 passes to the input of the pre-amplifier 28, and its output through the switch 29 to the input of the output amplifier 30, the output of the output switch 33 is connected to its third input, and both key blocks 31 and 32 are open and provide the passage of modulation pulses from the second input of the power amplifier 3 to the amplifiers 28 and 30. One At the same time, the durations of τ _И , Т _И and Т _П take the greatest set values, providing the possibility of detection at maximum ranges.

The probe pulses from the output of the power amplifier 3 pass through the antenna switch 2 into the antenna 1 through the first input, and are emitted into the space through the switch 25 and the antenna 23 of the active channel.

The reflected signals from the antenna 23 of the active channel through the switch 25 and the antenna switch 2 fall on the high-frequency amplifier 10 and after heterodyne conversion in the mixer 11 are amplified in the intermediate frequency amplifier 12 and fed to the signal input of the phase detector unit 13, to the input of the reference frequency of which the oscillations from the output of the frequency offset unit 17.

At the output of this unit, built on the principle of a mixer, vibrations with a frequency of

f ₀ = f _OD + F _∂

where f _OP - the frequency of the reference oscillations coming from the output 3 of the pathogen 5;

F _∂ is the Doppler frequency resulting from the mutual movement of the target and the radar carrier in a straight line connecting them.

In turn, the oscillations with the frequency F _∂ arriving at the second input of the frequency offset unit 17 are generated in the code-frequency converter 16, which operates as follows.

The Doppler frequency code F _∂ , which is calculated by summing the Doppler frequency code F _∂o corresponding to the radial component of the speed V _{0 of} the radar carrier in the direction to the target, that is, V _0, comes to the input of the code-frequency converter 16 from the first output of the control unit 21 cosφ _A , and the frequency code F _∂c , corresponding to the radial component of the target’s speed, set by the radar operator searching for speed in the process of radar observation. The value of F _∂o is determined from the expression

,

Codes of values of the carrier frequency f _ci in this repetition period are received through the first input of the control unit 21 (Fig. 10) from the information output of the frequency adjustment unit 6. Codes of values of V ₀ , φ _A come from the second and fourth inputs of the control unit 21, respectively, from external systems.

The values of the Doppler frequency codes F _∂ = F _∂o + F _∂c supplied to the code-frequency converter 16 change the division ratio of the controlled frequency divider of the pulse generator, the resulting pulse sequence with a repetition frequency equal to the Doppler frequency F _∂ falls onto the filter low frequencies, which selects the fundamental harmonic equal to F _∂ and supplied to the output of the Converter 16 "code-frequency".

Fluctuations in the frequency f ₀ = f _OP + F _∂ go to the input of the reference frequency of the block 13 of the phase detectors, and to the input of the reference frequency of one of the phase detectors directly, and to the input of the other through the 90 ° phase shifter, thus quadrature video channels are formed.

The video signals from the outputs of the block 13 phase detectors fall on the corresponding inputs of the block 14 of video amplifiers, the bandwidth of which can vary in accordance with changes in τ _And discrete phase-shift signals that determine

the width of their spectrum, this is achieved by supplying signals through the third output of the control unit 21 to the control input of the block 14 of video amplifiers switching capacitors that determine the cutoff frequency of the frequency response of the video amplifiers.

The signals from the outputs of block 14 of the video amplifiers fall on the corresponding inputs of the block 15 intra-period processing.

Block 15 intra-period processing operates as follows (Fig.6).

The code sequences from the output of the generator 9 phase-shift code codes fall through the fifth input of the intra-period processing unit 15 to the signal inputs of the shift registers 50 and 51 of the sine and cosine quadrature channels. These shift registers are controlled by clock pulses. received at the corresponding inputs from the fourth input of block 15 through the key block 52, the control input of which from the third input of block 15 receives clock pulses with a repetition frequency F _P and duration T _AND , the position of the trailing edge of which corresponds to zero distance to the target (taking into account the delay on T _And when compressing the FM signals), therefore, the advance along the shift registers 50 and 51 begins just at the moment corresponding to zero range. Code sequences appear on the taps from the bits of the shift registers 50 and 51 with numbers i at the moments of arrival of reflected signals from ranges R _i = iΔR, where

- resolution in range, corresponding to the duration τ _И = Т of the phase manipulation discrete (с - speed of light).

These code sequences with delays τ _И , 2τ _И , ..., mτ _И appear at the first inputs of the corresponding multipliers 48 ₁ , 48 ₂ , ..., 48 _{m of the} first quadrature and 49 ₁ , 49 ₂ , ..., 49 _m the second quadrature, the other inputs of which receive the quadrature components of the reflected signals from targets at ranges ΔR, 2ΔR, ..., mΔR (m is the number of range resolution elements viewed), unless, of course, they are there. After multiplication, the products accumulate in the corresponding accumulating adders 53 ₁ , 53 ₂ , ..., 53 _m and 54 ₁ , 54 ₂ , ..., 54 _{m of} quadrature channels,

that is, at their outputs are formed the values of cross-correlation (convolution) of the code sequence and the received signals in accordance with the optimal processing rule (see, for example, [5], p. 424), then, to exclude the unknown initial phase, corresponding to one and of the same range, the quadrature components of the convolution arrive at the inputs of the corresponding blocks 55 ₁ , 55 ₂ , ..., 55 _{m of the} union of quadratures in which they are combined, in particular, according to the “sum of squares” rule.

At the beginning of the next repetition period, on the trailing edge of the clock pulses coming from the third input of block 15 to the zero-setting inputs of the accumulating adders 53 ₁ , ..., 53 _m and 54 ₁ , ..., 54 _m , they are reset.

The compressed signals from the multi-channel output of the intra-period processing unit 15 go through the corresponding m range channels to the input of the secondary processing and display unit 20. This unit in the active mode of operation of the radar operates as follows (Fig.9).

From the first input of the secondary processing and display unit 20, the compressed signals from all m channels (range resolution elements) pass through the corresponding amplitude quantizers 63 ₁ , ..., 63 _m where they are binary quantized according to the rule

where S _i (t) is the signal at the input of the amplitude quantizer of the i-th range channel;

η _i is the binary signal at its output;

x ₀ is the threshold level determined by the permissible value of false response (due to noise).

The binary signals η _i fall on the corresponding shift registers 64 _i (i = 1, 2, ..., m) at the time of the leading edge of the clock pulses with a repetition frequency F _P clock pulses arriving at the clock inputs of the registers 64 _i from the sixth input of block 20, that is, at the end of the repetition period. The number of bits of the shift registers 64 _i is equal to the number of pulses in the packet, so that accumulated signals are formed at the outputs of the adders 65 _i - the results of the accumulation of bursts of pulses reflected

signals. These accumulated signals through the switch 66, interrogating alternately all range channels in each repetition period, are fed to the signal input (brightness signal) of the monitor 68.

The pulses of the clock frequency f _T fall from the fifth input of block 20 through the key block 67, controlled by clock pulses with a repetition frequency F _P and duration T _AND , at the same time, starting from the moment of zero range, to the switch 66 of the range channels and to the counter 69, which provides after him, the first digital-to-analog converter 70 generates a vertical voltage of the monitor 68. Thus, a range scan is performed.

The azimuthal scan is provided using the antenna position code signals coming from the second output of the antenna 1 through the third input of block 20 to the second digital-to-analog converter 71, and from it to the horizontal input of the monitor 71. Thus, the signals are displayed on the brightness indicator - monitor 68 - in a rectangular range-azimuth coordinate system.

The operation of the secondary processing and display unit 20 in the passive mode, as well as the operation of the control unit 21 (Fig. 10) are discussed above. It should only be noted that at the operator’s command, using the antenna control unit 82, the signals from the fourth output of the control unit 21 are fed to the third input (drive control) of the antenna 1 (Fig. 2), providing, if necessary, a transition to the manual drive control mode ( manual tracking of the target).

The operation of the synchronizer 7 (Fig. 12) consists in generating control signals (Fig. 11), while the signal 87 is formed by dividing the frequency of the pulses generated by the clock generator 88 by the required number of times, and other signals using the RS-90 block 90 triggers with decoders and driver 91 pulses, generating signals of the required duration and delay (lead) relative to the beginning of the probing signal.

Additional selection of the received signals of radio emissions by the carrier frequency and the formation of signs of signal reception by the main lobe of the radiation pattern eliminates errors in determining the number of sources of radio emissions, improves the accuracy of direction finding, which allows more accurate determination of the scanning sector and the operating mode of the active channel, which allows

reduce the scanning sector and reduce the radiation power when the radar is in active mode, which increases the stealth of the radar.

The technical result of using the utility model is to increase the resolution.

Using the information presented in the application materials, the proposed radar can be manufactured in production using well-known materials, elements, units and technology, and used to detect surface and coastal targets and measure their coordinates, which proves the industrial applicability of the utility model.

In accordance with the application materials, a prototype of the device was manufactured, tests of which confirmed the achievement of the technical effect indicated in the application.

Information sources

1. Guide to radar, ed. M. Skolnik // Translation from English. Volume 4. M :, Sov. Radio, 1978.

2. US patent No. 4.338.604 from 08.29.80, IPC G 01 S 13/24, 7/28, publ. 07/06/82.

3. RF patent №2124221 from 02/11/1998, IPC G 01 S 13/42, publication 12/27/1998 (prototype).

4. Cook C. and Bernfeld M. Radar signals. Owls Radio, Moscow: 1971.

5. Handbook of Radar, ed. M. Skolnik // Translation from English. Volume 3. M :, Sov. Radio, 1979.

Claims (1)

A radar station containing a serially connected synchronizer, transmitter, antenna switch and antenna, an echo signal receiver connected to the third arm of the antenna switch, the transmitter comprising serially connected frequency tuning unit, exciter, phase manipulator and power amplifier, as well as a phase-shift code generator and pulse modulator and the echo receiver contains a series-connected high-frequency amplifier, mixer, intermediate-frequency amplifier you and the phase detector unit, the first and second quadrature outputs of which are connected to the corresponding inputs of the video amplifier unit, as well as the secondary processing and information display unit, the output of the local oscillator frequency of the pathogen connected to the local oscillator input of the mixer, the output of the phase shift code generator and the input of the pulse modulator connected, respectively, with the control inputs of the phase manipulator and power amplifier, the output of the synchronization pulses of the synchronizer repetition frequency is connected to the control inputs pulse modulator and phase shift code generator, the clock output of the synchronizer is connected to the second input of the clock pulses of the phase shift code generator, and the output of the antenna angular position code is connected to the information input of the secondary processing and information display unit, the radio emission receiver and the detection unit are connected in series and measurements connected in series to the control unit, the code-frequency converter and the frequency offset unit, as well as the intra-period processing unit and, moreover, the output of the reference frequency of the pathogen is connected to the input of the reference frequency of the phase detector unit through the frequency offset unit, the information inputs of the control unit are connected, respectively, the first to the information output of the frequency adjustment unit, the fourth to the output of the antenna angular position code, and the second and third are the input of the input of the own speed of the carrier of the radar station and the input of the speed setting of the detected target, respectively, the outputs of the control signals of the control unit are connected, respectively Of course, the second is with the power amplifier power control input, the third is with the synchronizer input and the video amplifier band control input connected, the fourth is with the antenna drive control input, the fifth is with the frequency channel switching input of the secondary processing and display unit and the control input of the detection unit and measurements, and the sixth - with the antenna switching input, the first and second quadrature outputs of the video amplifier block are connected to the corresponding inputs of the intra-period processing block, the signal output to which is connected to the first signal input of the secondary processing and display unit, to the second signal input of which the output of the detection and measurement unit is connected, the signal input of the radio emission receiver is connected to the output of the radio emission signals of the antenna, the output of the phase-shift code generator is also connected to the input of codes of the intra-period processing unit, and the outputs of the clock pulses of the repetition frequency and pulses of the clock frequency of the synchronizer are also connected to the corresponding inputs of the block intraperiod th processing unit and secondary processing and display unit, characterized in that it includes an auxiliary antenna device of the passive channel, an auxiliary receiver of the passive channel, the outputs of which are connected to the second input of the detection and measurement unit, a device for selecting and measuring the carrier frequency, the control input of which is connected to the corresponding bits of the seventh output of the control unit, and the signal input is connected to the output of the radio emission signals of the antenna, and the first output of the selection and carrier carrier measurements the frequency is connected to the second input of the radio emission receiver, and the second output of the carrier frequency selection and measurement device is connected to the third input of the detection and measurement unit.