RU2611581C1 - Shf range-finder - Google Patents

Abstract

FIELD: radio engineering.

SUBSTANCE: invention relates to radio engineering and can be used in phase direction finders designing within radio measuring devices, systems and complexes of super-high frequency (SHF) range. Said result is achieved due to fact, that SHF range-finder comprises N receiving radio channels (consisting of receiving antenna, communication unit, frequency converter and intermediate frequency amplifier), frequency-generating device (FGD), first, second and third two-channel switches, except for first, loaded with first and second matched loads, respectively, heterodyne, connected to frequency converters heterodyne inputs, signal processing and control unit (SPCU), wherein FGD generates M calibration signals at different from each other frequencies, which are selected so, that calibration signal phase differences increment on adjacent frequencies from receiving radio channels outputs, for which phase mismatch is determined, not exceeded by module value π. SPCU is made with possibility of frequency-generating device operation algorithm controlling.

EFFECT: technical result is elimination of receiving radio channels phase mismatch ambiguity, which enables avoiding need for receiving radio channels pre-adjustment.

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Description

The invention relates to radio engineering and can be used in the construction of phase direction finders as part of radio measuring devices, systems and complexes of the microwave range.

Known technical solutions for the construction of phase direction finders to determine the bearing of the radiation source [1]. Phase direction finders contain the following functional blocks: receiving radio channels, consisting of series-connected antenna and receiving devices, and a computing device. The antenna device of each radio channel is connected to a computing device through a receiving device, while the receiving device has the structure of a superheterodyne receiver, and the antenna device contains a microwave antenna (with directional or non-directional radiation patterns) with a preliminary radio frequency amplifier. The antenna device of the direction finder contains two or more antennas (with directional or non-directional radiation patterns, or their variations) with preliminary radio frequency amplifiers. Direction finders formed by pairs of antennas measure the phase difference of the radiation source signal at the respective outputs of the receiving radio channels. The disadvantage of such phase direction finders is the low accuracy of determining the direction to the source of radio emission (bearing) due to the phase non-identity of the receiving radio channels. The elimination of phase non-identity of receiving radio channels by technical methods is a difficult task.

Known phase direction finder described in US patent No. 4494118 from 01/15/1985 [2], having a structure with a well-known type of construction of direction finding devices, which contains N antennas and receiving radio channels, a local oscillator, a control unit and a processing and control unit. On the example of a direction finder with two antennas and receiving channels, evidence of the achievement of a technical result is presented - measuring the phase non-identity of receiving radio channels to take it into account when determining the true phase difference of the signal received by the antennas. The disadvantage of this device is the dependence of the systematic error of measuring the identity of the receiving radio channel on the non-identity of the elements in the control circuit, such as power dividers and switches. Therefore, with the same electric length of the radio channels, the phase difference of the control signals measured at the output of these radio channels at the first and second stages of measurement will differ from each other by the phase non-identity of these elements, which limits the potential accuracy of the phase difference.

The prototype of the invention is a direction finding device (first option, patent RU No. 2269791) [3].

According to the first embodiment of the invention, the direction finder comprises N receiving radio channels, consisting of a series-connected receiving antenna, an omnidirectional communication element, a mixer and an intermediate frequency amplifier (IFA). The direction finder also contains a local oscillator, the outputs of which are connected to the heterodyne inputs of the mixers, three two-channel switches, the outputs of the first two-channel switch connected to the corresponding inputs of the second and third two-channel switches, the output arms of the second and third two-channel switches connected to the third arm of the first and fourth arm N-, respectively of omnidirectional communication elements, the second output shoulders of the second and third two-channel switches are connected respectively only to the inputs of the matched loads, the control generator, the output of which is connected to the input arm of the first two-channel switch, the outputs of all N intermediate frequency amplifiers are connected to the corresponding inputs of the processing and control unit, the fourth arm of the non-directional communication element of each radio channel, except the last, is connected to the third arm of the non-directional the communication element of the subsequent radio channel, that is, the fourth arm of the first non-directional communication element is connected to the third arm of the second non-direction lennogo coupler, the fourth port of the second non-directional coupler is connected to a third arm of the third non-directional coupler, etc., wherein the fourth non-directional coupler shoulder N-th radio receiver is connected to an output port of the third two-channel switch.

The direction finder works as follows. Through the receiving antennas, the input signals arrive at the non-directional communication elements, then to the signal inputs of the mixers, where they are converted in frequency, that is, the signal is transferred from the microwave range to the intermediate frequency range. After the mixer, the signals are amplified in the amplifiers of the intermediate frequency and fed to the processing and control unit, in which phase measurements are made and signals are generated according to a given program that control all two-channel switches.

Checking the phase identity of the radio channels is carried out in two stages, in the absence of input signals.

At the first stage, the signal of the control generator through the first and second two-channel switches is sequentially supplied to all the receiving radio channels from the first to the Nth through the shoulders of non-directional communication elements, as well as to the second matched load through the input arm and second output arm of the third two-channel switch, while the first the output arm of the third two-channel switch and the first matched load are disconnected from the control generator using the first and second two-channel switches.

At the second stage, the direction of propagation of the control signal is reversed and proceeds from the Nth receiving radio channel to the first through the shoulders of non-directional communication elements, as well as to the coordinated load through the second output shoulder of the second two-channel switch. In this case, the second coordinated load is disconnected from the control generator using the third two-channel switch.

The phase identity of the receiving radio channels with indices i, j, (i ≠ j), i, j∈ [1, N] is checked by processing the phase difference of the control signals at the corresponding outputs of the receiving radio channels, which differ from each other in the direction of propagation of the control signal. In this device, the error of measuring the phase non-identity of the receiving radio channels depends only on the non-identity of the nodes of the non-directional input of the control signal and can be made quite small. The obtained values of the phase non-identity of the receiving radio channels are taken into account in the final result of signal phase measurements or can be compensated with the help of controlled phase shifters included in the radio channels.

.The disadvantage of this technical solution is the ambiguity of measuring the phase non-identity of the receiving radio channels, due to the cyclical increment of the total phases of the control signal. The uncertainty of measuring the phase non-identity of the receiving radio channels is ± π, which leads to the need to pre-configure the receiving radio channels so that the phase non-identity of the receiving radio channels is in the range

.

The technical result of the invention is the elimination of the uncertainty of the phase non-identity of the receiving radio channels, which eliminates the need for preliminary adjustment of the receiving radio channels.

The technical result is achieved due to the fact that in the microwave direction finder containing N receiving radio channels, each of which is made up of a series-connected receiving antenna, a communication unit, a frequency converter and an intermediate frequency amplifier, a frequency-generating device (CCU), the output of which connected to the input of the first two-channel switch, the first and second inputs and outputs of which are connected respectively to the first inputs and outputs of the second and third two-channel switches, loaded respectively According to the first and second coordinated loads, the second input-output of the second two-channel switch is connected to the first input-output of the communication node of the first receiving radio channel, the second input-output of the communication node of each receiving radio channel, except the Nth one, is connected to the first input-output of the communication node of the subsequent the receiving radio channel, the second input-output of the communication node of the Nth receiving radio channel is connected to the second input-output of the third two-channel switch, a local oscillator connected to the local oscillator inputs of the frequency converters signal and control (BOSU), the inputs of which are connected to the corresponding outputs of the amplifiers of intermediate frequency, the control output is with the corresponding control inputs of the first, second and third two-channel switches, and the information output is with the output of the direction finder, the frequency-generating device is functionally designed in this way, which generates M calibration signals at different frequencies, which are selected so that at adjacent frequencies the increment of the phase differences of the calibration signal from the outputs receiver radio channels, for which phase non-identity is determined, did not exceed π in absolute value both at the first and at the second measurement stage, and the difference in neighboring frequencies was minimal. The signal processing and control unit is configured to control the operation algorithm of the frequency generating device, while the control output of the BOSU is connected to the control input of the ChSU.

The frequency-generating device can be made of M calibration signal generators and a multi-channel switch, while the signal output of each calibration signal generator is connected to the corresponding signal input of the multi-channel switch, the control input and output of which are connected to the input and output of the CGU, respectively.

The frequency-generating device can be made up of M calibration signal generators and a multi-channel adder, while the signal output of each calibration signal generator is connected to the corresponding signal input of the multi-channel adder, the control input and output of which are connected to the input and output of the CGU, respectively.

The frequency-generating device can be made in the form of a controlled generator of calibration signals in analogue design or digital in accordance with generally accepted circuitry solutions.

The invention is illustrated by the structural diagrams shown in FIG. 1, 2, 3.

In FIG. 1 shows a structural diagram of a microwave direction finder.

In FIG. 2, 3 are structural diagrams of a frequency generating device (versions).

The microwave direction finder (Fig. 1) contains N receiving radio channels 1.1, 1.2, 1.3, ..., 1.N, while each receiving radio channel 1.1, 1.2, 1.3, ..., 1.N consists of a series-connected receiving antenna 1.1.1, 1.2.1, 1.3.1, ..., 1.N.1, communication center 1.1.2, 1.2.2, 1.3.2, 1.N.2, frequency converter 1.1.3, 1.2.3, 1.3.3, ..., 1.N.3 and an intermediate frequency amplifier 1.1.4, 1.2.4, 1.3.4, ..., 1.N.4, a frequency-generating device 2, the output of which is connected to the input of the first two-channel switch 3, the first and second the inputs and outputs of which are connected respectively to the first inputs and outputs of the second and third two-channel switches 4, 5, respectively loaded with the first and second coordinated loads 6, 7. The second input-output of the second two-channel switch 4 is connected to the first input-output of the communication node 1.1.2, the second input-output of each communication node 1.1.2, 1.2. 2, 1.3.2, ..., 1.N-1.2, except 1.N.2, is connected respectively to the first input - the output of the communication node 1.2.2, 1.3.2, 1.4.2, ..., 1.N.2 of the subsequent radio channel, and the second input-output of the communication node 1.N.2 is connected to the second input-output of the third two-channel switch 5. The local oscillator 8 is connected to the heterodyne inputs of the transformer teley frequency 1.1.3, 1.2.3, 1.3.3, ..., 1.N.3. The inputs of the signal processing and control unit 9 are connected to the corresponding outputs of the intermediate frequency amplifiers 1.1.4, 1.2.4, 1.3.4, ..., 1.N.4, the control output is connected to the corresponding control inputs of the frequency-generating device, the first, second and third dual-channel switches, and information output - with the output of the direction finder.

The frequency-generating device 2 (Fig. 2) consists of M calibration signal generators 2.1, 2.2, 2.3, ..., 2.M and a multi-channel switch 10, while the signal outputs of all calibration signal generators 2.1, 2.2, 2.3, ..., 2. M are connected to the corresponding signal inputs of the multi-channel switch 10, the control input of which is connected to the input of the CGU, and the output to the output of the frequency-generating device.

The frequency generating device 2 (Fig. 3) consists of M calibration signal generators 2.1, 2.2, 2.3, ..., 2.M and a multi-channel adder 11, while the signal outputs of all calibration signal generators 2.1, 2.2, 2.3, ..., 2. M are connected to the corresponding signal inputs of the multi-channel adder 11, the control input of which is connected to the input of the CGU, and the output to the output of the frequency-generating device.

The microwave direction finder (Fig. 1) with a frequency-generating device 2 (Fig. 2, 3) works as follows. The input signals are received at the receiving antennas 1.1.1, 1.2.1, 1.3.1, ..., 1.N.1 of the corresponding receiving radio channels 1.1, 1.2, 1.3, ..., 1.N and through the communication nodes 1.1.2, 1.2.2 , 1.3.2, ..., 1.N.2 get to the signal inputs of the frequency converters 1.1.3, 1.2.3, 1.3.3, ..., 1.N.3, where using the local oscillator 8, the carrier frequencies of the input signals are converted into range of intermediate frequencies. After frequency conversion, these signals are amplified in intermediate frequency amplifiers 1.1.4, 1.2.4, 1.3.4, ..., 1.N.4 and then enter the signal processing and control unit 9, in which phase measurements are made and formed according to a given program control signals of two-channel switches 3, 4, 5 and frequency-generating device.

Verification of the phase non-identity of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N of the microwave direction finder (Fig. 1) with a frequency-generating device 2 (Fig. 2) is carried out by processing the measurement results of the phase difference increment of the calibration signal from the outputs of the receiving radio channels at frequencies , which are selected so that at adjacent frequencies the increment of the full phase of the calibration signal at the outputs of the receiving radio channels does not exceed ± π. Each stage is divided into M measures. The stage determines the direction of propagation of the calibration signal, and the cycle corresponds to the choice of frequency of the calibration signal. To simplify, we describe an algorithm for determining phase non-identity on the m-th clock cycle.

m-ого генератора сигнала калибровки частотно-генерирующего устройства 2 через многоканальный коммутатор 10 попадает на вход первого двухканального коммутатора 3, затем на первый вход-выход второго двухканального коммутатора 4 и далее последовательно поступает во все приемные радиоканалы 1.1, 1.2, 1.3, …, 1.N от первого к N-ому через узлы связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 7 через второй вход - выход и выход третьего двухканального коммутатора 5, при этом первый вход - выход третьего двухканального коммутатора 5 и согласованная нагрузка 6 отключены от m-ого генератора сигнала калибровки 2.m соответственно с помощью первого и второго двухканальных коммутаторов 3, 4, а все остальные генераторы сигнала калибровки 2.1, 2.2, 2.3, …, 2.m-1, 2.m+1, …, 2.М отключены от выхода частотно-генерирующего устройства 2 многоканальным коммутатором 10. Далее согласно заданному алгоритму управления многоканальным коммутатором 10, формируемому в блоке обработки сигналов и управления 9, на первом этапе m+1 такта происходит отключение выхода частотно-генерирующего устройства 2 от m-ого генератора сигнала калибровки 2.m и его подключение к m+1-ому генератору сигнала калибровки 2.m+1, при этом все остальные генераторы сигнала калибровки 2.1, 2.2, 2.3, …, 2.m, 2.m+2, …, 2.М отключены от выхода частотно-генерирующего устройства 2 многоканальным коммутатором 10. Аналогично далее происходит отключение и подключение к выходу частотно-генерирующего устройства 2 всех остальных генераторов сигнала калибровки 2.1, 2.2, 2.3, …, 2.М, соответствующих своему такту.At the first stage of the mth step, according to a given program, the signal at a frequency

m-th generator of the calibration signal of the frequency generating device 2 through the multi-channel switch 10 goes to the input of the first two-channel switch 3, then to the first input-output of the second two-channel switch 4 and then sequentially goes to all the receiving radio channels 1.1, 1.2, 1.3, ..., 1 .N from the first to the Nth through the communication nodes 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, as well as to the coordinated load 7 through the second input - the output and output of the third two-channel switch 5, with this first input is the output of the third two-channel switch 5 and matched load 6 is disconnected from the m-th calibration signal generator 2.m, respectively, using the first and second two-channel switches 3, 4, and all other calibration signal generators 2.1, 2.2, 2.3, ..., 2.m-1, 2.m + 1 , ..., 2.M are disconnected from the output of the frequency-generating device 2 by the multi-channel switch 10. Further, according to the specified control algorithm of the multi-channel switch 10, which is generated in the signal processing and control unit 9, at the first step m + 1 clock, the output of the frequency-generating device is disabled 2 from the mth signal generator calibration chamber 2.m and its connection to the m + 1st calibration signal generator 2.m + 1, while all other calibration signal generators 2.1, 2.2, 2.3, ..., 2.m, 2.m + 2, ..., 2.M are disconnected from the output of the frequency-generating device 2 by a multi-channel switch 10. Similarly, further disconnection and connection to the output of the frequency-generating device 2 of all other calibration signal generators 2.1, 2.2, 2.3, ..., 2.M corresponding to their own clock cycle.

At the second stage, the direction of propagation of the calibration signal is reversed. At the second stage of the mth cycle, the signal of the mth generator of the calibration signal 2.m through the multi-channel switch 10, the first and third two-channel switches 3, 5, is sequentially distributed from the N-th receiving radio channel 1.N to the first receiving radio channel 1.1 through communication nodes 1.N.2, ..., 1.3.2, 1.2.2, 1.1.2, as well as to the coordinated load 6 through the second input-output and output of the second two-channel switch 4, while the first input-output of the second two-channel switch 4 and the second matched load 7 disconnected from the m-th calibration signal generator 2.m respectively, using the first and third two-channel switches 3, 5, and all other generators of the calibration signal 2.1, 2.3, 2.4, ..., 2.m-1, 2.m + 1, ..., 2.M are disconnected from the output of the frequency generating device 2 by a multi-channel switch 10. Then, according to the specified control algorithm of the multi-channel switch 10, which is formed in the signal processing and control unit 9, at the second stage of the mth cycle, the output of the frequency-generating device 2 is disconnected from the mth calibration signal generator 2.m and its connection to m + 1st signal generator calibration 2.m + 1, while all other generators of the calibration signal 2.1, 2.3, 2.4, ..., 2.m, 2.m + 2, ..., 2.M are disconnected from the output of the frequency-generating device 2 by multi-channel switch 10. Similarly, later on, all other remaining signal generators of calibration signal 2.1, 2.2, 2.3, ..., 2.M, corresponding to their own clock, are turned off and connected to the output of the frequency-generating device 2.

The operation algorithm of the multi-channel switch 10 is set by the signal processing and control unit 9 in such a way that only one of the plurality of calibration signal generators 2.1, 2.2, 2.3, ..., 2.M is connected to the output of the frequency-generating device 2

Verification of the phase non-identity of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N of the microwave direction finder (Fig. 1) with the frequency-generating device 2 (Fig. 3) is carried out in two stages in the absence of input signals.

генераторов сигнала калибровки 2.1, 2.2, 2.3, …, 2.М частотно-генерирующего устройства 2 через многоканальный сумматор 11 попадают на вход первого двухканального коммутатора 3, затем на вход - выход второго двухканального коммутатора 4 и далее последовательно поступают во все приемные радиоканалы 1.1, 1.2, 1.3, …, 1.N от первого к N-ому через плечи узлов связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 7 через второй вход-выход и выход третьего двухканального коммутатора 5, при этом первый вход-выход третьего двухканального коммутатора 5 и согласованная нагрузка 6 отключены от выхода частотно - генерирующего устройства 2 соответственно с помощью первого и второго двухканальных коммутаторов 3, 4.At the first stage, calibration signals with frequencies

calibration signal generators 2.1, 2.2, 2.3, ..., 2.M of the frequency-generating device 2 through the multi-channel adder 11 go to the input of the first two-channel switch 3, then to the input - output of the second two-channel switch 4 and then sequentially enter all the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N from the first to the Nth through the shoulders of communication nodes 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, as well as to the agreed load 7 through the second input-output and the output of the third two-channel switch 5, while the first input-output of the third two-channel switch 5 and This load 6 is disconnected from the output of the frequency generating device 2, respectively, using the first and second two-channel switches 3, 4.

генераторов сигнала калибровки 2.1, 2.2, 2.3, …, 2.М через многоканальный сумматор 11, первый и третий двухканальные коммутаторы 3, 5 последовательно распространяются от N-го приемного радиоканала 1.N к первому через узлы связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 6 через второй вход - выход и выход второго двухканального коммутатора 4, при этом первый вход - выход второго двухканального коммутатора 4 и вторая согласованная нагрузка 7 отключены от выхода частотно-генерирующего устройства 2 соответственно с помощью первого и третьего двухканальных коммутаторов 3, 5.At the second stage, the direction of propagation of the calibration signals is reversed and proceeds from the Nth receiving radio channel 1.N to the first receiving radio channel 1.1. Now signals with frequencies

calibration signal generators 2.1, 2.2, 2.3, ..., 2.M through a multi-channel adder 11, the first and third two-channel switches 3, 5 are sequentially distributed from the N-th receiving radio channel 1.N to the first through communication nodes 1.1.2, 1.2.2 , 1.3.2, ..., 1.N.2, as well as to the coordinated load 6 through the second input — the output and output of the second two-channel switch 4, while the first input — the output of the second two-channel switch 4 and the second coordinated load 7 are disconnected from the output -generating device 2, respectively, using the first and third two channel switches 3, 5.

частотно-генерирующим устройством 2 осуществляется двумя способами.Verification of the phase non-identity of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N of the microwave direction finder (Fig. 1) with a frequency-generating device 2, which is a controlled generator of calibration signals, is carried out by processing the measurement results of the phase difference increment of the calibration signal from the outputs radio channels at frequencies that are selected so that at adjacent frequencies the increment of the full phase of the calibration signal at the outputs of the receiving radio channels does not exceed ± π. Frequency grid calibration signals

frequency-generating device 2 is carried out in two ways.

In the first method, the frequency-generating device 2 performs the formation of a frequency grid with time division, that is, its operation corresponds to the operation of the frequency-generating device 2 (Fig. 2). In this case, each step is divided into M measures. The stage determines the direction of propagation of the calibration signal, and the cycle corresponds to the choice of frequency of the calibration signal. To simplify, we describe an algorithm for determining phase non-identity on the m-th clock cycle.

частотно-генерирующего устройства 2 попадает на вход первого двухканального коммутатора 3, затем на первый вход-выход второго двухканального коммутатора 4 и далее последовательно поступает во все приемные радиоканалы 1.1, 1.2, 1.3, …, 1.N от первого к N-ому через узлы связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 7 через второй вход-выход и выход третьего двухканального коммутатора 5, при этом первый вход - выход третьего двухканального коммутатора 5 и согласованная нагрузка 6 отключены от частотно-генерирующего устройства 2 соответственно с помощью первого и второго двухканальных коммутаторов 3, 4. Затем согласно заданному алгоритму управления частотно-генерирующим устройством 2, формируемому в блоке обработки сигналов и управления 9, на первом этапе m+1 такта происходит переключение частотно-генерирующего устройства 2 на выдачу сигнала калибровки частоты

.At the first stage of the mth cycle, according to a given program, the calibration signal at a frequency

frequency-generating device 2 gets to the input of the first two-channel switch 3, then to the first input-output of the second two-channel switch 4 and then sequentially goes to all the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N from the first to the Nth through nodes communication 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, as well as to the coordinated load 7 through the second input-output and output of the third two-channel switch 5, while the first input is the output of the third two-channel switch 5 and matched load 6 disconnected from the frequency generating device 2 respectively but using the first and second two-channel switches 3, 4. Then, according to the specified control algorithm of the frequency-generating device 2, which is generated in the signal processing and control unit 9, at the first step m + 1 of the clock cycle, the frequency-generating device 2 switches to the calibration signal frequency

.

через первый и третий двухканальные коммутаторы 3, 5, последовательно распространяется от N-ого приемного радиоканала 1.N к первому приемному радиоканалу 1.1 через узлы связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 6 через вход-выход и выход второго двухканального коммутатора 4, при этом первый вход-выход второго двухканального коммутатора 4 и вторая согласованная нагрузка 7 отключены от частотно-генерирующего устройства 2 соответственно с помощью первого и третьего двухканальных коммутаторов 3, 5. Затем согласно заданному алгоритму управления частотно-генерирующим устройством 2, формируемому в блоке обработки сигналов и управления 9, на втором этапе m+1 такта происходит переключение частотно-генерирующего устройства 2 на выдачу сигнала калибровки частоты

.At the second stage, the direction of propagation of the calibration signal is reversed. In the second stage of the mth cycle, the calibration signal at the frequency

through the first and third two-channel switches 3, 5, sequentially distributed from the N-th receiving radio channel 1.N to the first receiving radio channel 1.1 through the communication nodes 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, and also into the coordinated load 6 through the input-output and output of the second two-channel switch 4, while the first input-output of the second two-channel switch 4 and the second coordinated load 7 are disconnected from the frequency-generating device 2, respectively, using the first and third two-channel switches 3, 5. Then according to the given algorithm at the control of the frequency-generating device 2, formed in the signal processing and control unit 9, in the second step m + 1 of the clock cycle, the frequency-generating device 2 is switched to the output of the frequency calibration signal

.

In the second method, the frequency-generating device 2 provides a frequency grid without time division, that is, its operation corresponds to the operation of the frequency-generating device 2 (Fig. 3). In this case, the operation step determines the direction of propagation of the calibration signal.

частотно-генерирующего устройства 2 попадают на вход первого двухканального коммутатора 3, затем на первый вход-выход второго двухканального коммутатора 4 и далее последовательно поступают во все приемные радиоканалы 1.1, 1.2, 1.3, …, 1.N от первого к N-ому через плечи узлов связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 7 через второй вход-выход и выход третьего двухканального коммутатора 5, при этом первый вход-выход третьего двухканального коммутатора 5 и согласованная нагрузка 6 отключены от частотно-генерирующего устройства 2 соответственно с помощью первого и второго двухканальных коммутаторов 3, 4.At the first stage, according to a given program, calibration signals with frequencies

frequency-generating device 2 go to the input of the first two-channel switch 3, then to the first input-output of the second two-channel switch 4 and then sequentially go to all the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N from the first to the Nth through the shoulders communication nodes 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, as well as to the coordinated load 7 through the second input-output and output of the third two-channel switch 5, while the first input-output of the third two-channel switch 5 and matched load 6 are disconnected from the frequency generating device 2 respectively using the first and second two-channel switches 3, 4.

управляемого генератора сигналов калибровки через двухканальные коммутаторы 3, 5 последовательно распространяются от N-ого приемного радиоканала 1.N к первому через узлы связи 1.1.2, 1.2.2, 1.3.2, …, 1.N.2, а также в согласованную нагрузку 6 через второй вход - выход и выход второго двухканального коммутатора 4. При этом первый вход - выход второго двухканального коммутатора и вторая согласованная нагрузка 7 отключены от частотно-генерирующего устройства 2 соответственно с помощью первого и третьего двухканальных коммутаторов 3, 5.At the second stage, the direction of propagation of the calibration signals is reversed and proceeds from the Nth receiving radio channel 1.N to the first receiving radio channel 1.1. Now calibration signals with frequencies

the controlled generator of calibration signals through two-channel switches 3, 5 are sequentially distributed from the N-th receiving radio channel 1.N to the first through communication nodes 1.1.2, 1.2.2, 1.3.2, ..., 1.N.2, as well as to the coordinated load 6 through the second input — the output and output of the second two-channel switch 4. In this case, the first input — the output of the second two-channel switch and the second matched load 7 are disconnected from the frequency-generating device 2, respectively, using the first and third two-channel switches 3, 5.

частным случаем является пример, когда один из приемных радиоканалов 1.1, 1.2, 1.3, …, 1.N выбирается как опорный и относительно него определяются параметры фазовой неидентичности приемных радиоканалов 1.1, 1.2, 1.3, …, 1.N. Измерения проводятся в два этапа, отличающихся друг от друга направлением распространения сигналов калибровки. Неидентичность электрических длин двух приемных радиоканалов 1.1, 1.2, 1.3, …, 1.N определяется через разность фаз сигналов калибровки на соответствующих частотах

измеренных в блоке обработки сигналов и управления 9 на первом и втором этапе, а неопределенность разности фаз определяется числом полных периодов разности фаз сигналов калибровки, вычисленных в блоке обработки сигналов и управления 9.Checking the phase non-identity of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N is carried out for randomly selected pairs of receiving radio channels 1.1, 1.2, 1.3, ..., 1.N at frequencies

A special case is an example when one of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N is selected as a reference and relative to it the phase non-identity parameters of the receiving radio channels 1.1, 1.2, 1.3, ..., 1.N are determined. The measurements are carried out in two stages, differing from each other in the direction of propagation of the calibration signals. The non-identity of the electrical lengths of the two receiving radio channels 1.1, 1.2, 1.3, ..., 1.N is determined through the phase difference of the calibration signals at the corresponding frequencies

measured in the signal processing and control unit 9 at the first and second stage, and the phase difference uncertainty is determined by the number of full periods of the phase difference of the calibration signals calculated in the signal processing and control unit 9.

Let us consider an algorithm for eliminating the phase non-identity of receiving radio channels for a multi-channel phase monopulse direction finder formed by N receiving radio channels, in which the phase difference between the outputs of randomly selected receiving radio channels (PK _i , PK _j , i ≠ j) is estimated.

The implementation of the algorithm to eliminate the phase non-identity of the receiving radio channels is carried out in the signal processing and control unit 9.

The essence of the algorithm is to alternately introduce fixed phase shifts at different frequencies into the calibration signal supplied to the inputs of the receiving radio channels of the monopulse phase direction finder, and from the information about the phase differences of the calibration signal from the outputs of the receiving radio channels, taking into account the frequency dispersion of these phase differences, the phase non-identity of the receiving radio channels.

(m∈[1, М]) и соответственно круговая частота равна

тогда полная разность фаз сигнала калибровки с выходов радиоканалов с индексами i и j (i≠j, i, j∈[1, N]) на первом и втором этапах равна:Let the frequency of the calibration signal be

(m∈ [1, M]) and, accordingly, the circular frequency is

then the total phase difference of the calibration signal from the outputs of the radio channels with indices i and j (i ≠ j, i, j∈ [1, N]) in the first and second stages is equal to:

- полная разность фаз сигнала калибровки;Where

- the total phase difference of the calibration signal;

i and j are the indices of the radio channels;

m is the frequency index of the calibration signal;

L is the stage number;

- полная фаза сигнала калибровки на выходе приемного радиоканала с индексом j на этапе L;

- the full phase of the calibration signal at the output of the receiving radio channel with index j in step L;

- полная фаза сигнала калибровки на выходе приемного радиоканала с индексом i на этапе L;

- the full phase of the calibration signal at the output of the receiving radio channel with index i in step L;

на выходе приемного радиоканала с индексом i равна:At the first stage, the full phase of the calibration signal at the frequency

at the output of the receiving radio channel with index i is equal to:

- групповая задержка на частоте ω_m приемного радиоканала с индексом i;Where

- group delay at a frequency ω _{m of the} receiving radio channel with index i;

ϕ _{m, i} is the initial phase of the calibration signal at a frequency ω _m at the input point of the signal of the receiving radio channel with index i.

The full phase of the calibration signal at the output of the receiving radio channel with index j during signal propagation along the communication line from the radio channel with index i in the direction of the radio channel with index j:

- групповая задержка на частоте ω_m приемного радиоканала с индексом j;Where

- group delay at a frequency ω _{m of the} receiving radio channel with index j;

- групповая задержка на частоте ω_m распространения сигнала калибровки по линии связи от точки ввода сигнала приемного радиоканала с индексом i до точки ввода сигнала приемного радиоканала с индексом j.

- group delay at a frequency ω _{m of the} propagation of the calibration signal over the communication line from the input point of the signal of the receiving radio channel with index i to the input point of the signal of the receiving radio channel with index j.

At the second stage, the full phase of the calibration signal at the output of the radio channel with index i when the signal propagates along the communication line from the radio channel with index j in the direction of the radio channel with index i is determined by the expression:

here ϕ _{m, j} is the initial phase of the calibration signal at the input point of the signal of the receiving radio channel j;

- групповая задержка на частоте ω_m распространения сигнала калибровки по линии связи от точки ввода сигнала приемного радиоканала с индексом j до точки ввода сигнала приемного радиоканала с индексом i.

- group delay at the frequency ω _{m of the} propagation of the calibration signal over the communication line from the input point of the signal of the receiving radio channel with index j to the input point of the signal of the receiving radio channel with index i.

.Due to the principle of reciprocity of the transmission path of the calibration signal from the radio channel from the input point of the signal of the receiving radio channel with index j (i) to the input point of the signal of the receiving radio channel with index

.

At a frequency ω _{m, the} total phase of the calibration signal at the output of the receiving radio channel with index j is equal to:

It should be noted that measuring the total phase of the signal θ due to the periodicity of the circular functions is impossible. Its value can be determined with an uncertainty multiple of the value 2π, i.e.

where k is the phase ambiguity parameter of the signal phase equal to an arbitrary integer from the range (-∞, ∞);

ϕ is the measured part of the total phase of the signal in the range [-π, π].

Expression (1) taking into account equalities (2, 3, 4, 5) and remarks (6) will take the form:

- измеренные в диапазоне [-π, π] разности фаз сигналов калибровки на выходах радиоканалов с индексами i, j на первом и втором этапах процедуры оценки фазовой неидентичности радиоканалов равные:

здесь

- операция исключения по модулю 2π;Where

- the phase differences of the calibration signals measured in the range [-π, π] at the outputs of radio channels with indices i, j at the first and second stages of the procedure for assessing the phase non-identity of radio channels are equal to:

here

- an exception operation modulo 2π;

- неизвестные параметры фазовой неоднозначности измерения разностей фаз

равные:

где

- неизвестные параметры фазовой неоднозначности фаз сигналов радиоканалов с индексами i, j на первом и втором этапах процедуры оценки фазовой неидентичности радиоканалов.

- unknown phase ambiguity parameters for measuring phase differences

equal:

Where

- unknown parameters of the phase ambiguity of the phases of the signals of the radio channels with indices i, j at the first and second stages of the procedure for assessing the phase non-identity of radio channels.

является по определению величиной полной фазовой неидентичности радиоканалов с индексами i и j, а

- полной фазовой задержкой линии передачи сигнала калибровки между радиоканалами с индексами i и j на частоте ω_m, (m∈[1, М]).Value

is by definition the total phase non-identity of radio channels with indices i and j, and

- the total phase delay of the transmission line of the calibration signal between the radio channels with indices i and j at a frequency ω _m , (m∈ [1, M]).

From (7) it follows:

значения производных разностей фаз на частоте ω_m.here

the values of the derivatives of the phase differences at the frequency ω _m .

We introduce the function P (α, β), which determines the difference between the angles α and β through circular functions:

P (α, β) = arctan (cos (α-β), sin (α-β))

here cos (α-β) = cosαcosβ + sinαsinβ

sin (α-β) = sinαcosβ-cosαsinβ

the difference in angles α and β is determined in the range [-π, π].

From equation (7) it follows that the total phase ambiguity of the radio channels with indices i and j is equal to:

и

на 1 и 2 этапах калибровки, равная

, имеет неопределенность кратную π.It follows that the phase non-identity of radio channels with indices i and j, which is determined by measuring the phase difference of the signal calibration

and

at 1 and 2 stages of calibration, equal to

, has an uncertainty multiple of π.

To eliminate this collision, we use the frequency dispersion of the phase delay θ.

выбираются таким образом, чтобы приращения полных разностей фаз между соседними частотами на обоих этапах калибровки не превышали по абсолютному значению величины равной π, то есть выполнялось неравенство:Frequencies

are selected so that the increments of the total phase differences between adjacent frequencies at both stages of the calibration do not exceed the value equal to π in absolute value, i.e., the following inequality holds:

Condition (10) can be satisfied, of course, for sufficiently small frequency increments Δω _m = ω _{m + 1} -ω _m ; m∈ [1, M-1]; L = 1, 2;

The phase ambiguity elimination algorithm has the following form:

1. The parameters of the phase ambiguity of the measurement of the total phase difference of the radio channels with indices i and j at a frequency of ω _{1 are} calculated for the first and second stages of calibration:

Expression (1) for frequency ω ₁ at the first and second stages of calibration has the form:

A-priory:

- параметры фазовой неоднозначности измерения полной разности фаз на частоте ω₁, на 1 и 2 этапах калибровки.Where

- parameters of the phase ambiguity of measuring the total phase difference at a frequency of ω ₁ , at stages 1 and 2 of the calibration.

From (11), (12), taking into account (13), (14), (15), (16) for the first and second stages (L = 1, 2) of calibration, it follows:

L = 1, 2

Note that the equalities are satisfied:

L = 1, 2

- приращения полной разности фаз при изменении частоты от ω₁ до ω_k для первого и второго этапов калибровки, вычисляемые по выражениям:Where

- increments of the total phase difference when changing the frequency from ω ₁ to ω _k for the first and second stages of calibration, calculated by the expressions:

L = 1, 2

могут быть определены из решения систем уравнений следующих из выполнения равенств (18):In the presence of random measurement errors, the estimate of the total phase differences at a frequency ω _k equal for the first and second stages of calibration (L = 1, 2)

can be determined from solving systems of equations following from the fulfillment of equalities (18):

L = 1, 2

вычисляется через приращения разностей фаз следующим образом:here

calculated through increments of phase differences as follows:

From (20) it follows:

L = 1, 2

- параметры фазовой неоднозначности измерения полной разности фаз на частоте ω₁ на 1 и 2 этапах калибровки определяются в соответствии выражением:and

- the parameters of the phase ambiguity of the measurement of the total phase difference at a frequency of ω ₁ at 1 and 2 stages of calibration are determined in accordance with the expression:

L = 1, 2

here [...] ^R is the calculation of the nearest integer value of the operand.

2. The phase non-identity of the radio channels with indices i and j and the phase delay of the calibration signal transmission path between these radio channels at a frequency ω lying in the interval [ω _m , ω _{m + 1} ] are calculated:

The total phase difference of the calibration signal at the frequency ω, (ω∈ [ω _m , ω _{m + 1} ]) at the first and second stages of calibration, taking into account (7), can be written in the form:

- измеренные разности фаз сигнала калибровки на частоте ω с выходов радиоканалов с индексами i и j для первого и второго этапов калибровки;here

- the measured phase differences of the calibration signal at a frequency ω from the outputs of the radio channels with indices i and j for the first and second stages of calibration;

- приращения параметров неоднозначности измерений разностей полных фаз сигнала калибровки на частоте ω для первого и второго этапов калибровки относительно параметров неоднозначности измерения разностей полных фаз сигнала калибровки на частоте ω₁ равные:

- increments of the ambiguity parameters of the measurement of the differences in the total phases of the calibration signal at a frequency ω for the first and second stages of calibration relative to the ambiguity parameters of the measurement of the differences of the full phases of the calibration signal at a frequency ω ₁ equal to:

- приращение полной разности фаз при изменении частоты от ω₁ до ω, (ω∈[ω_m, ω_m+1]) на первом этапе калибровки;Where:

- increment of the total phase difference when the frequency changes from ω ₁ to ω, (ω∈ [ω _m , ω _{m + 1} ]) at the first calibration stage;

The phase non-identity of the receiving radio channels with indices i and j at a frequency ω in the frequency range [ω _m , ω _{m + 1} ], expressed through the difference in the total phase delays of the radio channels, is equal to:

The total phase delay of the calibration signal transmission line between the radio channels with indices i and j at a frequency ω located in the frequency range [ω _m , ω _{m + 1} ] is equal to:

This implies:

приведенная к интервалу [-π, π], равна:1 - phase non-identity of the receiving radio channels with indices i and j at the frequency ω, (ω∈ [ω _m , ω _{m + 1} ]) denoted as

reduced to the interval [-π, π] is equal to:

and correspondingly:

- параметр устранения неоднозначности фазовой неидентичности радиоканалов с индексами i и j на частоте ω равныйhere

- the parameter for eliminating the ambiguity of the phase non-identity of radio channels with indices i and j at a frequency ω equal to

Where

между приемными каналами с индексами i и j на частоте ω, (ω∈[ω_m, ω_m+1]), приведенная к интервалу [-π, π], равна:2 - phase delay of the calibration signal transmission path

between the receiving channels with indices i and j at the frequency ω, (ω∈ [ω _m , ω _{m + 1} ]), reduced to the interval [-π, π], is equal to:

and correspondingly:

- параметр устранения неоднозначности фазовой неидентичности линии передачи сигнала калибровки от радиоканала с индексом i к радиоканалу с индексом j на частоте ω равный:here

- the parameter to eliminate the ambiguity of the phase non-identity of the transmission line of the calibration signal from the radio channel with index i to the radio channel with index j at a frequency ω equal to:

Where

между приемными каналами по выражению (22) решает поставленную задачу.Calculation in the signal processing and control unit of 9 phase-identity values of the receiving radio channels with indices i and j at the frequency ω, [ω∈ [ω _m , ω _{m + 1} ]) according to expression (21) and the phase delay of the calibration signal transmission path

between the receiving channels by the expression (22) solves the problem.

Information sources

1. Radio engineering systems: Textbook. for universities for special. "Radio Engineering" / Yu.P. Grishin, V.P. Ipatov, Yu.M. Kazarinov et al .; Ed. Yu.M. Kazarinova. - M .: Higher. school, 1990. - 496 p.: ill. (p. 281-283, p. 306-321, p. 377-381).

2. Direction finding interferometer internal calibration system, United States Patent No. 4494118, G01S 5/02, date of patent: jan. 15, 1985.

3. The microwave direction finding device and its variant, patent RU No. 2269791, G01S 3/10, G01S 7/40, bull. No 4 on 02/10/2006.

Claims (4)

1. A microwave direction finder, comprising N receiving radio channels, the inputs of which correspond to the inputs of the direction finder, each receiving radio channel made of a series-connected receiving antenna, a communication unit, a frequency converter and an intermediate frequency amplifier, a frequency-generating device (CCU), the output of which is connected to the input of the first two-channel switch, the first and second inputs - the outputs of which are connected respectively to the first inputs - the outputs of the second and third two-channel switches, are loaded according to the first and second coordinated loads, the second input is the output of the second two-channel switch connected to the first input - the output of the communication node of the first receiving radio channel, the second input is the output of the communication node of each receiving radio channel, except the Nth one, connected to the first input - the output of the communication node of the subsequent the receiving radio channel, and the second input is the output of the communication node of the Ν-th receiving radio channel is connected to the second input - the output of the third two-channel switch, the local oscillator connected to the heterodyne inputs of the converters the signal processing and control unit (BOSU), the inputs of which are connected to the corresponding outputs of the amplifiers of intermediate frequency, the control output to the corresponding control inputs of the first, second and third two-channel switches, and the information output to the output of the direction finder, characterized in that the generating device is functionally configured to generate M calibration signals at frequencies different from each other, chosen so that at adjacent frequencies the increment of the full phase of the control second signal at the outputs of all of the receiving radio is not more values ± π, Bos configured to control algorithms work-frequency generating device, wherein the control output is connected to the bare control input of the CSU. 2. The microwave direction finder according to claim 1, characterized in that the frequency generating device consists of M calibration signal generators and a multi-channel switch, while the signal outputs of all calibration signal generators are connected to the corresponding signal inputs of the multi-channel switch, the control input and output of which are connected respectively, with the entrance and exit of ChSU. 3. The microwave direction finder according to claim 1, characterized in that the frequency generating device consists of M calibration signal generators and a multi-channel adder, while the signal outputs of all calibration signal generators are connected to the corresponding signal inputs of the multi-channel adder, the control input and output of which are connected respectively, with the entrance and exit of ChSU. 4. The microwave direction finder according to claim 1, characterized in that the frequency-generating device is made in the form of a controlled calibration signal generator.

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