RU2201599C1 - Method of direction finding of radio signals and direction finder for its realization - Google Patents

Abstract

FIELD: radio engineering, establishment of location of sources of radio emission. SUBSTANCE: method includes reception of radio signals by N-element array, measurement of complex amplitudes of pairs of signals characterizing phase difference between signals received by all possible pairs of antenna elements by way of time-successive measurement of amplitudes of signals and signal combinations across chosen pairs of antenna elements. Formation of twodimensional angular spectra of taken bearings on basis of measured complex amplitudes of pairs of signals with due account of known relative position of antenna elements which are utilized to find azimuths and angles of elevation of radio signals. Direction finder for realization of method has antenna array, antenna switch, unit forming measurement signals, receiver, unit determining amplitudes of signals, storage of signal amplitudes, computer of complex amplitudes of pairs of signals, bearing computer and generator of synchronization pulses. EFFECT: increased accuracy of direction finding, simplified design of direction finder. 5 cl, 6 dwg

Description

 The invention relates to radio engineering and can be used in radio monitoring systems to determine the location of radio emission sources (IRI).

 A known method of direction finding of radio signals, including receiving radio signals of a five-element equidistant ring antenna array made of identical non-directional antenna elements located in the direction-finding plane, measuring phase differences between pairs of signals simultaneously and simultaneously received by successive pairs of antenna elements, forming direction-finding characteristics of radio signals from the measured phase differences signals on different pairs of elements of the antenna array and the corresponding reciprocal the orientation of pairs of antenna elements in the direction-finding plane, which judge the direction to Iran [British application 2140238, G 01 S 3/48, publ. 1984].

 A direction finder is also known, comprising a multi-element antenna array located in the direction-finding plane, an antenna switch, the inputs of which are connected to the outputs of the corresponding elements of the antenna array, and a pair of outputs is connected to a pair of inputs of a two-channel receiver made with a common local oscillator, a couple of outputs of which are connected to a pair of inputs of the meter phase difference, the output of which is connected to a bearing calculator [German Application 4128191, G 01 S 3/46, publ. 1993].

 The limitations of the indicated method and device are: firstly, a decrease in direction finding accuracy with the instability of synchronous reception of radio signals by pairs of antenna elements; secondly, an increase in the probability of anomalous direction-finding errors associated with measurements of phase differences of radio signals close to ± π radians; thirdly, the dependence of direction finding accuracy on the quality of measuring phase differences between pairs of signals; fourthly, the presence of paired units in a two-channel receiver that perform the same functions (filtering, amplification, signal conversion and others), which complicates its technical implementation, increases its weight and size characteristics and power consumption, reduces reliability, complicates the setup of the direction finder as a whole, which leads to reducing the quality of direction finding and limiting the scope of the direction finder.

 Closest to the technical nature of the proposed method is a method of direction finding radio signals, including receiving radio signals by an antenna array consisting of N antenna elements made identical in an amount of at least three and located in the direction-finding plane, measuring in each frequency subband the complex amplitudes of the pairs of signals characterizing the phases each radio signal received in the corresponding frequency subband by one of the antenna elements of the pair selected as a signal, relate the phase of the radio signal received in the same frequency subband by another of the antenna elements of the pair selected as a reference for all used pairs of antenna elements, the formation of two-dimensional angular spectra of each received in the corresponding frequency subband radio signal from the measured complex amplitudes of the signal pairs for different pairs of antenna elements of the antenna array according to the relative position of these antenna elements in the direction-finding plane, which are used to judge the azimuths and elevation angles radio [Russian Federation No. 21442200, G 01 S 3/14, publ. 2000].

сигналов, синхронно принятых соответственно сигнальным и опорным антенными элементами, вычисляют для каждой выбранной пары антенных элементов и каждого частотного поддиапазона комплексную амплитуду пары сигналов

в соответствии с выражением:

где * - знак комплексного сопряжения. Далее формируют, по измеренным комплексным амплитудам пар сигналов для различных пар антенных элементов антенной решетки, соответственно взаимному расположению этих антенных элементов в плоскости пеленгования, двумерные угловые спектры для каждого принятого в соответствующем частотном поддиапазоне радиосигнала и по значению аргументов максимального модуля двумерного углового спектра судят об азимутах и углах места радиосигналов.In the known method, the complex signal spectra are measured for the reference and signal channels, obtaining complex signal amplitudes for each channel and frequency subband, which after multiplication are represented by complex amplitudes of signal pairs synchronously received by selected pairs of antenna array elements for each frequency subband. Thus, in general terms in the known method after measuring pairs of complex amplitudes

signals synchronously received respectively by the signal and reference antenna elements, for each selected pair of antenna elements and each frequency subband, the complex amplitude of the signal pair is calculated

in accordance with the expression:

where * is the sign of complex conjugation. Next, form, according to the measured complex amplitudes of the signal pairs for different pairs of antenna elements of the antenna array, respectively, the relative position of these antenna elements in the direction-finding plane, two-dimensional angular spectra for each received in the corresponding frequency sub-band of the radio signal and the azimuths are judged by the value of the arguments of the maximum module of the two-dimensional angular spectrum and elevation angles of radio signals.

 The signal conversion in this technical solution is performed by a multi-channel receiver sequentially in time from a pair of antenna elements, while a signal from one element not included in this pair is used as a reference signal, and signals from the following pairs of elements are successively converted in time, while as The reference signal uses a signal from one element that is not included in the next pair, and signals from all possible pairs of antenna elements are converted in this way. In other similar technical solutions, it is possible to convert signals and compare complex spectral characteristics using only one reference element (see, for example, patent of the Russian Federation 2096797, G 01 S 3/14, publ. 1997).

 A direction finder is also known, which contains an antenna array made of N antenna elements in an amount of at least three, made identical and located in the direction-finding plane, an antenna switch made with N inputs and with two outputs - a reference and a signal with the possibility of serial connection in time in a single the time interval of any pair of inputs, respectively, to the reference and signal outputs, and the outputs of the antenna elements are connected to the corresponding inputs of the antenna switch, receiver, block amplification of the signal amplitudes, a bearing calculator, connected in series, and a clock generator, the output of which is connected to the control inputs of the antenna switch and the signal amplitude determining unit, and which is configured to issue commands to the control input of the antenna switch for a serial connection in a single time interval any pair of inputs, respectively, to the reference and signal outputs [Patent of the Russian Federation 21442200, G 01 S 3/14, publ. 2000].

 In this technical solution, the receiver, as well as the unit for determining the amplitudes of the signals, the function of which is performed by the Fourier transform unit and the storage device of the spectrum components, are made two-channel.

 The limitations of the indicated method and device are: firstly, a decrease in direction finding accuracy with the instability of synchronous reception of radio signals by pairs of antenna elements; secondly, the presence in the two-channel receiver of blocks that perform the same functions (filtering, amplification, signal conversion and others), which complicates its technical implementation, increases its weight and size characteristics and power consumption, reduces reliability, complicates the setup of the direction finder as a whole, which leads to a decrease direction finding quality and limiting the scope of the direction finder.

 The problem solved by the invention is improving the quality of direction finding and expanding the arsenal of means intended for direction finding of radio emission sources.

 The technical result that can be obtained by implementing the method is to increase the accuracy of direction finding by eliminating the dependence of the bearing on the instability of the synchronous reception of radio signals.

 The technical result that can be obtained when performing the device is to increase the reliability of direction finding, simplifying the design, reducing weight and size characteristics and energy consumption.

пар сигналов в соответствии с выражением

Возможны дополнительные варианты осуществления способа, в которых целесообразно, чтобы:
- антенный элемент пары, выбранный в качестве опорного, был выбран также опорным для различных пар антенных элементов антенной решетки;
- в качестве элементов антенной решетки использовали ненаправленные антенны, а в качестве антенной решетки использовали J-кольцевую многоэлементную эквидистантную антенную решетку, выполненную с количеством колец не менее одного.The problem is solved in that in the method of direction finding of radio signals, including the reception of radio signals by an antenna array consisting of N antenna elements made identical in an amount of at least three and located in the direction finding plane, measuring in each frequency subband the complex amplitudes of the signal pairs for a pair of antenna elements, characterizing the phases of each radio signal received in the corresponding frequency subband by one of the antenna elements of the pair selected as a signal relative to of a radio signal received in the same frequency subband by another of the antenna elements of the pair selected as a reference, the formation of two-dimensional angular spectra of each received in the corresponding frequency subband radio signal from the measured complex amplitudes of the signal pairs for different pairs of antenna elements of the antenna array according to the relative position of these antenna elements in the direction-finding plane, by which the azimuths and elevation angles of the received radio signals are judged, according to the invention, the measurement in each the home frequency subband of the complex amplitudes of the pairs of signals for a pair of antenna elements is produced by measuring the amplitude B _{1 of the} signal for one of the antenna elements of the pair selected as a signal, measuring the amplitude of B ₂ signal for another of the antenna elements of the pair selected as a reference, calculating the amplitude B ₃ signals, which is the sum of the signals for both antenna elements of the pair, calculating the amplitude of ₄ signals, which is the sum of the signals for both antenna elements of the pair with a delayed phase of the signal for the other about from the antenna elements of the pair selected as the reference, 90 ^o , and calculations for various pairs of antenna elements of the antenna array of complex amplitudes

pairs of signals in accordance with the expression

There are additional options for implementing the method, in which it is advisable that:
- the antenna element of the pair, selected as the reference, was also selected as the reference for various pairs of antenna elements of the antenna array;
- omnidirectional antennas were used as elements of the antenna array, and a J-ring multi-element equidistant antenna array made with at least one ring number was used as the antenna array.

для каждой пары сигналов в соответствии с выражением:

где B₁, В₂, В₃ и B₄ - значения амплитуд сигналов, поступающих на его первый, второй, третий и четвертый входы соответственно.The problem is also solved by the fact that in the direction finder containing the antenna array made of N antenna elements in an amount of at least three, made identical and located in the direction finding plane, the antenna switch is made with N inputs and with two outputs - a reference and a signal with consecutive in time connection in a single time interval of any pair of inputs to the reference and signal outputs, respectively, and the outputs of the antenna elements are connected to the corresponding inputs of the antenna a switch, a receiver, a signal amplitude determining unit, a bearing calculator, connected in series, and a clock generator, the output of which is connected to the control inputs of the antenna switch and the signal amplitude determining unit, and which is configured to issue commands to the control input of the antenna switch for a serial connection in time in a single time interval of any pair of inputs, respectively, to the reference and signal outputs, according to the invention, the receiver and the unit for determining the amplitude Itud signals were made single-channel, a unit for generating measuring signals was introduced, the reference, signal and control inputs of which are connected respectively to the reference and signal outputs of the antenna switch, the output of the clock generator, and the output to the input of the receiver, a signal amplitude storage device, the input of which is connected to the output of the block determining the amplitudes of the signals, a complex amplitude computer calculator of signal pairs, four inputs and a pair of outputs of which are connected respectively to the four outputs the signal amplitude measuring device and the pair of inputs of the bearing calculator, while the signal amplitude determination unit is provided with a control output connected to the control inputs of the signal amplitudes storage device, the complex amplitudes of the signal pairs calculator, the bearing calculator, the measuring signal generation unit is arranged to be sequential in the first, second , the third and fourth intervals of the aforementioned single period of time of formation at its output, respectively, of the first signal from its supports input signal, the second signal from its signal input, the third signal equal to the sum of the signals from the reference input and the signal input, and the fourth signal equal to the sum of the signal from the signal input and the signal from the reference input, the phase of which is delayed by 90 ^o , the clock generator is made with the ability to issue commands to the control input of the measuring signal generation unit for generating the indicated first, second, third and fourth signals at the indicated intervals of a single time interval and generating at the first, second, the third and fourth outputs of the storage device of the amplitude values of B ₁ , B ₂ , B ₃ and B _{4 of} these signals, and the calculator of the complex amplitudes of the signal pairs is configured to calculate the complex amplitudes of the signal pairs

for each pair of signals in accordance with the expression:

where B ₁ , B ₂ , B ₃ and B ₄ are the amplitudes of the signals arriving at its first, second, third and fourth inputs, respectively.

 An additional embodiment of the device is possible, in which it is advisable that the measuring signal generation block be made of five switches, of the first, second and third switches, each of which is configured to connect its input to one of a pair of its outputs, from the fourth switch made with the ability to connect its output to one of a pair of its inputs, from the fifth switch, configured to connect its output to one of its three inputs, from the phase shifter and from the adder, moreover, the first and second outputs of the first switch are connected respectively to the first input of the fourth switch and the input of the phase shifter, the output of which is connected to the second input of the fourth switch, the output of which is connected to the input of the second switch, the first and second outputs of which are connected respectively to the first input of the fifth switch and the first input the adder, the first and second outputs of the third switch are connected respectively to the second input of the fifth switch and the second input of the adder, the output of which dsoedinen to the third input of the fifth switch, the control inputs of all five switches are connected to the control input generation unit measuring signal input of the first input and the third switch are respectively the reference and signal input unit for generating measurement signals, and the output of the fifth switch - the output unit for generating measurement signals.

 The solution of the problem with the achievement of the technical result is due to the fact that the phase distribution of the radio signals received by the elements of the antenna array, necessary for the formation of two-dimensional angular spectra, is determined by measuring the amplitudes of the signals received by the antenna elements and measuring the amplitudes of these combinations of signals. To carry out the proposed actions on signals, synchronous conversions of signal pairs are not required followed by direct measurement of phase differences, and accordingly there is no need to use a sufficiently complex, at least two-channel receiver with combined local oscillator for receiving and converting signals.

These advantages, as well as features of the present invention are illustrated by the best option for its implementation with reference to the accompanying drawings
figure 1 depicts a functional diagram of the direction finder;
FIG. 2 - arrangement of elements of the antenna array in the direction-finding plane;
FIG. 3 is a vector diagram of signals received by a selected pair of antenna array elements;
FIG. 4 is a functional diagram of an embodiment of a unit for determining signal amplitudes;
5 is a block diagram of a program of an automaton that implements a signal detector in a signal amplitude determining unit;
6 is a functional diagram of an embodiment of a calculator of complex amplitudes of signal pairs.

 Since the claimed method of direction finding of radio signals is implemented in the operation of the device, its detailed description is given in the direction finder operation section.

The direction finder (Fig. 1) contains an antenna array (AR) 1 made of N antenna elements in an amount of at least three located in the direction finding plane (azimuthal plane). Antenna switch (AK) 2 made with N inputs and two outputs, one of which is selected as the reference, and the second after the signal. The outputs of the antenna elements (AE) of the antenna array 1 are connected to the corresponding inputs of AK 2. The unit for generating measurement signals (BFIS) 3, the receiver 4, the unit for determining signal amplitudes (BOAS) 5, a memory device for amplitudes of signals (ZUAS) 6, a calculator of complex amplitudes of pairs signals (VKAPS) 7, the bearing calculator (VP) 8, are connected in series. The reference and signal outputs of AK 2 are connected respectively to the reference and signal inputs of the BFIS 3, the four outputs of the ZUAS 6 are connected respectively to the four inputs of VKAPS 7. The pair of outputs of VKAPS 7 is connected respectively to the pair of inputs of VP 8. Two outputs of VP 8 serve as the output of azimuth θ and angle places β direction finder. The direction finder also contains a clock generator (HS) 9, the output of which is connected to the control inputs of AK 2, BFIS 3, BOAS 5. BFIS 3 can be performed using various functional circuits. The main functional requirement for BFIS 3 is to ensure the sequential formation of measuring signals at its output — accordingly, the first signal from its reference input, the second signal from its signal input, the third signal equal to the sum of the signals from the reference input and signal input, and the fourth signal equal to the sum signal from the signal input and the signal from the reference input, the phase of which is delayed by 90 ^o .

 To simplify the direction finder, it is advisable to perform BFIS 3 on the basis of switches, a phase shifter and an adder.

 In this additional embodiment, BFIS 3 (figure 1) contains the first, second and third switches 10, 11 and 12, respectively, the fourth switch 13, the fifth switch 14, the phase shifter 15 and the adder 16. The first and second outputs of the first switch 10 are connected respectively to the first input of the fourth switch 13 and the input of the phase shifter 15, the output of which is connected to the second input of the fourth switch 13. The output of the fourth switch 13 is connected to the input of the second switch 11. The first and second outputs of the second switch 11 are connected to the first inputs respectively, the fifth switch 14 and the adder 16. In addition, the first and second outputs of the third switch 12 are connected to the second inputs of the fifth switch 14 and the adder 16. The output of the adder 16 is connected to the third input of the fifth switch 14. In addition, the control inputs of the switches 10, 11 , 12, 13 and 14 are connected to the control input of the BFIS 3. The inputs of the first and third switches 10 and 12 are respectively the reference and signal inputs of the BFIS 3, and the output of the fifth switch 14 is the output of the BFIS 3.

 Antenna array 1 is made of N AE with identical characteristics (amplitude and phase radiation patterns) placed, in order to simplify the design, in the direction-finding plane (azimuthal plane). To further simplify the design, it is advisable to use identical non-directional antennas, for example, symmetric or asymmetric vibrator antennas, as antenna elements of AP 1. In order to improve the direction finding accuracy, it is advisable to use single or multi-ring equidistant antenna arrays as the AR 1.

 Antenna switch 2 is made with the ability to connect to the appropriate commands from the GS 9 in uniform time intervals of any of its pairs of inputs, respectively, to its reference and signal outputs.

The unit for generating measuring signals 3 is configured to, according to commands from GS 9, sequentially in four intervals of a single time interval transmitting, respectively, the first and second signals from its reference and signal inputs, the third signal, which is the sum of the signals from the reference and signal inputs, and the fourth signal, which is the sum signal from the signal input and the signal from the reference input, the phase of which is delayed by 90 ^o .

 The receiver 4 is made single-channel with the ability to filter, amplify and convert radio signals to a low frequency (to simplify subsequent processing).

 BOAS 5 is made single-channel with the possibility of measuring signal amplitudes in each subband of the operating frequency range, and, in addition, with the possibility of issuing control commands to the signal amplitude storage device 6, a complex amplitude computer calculator of signal pairs 7 and a bearing computer 8.

 ZUAS 6 is made with the possibility of storing for each frequency subband and each pair of AE four amplitudes of the signals transmitted through BFIS 3 in the corresponding intervals of the time interval from the corresponding pairs of AE AR 1.

и мнимых

компонент комплексных амплитуд пар сигналов в соответствии с вышеупомянутым выражением.VKAPS 7 is configured to calculate four indicated signal amplitudes for each AE pair and each real frequency sub-band

and imaginary

component of the complex amplitudes of the signal pairs in accordance with the above expression.

 Bearing calculator 8 is capable of generating, according to the measured complex amplitudes, signal pairs for different pairs of AEs of antenna array 1 and, respectively, relative positions of AEs in the direction-finding plane of the two-dimensional (in the azimuthal and elevation planes) angular spectra of each radio signal received in the corresponding frequency subband, which comprise information about azimuths θ and elevation angles β of radio signals.

 The clock generator 9 is configured to issue commands to the control input of AK 2 for sequentially connecting in time at regular intervals the corresponding pairs of AE AR 1 to the reference and signal outputs of AK 2, with the possibility of issuing commands to the control input of BFIS 3 for sequential in each time interval forming in the corresponding four time intervals of the aforementioned measuring signals. In addition, the GS 9 is configured to issue commands to the control inputs of the BOAS 5 to synchronize its operation.

 The direction finder (figure 1) works as follows.

где Z_n= hEcosβ - амплитуда радиосигнала, принимаемого в соответствующем частотном поддиапазоне;
F_n(t) = Ф_n+ωt+φ(t)+φ₀ - текущая фаза радиосигнала, принимаемого в соответствующем частотном поддиапазоне;
n = 1, 2,..., N - номер антенного элемента N - элементной решетки;
ω - круговая частота радиосигнала;
t - время;
φ(t) - закон изменения фазы радиосигнала, обусловленный его угловой модуляцией;
φ₀ - начальная фаза радиосигнала в центре О антенной решетки 1 (фиг.2),
h - действующая высота идентичных АЭ решетки;
Е - напряженность электромагнитного поля радиосигнала;
Ф_n = (2π/λ)r_ncosβcos(θ-α_n) - фаза n-го АЭ решетки, зависящая от его пространственного положения относительно центра O антенной решетки;
λ - длина волны радиосигнала;
r_n - расстояние от центра О антенной решетки до точки размещения n-го АЭ;
α_n - угол ориентации пространственного положения n-ого АЭ относительно выбранного опорного направления ОС, проходящего через центр О антенной решетки;
β - угол места (угол наклона фронта волны) радиосигнала, то есть угол между направлением вектора

распространения ЭМВ и проекцией направления

на азимутальную плоскость (плоскость пеленгования);
θ - азимут радиосигнала, то есть угол между проекцией направления вектора

распространения ЭМВ радиосигнала на плоскость пеленгования и опорным направлением ОС.Electromagnetic waves (EMW) of each radio signal emitted by the corresponding source of radio emission (IRI) in the corresponding frequency subband are received by each identical AE of the antenna array 1 A ₁ , A ₂ , ... A _n , ... A _N (Fig. 2), for simplicity, shown in the form of a ring multielement equidistant antenna array, and at the output of the nth AE, signals are generated that can be represented as:

where Z _n = hEcosβ is the amplitude of the radio signal received in the corresponding frequency subband;
F _n (t) = Ф _n + ωt + φ (t) + φ ₀ - the current phase of the radio signal received in the corresponding frequency subband;
n = 1, 2, ..., N is the number of the antenna element of N - element array;
ω is the circular frequency of the radio signal;
t is the time;
φ (t) is the law of phase change of the radio signal due to its angular modulation;
φ ₀ - the initial phase of the radio signal in the center O of the antenna array 1 (figure 2),
h is the effective height of identical AE lattices;
E is the electromagnetic field strength of the radio signal;
Ф _n = (2π / λ) r _n cosβcos (θ-α _n ) is the phase of the n-th AE array, depending on its spatial position relative to the center O of the antenna array;
λ is the wavelength of the radio signal;
r _n is the distance from the center O of the antenna array to the location point of the n-th AE;
α _n - the orientation angle of the spatial position of the n-th AE relative to the selected reference direction of the OS passing through the center O of the antenna array;
β is the elevation angle (angle of inclination of the wave front) of the radio signal, that is, the angle between the direction of the vector

EMV propagation and projection directions

on the azimuthal plane (direction-finding plane);
θ is the azimuth of the radio signal, that is, the angle between the projection of the direction of the vector

the propagation of electromagnetic waves of the radio signal on the direction-finding plane and the reference direction of the OS.

где n₀ = 1, 2,..., N - порядковый номер опорного АЭ в выбранной паре;
n_с = 1, 2,..., N - порядковый номер сигнального АЭ в выбранной паре;
n₀≠n_c.In this case, the phases of the selected pair of AEs Ф _no and Ф _nc , depending on the spatial position relative to the center О of the antenna array 1 n _0th AE, taken as the reference, and n _c- th AE, taken as a signal (see figure 2), are described by the expressions:

where n ₀ = 1, 2, ..., N is the serial number of the reference AE in the selected pair;
n _with = 1, 2, ..., N is the serial number of the signal AE in the selected pair;
n ₀ ≠ n _c .

и

, так и фаз

и

сигналов принятых n₀-м опорным и n_с-м сигнальным АЭ. При этом результирующие амплитуды

и

n₀-го и n_с-го АЭ и разность фаз

между n_с-м и n₀-м АЭ для пары АЭ можно представить в виде:

где

- изменения амплитуд сигналов для опорного и сигнального АЭ за счет переизлучения в решетке;

- погрешность разности фаз между сигналами, принятыми сигнальными и опорным АЭ, обусловленная переизлучением в антенной решетке.It should be noted that reemission of electromagnetic waves by antenna elements of the array leads to distortion of both amplitudes

and

and phases

and

signals received by the n _0th reference and n _{with the} th signal AE. In this case, the resulting amplitudes

and

n ₀ th and n _s th AE and phase difference

between n _with -th and n ₀ -th AE for a pair of AE can be represented as:

Where

- changes in the amplitudes of the signals for the reference and signal AE due to re-radiation in the grating;

- the error of the phase difference between the signals received by the signal and reference AE, due to re-radiation in the antenna array.

, которые при формировании общей пеленгационной характеристики пеленгатора на основе усреднения результатов измерений разностей фаз по всем возможным пеленгационным парам АЭ взаимно компенсируются.The errors of the phase difference between the pairs of signals received by the AE of the array depend on the efficiency of reemission of electromagnetic waves by antenna elements. The use of non-directional antennas as AE reduces these errors. In addition, the use of a multi-element equidistant single or multi-ring array as an antenna array 1 leads to a harmonic (alternating) nature of the errors

which during the formation of the overall direction-finding characteristic of the direction finder based on averaging the results of measurements of phase differences over all possible direction finding pairs of AEs are mutually compensated.

Radio signals received N antenna elements of the antenna array 1 described above expression, with their outputs fed to the respective inputs AK N 2. On command, outputted from the farm to the control input 9 AK 2, signals from a selected pair _{of the} n th and n _with -th AE during a period of time Δt are supplied respectively to the reference and signal outputs of AK 2 and further, respectively, to the reference and signal inputs of the BFIS 3, that is, to the inputs of the first and third switches 10 and 12, respectively (Fig. 1).

Сигналы, соответствующие измеренным в первый интервал Δt₁ промежутка Δt времени амплитудам B₁ каждого радиосигнала в соответствующем частотном поддиапазоне, с выхода БОАС 5 поступают на вход ЗУАС 6, где по команде, поступающей с управляющего выхода БОАС 5 на управляющий вход ЗУАС 6, производится их запоминание.According to the command coming from the output of the GS 9 to the control inputs of the BFIS 3 (to the control inputs of the first, second, fourth and fifth switches 10, 12, 13 and 14), BOAS 5 in the first interval Δt _{1 of the} time interval Δt taken by the n _- th AE in the working frequency range, the signals from the first output of the first switch 10 go to the first input of the fourth switch 13, and from its output to the input of the second switch 11, and then, from the first output of the second switch 11 to the first input of the fifth switch 14, and from it output to the input of the receiver 4. The signals received at the input of the receiver 4, subjected therein filtration and amplification in the receiver frequency subband with a gain K _p, the transfer to the intermediate frequency and the receiver 4 outputs to the input Boas 5. Boas 5 for each frequency subband corresponding to each _{of the} n-th received antenna array AE 1 the radio signal from the corresponding IRI, the amplitude of B ₁ signal is determined, which is described by the expression:

The signals corresponding to the amplitudes B ₁ measured in the first interval Δt _{1 of the} time interval Δt _of each radio signal in the corresponding frequency subband, from the output of the BOAS 5 are fed to the input of the ZUAS 6, where, by the command from the control output of the BOAS 5 to the control input of the ZUAS 6 memorization.

Сигналы, соответствующие измеренным во второй интервал Δt₂ промежутка Δt времени амплитудам В₂ каждого радиосигнала в соответствующем частотном поддиапазоне, с выхода БОС 5 поступают на вход ЗУАС 6, где по команде, поступающей с управляющего выхода БОАС 5 на управляющий вход ЗУАС 6, производится их запоминание.Further, according to the command received from the output of the GS 9 to the control inputs of the BFIS 3 (to the control inputs of the third and fifth switches 12 and 14) and BOAS 5 in the second interval Δt _{2 of the} time interval Δt, taken n _{with the} AE AR 1 in the operating range frequency signals from the first output of the third switch 12 are fed to the second input of the fifth switch 14, and from its output to the input of the receiver 4, where they are converted as described above and fed to the input of the BOAS 5. In BOAS 5 for each frequency subband corresponding to each received n _with AE antenna array 1 radio sig Nalu from the corresponding IRI, the amplitude of the ₂ signal is determined, which is described by the expression:

The signals corresponding to the amplitudes B ₂ measured in the second interval Δt _{2 of the} time interval Δt _of each radio signal in the corresponding frequency subband, from the output of the BOS 5 are fed to the input of the ZUAS 6, where, according to the command received from the control output of the BAS 5 to the control input of the ZUAS 6 memorization.

Сигналы, соответствующие измеренным в третий интервал Δt₃ промежутка Δt времени амплитудам В₃ каждого суммарного радиосигнала в соответствующем частотном поддиапазоне, с выхода БОАС 5 поступают на вход ЗУАС 6, где по команде, поступившей с управляющего выхода БОАС 5 на управляющий вход ЗУАС 6, производится их запоминание.Further, according to the command received from the output of the GS 9 to the control inputs of the BFIS 3 and BOAS 5 in the third interval Δt _{3 of the} time interval Δt, the received n _о- th AE in the frequency range, the signals from the first output of the first switch 10 are sent to the first input of the fourth switch 13 and from its output to the input of the second switch 11, and further, from the second output of the second switch 11 to the first input of the adder 16. In addition, simultaneously received n _{with the} th AE in the frequency range, the signals from the second output of the third switch 12 are fed to the second input of the adder 16, where they are summed with corresponding signals received n _about th AE. The summed signals from the output of the adder 16 go to the third input of the fifth switch 14, and from its output to the input of the receiver 4, where they are converted as described above and fed to the input of the BOAS 5. In the BOAS 5 for each frequency subband corresponding to each received n _oh and n _{with the} th AE radio signal from the corresponding IRI, the amplitude B _{3 of the} total signal from the specified AE pair is determined, which, taking into account the vector diagram presented in Fig. 3, and the well-known cosine theorem [see , eg. Korn G., Korn T. Handbook of mathematics (for scientists and engineers). -M .: Science, 1978 - 832 S.] is described by the expression:

The signals corresponding to the amplitudes B ₃ measured in the third interval Δt _{3 of the} Δt time interval in each of the total radio signals in the corresponding frequency subband, from the output of the BOAC 5 are fed to the input of the ZUAS 6, where, according to the command received from the control output of the BOAS 5 to the control input of the ZUAS 6, their memorization.

Сигналы, соответствующие измеренным в четвертый интервал Δt_4/ промежутка Δt времени амплитудам В₄ каждого суммарного радиосигнала в соответствующем частотном поддиапазоне, поступают на вход ЗУАС 6, где по команде, поступившей с управляющего выхода БОАС 5 на управляющий вход ЗУАС 6, также производится их запоминание.And finally, according to the command received from the output of the GS 9 to the control inputs of the BFIS 3 and BOAS 5 in the fourth interval Δt _{4 of the} time interval Δt, the received n _о- th AE in the operating frequency range, the signals from the second output of the first switch 10 are fed to the input of the phase shifter 15 where the phase delay of the radio signals by 90 ^o . From the output of the phase shifter 15, the signals are fed to the second input of the fourth switch 13, and from its output to the input of the second switch 11, and then, from the second output of the second switch 11 to the first input of the adder 16. In addition, simultaneously received n _{with the} AE in the frequency range signals from the second output of the third switch 12 receives on a second input of adder 16 where the summed with the corresponding signals received _{on the} n th AE whose phases are delayed by 90 ^o. The summed signals from the output of the adder 16 go to the third input of the fifth switch 14, and from its output to the input of the receiver 4, where they are converted as described above and fed to the input of the BOAS 5. In the BOAS 5 for each frequency subband corresponding to each received n _oh and n _s- th AE to the radio signal from the corresponding IRI, the amplitude B _{4 of the} signal is determined, which is the sum of the signal received by the n _- th AE, the phase of which is delayed by 90 ^o and the signal received by the n _- th AE of the selected pair of AE, which adjusted vector diagram, pre positioned in FIG. 3, the well-known theorem of cosines and simple trigonometric transformations is described by the expression:

The signals corresponding to the amplitudes B ₄ measured in the fourth interval Δt _{4 /} time interval Δt of time for each total radio signal in the corresponding frequency subband are fed to the input of the ZUAS 6, where, by the command from the control output of the BOAS 5 to the control input of the ZUAS 6, they are also stored .

могут быть определены из любого вышеуказанного выражения, описывающего В₃ или В₄. При этом наиболее целесообразно для определения двузначной разности фаз

использовать выражение, описывающее В₃. Так как в это выражение для В₃, в отличие от выражения, описывающего В₄, не входит параметр, зависящий от дополнительного функционального преобразования радиосигналов - задержки фазы на 90^o. Следовательно, погрешность задержки фазы, которая может возникать при технической реализации фазовращателя 15, в случае использования выражения для В₃ не влияет на точность оценки

. Поэтому, двузначные значения разности фаз

в области от 0 до ±π радиан, целесообразно определять из выражения:

При этом математическое выражение, описывающее В₄, целесообразно использовать для устранения неоднозначности определения

. Из вышеупомянутого выражения для B₄ следует:

и далее

Отсюда получаем правило выбора знака разности фаз

:

где

В связи с этим сигналы, соответствующие измеренным амплитудам B₁, В₂, В₃ и В₄, с выходов ЗУАС 6 поступают на соответствующие входы ВКАПС 7, где для каждой пары антенных элементов и каждого частотного поддиапазона по командам, поступающим с управляющего выхода БОАС 5 на управляющий вход ВКАПС 7, производится вычисление комплексных амплитуд пар сигналов

, аналогичных комплексным амплитудам пар сигналов наиболее близкого аналога, но в соответствии с другим выражением:

,
в котором распределение фаз радиосигналов, принимаемых АЭ антенной решетки 1, необходимое для формирования двумерных угловых спектров, определяется путем измерения амплитуд сигналов, принятых АЭ, и измерения амплитуд указанных комбинаций сигналов.Two-digit phase difference values

may be determined from any of the above expressions describing B ₃ or B ₄ . In this case, it is most appropriate to determine the two-digit phase difference

use an expression that describes B ₃ . Since this expression for B ₃ , unlike the expression describing B ₄ , does not include a parameter depending on the additional functional conversion of radio signals - phase delay of 90 ^o . Therefore, the error of the phase delay, which may occur during the technical implementation of the phase shifter 15, in the case of using the expression for B ₃ does not affect the accuracy of the estimate

. Therefore, two-digit phase difference values

in the range from 0 to ± π radians, it is advisable to determine from the expression:

In this case, the mathematical expression describing In ₄ , it is advisable to use to eliminate the ambiguity of the definition

. From the above expression for B ₄ it follows:

and further

From here we get the rule of choosing the sign of the phase difference

:

Where

In this regard, the signals corresponding to the measured amplitudes B ₁ , B ₂ , B ₃ and B ₄ from the outputs of the ZUAS 6 are supplied to the corresponding inputs of the VCAPS 7, where for each pair of antenna elements and each frequency subband according to the commands received from the BOAS control output 5 to the control input of VKAPS 7, the complex amplitudes of the signal pairs are calculated

similar to the complex amplitudes of the pairs of signals of the closest analogue, but in accordance with another expression:

,
in which the phase distribution of the radio signals received by the AE of the antenna array 1, necessary for the formation of two-dimensional angular spectra, is determined by measuring the amplitudes of the signals received by the AE and measuring the amplitudes of these signal combinations.

 As follows from this expression, synchronized transformations of signal pairs with subsequent direct measurement of phase differences are no longer required to carry out the declared actions on the signals, and accordingly, there is no need to use a sufficiently complex, at least, two-channel receiver with combined channel oscillator for receiving and converting signals.

в виде действительной

и мнимой

компонент с пары выходов ВКАПС 7 поступают соответственно на пару входов ВП 8, на управляющий вход которого поступают соответствующие команды с управляющего выхода БОАС 5.Similarly, according to the commands received from the output of the HS 9, signals from other possible pairs of AEs of the antenna array 1 are processed sequentially in time for other time intervals Δt. The complex amplitudes of signal pairs calculated in VKAPS 7 for various pairs of antenna elements and for each k-frequency subbands

as valid

and imaginary

the component from the pair of outputs of VCAPS 7 are respectively supplied to the pair of inputs of VP 8, to the control input of which the corresponding commands from the control output of BOAS 5 are received.

пар сигналов для различных пар элементов антенной решетки 1 двумерных угловых спектров, по которым судят об азимутах θ и углах места β радиосигналов, можно осуществлять различными методами. Для заявляемого способа уже не является принципиальным, какой из алгоритмов оценки комплексных амплитуд пар сигналов был использован.Formation in VP 8 according to the measured complex amplitudes

pairs of signals for different pairs of elements of the antenna array 1 of two-dimensional angular spectra, which are used to judge the azimuths θ and elevation angles β of the radio signals, can be carried out by various methods. For the proposed method, it is no longer critical which of the algorithms for evaluating the complex amplitudes of signal pairs was used.

где р = 1, 2,..., Р - порядковый номер группы комплексных амплитуд пар сигналов, содержащий N_p комплексных амплитуд пар сигналов, принятых n_о-м и n_с-м АЭ решетки, имеющих одинаковую базу

- радиус кольца, антенной решетки, на котором расположен сигнальный АЭ пары;

- радиус кольца, антенной решетки, на котором расположен опорный АЭ пары;

- угловые ориентации соответственно сигнального и опорного элементов пары относительно опорного направления антенной решетки.The best option for performing calculations in VP 8 is described in the closest analogue. For this option, firstly, according to the signals coming from VKAPS 7 to the pair of inputs of VP 8, P groups of complex amplitudes of pairs of signals obtained using pairs of AEs having the same base b _p that is, with the same distance between n _о- th and n _with AE:

where p = 1, 2, ..., R - number of groups of pairs of amplitude signals comprising N _p complex amplitudes of pairs of signals received _{on the} n th and n -th _with AE lattice having the same base

- radius of the ring, antenna array, on which the signal AE of the pair is located;

- radius of the ring, antenna array, on which the reference AE of the pair is located;

- angular orientations, respectively, of the signal and reference elements of the pair relative to the reference direction of the antenna array.

каждого k-го радиосигнала, соответствующего k-му частотному поддиапазону, в соответствии с выражением:

где k = 1, 2,..., К - порядковый номер частотного поддиапазона;
lp=1, 2,...,N_p - порядковый номер пары n_о-го и n_с-го АЭ, удовлетворяющих указанному выше условию;
L_θdθ - аргумент азимута углового спектра,

dθ - шаг вычисления азимута углового спектра,

L_βdβ - аргумент угла места углового спектра,

dβ - шаг вычисления угла места углового спектра,

- расчетное значение сдвига фаз между сигналами, принимаемыми n_о-й и n_с-й АЭ для k-го частотного поддиапазона, определяемое выражением:

В-третьих, формируют результирующий двумерный угловой спектр

каждого k-го радиосигнала путем перемножения всех его Р спектров в соответствии с выражением:

В-четвертых, производят вычисление наибольшего значения Q_k модуля действительной части результирующего двумерного углового спектра q_k для каждого k-го радиосигнала по всем аргументам L_θdθ и L_βdβ:

по всем значениям

И наконец, производят определение значений азимутов θ и углов места β радиосигналов, равных аргументам соответственно L_θdθ и L_βdβ, при которых модули соответствующих действительных частей результирующих двумерных угловых спектров радиосигналов принимают максимальные значения.Secondly, for each group of complex amplitudes of signal pairs, P two-dimensional angular spectra are calculated

each k-th radio signal corresponding to the k-th frequency subband, in accordance with the expression:

where k = 1, 2, ..., K is the serial number of the frequency subband;
lp = 1, 2, ..., N _p is the sequence number of the pair n _о th and n _s th AE satisfying the above condition;
L _θ dθ is the argument of the azimuth of the angular spectrum,

dθ is the step of calculating the azimuth of the angular spectrum,

L _β dβ is the argument of the elevation angle of the angular spectrum,

dβ is the step of calculating the elevation angle of the angular spectrum,

- the calculated value of the phase shift between the signals received n _about and n _{with the} AE for the k-th frequency subband, defined by the expression:

Thirdly, the resulting two-dimensional angular spectrum is formed

each k-th radio signal by multiplying all its P spectra in accordance with the expression:

Fourthly, the largest modulus Q _{k of} the real part of the resulting two-dimensional angular spectrum q _{k is} calculated for each k-th radio signal for all arguments L _θ dθ and L _β dβ:

in all respects

Finally, the azimuths θ and elevation angles β of the radio signals are determined equal to the arguments L _θ dθ and L _β dβ, respectively, at which the modules of the corresponding real parts of the resulting two-dimensional angular spectra of the radio signals take maximum values.

 The implementation of VP 8 in this way allows you to compensate for errors in the measurement of phase differences between pairs of AE, due to the mutual influence of AE, by summing them over the corresponding groups of complex amplitudes of signal pairs. The multiplication of the angular spectra corresponding to the groups of complex amplitudes of the signal pairs leads to a narrowing of the main lobe and a decrease in the level of the side lobes of the resulting angular spectrum, which leads to an increase in direction finding accuracy and the possibility of an increase in the interelement distances of the side lobes in the antenna array 1, which simplifies the implementation of the antenna grating 1 if necessary, operating in a wide range of frequencies.

 The device that implements the proposed method uses well-known typical direction finder blocks, various embodiments of which are described in a number of scientific and technical information sources. It will be appreciated by those skilled in the art that specific functional circuits of individual blocks may differ in functional circuits for their implementation, structural and elemental base, and connections between functional elements, however, the generalized functional diagram (Fig. 1), which describes the claimed device as an independent claim, is preserved. Implementation options for antenna elements and antenna array 1 are given, for example, in [Saidov A.S. and others. Design of phase automatic direction finders. - M .: Radio and communications, 1997], antenna switch 2 and switches 10 - 14 of the unit for generating measuring signals 3 - in [Dzehtser GB, Orlov OS P-i-n diodes in microwave broadband devices. - M .: Owls. radio, 1970 - 200 p.], [Giniyatulin F.A. Electronic key for switching - Proceedings of the NIIR, 1979, 3.], [Vaysblat A.V. Microwave switching devices on semiconductor diodes. - M .: Radio and communications, 1987. - 120 p.], [Nefedov E.I., Saidov A.S., Tagilaev A.R. Microwave broadband microstrip controls. - M .: Radio and communications, 1994], phase shifter 15 - in [Nefedov E.I., Saidov A.S., Tagilaev A.R. Microwave broadband microstrip controls. - M .: Radio and communications, 1994], [Avramenko V.L., Galyamichev Yu.P., Lanne A.A. Electric delay lines and phase shifters. - M .: Communication, 1973. - 107 p. ], adder 16 - in [Red E. Reference manual on high-frequency circuitry: Circuits, blocks, 50-ohm technology: TRANS. with him. - M .: Mir, 1990. - 256 pp.], Receiver 4 - in [Red E. Reference manual on high-frequency circuitry: Circuits, blocks, 50 ohm technology: Trans. with him. -M.: Mir, 1990 .-- 256 p. ], [Red E.T. Circuitry radios. Practical Guide: Trans. with him. - M .: Mir, 1989. - 152 p.].

 A functional diagram of an embodiment of the BOAS 5 using digital signal processing is shown in FIG. 4. In this case, the BOAS 5 contains an analog-to-digital converter (ADC) 17, a memory device 18 of temporary samples (ZUVV), a block 19 of a discrete Fourier transform (BDPF), a block 20 of a signal detector (OS), a memory device 21 of the frequency subbands (ZUCHP ), control unit 22 (CU), digital multiplexer 23 (CM), a 24-square-wave component of the spectra (VKKS) calculator, a storage device of 25 square-wave components of the spectra (ZKKS), an adder of 26 square-wave components of the spectra (SKKS), a 27 square root calculator (VCC) ) The input of the ADC 17 is the input of the BOAS 5. The output of the ADC 17 is connected to the input of the RAM 18 with M outputs (for simplicity, one output M is shown in Fig. 4). The outputs of the ZUVV 18 are connected to the corresponding inputs of the BDPF 19, having M inputs and M / 2 data outputs. The outputs of the BDPF data 19 are connected to the corresponding data inputs of the M / 2 channel OS 20 and simultaneously to the corresponding data inputs of the M / 2 channel CM 23. The outputs of the OS 20 are connected to the input of the ZUCHP 21, the outputs of which are connected to the data inputs of the BC 22. The output of the CM 23 is connected to two inputs of VKKS 24, the output of which is connected to the input of ZUKKS 25. The outputs of ZUKS 25 in the amount of N / 2 are connected respectively to the M / 2 data inputs of the M / 2-channel SKKS 26, the only output of which is connected to the VKK 27. The output of the VKK 27 is the output of the BOAS 5. In addition, the control inputs of the ADC 17, ZUVV 18, BDPF 19, OS 20, ZUCHP 21 and BU 22 are connected to the control input of the BOAS 5. and the control inputs of the CM 23, VKKS 24 and ZUKS 25 are connected to the output of the BU 22, the output of which is the control output of the BOAS 5.

The ADC 17 performs time sampling operations with a frequency F _T and quantization according to the level of the signal received at the input of the BOAS 5 from the output of the receiver 4. The sampling frequency F _T is selected in accordance with the expression [I. Gonorovsky Radio engineering circuits and signals. Textbook for high schools. Ed. 3rd rev. and add. - M .: Soviet Radio, 1977. - 608 pp.]: F _T ≥2D _f , where D _f is the receiver sub-band.

,
где Δf_min - минимальный разнос частот между двумя сигналами.Digital values corresponding to samples of a digital (discretized and quantized signal) are stored in the RAM 18, in the number of M samples. The number M is chosen so as to enable frequency resolution of two signals having close carrier (center) frequencies. For this, it is necessary that the neighboring spectral components of the discrete Fourier transform differ in frequency by no more than half the minimum frequency spacing between adjacent signals. Therefore, the choice of the number M can be carried out in accordance with the expression:

,
where Δf _min is the minimum frequency spacing between two signals.

 After the accumulation of M samples of the digital signal in the RAM 18, the entire array of accumulated values of the digital signal is fed to the BDPF 19, where the discrete Fourier transform (DFT) operation is performed. The accumulation of M samples in ZUVV 18 allows the use of efficient mathematical algorithms of the "fast" Fourier transform (FFT) in the FFT 19. BDPF 19 using FFT is advisable to implement in the form of a software machine [L. Rabiner, B. Gould. Theory and application of digital signal processing. - M.: Mir, 1978.]. At the outputs of the BDPF 19, M / 2 real digital values are formed corresponding to the M / 2 values of the spectral components of the amplitude spectrum of the full frequency range under consideration.

 The outputs of the BDPF 19 are connected simultaneously to the inputs of the OS 20 and the CM 23. The OS 20 detects signals in the frequency range under consideration and combines the spectral components from the outputs of the BDPF 19 into K groups corresponding to the K subbands in which the signals are detected. Methods for detecting signals in OS 20 may be different and are not the subject of the invention. For example, a signal in a subband can be considered detected if the amplitudes of all spectral components within a given frequency subband exceed a certain threshold level that obviously exceeds the noise level at the BDPF outputs 19. Acting in accordance with the above detection method, OS 20 can be implemented as an automaton implemented on based on the microprocessor and operating in accordance with the program, a block diagram of which is shown in Fig.5.

 The program uses: the boolean variable noSignal (accepting the values TRUE or FALSE), the variable A into which the value of the amplitude of the spectral component S [i] considered at this step is written, i is the integer parameter of the cycle (0≤i≤M / 2), k - the integer number of the subband under consideration (0≤k≤K). In addition to variables, the program uses the constant value findLevel, equal to the signal level necessary for detection.

The program works as follows. The first block B1 of the program - its beginning - start. In the second block B2 of the program, the internal variables of the program are initialized: the parameter i is assigned the value 0 (i = 0); the number of the subband k under consideration is assigned the value 0 (k = 0); the noSignal variable is set to TRUE (no signal detected). In the third block In ₃ programs from the i-th output of the BDPF 19 is read the value of the i-th spectral component of the spectrum. In the fourth block B4 of the program, the value read in the previous block B3 of the program is compared with the constant value findLevel. If it is larger than findLevel (the signal is above the detector level), then the program goes to block B5, otherwise - to block B6. In the fifth block B5, the condition is checked: is the signal already detected at one of the previous steps (noSignal = ICTIHA). If the signal has not yet been detected (noSignal = ICTIHA), then the transition to block B7 is performed, otherwise (the signal has already been detected) to block B12, in block B7, the value no is assigned to the variable noSignal FALSE, which means that the signal is detected on this step. From block B7, the program proceeds to block B8. In block B8, the result of detecting the initial spectral component of a given frequency subband is output - recording the number I of the _{beginning of the} spectral component corresponding to the initial frequency of this frequency subband, and equal to the number of the current spectral component i, in the memory address 21. From block B8, the program goes to block B12. In block B6, it is checked whether a signal has already been detected in one of the previous steps (noSignal = FALSE). If the signal has already been detected (noSignal = FALSE, then the transition to block B9 is performed, otherwise to block B12. In block B9, the noSignal variable is set to TRUE, which indicates that this spectral component is the final spectral component of this frequency subband .

From block B9, the program proceeds to block B10. In block B10 is performed final detection result output spectral component of the frequency subband - numbers I _con record spectral component corresponding to the final frequency of the frequency subband, and an equal number of the current spectral component i, at ZUCHP 21. In block B10 program proceeds to block B11, in which is an increase in the number of the considered subband k. From the CC block, the program switches to the B12 block. In block B12, the condition is checked: is the current number i of the spectral component less than M / 2. If the condition is satisfied (i <M / 2), then the transition to block B13 is performed, where the current number of the spectral component i is increased by one. From the output of block B13, the program proceeds to block B3 - to the next step. If the condition in block B12 is not satisfied (i≥M / 2), then a direct transition to the beginning of the program is performed, which means the end of the detection of signals in this spectrum.

 The implementation of devices based on microprocessors is given in a number of scientific and technical sources of information, for example, in [Horowitz P., Hill W. Art of circuitry: In 2 vols. T.2. Per. from English - Ed. 3rd stereotype. - M .: Mir, 1986. - 590 p.].

The results of the program are the numbers I and I _{nach con} spectral components corresponding to the initial and final frequency of each frequency subband that is stored in ZUCHP 21 (Figure 4). The amount of memory ZUCHP 21 is equal to M / 2 (it consists of M / 4 values of I _beg and M / 4 values of I _con ).

 The CM 23 under the control of the BU 22 commands outputs a digital value equal to the digital value at one of the M / 2 of its data inputs. The control commands of the control unit 22 are such that values equal to the amplitudes of the spectral components of the k-th frequency subband are sequentially issued from the inputs to the output of the CM 23, with 1≤k≤K.

 The amplitudes of the spectral components of the kth frequency subrange from the output of the CM 23 are sequentially delivered in time to the VKKS 24, where, under the control of the commands from the control unit 22, the operation of squaring their values is performed. VKKS 24 is an ordinary digital multiplier, on both inputs of which the same value is supplied.

The squares of the spectral components from the output of VKKS 24 under the control of the BU 22 commands are sequentially stored in time in ZUKKS 25, in the amount of P _S , equal to the number of spectral components in the considered k-th subband. Since, in accordance with the above expression, the maximum number of spectral components in the subband is M / 2, the memory size of ZUKKS 25 is equal to M / 2 cells, the size of which is equal to the number of bits of the digital signal. In the event that P _S <M / 2, zero values are recorded in the remaining empty cells of ZUKKS 25.

After the values of the squares of the spectral components of the considered k-th subband of frequencies are accumulated in ZUKKS 25 Р _S , these values are sent to SKKS 26, where they are summed under the control of BU 22 commands. SKKS 26 is an ordinary digital adder.

 The sum of the squares of the spectral components from the output of SCKS 26 goes to the square root calculator VKK 27, at the output of which a digital value is generated that is directly proportional to the amplitude of the signal operating in the considered kth subband.

 As the RAM 18 and ZUKS 25 can be used as random access memory (random access memory), and a set of shift registers with the possibility of parallel loading and reading. When using shift registers, their length should be equal to M / 2, and the number of such registers should be equal to the number of bits of the digital signal.

 Functional diagram of an embodiment of the VKAPS 7 direction finder (Fig. 6) using a specialized digital computer includes digital multipliers 28, 29, 30, 31, 32, 33, 34, 35, digital sign-changing devices 36, 37, 38, digital adders 39 , 40, 41, 42, a digital device for calculating the quotient of the division of two numbers 43, functional converters 44, 45, 46, 47, 48, which perform the following functions, respectively: determining the sign of a number (44), calculating the trigonometric arccosine (45), weighting the number sign (46), the calculation of the trigonometric s sine (47), the calculation of the trigonometric cosine (48). In this case, the first VKKPS input is connected to both inputs of the multiplier 31, and the second to both inputs of the multiplier 32, thereby realizing the squaring of the corresponding values. In addition, the first and second inputs of VKAPS 7 are connected to two inputs of the multiplier 28, carrying out their multiplication. The second input of VKAPS 7 is connected to both inputs of the multiplier 29, and the third input, respectively, to both inputs of the multiplier 30, realizing the squaring of the corresponding values. The output of the multiplier 28 is connected to one of the inputs of the multiplier 33, the second input of which is supplied with a constant value equal to the number 2 in the selected code, in addition, the output of the multiplier 28 is connected to one of the inputs of the multiplier 34 and, similarly, to one of the inputs of the multiplier 35. Output the multiplier 29 is connected to the input of the sign-changing device of the number 36, and the output of the multiplier 30 is connected to the input of the sign-changing device of the number 37.

 The outputs of the multipliers 31 and 32 are connected to the inputs of the two-input adder 39. The output of the sign-changing device of the number 36 together with the output of the adder 39 are respectively connected to the two inputs of the adder 40, and the output of the sign-changing device of the number 37 together with the output of the adder 39 are connected to the inputs of the adder 41. The output the adder 40 is connected to the input of the divisible device for calculating the quotient of the division of two numbers 43. The output of the multiplier 33 is connected to the input of the divider of the device for calculating the quotient of the division of two numbers 43. The output of the device for calculating h By dividing the two numbers 43, it is connected to the input of the functional converter 45, the output of which is connected to the input of the sign-changing device 38, the output of which is connected to one of the inputs of the adder 42, the other input of which is supplied with a constant value equal to + π in the selected code. The output of the adder 41 is connected to the input of the function converter 44 for determining the sign of the number, the output of which is connected to the input of the sign of the functional converter 46 for weighing the number with a sign.

 The output of the adder 42 is connected to the input of the number of the functional Converter 46 weighing the number of signs. The output of the functional transducer 46 is connected to the inputs of the functional transducers 47 of the sine and 48 cosines, which are connected by their outputs to the second of the inputs of the multiplier 34 and, respectively, to the second of the inputs of the multiplier 35. The outputs of the multipliers 34 and 35 are the outputs of VKAPS 7, respectively, of the real and imaginary parts complex amplitude of a pair of signals. In addition, the sync inputs of the multipliers 28, 29, 30, 31, 32, 33, 34, 35, as well as the device for calculating the quotient of the division of two numbers 43 are connected to the control input (sync input) of the VKAPS 7.

 VKAPS 7 works as follows. In the multiplier 28, the values are multiplied at the first and second inputs of the VKAPS 7. The multipliers 31 and 32 are squared the values at the first and second inputs of the VKAPS 7, and the sign-changing devices 36 and 37 reverse the sign obtained in the multipliers 29 and 30. The multipliers 29 and 30 square the values at the third and fourth inputs of the VKAPS 7. The multiplier 33 doubles the value obtained in the multiplier 28. In the adder 39, the squares of the values at the first and second inputs of the VKAPS 7 are obtained in the multipliers 31 and 32. In the adder 40 to the sum of the squares of the values at the first and second inputs of VKAPS 7 received at the output of the adder 39, adds the square of the values at the third input of VKAPS 7 taken with a negative sign (from the output of the device for changing the sign of the number 36).

 Similarly, in the adder 41, the sum of the squares of the values at the first and second inputs of the VKAPS 7 received at the output of the adder 39, adds the square of the values at the fourth input of the VKAPS 7 taken with a negative sign (from the output of the sign reversing device of the number 36). In the device for calculating the quotient of dividing two numbers 43, the quotient of dividing the value at the output of the adder 40 is calculated by the value at the output of the multiplier 33. The result obtained at the output of the device for calculating the quotient of dividing two numbers 43 is subjected to a functional transformation of the calculation of the trigonometric arccosine in the converter 45. The resulting the value of the arccosine undergoes a change of sign to the opposite in the sign change device 38. The resulting value is added up with a constant value equal to the number + π in the adder 42. In the function converter 44 for determining the sign of the number, the sign of the number at the output of the adder 41 is highlighted. In the function converter 46 for weighing the number, the value is transferred from its upper input to the output with the sign changed to the opposite if its lower input is given a value corresponding to a negative sign; otherwise, the output of the value from the upper input of the functional Converter 46 is performed without changing the sign discharge. The value from the output of the functional transducer 46 undergoes functional transformations: taking the trigonometric sine and trigonometric cosine in the functional converters 47 and 48, respectively. The values obtained at their outputs are multiplied in the multipliers 34 and 35, respectively, by the product of the signals at the first and second inputs of VKAPS 7, which is obtained at the output of the multiplier 28. Thus, at the output of the multipliers 34 and 35, the real and imaginary parts of the complex amplitude of the corresponding signal pair are obtained .

 All devices included in the VKAPS 7 scheme are typical digital devices known from the prior art and described in various scientific and technical sources. For example, the implementation of multipliers and adders is described in [Ugryumov EP Digital circuitry. - SPb .: BHV-Petersburg, 2001. - 528 p.], Sign replacement devices - ordinary sign inverters, described for example in [Horowitz P., Hill W. Art of circuitry: In 2 vols. T.2. Per. from English - Ed. 3rd stereotype. - M .: Mir, 1986. - 590 pp.], Functional converters 45, 44, 48, associated with the taking of trigonometric functions, can be implemented, for example, on the basis of read-only memory (ROM).

 Thus, the phase distribution of the radio signals received by the elements of the antenna array, necessary for the formation of two-dimensional angular spectra from which the azimuths and elevation angles of the radio signals are determined, in the claimed invention is carried out by measuring the amplitudes of the signals received by the antenna elements sequentially in time and measuring the amplitudes of these combinations signals based on the reception and conversion of signals by a single-channel receiver. In addition to improving the accuracy of direction-finding by eliminating direction-finding errors associated with the instability of synchronous reception of radio signals, the proposed invention improves the reliability of direction-finding, simplify the design, reduce weight and size characteristics and power consumption of the direction finder by simplifying the structure of the receiver.

 The most successfully claimed method of direction finding of radio signals and direction finder can be used in radio engineering when searching and determining the location of unauthorized sources of radio emission, in radio monitoring of analog and digital communication systems when working as part of mobile positioning systems, which are subject to severe restrictions on weight and size characteristics and power consumption.

Claims (4)

1. The method of direction finding of radio signals, including the reception of radio signals by an antenna array consisting of N antenna elements made identical in an amount of at least three and located in the direction-finding plane, measuring in each frequency subband the complex amplitudes of the signal pairs for a pair of antenna elements characterizing the phases of each radio signal, received in the corresponding frequency subband by one of the antenna elements of the pair selected as a signal relative to the phase of the radio signal received in the same the frequency subband to the other of the antenna elements of the pair selected as the reference, the formation of two-dimensional angular spectra of each received in the corresponding frequency subband radio signal from the measured complex amplitudes of the pairs of signals for different pairs of antenna elements of the antenna array according to the relative position of these antenna elements in the direction-finding plane, by which they judge azimuths and elevation angles of received radio signals, characterized in that the measurement in each frequency subband is complex x amplitudes of pairs of signals for the pair of antenna elements is performed by measuring the amplitude B ₁ of the signal for one of the antenna elements couple selected as a signal, the amplitude measurement B ₂ signal to the other of the antenna elements couple selected as reference amplitude calculating IN ₃ signal, which is the sum of the signals for both antenna elements of the pair, calculating the amplitude of the B ₄ signal, which is the sum of the signals for both antenna elements of the pair when the phase delay of the signal for the other of the antenna elements of the pair is selected m as a reference, 90 ^o , and calculations for various pairs of antenna elements of the antenna array of complex amplitudes

pairs of signals in accordance with the expression:

2. The method according to p. 1, characterized in that the antenna element of the pair selected as the reference is also selected as the reference for various pairs of antenna elements of the antenna array.  3. The method according to p. 1, characterized in that as the elements of the antenna array use non-directional antennas, and as the antenna array use a J-ring multi-element equidistant antenna array, made with at least one ring number. 4. A direction finder containing an antenna array made of N antenna elements in an amount of at least three, made identical and located in the direction-finding plane, an antenna switch made with N inputs and with two outputs - reference and signal with the possibility of serial connection in time in a single the time interval of any pair of inputs, respectively, to the reference and signal outputs, and the outputs of the antenna elements are connected to the corresponding inputs of the antenna switch, receiver, amp itud signals, a bearing calculator, connected in series, and a clock generator, the output of which is connected to the control inputs of the antenna switch and the unit for determining the amplitude of the signals and which is configured to issue commands to the control input of the antenna switch for sequential connection in time in a single time interval of any pair inputs respectively to the reference and signal outputs, characterized in that the receiver and the unit for determining the amplitudes of the signals are made single-channel, input We have a unit for generating measuring signals, the reference, signal and control inputs of which are connected respectively to the reference and signal outputs of the antenna switch, the output of the clock generator, and the output is to the input of the receiver, a signal amplitude storage device, the input of which is connected to the output of the signal amplitude determination unit, the calculator complex amplitudes of pairs of signals, four inputs and a pair of outputs of which are connected respectively to four outputs, a storage device for amplitudes of signals and pairs e inputs of the bearing calculator, while the signal amplitude determination unit is provided with a control output connected to the control inputs of the signal amplitude storage device, the complex signal amplitude calculator, the bearing calculator, the measurement signal generation unit is arranged to be sequential in the first, second, third and fourth intervals the said single period of time of formation at its output, respectively, of the first signal from its reference input, the second signal from its signal input, the third signal equal to the sum of the signals from the reference input and the signal input, and the fourth signal equal to the sum of the signal from the signal input and the signal from the reference input, the phase of which is delayed by 90 ^o , the clock generator is configured to issue commands to the control input of the formation unit measuring signals for generating the indicated first, second, third and fourth signals at said intervals of a single time interval and generating at the first, second, third and fourth outputs of the memory the structure of the amplitude values of B ₁ , B ₂ , ₃ and B _{4 of} these signals, and the complex amplitude computer calculator of the signal pairs is configured to calculate the complex amplitude

for each pair of signals in accordance with the expression

where B ₁ , B ₂ , B ₃ and B ₄ are the amplitudes of the signals arriving at its first, second, third and fourth inputs, respectively.  5. The direction finder according to claim 4, characterized in that the measuring signal generating unit is made up of five switches: the first, second and third switches, each of which is configured to connect its input to one of a pair of its outputs, the fourth switch, configured to connecting its output to one of a pair of its inputs, a fifth switch, configured to connect its output to one of its three inputs, from a phase shifter and from an adder, the first and second outputs of the first switch connecting respectively, to the first input of the fourth switch and the input of the phase shifter, the output of which is connected to the second input of the fourth switch, the output of which is connected to the input of the second switch, the first and second outputs of which are connected respectively to the first input of the fifth switch and the first input of the adder, the first and second outputs of the third the switches are connected respectively to the second input of the fifth switch and the second input of the adder, the output of which is connected to the third input of the fifth switch s inputs of all five switches are connected to the control input generation unit measuring signal input of the first input and the third switch are respectively the reference and signal input unit for generating measurement signals, and the output of the fifth switch - the output unit for generating measurement signals.

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