RU2504796C2 - Direction-finding device (versions) - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: direction-finding device has a heterodyne and a control unit, N receiving radio links consisting of N receiving antennae, N control units, N low-noise amplifiers, N mixers and N intermediate frequency amplifiers. The direction-finding device also has a control radio link which consists of one or two control generators, two or three switches, two or four matched loads and N omnidirectional communication elements. Antennae of the receiving radio link are assembled into a linear or flat phased antenna array of the direction-finding device. One or two radio links of the direction-finding device serve as reference radio links.

EFFECT: high accuracy of direction-finding and widening the operating range towards high frequencies.

2 cl, 22 dwg

Description

The invention relates to the field of radio engineering and can be used in phase and amplitude direction finders of the microwave range, up to 18 GHz.

Known phase direction finder (US Pat. No. 4494118, 15.01.85), which contains N receiving radio channels, a local oscillator, a control unit and a processing and control unit. The direction finding device (Fig. 1) contains two radio channels (in the general case, N radio channels), each of which contains receiving antennas 1-1 and 1-2, adders 2-1 and 2-2, mixers 3-1 and 3-2 and intermediate frequency amplifiers (IFA) 4-1 and 4-2, as well as a local oscillator 5, a control unit comprising a serially connected control generator 6 and a switch 7 of a control generator, the outputs of which are respectively through series-connected power dividers into two channels 8-1 and 8-2 and two-channel switches 9-1 and 9-2 are connected to the second input I will give adders 2-1 and 2-2 respectively. The second outputs of the power dividers into two channels are connected respectively to the connecting line 10 through two-channel switches 10-1 and 10-2. The outputs of the converter 4-1 and 4-2 are connected respectively to the inputs of the processing and control unit 11, which includes a phase meter. As adders 2-1 and 2-2, directional couplers with weak coupling are used.

Input signals are received by direction finder antennas 1-1 and 1-2, frequency-converted by mixers 3-1 and 3-2, amplified by amplifiers 4-1 and 4-2, and fed to processing and control unit 11, where the phase difference is determined using a phase meter signals coming from the first and second channels, and the bearing of the source of radio emissions is determined. To determine the systematic errors arising due to the phase non-identity of the radio channels, at the time of absence of input signals, the processing and control unit 11 includes a control generator 6 according to a special program and controls the switches 7, 9-1, 9-2, 10-1, and 10 -2. Radio channel identity verification is carried out in two stages. At the first stage, through the first output of the switch, the signal of the control generator 6 is connected to the input of the power divider into two channels 8-1 and then through the first output of this divider and the first input of the switch 9-1 is connected to the second input of the adder 2-1, through which it enters first radio channel. There is no connection between the second output of the switch 7 and the input of the power divider into two channels 8-2, as well as the connection between the input of the switch 9-1 and the first output of the switch 10-1. From the second output of the power divider into two channels 8-1, the signal of the control generator 6 through the switch 10-1 and the connecting line 10 is supplied to the first input of the switch 10-2 and through its second input and the second input of the switch 9-2, bypassing the second power divider two 8-2, which is disconnected from the switches 7, 10-2 and 9-2, is fed to the second input of the adder 2-2 and through it to the second radio channel.

The signals that passed through the first and second radio channels enter the processing and control unit 11, in which their phase difference is measured.

At the second stage, the signal of the control generator through the second output of the switch 7 is supplied to the input of the power divider into two channels 8-2 and through the first input of the switch 9-2 and the second input of the adder 2-2 to the second radio channel, and through the switch 10-2, connecting line 10, switches 10-1 and 9-1, bypassing the power divider into two channels 8-1, to the second input of the adder 2-1 and through it to the first radio channel. Next, the signals that passed through the first and second radio channels enter the processing and control unit 11, in which their phase difference is measured. A comparison of the phase difference values measured in the first and second stages allows us to determine the phase identity of the first and second radio channels. The sum of the values of the phase differences obtained at the two stages of calibration corresponds to the doubled phase difference of the two compared channels (for more details see the section "The second stage of calibration (1st option)"). The difference in these phases corresponds to the difference in the electrical lengths of the measured radio channels. This difference can be taken into account when calculating the bearing of the source of radio emission or can be used to adjust the electrical lengths of the radio channels using special controlled correctors, for example phase shifters, which can be inserted into one or both radio channels. The connecting line does not affect the accuracy of measurements, as the phase shifts introduced by it are compensated by comparing the results obtained in the first and second stages of measurements.

The disadvantage of this device is the narrow operating frequency band and the dependence of the systematic error of measuring the identity of the radio channels on the phase non-identity of the elements in the control circuit - power dividers, switches. Because of this, for example, for the same electric lengths of the radio channels, the phase differences of the control signals measured at the output of these radio channels at the first and second stages of measurements will differ from each other, despite the identity of the radio channels, there will be a fictitious systematic error of phase measurements, which in turn, will reduce the accuracy of the measurement of the bearing of the source of radio emissions.

The closest analogue (prototype) of the invention is a microwave direction finding device and its variants (Pat. RU No. 2269791, G01S 3/10, G01S 7/40. Bull. No. 4 of 02/10/2006). Structural diagrams of the first and second variants of the invention of the prototype are shown in figure 2. and 3, respectively.

According to the first embodiment of the invention of the prototype (FIG. 2), the direction-finding device contains N receiving radio channels consisting of N receiving antennas 1-1, 1-2, 1-3, ... 1-N, N non-directional communication elements 2-1, 2- 2, 2-3, ..., 2-N, N mixers 3-1, 3-2, 3-3, ..., 3-N, N intermediate frequency amplifiers (IFA) 4-1, 4-2, 4-3 , ..., 4-N. The heterodyne inputs of the mixers 3-1, 3-2, 3-3, ..., 3-N are connected to the output of the local oscillator 5. The device also contains a control oscillator 6 connected to the input arm of the first two-channel switch 7, the second and third two-channel switches 8 and 9 The outputs of the IFA 4 of all the receiving radio channels are connected to the corresponding inputs of the processing and control unit 10. The input arm of the first switch 7 is connected to the output of the control generator 6. The input arms of the switches 8, 9 are connected respectively to the third arm 2-1 and the fourth arm 2-N directional communication elements, the first output shoulders of these switches are connected to the output shoulders of the switch 7, and their second output shoulders are connected respectively to the agreed loads 11 and 12. The fourth arm of the non-directional communication element of each receiving radio channel except the last is connected to the third shoulder of the non-directional communication element of the subsequent receiving radio channel namely, the fourth arm of the omnidirectional coupler 2-1 is connected to the third arm of the omnidirectional coupler 2-2, the fourth arm is not -directional coupler 2-2 is connected to a third non-directional coupler arm 2-3, etc., the fourth port non-directional coupler 2-N N-th radio receiver is connected to the input port of the third two-channel switch 9.

According to the second embodiment of the invention of the prototype (Fig. 3), the direction-finding device contains N receiving radio channels, respectively consisting of 1-1, 1-2, 1-3, ... 1-N receiving antennas, N omnidirectional communication elements 2-1, respectively 2-2, 2-3, ..., 2-N mixers 3-1, 3-2, 3-3, ..., 3-N, UPCH 4-1,4-2, 4-3, ..., 4-N connected to the inputs of the processing and control unit 10, the local oscillator 5, the output of which is connected to the heterodyne inputs of the mixers 3-1, 3-2, 3-3, ..., 3-N. The device also contains a control generator 6 connected to the first output arm of the first two-channel switch 7, the second output arm of which is loaded on the matched load 11, and the input arm is connected to the third arm of the non-directional communication element 2-1 of the first receiving radio channel, an additional control generator 9, output which is connected to the second output arm of the second two-channel switch 8, the first output arm of which is loaded on the agreed load 12, and the input arm is connected to the four the fourth arm of the non-directional communication element of the 2-N Nth receiving radio channel, while the fourth arm of the non-directional communication element of each receiving radio channel, except the last (Nth), is connected to the third shoulder of the undirected communication element of the subsequent receiving radio channel, namely the fourth arm of the non-directional element communication 2-1 is connected to the third arm of the omnidirectional communication element 2-2, the fourth arm of the omnidirectional communication element 2-2 is connected to the third arm of the non-directional communication element 2-2, etc.

The device according to the first embodiment of the invention of the prototype (figure 2) works as follows. The input signals received by the receiving antennas, respectively, are transmitted through non-directional communication elements to the signal inputs of the mixers, where, using a local oscillator signal, the carrier frequencies of the input signals are converted into a range of intermediate frequencies. Then these signals are amplified by the amplifier and then transferred to the processing and control unit, in which phase measurements (in the case of a phase direction finder) or amplitude measurements (in the case of an amplitude direction finder) are carried out and signals are generated according to a given program that control the two-channel switches 7, 8 and 9.

The phase or amplitude identity of the radio channels is checked in two stages in the absence of input signals. At the first stage, according to a predetermined program, the signal of the control generator 6 through the first two-channel switch 7 and the second two-channel switch 8 is sequentially supplied through the shoulders of the non-directional communication elements 2-1, 2-2, 2-3 and 2-N sequentially to all the receiving radio channels from the first to the Nth, as well as through the input arm and the first output arm of the third two-channel switch 9 into the matched load 12. In this case, the second output arm of the third two-channel switch 9 and the first matched load 11 using the first- two-channel switch 7 and the second two-channel switch 8 are disconnected from the reference oscillator 6. In the second step the direction of propagation of the pilot signal is reversed, and the value is derived from the N-th radio channel to the first. Now the signal of the control generator 6 through the first two-channel switch 7, the third two-channel switch 9 is distributed from the non-directional Nth communication element of the Nth receiving radio channel to the non-directional communication element 2-1 of the first receiving radio channel and then through the second output arm of the second two-channel switch 8 to the first matched load 11. In this case, the second matched load 12 using the third bi-directional switch 9 is turned off.

Omnidirectional communication elements are designed to enter control signals into the receiving radio channels, regardless of the direction of propagation of these signals (the first channel to the Nth or from the Nth to the first). They also should not significantly attenuate the input signals coming from the outputs of the antennas to the signal inputs of the mixers, for which the connection between the radio channels and the control channel should be weak (of the order of minus 10 ÷ 30 dB). As such non-directional communication elements, for example, non-directional dividers can be used. In this case, a small directionality will not degrade the quality of measurements if the signal power levels, regardless of their propagation direction, remain within the dynamic range of the receiving radio channels. The phase or amplitude identity of the receiving radio channels is checked for the selected pairs of receiving radio channels, moreover, all receiving radio channels can be paired and their parameters sequentially compared, or you can take one receiving radio channel as the base channel and compare the remaining receiving radio channels with it. Measurements are carried out in two stages, differing from each other in the direction of propagation of control signals. For example, the identity of the electrical lengths of two receiving radio channels is uniquely characterized by the phase difference of the control signals measured in the processing and control unit 10. In this device, the phase difference will depend only on the phase identity of the selected radio channels and will not depend on the parameters of the elements of the calibration circuit and phase identity of the paths through which control signals are fed to the radio channels, since the errors introduced by them will be mutually compensated in the final measurement result.

Thus, the obtained values of the phase differences uniquely characterize the phase non-identities of the selected radio channels and can be taken into account in the final result of determining the bearing of the radio emission source or compensated using a controlled phase shifter included in one or both radio channels of the selected pair. In a similar way, errors that occur during amplitude measurements in amplitude direction finders can be determined.

The disadvantages of the first embodiment of the invention of the prototype are:

- bearing errors due to reflection from the antennas, because due to the non-directional connection of the calibration channel with the radio channels, half of the calibration power enters the antenna and is reflected from it into the radio channel with its amplitude and phase;

- bearing errors caused by the interaction of adjacent antennas on the side lobes of their ether patterns and causing additional reflections to their radio channel in the calibration mode, which are not compensated in this mode and do not coincide with the same interaction in the operating mode;

- Bearing errors due to the difference in the lengths of the paths and connecting cables from the input point of the calibration power into the radio channel to the antennas, since only parts of the radio channels located after this input point are calibrated.

The second embodiment of the prototype works similarly to the first embodiment. Checking the phase and amplitude identity of the receiving radio channels is also carried out in it in two stages. At the first stage, according to a given program, the signal of the first control generator 6 through a two-channel switch 7 and sequentially through non-directional communication elements enters all the receiving radio channels - from the first to the Nth and then through the second two-channel switch 8 to the second matched load 12. In this case, the first matched the load 11 with the first two-channel switch 7 and the second control generator 13 with the second two-channel switch 8 are turned off. At the second measurement stage, the second control oscillator 13 is turned on, and the propagation direction of the control signal changes in the opposite direction from the Nth receiving radio channel to the first. In this case, the second agreed load 12 using the second switch 8 and the first control generator 6 using the first switch 7 are turned off. To simplify the device and simplify the measurement process, it is necessary to adjust the control oscillators 6 and 13 to the same frequency.

The second embodiment of the prototype has the disadvantages of the first embodiment. The cost of the first version of the prototype is less than the second due to the lack of a second calibration generator.

The technical result of the invention is the reduction of direction finding errors and the expansion of the operating range towards high frequencies.

Proof of the extension of the operating range towards high frequencies.

BUT on an ordinary microstrip line (MPL) does not allow to obtain a weak connection of less than minus 15 dB, since isolation with the main channel for such a line is also minus 15 dB (in fact, an NES, an omnidirectional connection is obtained). Modifications of weak links with weak coupling at the MPL known to us do not allow us to rise in frequency above 10 GHz. The invention uses a BUT with weak coupling on a suspended strip line (PPL) on a multicore board without a screen, which allows a weak coupling of minus 20 dB when decoupling minus 30 dB (Fig. 14). The use of such a BUT leads to some complication of the microwave circuit of the device (two different boards are used, Figs. 10, 11) and a special kind of load, but it provides a technical result. Decoupling minus 30 dB allows you to neglect the effect of reflections from the antenna on the calibration error.

Thus, the achievement of the technical result is obtained by using BUT with weak coupling on the PPL and the design of the node consisting of two boards, on one of which is BUT, and on the other a balancing device.

Description of technical solutions according to the invention

An object of the invention is to improve the accuracy of direction finding and expanding the operating range towards high frequencies.

The technical result of the invention is the error in determining the bearing is an order of magnitude smaller than that of the prototype and in both cases depends on the frequency of the signal.

The invention is illustrated by drawings.

Figure 1 presents the structural diagram of an analogue of the invention.

Figure 2 presents the structural diagram of the first variant of the closest analogue of the invention adopted for the prototype of the first and third variants of the invention.

Figure 3 presents the structural diagram of the second variant of the closest analogue of the invention, adopted as a prototype of the second variant of the invention.

4 is a structural diagram of a first embodiment of the invention.

5 is a structural diagram of a second embodiment of the invention.

Figure 6 presents a structural diagram of a third embodiment of the invention.

Figure 7 presents the structural diagram of the control unit.

On Fig presents a view of the opening of the antenna.

Figure 9 presents a side view of the housing of the control node with a diametrical cross section of the antenna.

Figure 10 presents a top view of the topological drawing of the control node circuit.

11 is a top view of the boards inside the housing of the control unit.

On Fig presents a sketch of the agreed load.

On Fig shows a calculated graph of the reflection coefficient of the matched load in decibels (dB) as a function of frequency from 6 to 18 GHz.

On Fig. calculated graphs of the amplitude-frequency characteristics (AFC) of a directional coupler (BUT) with weak coupling, performed on a suspended strip line (PPL), are presented. The operating frequency in GHz is plotted along the abscissa, and the values of the different coefficients of the scattering matrix of the directional coupler (BUT) in dB are plotted along the ordinate. The coefficient of the matrix S ₂₂ is equal to the coefficient S ₁₁ . In the graphs, the curve marked with the Δ symbol corresponds to the reflection coefficient, the icon corresponds to the coupling coefficient S ₁₃ , and the decoupling coefficient S ₁₄ .

On Fig presents a graph of the calculated values of the reflection coefficient for the transition from the suspended strip line (PPL) to the microstrip line (MPL) when connecting lines located on different boards.

On figa, b presents the electrical circuit of the control signal switches on two 16A and three channels 16b.

On Fig shows a table of values of the errors of determination of the bearing for the prototype and invention.

On Fig presents the design of an omnidirectional communication element in the form of a resistive coupler.

On Fig presents the design of the pin connector in the context.

On Fig presents the calculated curve of the reflected power from the pin connector. The frequency in GHz is plotted along the abscissa, and the power in dB is plotted along the ordinate.

On Fig presents the amplitude-frequency characteristics for the element of the NES with a resistive coupler. The frequency in GHz is plotted on the abscissa, and the power in dB on the ordinate. On Fig indicated:

- □ - branch power;

- Δ is the power reflected from the input.

The loss of transmitted power on the main channel is 1.2 dB.

On Fig presents a calculation table of estimates of errors of direction finding in the case of using elements of the NES in the form of a resistive coupler.

Figure 4, 5 and 6 introduced the designation of the structural elements of the embodiments of the invention:

1-1, 1-2, ..., 1-N - receiving antennas;

2-1, 2-2, ..., 2-N - non-directional communication elements (NES);

3-1, 3-2, ..., 3-N - mixers;

4-1, 4-2, ..., 4-N - intermediate frequency amplifiers (IFA);

5 - local oscillator (local oscillator);

6, 6.1 and 6.2 - control signal generators (GCS);

7.1, 7.2 and 7.3 - two-channel control signal switches (PKS2);

8.1, 8.2, 8.3 and 8.4 - coordinated loads (SN);

9 - processing and control unit (CU);

10-1, 10-2, ..., 10-N - control nodes;

11-1, 11-2, ..., 11-N- low noise amplifiers (LNA);

12 - power divider (DM);

13.1, 13.2 - three-channel control signal switches (PKSZ).

In figures 4, 5 and 6, a double digital designation of positions is introduced: the first digit indicates the number of the functional unit, the second digit indicates the serial number of a specific functional unit in the structural diagram of the direction finding device. The only node in the structural diagram of the direction finding device is indicated by a single digit or number.

In Fig.7, the nodes of the control unit 9 are indicated by the numbers of the first hundred.

101 - node digitization of signals in the radio channels 1, 2, ... N;

102 - control unit operating modes of the blocks of the direction finding device;

103 - programmable logic integrated circuit (FPGA);

104 - communication bus.

On Fig, 9, 10, 11, 12, the nodes of the control device 10-i are indicated by the numbers of the second hundred.

201 - two-way spiral (antenna emitter);

202 is a cavity resonator of an antenna forming an antenna pattern;

203 - the body of the control device;

204 - flange of the housing 203 with a conical protrusion 205;

205 - a hollow conical protrusion with a cut top and a through conical hole in its center;

206 - a dielectric board without a screen on the reverse side is designed to place microwave elements on a suspended strip line (PPL) and is made of polycor;

207 - the main shoulder of a directional coupler (BUT) with weak coupling, of the order of minus 20 dB;

208 - lateral shoulder BUT;

213 - resistive platform matched load on the board 206;

214 - metallized areas of the agreed load, made on the face of the board 206;

215 - metallized pads made on the back of the board 206;

216 - the second dielectric board with a screen on the reverse side is made of material of the type RO3006;

217 is a segment of a microstrip line (MPL) on a board 216 connecting the input of the BUT to the front conductor 218 of the balancing device (FIG. 10).

218 —conductor of the balancing device on the front side of the board 216, connecting the segment 217 MPL with the conductor of the two-wire line 220 on the front side of the board;

219 - a conductor of a balancing device on the back of the board 216, connecting the MPL screen with the conductor of the two-wire line 220 on the back of the board;

220 - a two-wire line connected to the input of the two-way antenna spiral;

221 - metallized area on the board 216;

222 - metallized holes on the site 221 of the board 216;

223 - a metal jumper connecting the segments of lines 210 and 217;

224 - metal jumpers connecting the metallized site 214 with 221;

227 - coaxial microwave connector through which the control node 10-k is connected to the LNA 11-k;

228 — a coaxial microwave connector through which a 10-k control unit is connected to a 2-k control channel element;

On figa elements of the electrical circuit of the signal switches to two channels (PKS2) are indicated by the numbers of the third hundred.

301 - contact for the signal, the control voltage.

302 is a resistor providing voltage to control the state of the diode. 303.1, 303.2 and 303.3 are inductances that decouple the DC circuit from the microwave circuit.

304.1 and 304.2 are pin diodes.

305 - input microwave signal.

306 - the first output of the microwave signal.

307 - the second output of the microwave signal.

On Fig elements of the electrical circuit of the switch to three channels (PKSZ) are indicated by the numbers of the fourth hundred.

401.1 and 401.2 - contacts for supplying control voltage.

402.1 and 402.2 are resistors that provide voltage for controlling the state of diodes.

403.1 - 403.5 - inductance, decoupling the DC circuit from microwave circuits.

404.1 and 404.2-pin diodes.

405.1, 405.2 - microwave matched loads without grounding.

406 - input microwave signal.

407 - the output of the microwave signal.

408, 409, 410, and 411 - connection points of microwave - circuit elements. The switches 7.1, 7.2 and 7.3 are made according to the circuit diagram of FIG. 16a, and the switches 13.1 and 13.2 according to the circuit 166.

On Fig introduced designation of the structural elements of the resistive coupler:

501, 502 - standard female connectors (SRG-50-751 FV VRO.364.049 TU);

503 - pin connector;

504 - case;

505 - film resistor R = 100 Ohms, with a surface resistance of 100 Ohms / a;

506 - line of the main channel on the PPL;

507 - line resistive coupler.

On Fig introduced designations of the structural elements of the pin connector;

601 - the central pin;

602 - a nut;

603 - connector housing;

604, 605 - fluoroplastic washers;

606 - a fixing ring;

607 - spring;

608 - NES building;

609 - board with a resistive coupler.

The switch 7.1 microwave input 305 is connected to the output of the generator 6. The first output of the switch 7.1. connected to the first output of the switch 7.2, the input of which is connected to the input-output of the communication element 2-1. The second output of switch 7.2 is connected to the matched load 8.1. Switch 7.3 microwave input 305 is connected to the input-output of the communication element 2-N. The first output 306 of the switch is connected to the matched load 8.2, and the second output 307 of the switch 7.3 is connected to the second output of the switch 7.1.

Switch 7.1 provides connections: with minus on pin 301, microwave inputs 305, 306 are connected, and with plus on pin 301, microwave inputs 305 and 307 are connected.

Switches 13.1 and 13.2 provide three connections: with a plus on pin 401.1 and a minus on pin 401.2, a microwave input 406 with a matched load of 405.1 is connected, and a microwave output 407 with a load of 405.2, two connections are provided, with a minus on pin 401.1 and a plus on pin 401.2 are connected Microwave inputs 406 with microwave output 407, provides another connection.

The first embodiment of the invention (figure 4)

The technical result of this embodiment of the invention is achieved due to the fact that the direction finding device contains: N receiving radio channels, consisting of N receiving antennas 1-1, 1-2, 1-3, ... 1-N, N control nodes 10-1, 10- 2, ..., 10-N, N low-noise amplifiers 11-1, 11-2, ..., 11-N, N mixers 3-1, 3-2, 3-3, ..., 3-N and N intermediate frequency amplifiers ( UPCH) 4-1, 4-2, 4-3, ..., 4-N.

In addition, the direction finding device contains a control radio channel, which consists of a control generator 6, three switches 7.1, 7.2 and 7.3, two matched loads 8.1, 8.2 and N non-directional communication elements 2-1, ... 2-N.

The direction finding device also comprises: a local oscillator 5 and a control unit 9.

All N antennas are identical and designed to receive a radio signal and can be made, for example, spiral, horn, and other microwave wave range. Antennas are assembled in a linear or flat phased antenna array (PAR) of a direction finding device. One or more radio channels of the direction finding device serve as the radio channel of the reference signal for measuring the phase difference of the radio signals of other channels.

Non-directional communication elements (NES) 2-1, 2-2, 2-N are designed to transmit the control signal of the generator 6 to the inputs of the N control nodes 10-1, 10-2, ..., 10-N direction finding device. NES can be performed on crossed loosely coupled microwave lines on resistive power dividers. Each NES has an input-output and an output-input on the other hand on the one side of the main line, and a side line output.

Mixers 3-1, 3-2, ..., 3-N are designed to convert a high frequency radio signal to an intermediate frequency and have a radio signal input, a heterodyne signal input and an intermediate frequency signal output. Mixers can be made on diodes according to known microwave circuits.

Amplifiers of intermediate frequency (UPCH) 4-1, 4-2, ..., 4-N can be made on transistors according to well-known schemes of UPCH.

The local oscillator 5 signal is designed to convert high-frequency radio signals to intermediate frequency (IF) signals using mixers. The local oscillator 5 can be performed on transistors according to the known schemes of microwave generators.

The generator 6 of the control signals is designed to calibrate the direction finding device in the control mode of operation. Tunable local oscillator 5 generator 6 are performed on transistors according to known schemes of microwave generators. At frequencies of 1-2 GHz, a circuit with a common base on a transistor with a varactor diode is used for frequency tuning. At higher frequencies, the generator circuit is supplemented by a frequency multiplier with filters. The generator 6 has an operating frequency range that matches the operating range of the direction finding device.

The third switches 7.1, the first 7.2 and the second 7.3 are made two-channel and are designed to switch the direction of the control signal in the radio channels at the first and second stages of calibrating the direction finding device from the first to the 14th radio channel and, conversely, from the Nth to the first. As switches, a switch can be used, the circuit diagram of which is shown in figa. The switch 7.1 has an input 301 of control signals, an input 305 of the control signals of the microwave and outputs 306, 307 of the control signals.

Consistent loads 8.1 and 8.2 are designed to absorb the control signal at different ends of the control channel line at different stages of calibration and can be performed in film version. The standing wave voltage coefficient (CTF) of the agreed loads should be less than 1.5, which corresponds to the reflection of the control signal from the load input at a level of less than minus 16 dB.

The control unit BU 9 is designed for:

- control of the local oscillator 5, generator 6 and switches 7.1, 7.2, 7.3;

- digitization of signals in the radio channels 1, 2, ..., N at the outputs of the UPCH 4-k;

- control of calibration and direction finding modes;

- definition of calibration data;

- definitions of direction finding data;

- Correction of direction finding data taking into account calibration.

The control unit 9 contains (Fig. 7): a node 101, which is designed to digitize the IF signals of the radio channels 1,2, ..., N, received from the IFA, and is made on analog-to-digital converters (ADCs) - a component product, node 102, which it is intended for processing the measurement results and the organization of work of BU 9, which is a processor - a component product for digital signal processing (DSP), node 103, which is designed to turn on and off the controlled nodes of the direction-finding device, which is a programmable logic th integrated circuit (FPGA) - completing a product node 104, which is intended for transmitting digital information from the CPU 102 to the FPGA 103.

The processor 102 consists of RAM - random access memory and ROM - read-only memory.

RAM is intended for the operational storage of input and output data of programs 102a-102g. ROM is intended for storing programs 102a-102g.

Program 102a is intended to determine the phase difference between the signal of the reference radio channel and the signals of all other radio channels.

Program 102b is intended to determine the calibration values of the phase differences of the signals of the radio channels with respect to the signal of the reference channel.

Program 102c is intended to correct phase differences of direction finding signals.

Program 102g is designed to control the operating and calibration modes of the direction finding device. Program data 102g is received via bus 104 to a programmable logic integrated circuit (FPGA) 103.

At the FPGA output, digital analog converters (DACs) are connected, which convert digital signals to analog control voltages. Operator - the user programs the FPGA in accordance with the requirements of the operating modes and control of these modes using the controlled elements of the direction finding device to which the DAC outputs are connected.

BU 9 in the first embodiment of the invention has N inputs of intermediate frequency (IF) signals and 5 outputs of control signals: control oscillator 6, local oscillator 5 and three switches 7.1, 7.2 and 7.3.

BU 9 in the second embodiment of the invention has N inputs of IF signals and 5 outputs of control signals: control oscillators 6.1 and 6.2, local oscillator 5 and two switches 7.2 and 7.3.

BU 9 in the third embodiment of the invention has N inputs of IF signals and 4 outputs of control signals: a control oscillator 6, a local oscillator 5 and two switches 13.1 and 13.2.

The control nodes 10-1, 10-2, ..., 10-N are identical and are designed to calibrate the radio channels. Each control unit contains (Figs. 9, 10, 11) a housing 203, to the front wall 204 of which a resonator 202 with an antenna 201 is attached, a radio circuit consisting of two boards 206 with elements of a suspended strip line (PPL) and 216 with elements of a microstrip line ( MPL) and two wire lines. The radio circuit of the control unit (figure 10) includes: BUT, the coordinated load, a balancing device and a two-wire line.

The main arm 207 of the NO is connected by a segment 210 of the PLL and the segment 217 of the MPL with the front conductor 218 of the balancing device ending with the first face of the two-wire line 220. The screen of the board 216 goes into the conductor 219 of the balancing device ending with the second segment of the two-wire line 220. The output of the main arm 207 of the NO is connected with connector 227. The lateral arm 208 of the BUT is connected by a segment of the PPL 211 to the connector 228, the output of the lateral arm of 208 by a segment of 212 is connected to the matched load 213, the metal pads 214 of which are connected to the “ground” by means of metal webs 224 of the metal pad 221 with metallized holes 222 with a metal screen - "ground" board 216.

The control unit has a radio channel input connected to the antenna. The output of the radio channel, which is also the output of the control signal during calibration, is connected via connector 227 to the input of the LNA of the radio channel.

The control unit has a connector 228, to which the NES of the control channel is connected. Connector 228 is loosely coupled to the output of the radio channel of this node.

The first dielectric chamber 206 is made of polycor without a screen on the reverse side and is designed to accommodate microwave elements on the submarine (Fig. 10, 11).

The second dielectric chamber 216 with a screen on the reverse side is designed to accommodate the elements of the microwave control device on the MPL and two-wire line (figure 10, 11).

Low-noise amplifiers LNA 11-1, 11-2, ..., 11-N are identical and are designed to amplify high-frequency radio signals with a low noise level. Noise level should not exceed 2 dB. LNA amplifiers are made according to well-known schemes.

The connection of the circuit elements of the direction finding device according to the first embodiment of the invention (figure 4)

In each i-th radio channel of the direction-finding device, the antenna 1-i, the control unit 10-i, the amplifier LNA 11-i, the mixer 3-i and the amplifier 4-i. connected in series. The output of the UPCH 4-i is connected to the input 4-i of the intermediate frequency signal of the control unit (CU) 9. The output of the local oscillator 5 is connected to all heterodyne inputs of N mixers.

In the control radio channel, all N omnidirectional communication elements (NES) 2-i are connected by inputs-outputs and outputs-inputs in series. The outputs of the control signals of the NES are connected to the inputs of the control signals of the respective control nodes.

The switch 7.1 input control signal 305 is connected to the output of the generator 6. The first control signal output of the switch 7.1. connected to the first control signal input of switch 7.3.

The second control signal output of the switch 7.1. connected to the control signal input of switch 7.2, the control signal input-output of which is connected to the input-output of the first communication element 2.1. The second control signal output of switch 7.2 is connected to the matched load 8.1.

The switch 7.3 is connected by the output-input 305 of the control signal with the input-output of the last non-directional communication element 2-N. The control signal output of switch 7.3 is connected to the matched load 8.2. The outputs of the agreed loads 8.1 and 8.2 are connected to a common conductor "ground".

With a minus on the contact 301, the control signal input 305 and the first control signal output 306 are connected, with a plus on the contact 301, the control signal input 305 and the second control signal output 307 are connected.

The inputs of the control signals: local oscillator 5, generator 6 and switches 7.1, 7.2, 7.3 are connected to the corresponding outputs of the control unit 9.

Calibration and operation of the direction finding device of the first embodiment of the invention (figure 4)

Calibration of the radio channels of the direction finding device is carried out in two stages in the absence of direction finding radio signals.

The first stage of calibration (1st option)

Using the control unit 9, the generator 6 and the local oscillator 5 are turned on, the switches 7.1, 7.2 and 7.3 are turned on when the input 305 is connected to the output 306. In this case, the output of the generator 6 is connected through the output of the switch 7.1 to the output 306 of the switch 7.2 and through the input 305 of the switch 7.2 is connected to the input-output of the NES 2-1 of the calibration channel, and the input-output of the NES 2-N is connected through the input 305 and the output 306 of the switch 7.3 with the input of the agreed load 8.2.

The control signal of the generator 6 through the switches 7.1 and 7.2 and non-directional communication elements (NES) is supplied to the inputs of the control devices, through the lateral shoulders of the HO 208 and the main 207 with weak connection to all radio channels of the direction finding device, starting from the first. Next, the control signal in the radio channel is amplified by the LNA 11-i, converted by the 3-i mixer into an intermediate frequency (IF) signal, amplified by the 4-i frequency converter and fed to the control unit 9. In the control unit 9 in node 101, the signals are digitized in the node 102, using the program 102a, the amplitudes and phase differences of the signals of the radio channels relative to the reference radio channel corresponding to the first stage are determined. These values are stored in the RAM node 102. Turn off the generator 6.

The second stage of calibration (1st option)

Using commands from control unit 9, switches 7.1, 7.2 and 7.3. are translated to the position when input 305 is connected to output 307.

In this case, the output of the generator 6 is connected via switches 7.1 and 7.3 with the input-output of the NES 2-N, and the input-output of the NES 2-1, through the switch 7.2, is connected to the input of the matched load 8.1. Include a generator 6 and a local oscillator 5.

The control signal of the generator 6 through the switches 7.1 and 7.3 and the lateral arm of the non-directional communication elements is fed to the inputs of the control devices, to the lateral 208 and main 207 arms of the ND with weak coupling to all radio channels of the direction finding device, starting from the Nth, and then the control signal is converted, as in the first stage of calibration. Turn off the generator 6.

Let us consider in detail the process of calibration corrections for two channels. We accept the first channel as the reference one.

At the first stage of calibration, we obtain the phase difference:

Δ ₂₁ = (Ф ₂ + Ф ₁₂ ) -Ф ₁ ,

where f ₁ is the phase of the microwave signal in the reference channel, when passing from the input point to BU 9.

F ₂ - phase in the second channel, when passing from the entry point into the second channel to BU 9.

F ₁₂ is the phase of the microwave signal when passing in the calibration channel from the first radio channel to the second.

At the second stage of calibration, we obtain the phase difference:

Δ ₂₁ = Ф ₂ - (Ф ₁₂ + Ф ₁ ).

Thus, the phase correction to the operating mode for two channels is determined by software:

ΔΦ ₂₁ = (Δ ₂₁ + Δ ₂₁ ) / 2.

Moreover, the value of F _{12 is} not included in the final formula.

Direction finding device operating mode (1st option)

In the operating mode, the direction finder turns off the generator 6. The state of the switches 7.1, 7.2 and 7.3 in an arbitrary position. The signals through the antennas enter all the radio channels and go their way to the BU 9.

After digitization, phase differences are determined relative to the k-th reference channel.

Due to the weak coupling BUT (elements 207, 208 of the control device 10-i), when the signal from the antenna side enters the calibration channel, the power gets less than minus 30 dB from the power received in the radio channel, which can be neglected.

The values of the phase differences ΔΦik of the calibration signals are proportional to the difference in the electrical lengths of the radio channels, starting from the point of entry of the calibration signal into the radio channel. These phase differences are subtracted from the phase differences obtained in the direction finding mode.

The second embodiment of the invention (figure 5)

The technical result of this embodiment of the invention is achieved due to the fact that the direction finding device contains: N receiving radio channels, consisting of N receiving antennas 1-1, 1-2, 1-3, ... 1-N, N control nodes 10-1, 10- 2, ..., 10-N, N low-noise amplifiers 11-1, 11-2, ..., 11-N, N mixers 3-1, 3-2, 3-3, ..., 3-N and N intermediate frequency amplifiers ( UPCH) 4-1, 4-2, 4-3, ..., 4-N.

In addition, the direction-finding device contains a control channel, which consists of two identical control oscillators 6.1 and 6.2, two identical first switches 7.2 and second 7.3 to two positions, two matched loads 8.1, 8.2 and N non-directional communication elements (NES) 2-1, ... 2-N. The direction finding device also comprises: a local oscillator 5 and a control unit 9.

The connection of the circuit elements of the direction finding device according to the second embodiment of the invention (figure 5)

In each i-th radio channel of the direction-finding device, the antenna is 1-i, the control unit is 10-i, the LNA 11-i, the mixer is 3-i and the amplifier is 4-i. connected in series. The output of the UPCH 4-i is connected to the input 4-i of the intermediate frequency signal of the control unit (CU) 9. The output of the local oscillator 5 is connected to all heterodyne inputs of N mixers.

In the control channel, all N omnidirectional communication elements (NES) 2-i are connected by inputs-outputs and outputs-inputs in series. The outputs of the control signals of the NES are connected to the inputs of the control signals of the respective control nodes.

The control signal output of the control generator 6.1 is connected to the control signal input of the switch 7.2, the output-input of which is connected to the input-output of the first non-directional communication element 2-1. The coordinated load 8.1 is connected to the control signal output of switch 7.2.

The output of the control generator 6.2 is connected to the control signal input of the second switch 7.3., The input-output of the last N-th element of the NES is connected to the output-input of the switch 7.3, the control signal output of which is connected to the input of the matched load 8.2.

The outputs of the agreed loads 8.1 and 8.2 are connected to a common conductor "ground".

The inputs of the control signals of the local oscillator 5, generators 6.1, 6.2 and switches 7.2 and 7.3 are connected to the corresponding outputs of the control unit 9.

Calibration and operation of the direction finding device of the second embodiment of the invention (figure 5)

Calibration of the radio channels of the direction finding device is carried out in two stages in the absence of direction finding radio signals.

The first stage of calibration (2nd option)

Using commands BU 9 diodes switches 7.2 and 7.3. are transferred to the position (figa), when the input 305 is connected to the output 306. In this case, the output of the generator 6.1 is connected via a switch 7.2 to the input-output of the NES 2-1 of the control channel, and the input-output of the NES 2-N is connected to the input of the matched load 8.2.

Include a 6.1 generator and a local oscillator 5.

The control signal of the generator 6.1 through the switch 7.2 and non-directional communication elements (NES) is fed to the inputs of the control devices, the side 208 and the main 207 shoulders of the non-contact with weak communication and to all radio channels of the direction finding device, starting from the first. Next, the control signal in the radio channel is amplified by the LNA amplifier 11-i, converted by the 3-i mixer into an intermediate frequency (IF) signal, amplified by the 4-i amplifier and supplied to the control unit 9. In the control unit 9 in node 101, the signals are digitized, the node 102 using the program 102a determines the values of the amplitudes and the phase difference and the signals of the radio channels relative to the reference radio channel corresponding to the first stage. These values are stored in the RAM of the node 102.

The second stage of calibration (2nd option)

Using commands BU 9 diodes switches 7.2 and 7.3. are transferred to the position when input 305 is connected to output 307. In this case, the output of the generators 6.2 is connected via switch 7.3 to the input-output of the NES 2-N, and the input-output of the NES 2-1 is connected to the input of the matched load 8.1.

Turn on the generator 6.2.

The control signal of the generator 6.2 through the switch 7.3 and the lateral arm of the omnidirectional communication elements is fed to the inputs of the control devices, to the lateral 208 and main 207 arms of the NO with weak coupling to all radio channels of the direction finding device, starting from the Nth, and then the control signal is converted, like at the first stage of calibration. After the second calibration step is completed, calibration corrections to the phase differences of the operating mode signals are calculated. The matrix of these amendments is stored in RAM. Turn off the generator 6.2.

Direction finding device operating mode (2nd option)

In the operating mode of the direction finder, the 6.1 and 6.2 generators are turned off. The state of the switches 7.2. And 7.3 is arbitrary. The direction-finding signals through the antennas enter the radio channels and each go its own way to the BU 9. After digitization, the phase differences of these signals are determined relative to the k-th reference channel. Due to the fact that a BUT with weak coupling of the control device 10-i when the received signal from the antenna side enters the calibration channel, a power less than minus 30 dB is received through the untied shoulder of the BUT compared to the power received by the radio channel, we neglect the influence of this power.

Using program 102b, the calibration values of the phase differences for the radio channels are determined from the results of two calibration steps. These phase differences are algebraically subtracted from the phase differences obtained in the direction finding mode.

The third embodiment of the invention (Fig.6)

The technical result of this embodiment of the invention is achieved due to the fact that the direction finding device comprises: a control unit 9, a local oscillator 5, N receiving radio channels, consisting of N receiving antennas 1.1, ... 1.-N, N non-directional communication elements 2-1, ... 2- N, which have an input-output and an output-input on the other side of the main line and an output of the side line, N mixers 3-1, ... 3-N, N amplifiers of an intermediate frequency 4-1, ... 4-N, and the output each mixer is connected to the input of the corresponding intermediate frequency amplifier, the outputs of which oedineny to corresponding inputs of the control unit 9, a control radio channel consisting of pilot generator 6, two three-channel switches 13.1 and 13.2 and the first 8.1 and the second 8.2, the third 8.3 and fourth 8.4 matched loads.

In addition, the direction finding device includes: a power divider 12, N control nodes 10-1, ... 10-N, each with an input and output radio signal and a control signal input, N low-noise amplifiers 11-1, ... 11-N.

The switches have inputs of control signals and inputs of control signals, outputs and inputs of control signals and two outputs of control signals.

The control signal outputs of the first switch 13.1 are connected to the inputs of the first 8.1 and second 8.2 matched loads, respectively, and the control signal outputs of the second switch 13.2 are connected to the corresponding inputs of the third 8.3 and fourth 8.4 matched loads.

The control unit 9 has outputs of the control signals by a local oscillator, a control generator and two switches.

Non-directional communication elements have one side line output.

In the radio channels, the antennas, control nodes and low-noise amplifiers are connected in series, the outputs of low-noise amplifiers are connected to the signal inputs of the respective mixers, the control signal outputs of the control unit are connected to the corresponding inputs of the control generator, local oscillator, and switch inputs.

The input of the power divider is connected to the output of the control generator, its first control signal output is connected to the control signal input of the first switch, and the second control signal output is connected to the control signal input of the second switch

The first switch is connected by the output-input of the control signal with the input-output of the first non-directional communication element, and the second switch is connected by the output-input of the control signal with the input-output of the Nth - the last non-directional communication element.

The connection of the circuit elements of the direction finding device according to the third embodiment of the invention (Fig.6)

In each i-th radio channel of the direction-finding device, the antenna is 1-i, the control unit is 10-i, the LNA 11-i, the mixer is 3-i and the amplifier is 4-i. connected in series. The output of the UPCH 4-i is connected to the input 4-i of the intermediate frequency signal of the control unit (CU) 9. The output of the local oscillator 5 is connected to all heterodyne inputs of N mixers.

In the control channel, all N omnidirectional communication elements (NES) 2-i are connected by inputs-outputs and outputs-inputs in series. The outputs of the control signals of the NES are connected to the inputs of the control signals of the respective control nodes.

The control signal input (point 406) of each switch is connected to point 408, the control signal output (point 407) of each switch is connected to point 409. The coordinated loads are made without grounding and are connected to points 410, 411 in each switch.

The output of the local oscillator 5 is connected to all heterodyne inputs of N mixers.

The output of the control generator 6 is connected to the input of the power divider 12, the outputs of which are connected respectively to the control signal inputs of the switches 13.1 and 13.2 (point 406).

The output (407) of the control signal of the switch 13.1 is connected to the series-connected inputs / outputs of N non-directional communication elements. The input-output of the last N-th element of the NES is connected to the output 407 of the switch 13.2.

The pilot input (point 406) of each switch is connected to point 408, the pilot output (point 407) of each switch is connected to point 409. The coordinated loads made without grounding are connected to points 410, 411 in each switch.

In the first state of each switch, a minus (negative voltage) is supplied to the control input of the switch 401.1, and a plus (positive voltage) is supplied to the control input 401.2. In this case, the points 408 and 409 are closed and the input 406 and the output 407 are connected.

In the second state of each switch, “plus” (positive voltage) is supplied to the control input of switch 401.1, and “minus” (negative voltage) is supplied to control input 401.2, points 408 and 410, as well as points 409 and 411, are closed. input 406 with matched load 8.1 for switch 13.1 and with matched load 8.3 for switch 13.2, while output 407 is connected to matched load 8.2 for switch 13.1 and matched load 8.4 for switch 13.2.

The inputs of the control signals of the local oscillator 5, generators 6 and switches 13.1 and 13.2 are connected, with the corresponding outputs of the control unit 9.

Calibration and operation of the direction finding device of the third embodiment of the invention (Fig.6)

Calibration of the radio channels of the direction finding device is carried out in two stages in the absence of direction finding radio signals.

The first stage of calibration (3rd option)

Using commands from the control unit 9, the switch 13.1 is moved to position 1, and the switch 13.2 to position 2. (fig.16b). Include a generator 6 and a local oscillator 5.

The control signal of the generator 6 through the right shoulder of the power divider 12, the input and output of the switch 13.1 and the NES is fed to the inputs of the control devices, and through the lateral 208 and the main 207 shoulders of the NO with weak coupling enters all the radio channels of the direction finding device, starting from the first. The control signal from the generator 6, going through the left arm of the power divider, is loaded through the switch 13.2, included in position 2 for the agreed load 8.4, and the input-output of the NES 2-N, which receives the control signal after distribution over all the radio channels, also through the switch 13.2 loaded to a consistent load 8.3. Next, the control signal in the radio channel is amplified by the LNA amplifier 11-i, converted by the 3-i mixer into an intermediate frequency (IF) signal, amplified by the 4-i amplifier and supplied to the control unit 9. In the control unit 9 in node 101, the signals are digitized, the node 102 using the program 102a determines the values of the amplitudes and the phase difference and the signals of the radio channels relative to the reference radio channel corresponding to the first stage. These values are stored in the RAM of the node 102.

The second stage of calibration (3rd option)

Using the commands of the control unit 9, the switch 13.1 is moved to position 2, and the switch 13.2 to position 1. Turn on the generator 6 and the local oscillator 5.

The control signal of the generator 6 through the left shoulder of the power divider 12 is fed to the input 406 of the switch 13.2 and through the output 407 to the input-output of non-directional communication elements, from where it goes to the inputs of the control devices, and through the lateral 208 and main 207 shoulders of the NO with weak connection to all radio channels direction finding device starting from the Nth. The signal of the generator 6, going through the right shoulder of the power divider, is loaded onto the agreed load 8.2, and the input-output of the NES 2-1, which receives the control signal after distribution over all radio channels, is also loaded through the switch 13.1 to the agreed load 8.1. Next, the control signal is converted, as in the first stage of calibration. After completing this step, calibration corrections to the phase differences of the operating mode are determined. The generator 6 does not turn off, and the switches 13.1 and 13.2 are turned on to position 2. In this case, the control generator 6 is loaded through a power divider to the matched loads 8.1 and 8.3 and disconnected from the control channel, the input and output of which are loaded on the matched loads 8.2 and 8.4, respectively.

Direction finding device operating mode (3rd option)

In the operating mode of the direction finder, the switches 13.1 and 13.2 are included in position 2 - the calibration values of the phase differences for the radio channels are algebraically subtracted from the phase differences obtained in the direction finding mode.

Proof of the achievement of the declared technical result The technical result of the invention is the reduction of direction finding errors (improving accuracy) is achieved:

- replacement of the omnidirectional communication of the calibration channel with the radio channels by directional weak communication in the control node (figure 10, 11);

- excluding cables between the input of the calibration signal to the radio channel and the antennas of the radio channel, due to the design of the control unit and without cable connection of the omnidirectional communication element to the control unit with connectors. The cables of the direction finding device are located only in the calibration channel and connect the elements of the NES (2-1 -2-N).

The technical result of the invention is the expansion of the operating range towards high frequencies is achieved due to the design of the control unit.

The design of the directional coupler with weak coupling to the PPL, the coordinated load (12, 13) and the connection of the elements on the PPL with a balancing device on the MPL (Fig. 15) ensure the operability of these elements up to 18 GHz. The cordless connection of the antenna to the control node provides an increase in direction finding accuracy by 7 times (Table, FIG. 17).

Consider the question of improving the accuracy of direction finding of the invention compared to the prototype. Calibration of the radio channel in the prototype does not include a line segment from the input point of the calibration signal to the antenna. This line segment is a cable of a given length. If this segment is performed using a waveguide, which can be done more accurately, we obtain a narrow-band device and do not obtain the required accuracy that the proposed device has, because the column "calibration error" (Fig.2.17) for any additional segment will not be zero.

The maximum error in the manufacture of cables of the same geometric length is 0.5 mm. KSTi reflection from the antenna is at least 2.0. In this case, due to the omnidirectionality of the communication elements, a signal reflected from the antenna with an amplitude of 0.33exp (j * Ф) from the amplitude of the main signal is added to the calibration signal, where Ф is the phase incursion when the signal passes the cable in the forward and reverse directions, which is proportional its electrical length, and a coefficient of 0.33 takes into account the CTF antenna. Thus, the mathematical expression for the calibration signal for each radio channel will have the form:

exp (j * Ψi) * [1 + 0.33 exp (j * Фi)],

where (j * Ψi) is the phase factor taking into account the phase incursion of the signal in the line from the input point of the calibration signal into the calibration channel to the i-th radio channel. This factor does not include the phase incursion of the radio channels from the point of entry into the radio channel of the calibration signal to the antenna. The exp (j * Ψi) factor is compensated during calibration.

We define an additional phase incursion to the calibration value, phase in each channel, which depends on the phase factor 0.33 exp (j * Фi) of the i-th radio channel:

φi = arctan [0.33sin (Фi) / (1 + 0.33cos (Фi)].

The value of Ф corresponds to two phase incursions along the cable length. If the geometric cable length is 5 cm, which is real, then Ф, at frequencies of the order of 2 GHz, can take values up to 2 l. The maximum error of the phase difference of the signals of the reference and calibrated channel is achieved when the signal has the phase Ф ₁ = (2n-1) * π in the reference channel, and the phase Ф ₁ = (2n-1) * π ± δ in the calibrated channel. Moreover, φ ₁ = 0.

φi = arctan (0.33 * sin ((2n-1) * π + δ) / (1 + 0.33cos (2n-1) * π + δ)) ~ 0.5δ.

Thus, in this case Ф ₁ i is of the order of 0.5δ. This is the maximum possible calibration error for the phase of the radio channel, which occurs at a specific cable length and a specific wavelength. Such an error corresponds to such a wavelength, half of which fits at twice the electrical cable length. In our example, two cable lengths are 10 cm, which corresponds to an electric length of 10 * 1.4 = 14 cm, where 1.4 is the wavelength shortening factor in the cable, λ = 28 cm, frequency F = 1.07 GHz. We assume approximately λ = 30 cm, F = 1.0 GHz.

Thus, approximately 10 cm corresponds to 180 °, the error in the length of 0.5 mm * 2, respectively, corresponds to the phase error δ = 1.8 °, i.e. the maximum possible calibration error in the phase of the radio channel at the indicated frequency f ₁ i = 0.9 °.

With a bearing at a frequency (approximately F = 1.0 GHz, λ = 30 cm), an additional error arises due to differences in lengths of the length of the connecting line with the antenna not taken into account when calibrating. An error in the cable length of 0.5 mm gives an error (λ = 30 cm) in phase 360 / (300 / 1.4) * 0.5 = 0.84 °.

This error will increase in proportion to the increase in frequency, and the maximum calibration error will change stepwise. It will change its value when, at the selected cable length, the phase in the reference channel becomes 3π. This will happen at 3 GHz. Moreover, δ = 5.4 °, ΔФ ₁ i ~ 2.7 °.

Thus, you can make the following table for the direction finding error of the prototype (see data for the prototype in the table, Fig.17). The total error does not depend on the direction of arrival of the signals, but depends on the number of the radio channel and frequency.

Calibration of the radio channel in the invention, as well as for the prototype, does not include a segment from the input point of the calibration signal to the antenna. This segment in the invention is a segment 21 - on the circuit board 206 plus a segment 217 on the circuit board 216 of FIG. A balancing device that is not indicated in the prototype relates to an antenna, which we take into account in this calculation only with the help of KCTu.

In the invention, the calibration power supplied to the antenna is 10 dB less than the power supplied during calibration to the radio channel at KCTu = 2. The addition due to the reflection of this signal will decrease by a total of 25 dB; therefore, the influence of the signal reflected from the antenna on the phase of the radio channel signal during calibration can be neglected.

The error in the length of the segments of the boards 210 and 217 in the manufacture of microwave technology is also negligible. Based error is associated with the accuracy of the manufacture of the housing, it is not more than 0.1 mm In the direction finding mode, this can lead to a phase error at a wavelength of 30 cm and a frequency of 1 GHz: Δθ ° = 360 ° × 0.1 / (300/2) = 0.240 °. In the last formula, a deceleration factor of 1.4 for a cable is replaced by a deceleration factor of 2 for a microwave circuit.

For other frequencies, the value of the phase error of direction finding is given in the table of FIG.

The bearing error of the three variants of the invention is the same. The differences are insignificant due to the use of one or two control generators and three or two switches. In the third version, the control generator does not need to be turned off, it is always ready for operation.

From a comparison of the data of the last column of the table (Fig.17) at the same frequencies for the invention and the prototype of the invention, it follows that the direction finding error of the device according to the invention is 7 times less than the direction finding error of the prototype device.

The implementation of the direction finding device

Direction finding device according to the first embodiment of the invention. It consists of N-1 (N = 5) receiving radio channels and contains a control channel. The radio channels and the control channel are connected to a common direction finding device circuit according to the first embodiment (Fig. 4).

Antennas are made spiral. Spiral antennas are assembled in a linear array. Each i-th radio channel consists of a series-connected: antenna 1-i, control node 10-i, LNA 11-i, mixer 3-i and UPCH 4-i. The output of the UPCH 4-i is connected to the input 4-i of the intermediate frequency signal of the control unit BU 9.

Tunable generators 5 and 6 are made on transistors according to the microwave oscillator circuit. At frequencies of 1-2 GHz, a circuit with a common base on a transistor with a varactor diode is used for frequency tuning. At higher frequencies, the oscillator circuit is supplemented by a frequency multiplier and corresponding filters.

The switches 7.1, 7.2 and 7.3 are made according to the scheme of figa.

The low-noise amplifiers of the LNA 11-i are made on field-effect transistors with gates on the Schottky barrier, which interface well with microstrip transmission lines.

Mixers 3-i are made on diodes according to the well-known double balanced microwave circuit, which allows phase suppression of reception through the mirror channel.

Amplifiers of intermediate frequency UPCH 4-i are made on transistors according to the well-known scheme of UPCH.

BU 9 in the first embodiment of the invention has 5 IF inputs and 5 outputs of control signals: a control oscillator 6, a local oscillator 5 and three switches 7.1, 7.2 and 7.3.

The control node is made according to the scheme of figure 10.

The non-directional communication elements 2-i are made in the form of a resistive coupler on the PPL (Fig. 18) with film resistors 505 R = 300 Ohms, with a surface resistance of 100 Ohms / □. PPL elements are made on a polycrust substrate with the same geometric parameters as the elements of the control node 10-i.

The omnidirectional communication element has three connectors: 501, 502 standard sockets (SRG-50-751 ФВ ВРО.364.049 ТУ) and 503 pin (Fig. 19). Inside the connector, there are two line segments with a wave impedance of not equal to 50 ohms. The lengths of coaxials with PTFE filling with a wave resistance of not equal to 50 Ohms are calculated from the condition for compensation of reflections from wave resistance jumps in the working frequency range. The lengths of these segments and the distances between the jumps were optimized to minimize the value of S ₁₁ in the required frequency range. The reflection coefficient optimization results are shown in FIG. The characteristics of the NES are presented in Fig.21. The designations of the curves in Fig.21:

- Δ is the power reflected from the input of the HEC element with a resistive coupler;

- □ - power branched by the resistive element of the NES.

The signal attenuation along the main channel at 18 GHz is of the order of 0.5 dB.

The input-output of element 2-5 is connected by a cable to the input of switch 7.2, the next inputs and outputs of the elements of the NES are interconnected by cables, the last output-input of element 2-N is connected by cable to the input of switch 7.3. Pin connectors 503 are connected directly to standard connectors 228 of the respective control nodes 10-i.

At the first stage of calibration using BU 9, the generator 6 and the local oscillator 5 are turned on, the switches 7.1, 7.2 and 7.3 are turned on when the input 305 is connected to the output 306 (Fig. 16a). The output of the generator 6 is connected through the output of the switch 7.1 with the output 306 of the switch 7.2. and through the input 305 of the switch 7.2 is connected to the input-output of the NES 2-1 of the calibration channel, and the input-output of the NES 2-5 is connected through the input 305 and the output 306 of the switch 7.3. with matched load input 8.2.

The control signal of the generator 6 through the switches 7.1 and 7.2 and the resistive coupler on the PPL (Fig. 18) of the NES element is supplied to the inputs of the control devices and through the NO with weak coupling to all radio channels of the direction finding device, starting from the first. Next, the control signal in the radio channel is amplified by the LNA 11-i, converted by the 3-i mixer into an intermediate frequency (IF) signal, amplified by the 4-i frequency converter and fed to the control unit 9. In the control unit 9 in node 101, the signals are digitized in the node 102, using the program 102a, the amplitudes and phase differences of the signals of the radio channels relative to the reference radio channel corresponding to the first stage are determined. The third channel is selected as the reference channel. At the calibration stage, differences in the amplitudes of the calibration signal in the radio channels are taken into account programmatically. The calibration values of the phase differences of the radio channels are stored in the RAM node 102. Turn off the generator 6.

At the second stage of calibration, using the commands from BU 9, the switches 7.1, 7.2 and 7.3 are put into position when the input 305 is connected to the output 307. At the same time, the output of the generator 6 is connected via switches 7.1 and 7.3 to the input-output of the NES 2-5, and the input -NES output 2-1, through the switch 7.2. connected to the input of the agreed load 8.1. Include a generator 6 and a local oscillator 5.

The control signal of the generator 6 through the switches 7.1 and 7.3 and the resistive coupler on the PPL (Fig. 18) of the NES element is fed to the inputs of the control devices, and through the NO with weak coupling to all radio channels of the direction finding device, starting from the 5th, the control signal is then converted, as in the first stage of calibration. Turn off the generator 6.

After performing the first and second stages of calibration, calibration corrections to the phase differences of the operating mode are calculated by software.

Let us evaluate the error of corrections to the phase difference of the operating mode associated with the input of the calibration signal into each radio channel. This error is determined by the error in the wavelengths from the output of the resistive coupler to the PPL (Fig. 18) of the element of the NES to the input of the BUT with a weak connection of the control node. Recall that the lengths between the resistive couplers do not contribute to the calibration values of the phases of the radio channels.

Since the error in the manufacture of circuit boards in comparison with the error in the mechanical manufacture of the case can be neglected, the phase error in the calibration is determined by the error in the manufacture of two walls of the cases. This thickness is less than 10 mm, and the mechanical manufacturing error is 0.1 mm. Thus, it may introduce further amendments to the table of FIG. The correction table for an example implementation is presented in Fig.22. In the section of the table “For inventions with resistive couplers NES” added the third column and took into account the additive in the column “Total”. The total error was 3.4 times less than the direction finding error in the prototype.

Thus, the declared technical result of the invention is achieved.

Features of the invention Features of the first embodiment.

N control nodes 10-1, 10-2, ..., 10-N each with an input and output of a radio signal and a control signal input, N low-noise amplifiers 11-1, 11-2, ..., 11-N, the third two-channel switch with control input signals and control signal input and two control signal outputs.

The control unit 9 has outputs of the control signals by a local oscillator, a control oscillator and three switches.

Non-directional communication elements 2-1, ... 2-N have one side line output.

In the radio channels, the antennas, control nodes and low-noise amplifiers are connected in series, the outputs of low-noise amplifiers are connected to the signal inputs of the respective mixers, the control signal outputs of the control unit 9 are connected to the corresponding inputs of the control generator, local oscillator, and the inputs of the three switches 7.1,7.2 and 7.3.

The third switch 7.1 control signal input is connected to the output of the control generator 6, the first control signal output of the third switch 7.1 is connected to the control signal input of the second switch 7.3.

The control signal output of the third switch 7.1 is connected to the control signal input of the first switch 7.2, the control signal output-input of which is connected to the input-output of the first communication element 2.1, the control signal output of the first switch 7.2 is connected to the input of the first matched load 8.1.

The second switch 7.3 is connected by the output-input of the control signal with the input-output of the Nth - the last non-directional communication element, the output of the control signal of the second switch is connected to the input of the second matched load 8.2, while the outputs of the matched loads 8.1 and 8.2 are connected to a common ground conductor .

Distinctive features of the second option.

N control nodes 10-1, 10-2, ..., 10-N each with an input and output of a radio signal and an input of a control signal, N low-noise amplifiers 11-1, 11-2, ..., 11-N.

The control unit 9 has outputs of control signals by a local oscillator, control generators and two switches.

Non-directional communication elements 2-1, ... 2-N have one side line output.

In the radio channels, the antennas, control nodes and low-noise amplifiers are connected in series, the outputs of low-noise amplifiers are connected to the inputs of the respective mixers, the control signal outputs of the control unit 9 are connected to the corresponding inputs of the control generator, local oscillator, and the inputs of two dual-channel switches 7.2 and 7.3, while the outputs of the matched loads 8.1 and 8.2 are connected to a common ground conductor.

Distinctive features of the third option.

A power divider 12, third 8.3 and fourth 8.4 matched loads, N control nodes, each with an input and output radio signal and an input of a control signal, N low-noise amplifiers are introduced.

The switches 13.1 and 13.2 are made on three channels and have inputs of control signals and inputs of control signals, outputs and inputs of control signals and two outputs of control signals.

The control signal outputs of the first switch 13.1 are connected respectively to the inputs of the first 8.1 and second 8.2 matched loads, and the control signal outputs of the second switch 13.2 are connected to the inputs of the third 8.3 and fourth 8.4 matched loads.

The control unit 9 has outputs of the control signals by a local oscillator, a control generator and two switches.

Non-directional communication elements have one side line output.

In the radio channels, the antennas, control nodes and low-noise amplifiers are connected in series, the outputs of low-noise amplifiers are connected to the signal inputs of the respective mixers, the control signal outputs of the control unit are connected to the corresponding inputs of the control generator, local oscillator, and switch inputs

The input of the power divider 12 is connected to the output of the control generator 6, its first output of control signals is connected to the input of the control signals of the first switch 13.1, and the second output of control signals is connected to the input of the control signals of the second switch 13.2.

The first switch 13.1 is connected by the output-input of the control signal with the input-output of the first non-directional communication element 2-1, and the second switch 13.2 is connected by the output-input of the control signal with the input-output 2-N of the last non-directional communication element.

Distinctive features of three variants of the invention

The control unit contains a directional coupler, a coordinated load, a balancing device and a two-wire line.

The two-wire line, the balancing device and the main arm of the directional coupler are connected in series.

The agreed load is connected to the output of the lateral arm of the directional coupler.

The input of the two-wire line is the input of the radio channel of the control unit, and the output of the main arm of the directional coupler is the output of the radio channel of the control unit, as well as the output of the control signal.

The input of the lateral arm of the directional coupler is the input of the control signal of the control unit.

Claims (2)

1. A direction finding device, comprising: a control unit, a local oscillator, N receiving radio channels, including N receiving antennas, N omnidirectional communication elements, which are designed to transmit the control signal of the control generator to the inputs of the respective control nodes, have on one side input-output and output- the input on the other side of the main line, which are connected in series with their inputs-outputs and outputs-inputs, N mixers, N intermediate frequency amplifiers, the output of each mixer being connected to the input corresponding intermediate frequency amplifier, the outputs of which are connected to the corresponding inputs of the control unit, a control radio channel consisting of a control generator, two two-channel switches with control inputs and inputs of the control signals and outputs-inputs and outputs of the control signals, two matched loads, the outputs of the switches connected to inputs of the respective coordinated loads, in addition, the output of the local oscillator is connected to the heterodyne inputs of all N mixers, and the control nodes and low-noise amplifiers are connected in series, characterized in that N control nodes are introduced, each with an input and output of a radio signal and a control signal input, wherein the input of each control node is connected to an antenna, N low-noise amplifiers, control nodes and low-noise amplifiers are connected in series, the third two-channel switch with an input of control signals and an input of control signals and two outputs of control signals, and non-directional communication elements have one output of the side line, chrome Moreover, in the radio channels of the antenna, the control nodes and low-noise amplifiers are connected in series, the outputs of low-noise amplifiers are connected to the signal inputs of the respective mixers, the control signal outputs of the control unit are connected to the corresponding inputs of the control generator, local oscillator and the inputs of three switches, and the third switch is connected to the control signals by control generator output, the first control signal output of the third switch is connected to the control signal input and the second switch, in addition, the control signal output of the third switch is connected to the control signal input of the first switch, the control signal output-input of which is connected to the input-output of the first communication element, the second switch connected to the control signal output-input, and the input-output N-th - the last non-directional communication element, while the outputs of the coordinated loads are connected to a common conductor "ground". 2. The direction finding device according to claim 1, characterized in that the control unit comprises a directional coupler, a matching load, a balancing device and a two-wire line, the two-wire line, a balancing device and the main arm of the directional coupler being connected in series, in addition, the matched load is connected to the output the side arm of the directional coupler, the input of the two-wire line being the input of the radio channel of the control unit, and the output of the main arm of the directional coupler is It is output by the radio channel of the control unit, as well as by the output of the control signal, in addition, the input of the lateral arm of the directional coupler is the input of the control signal of the control unit.

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