RU2488945C2 - Method for amplitude, phase and frequency modulation of high-frequency signals and multifunctional apparatus for realising said method - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: method for amplitude, phase and frequency modulation of a high-frequency signal is based on interaction of a high-frequency signal and a low-frequency signal with a multifunctional apparatus for amplitude, phase and frequency modulation of a high-frequency signal, made from a three-terminal nonlinear element, a matching four-terminal element, a complex two-terminal element, a low-frequency control signal source, a high-frequency signal source and a load. The multifunctional apparatus has components given above to enable execution of said procedures, wherein parameters of elements of the matching four-terminal element are selected to be optimum in accordance with given mathematical expressions.

EFFECT: providing amplitude, phase and frequency modulation using one device in accordance with the law of variation of the amplitude of the low-frequency control signal with a longer linear section of the frequency modulation characteristic.

2 cl, 5 dwg

Description

The invention relates to the fields of radio communications, radar, radio navigation and electronic warfare and can be used to provide amplitude, phase and frequency modulation.

A known method of amplitude, phase and frequency modulation of a high-frequency signal, based on the frequency modulation mode by converting the energy of a constant voltage source into energy of a high-frequency signal, organizing external positive feedback between the load and the control electrode of the first nonlinear element, fulfilling the excitation conditions in the form of amplitude balance and balance phases determining respectively the amplitude and frequency of the generated high-frequency signal, and the matching conditions of the first a linear element with a load, changing the frequency of the generated high-frequency signal by changing the phase balance by changing the parameter of the second non-linear element included in the selective load, according to the law of changing the amplitude of the low-frequency control (primary, information) signal (see Gonorovsky I.S. signals - M .: “Bustard.”, - 2006, p. 434-437). In the mode of amplitude and phase modulation, the source of the high-frequency signal is connected to the input of the device and its amplitude and phase are changed.

A device for amplitude and phase modulation and frequency modulation of a high-frequency signal is known, consisting of a constant voltage source that sets an operating point in the middle of a quasilinear section of the current-voltage characteristic of a transistor, a four-terminal reactive load, in the form of a parallel oscillatory circuit, which includes a varicap connected to a control signal source , RC - external positive feedback circuit between the load and the control electrode of the transistor, while the parameters of the circuit, transistor and varicap are selected from the condition of ensuring the specified amplitude and frequency range of the generated high-frequency signal according to the law, changing the amplitude of the low-frequency control (primary, information) signal (see IS Gonorovsky, Radio engineering circuits and signals - M.: “Drofa "., - 2006, - p. 434-437). In the mode of amplitude and phase modulation, the source of the high-frequency signal is connected to the input of the device and its amplitude and phase are changed.

The principle of operation of this device is as follows. In the frequency modulation mode, when a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of a positive feedback circuit, the oscillation with a frequency equal to the resonant frequency of the oscillating circuit is supplied to the control electrode of the transistor, which, by matching with the reactive four-terminal device, starts to operate in the amplification mode until the amplitude of this oscillation increases to the level at which saturation mode (amplitude limits). There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal. In the mode of amplitude and phase modulation, the source of the high-frequency signal is connected to the input of the device and its amplitude and phase are changed under the action of the control signal in the general case according to an uncontrolled law, since the device is synthesized only by the criterion of ensuring frequency modulation.

The closest in technical essence and the achieved result (prototype) is a method of amplitude, phase and frequency modulation of a high-frequency signal, based in the frequency modulation mode on converting the energy of a constant voltage source into the energy of a high-frequency signal, organizing internal feedback in the first nonlinear element by using as of a bipolar nonlinear element with negative differential resistance, the fulfillment of the excitation conditions in the form of a balance amplitudes and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signal, and the conditions for matching the first non-linear element with the load, changing the frequency of the generated high-frequency signal by changing the phase balance by changing the parameter of the second non-linear element included in the selective load, according to the law of changing the low-frequency amplitude control (primary, informational) signal (see Gonorovsky I.S. Radio engineering circuits and signals - M .: "Bustard.", - 2006, p. 414-417, 434-437).). In the mode of amplitude and phase modulation, the source of the high-frequency signal is connected to the input of the device and its amplitude and phase are changed.

The closest in technical essence and the achieved result (prototype) is a device of amplitude, phase and frequency modulation of a high-frequency signal, consisting of a constant voltage source that sets the operating point in the middle of the falling section of the current-voltage characteristics of a bipolar nonlinear element with negative differential resistance, reactive four-terminal, load in in the form of a parallel oscillatory circuit with the varicap turned on, connected to the source I control its signal, while the parameters of the circuit, the bipolar nonlinear element and the varicap are selected from the condition of providing the specified amplitude and frequency range of the generated high-frequency signal according to the law of the amplitude of the low-frequency control (primary, information) signal (see Gonorovsky I.S. Radio engineering circuits and signals - M .: "Bustard.", - 2006, p. 414-417, 434-437).

The principle of operation of this device is as follows. In the frequency modulation mode, when a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback in a bipolar nonlinear element, a negative differential resistance arises in the section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal, compensates for losses in the circuit. Due to this, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond the falling section of the current-voltage characteristic. There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal. In the mode of amplitude and phase modulation, the source of the high-frequency signal is connected to the input of the device and its amplitude and phase are changed.

The disadvantage of this method and device is the presence of two nonlinear elements, one of which works as an amplifier and a limiter, and the second is used in the frequency modulation mode to change the frequency of the generated high-frequency signal and a small linear section of the modulation characteristic due to the smallness of the linear section of the capacitance-voltage characteristic of the varicap. In addition, it does not indicate how it is necessary to choose the values of the parameters of both four-terminal networks, at which the excitation mode and the stationary mode occur. This question arises especially sharply when designing generation and frequency modulation devices in the HF and UHF bands, on which the reactive components of the parameters of nonlinear elements must be taken into account. Currently, the classical theory of radio circuits does not take this into account. In the mode of amplitude and phase modulation, the main disadvantage is the change in the amplitude and phase of the high-frequency signal according to an uncontrolled law, but they must be changed according to the law of change in the amplitude of the low-frequency control signal.

Thus, the main disadvantage of all known methods and devices for modulating the parameters of a high-frequency signal is the inability to effectively perform amplitude, phase and frequency modulation using one device according to the law of changing the amplitude of the low-frequency control signal.

The technical result of the invention is the provision of amplitude, phase and frequency modulation using one device according to the law of changing the amplitude of the low-frequency control signal with an increased linear portion of the frequency modulation characteristic when using one nonlinear element in the frequency modulation mode and with a given ratio of modules and phase difference of the transfer function in two states characterized by two values of the amplitude of the low-frequency control signal in the amplitude mode and phase modulation, which allows you to create efficient compact devices of amplitude, phase and frequency modulation when using a reactive basis with lumped parameters.

1. The specified result is achieved by the fact that in the method of amplitude, phase and frequency modulation of a high-frequency signal, based on the interaction of high-frequency and low-frequency signals with a multifunctional device of amplitude, phase and frequency modulation of a high-frequency signal, made of a nonlinear element matching the four-terminal and load, and In the frequency modulation mode, they convert the energy of a constant voltage source into the energy of a high-frequency signal, organize feedback, satisfy the conditions for the excitation of the stationary generation mode in the form of a balance of amplitudes and phase balance, which respectively determine the amplitude and frequency of the generated high-frequency signal, and the conditions for matching the non-linear element with the load using the matching four-terminal, change the frequency of the generated high-frequency signal by changing the phase balance according to the law of changing the amplitude of the low-frequency signal, in the amplitude and phase modulation mode change the amplitude and phase of the input high-frequency signal and under the influence of a low-frequency control signal, in addition, a three-pole non-linear element is used as a non-linear element, connected between the output of the four-terminal and the load according to a circuit with a common one of the three electrodes, a complex two-terminal is connected parallel to the input of the four-terminal, in the frequency modulation mode, the frequency of the generated high-frequency signal is changed and implemented matching conditions by changing the elements of the resistance matrix of a three-pole nonlinear element under the action of of a high-frequency control signal and providing the conditions for a stationary generation mode in the form of a vanishing of the denominator of the transmission coefficient over the entire range of changes in the elements of the resistance matrix of a three-pole nonlinear element from the amplitude of the low-frequency control signal and in the amplitude and phase modulation mode the amplitude and phase modulation change the amplitude and phase of the output high-frequency signal according to the law of variation of the amplitude of the low-frequency control signal by implementing the given ratios of the modules and the phase differences of the transfer function of the multifunctional device in two states, determined by two values of the amplitude of the low-frequency signal, on a given second frequency variation range by choosing the optimal frequency characteristics of the four-terminal parameters from the conditions for ensuring the physical realizability of these operations in accordance with the following mathematical expressions :

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{11}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

- заданные зависимости действительных и мнимых составляющих элементов матрицы сопротивлений трехполюсного нелинейного элемента от частоты в первом диапазоне изменения частоты и амплитуды низкочастотного управляющего сигнала в режиме частотной модуляции; r_0a, x_0a - заданные частотные зависимости действительной и мнимой составляющих сопротивления комплексного двухполюсника во втором диапазоне изменения частоты в режиме амплитудной и фазовой модуляции, совпадающего с сопротивлением источника высокочастотного гармонического сигнала; r_на, х_на - заданные частотные зависимости действительной и мнимой составляющих сопротивления нагрузки во втором диапазоне изменения частоты в режиме амплитудной и фазовой модуляции; $$r_{11}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{11}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

- заданные зависимости действительных и мнимых составляющих элементов матрицы сопротивлений трехполюсного нелинейного элемента в двух состояниях, определяемых двумя значениями амплитуды низкочастотного управляющего сигнала, от частоты во втором диапазоне изменения частоты в режиме амплитудной и фазовой модуляции; m₂₁, φ₂₁ - заданные частотные зависимости отношения модулей и разности фаз передаточных функций в двух состояниях, определяемых двумя значениями амплитуды низкочастотного управляющего сигнала, во втором диапазоне изменения частоты в режиме амплитудной и фазовой модуляции; остальные обозначения имеют смысл промежуточных обозначений в интересах упрощения математических выражений.a, b, c, d - elements of the classical transmission matrix of a four-terminal network; α, β, γ are the optimal frequency dependences of the relations of the corresponding elements of the classical quadrupole transmission matrix in both modes; a is the optimal frequency dependence of the corresponding element of the classical transmission matrix of the four-terminal network in both modes; r ₀ , x ₀ is the given frequency dependence of the real and the optimal frequency dependence of the imaginary components of the resistance of the complex two-terminal network in the first frequency range in the frequency modulation mode that simulates the resistance of the source of high-frequency signals that occur when the DC voltage source is turned on; r _n , x _n - the given frequency dependences of the real and imaginary components of the load resistance in the first frequency range in the frequency modulation mode; $$r_{\mathrm{eleven}}^{*}$$

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

- the given dependences of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element on frequency in the first range of changes in the frequency and amplitude of the low-frequency control signal in the frequency modulation mode; r _0a , x _0a - given frequency dependences of the real and imaginary components of the resistance of a complex two-terminal network in the second frequency range in the amplitude and phase modulation mode, which coincides with the resistance of the source of a high-frequency harmonic signal; r _on , x _on - given frequency dependences of the real and imaginary components of the load resistance in the second frequency range in the amplitude and phase modulation mode; $$r_{\mathrm{eleven}}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{\mathrm{eleven}}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

- the given dependences of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element in two states, determined by two values of the amplitude of the low-frequency control signal, on the frequency in the second frequency range in the amplitude and phase modulation mode; m ₂₁ , φ ₂₁ are the given frequency dependences of the ratio of the modules and the phase difference of the transfer functions in two states determined by two values of the amplitude of the low-frequency control signal in the second frequency range in the amplitude and phase modulation mode; the remaining notation has the meaning of intermediate notation in the interests of simplifying mathematical expressions.

2. The specified result is achieved by the fact that in a multifunctional device of amplitude, phase and frequency modulation of a high-frequency signal, consisting of a constant voltage source, a nonlinear element, a reactive four-terminal device, a load and a source of a low-frequency control signal, in addition, a three-pole nonlinear element included is used as a nonlinear element between the output of the four-terminal and the load according to the scheme with a common one of the three electrodes, parallel to the input of the four-terminal complex two-terminal, the source of the low-frequency control signal is connected to a three-pole non-linear element, the imaginary component of the resistance of the complex two-terminal is implemented by a series oscillatory circuit with parameters L ₁ , C ₁ parallel connected to the capacitance C ₀ , the reactive four-terminal is made in the form of an overlapped T-shaped connection of four two-terminal, made in the form of two series-connected parallel circuit of elements with parameters _{L 1k, C 1k, L 2k} , C 2k, NOTES x parameters defined in accordance with the following mathematical expression:

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{11n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

- заданные значения действительных и мнимых составляющих элементов матрицы сопротивлений трехполюсного нелинейного элемента на заданных первых трех частотах и соответствующих трех значениях амплитуды низкочастотного управляющего сигнала в режиме частотной модуляции; r_0an, x_0an - заданные значения действительной и мнимой составляющих сопротивления комплексного двухполюсника на заданной четвертой частоте в режиме амплитудной и фазовой модуляции, совпадающего с сопротивлением источника высокочастотного гармонического сигнала; r_нan, x_нan - заданные значения действительной и мнимой составляющих сопротивления нагрузки на заданной четвертой частоте в режиме амплитудной и фазовой модуляции; $$r_{11n}^{I,II}$$

, $$r_{12n}^{I,II}$$

, $$r_{21n}^{I,II}$$

, $$r_{22n}^{I,II}$$

, $$x_{11n}^{I,II}$$

, $$x_{12n}^{I,II}$$

, $$x_{21n}^{I,II}$$

, $$x_{22n}^{I,II}$$

- заданные значения действительных и мнимых составляющих элементов матрицы сопротивлений трехполюсного нелинейного элемента в двух состояниях, определяемых двумя значениями амплитуды низкочастотного управляющего сигнала, на заданной четвертой частоте в режиме амплитудной и фазовой модуляции; m_21n, φ_21n - заданные значения отношения модулей и разности фаз передаточных функций в двух состояниях, определяемых двумя значениями амплитуды низкочастотного управляющего сигнала, на заданной четвертой частоте в режиме амплитудной и фазовой модуляции; x_1n, x_2n, x_3n=x_4n - оптимальные значения сопротивлений двухполюсников перекрытого Т-образного соединения четырех двухполюсников на заданных четырех частотах; k=1, 2, 3, 4 - номера двухполюсников перекрытого Т-образного соединения; остальные обозначения имеют смысл промежуточных обозначений в интересах упрощения математических выражений.a, b, c, d - elements of the classical quadrupole transmission matrix; α, β, γ are the optimal values of the ratios of the corresponding elements of the classical four-terminal transmission matrix in both modes at the given four frequencies ω _n = 2πf _n ; n = 1, 2, 3, 4 - frequency number; d are the optimal values of the corresponding element of the classical quadrupole transmission matrix in both modes at given four frequencies; r _0n , x _0n are the set values of the real and optimal values of the imaginary components of the resistance of the complex two-terminal network in the first frequency range at the given first three frequencies in the frequency modulation mode that simulates the resistance of the source of high-frequency signals that occur when the DC voltage source is turned on; r _nn , x _nn - set values of the real and imaginary components of the load resistance at the given first three frequencies in the frequency modulation mode; $$r_{\mathrm{eleven}n}^{*}$$

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{\mathrm{eleven}n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

- the set values of the real and imaginary components of the resistance matrix of a three-pole non-linear element at the given first three frequencies and the corresponding three values of the amplitude of the low-frequency control signal in the frequency modulation mode; r _0an , x _0an - set values of the real and imaginary components of the resistance of the complex bipolar at a given fourth frequency in the mode of amplitude and phase modulation, which coincides with the resistance of the source of a high-frequency harmonic signal; r _нan , x _нan - set values of the real and imaginary components of the load resistance at a given fourth frequency in the amplitude and phase modulation mode; $$r_{\mathrm{eleven}n}^{I,II}$$

, $$r_{12n}^{I,II}$$

, $$r_{21n}^{I,II}$$

, $$r_{22n}^{I,II}$$

, $$x_{\mathrm{eleven}n}^{I,II}$$

, $$x_{12n}^{I,II}$$

, $$x_{21n}^{I,II}$$

, $$x_{22n}^{I,II}$$

- the set values of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element in two states, determined by two values of the amplitude of the low-frequency control signal, at a given fourth frequency in the amplitude and phase modulation mode; m _21n , φ _21n are the set values of the ratio of the modules and the phase difference of the transfer functions in two states determined by two values of the amplitude of the low-frequency control signal at a given fourth frequency in the amplitude and phase modulation mode; x _1n , x _2n , x _3n = x _4n are the optimal resistance values of the two-terminal circuits of the blocked T-shaped connection of four two-terminal networks at given four frequencies; k = 1, 2, 3, 4 - numbers of two-terminal circuits of the closed T-shaped connection; the remaining notation has the meaning of intermediate notation in the interests of simplifying mathematical expressions.

Figure 1 shows a diagram of a multifunctional device for amplitude, phase and frequency modulation of high-frequency signals (prototype) that implements the prototype method.

Figure 2 shows the structural diagram of the proposed multifunctional device of the amplitude, phase and frequency modulation of high-frequency signals according to claim 2., Which implements the proposed method according to claim 1.

In Fig.3 shows a diagram of a four-terminal network in the form of an overlapped T-link included in the proposed device, a diagram of which is presented in Fig.2.

Figure 4 shows a diagram of the first, second, third and fourth reactive bipolar included in the four-terminal, a diagram of which is presented in figure 3.

Figure 5 shows a diagram of the formation of a two-terminal, characterizing the imaginary component of the load resistance.

The prototype device (Figure 1), which implements the prototype method, contains a non-linear element-1 with negative differential resistance, connected to a voltage source-2 with low internal resistance, matching filtering device-3 (reactive four-terminal), the load is in the form of an oscillatory contour on the elements L-4, R-5, C (t) -6. The controlled capacitance C (t) realized by the varicap -6 is connected to the source of the low-frequency control (information) signal-7. The principle of operation of the device for generating and modulating high-frequency signals (prototype) that implements the prototype method is as follows.

When you turn on the DC voltage source (2), due to the abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback, in a bipolar nonlinear element, for example, tunnel diode-1, a negative differential resistance arises in the section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal-3, compensates for losses in the circuit L-4, R- 5, C (t) -6. Due to this, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond the falling section of the current-voltage characteristic. There is a stationary mode. In this mode, a change in the capacitance of varicap C (t) -6 under the action of the control signal of source-7 leads to a change in the frequency of the generated signal according to the law of the amplitude of this signal in the first frequency range. This is the frequency modulation mode. In the amplitude and phase modulation mode in a different frequency range, the amplitude and phase of the output high-frequency signal changes under the influence of the low-frequency control signal in the general case according to an uncontrolled law.

The remaining disadvantages of the prototype method and device for its implementation are described above.

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{11n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

в режиме частотной модуляции и с заданными значениями элементов матрицы сопротивлений $$r_{11}^{I,II},$$

$$r_{12}^{I,II},$$

$$r_{21}^{I,II},$$

$$r_{22}^{I,II},$$

$$x_{11}^{I,II},$$

$$x_{12}^{I,II},$$

$$x_{21}^{I,II},$$

$$x_{22}^{I,II}$$

в двух состояниях в режиме амплитудной и фазовой модуляции на заданных частотах, подключенный к источнику низкочастотного управляющего напряжения с постоянной составляющей-9 и включенный по высокой частоте по схеме с общим одним из трех электродов между выходом четырехполюсника (согласующе-фильтрующего устройства (СФУ))-3 и нагрузкой-10 с сопротивлением z_нn=r_нn+jx_нn на заданных частотах. Четырехполюсник-3 выполнен в виде перекрытого Т-образного соединения четырех двухполюсников (Фиг.3) с сопротивлениями x_1n-11, x_2n-12, x_3n-13, x_4n=x_3n-14. К входу четырехполюсника-3 параллельно (при анализе и синтезе вместо источника высокочастотного сигнала необходимо учитывать короткозамыкающую перемычку) подключен комплексный двухполюсник-8 с сопротивлением z_0n=r_0n+jx_0n на заданных трех частотах, имитирующим в режиме частотной модуляции сопротивление источника высокочастотных колебаний, возникающих при включении источника низкочастотного управляющего напряжения с постоянной составляющей-9 в момент скачкообразного изменения амплитуды его напряжения и сопротивление источника входного высокочастотного сигнала в режиме амплитудной и фазовой модуляции z_0an=r_0an+jx_0an на четвертой частоте. Мнимая составляющая сопротивления комплексного двухполюсника сформирована двухполюсником из последовательного колебательного контура, параллельно соединенного с емкостью. Синтез этого двухполюсника осуществлен по критерию обеспечения всех режимов с помощью одного устройства (см. ниже). Синтез четырехполюсника (выбор значений сопротивлений-11, 12, 13, 14 первого, второго, третьего и четвертого двухполюсников перекрытого Т-образного соединения (Фиг.3) на четырех заданных частотах (n=1, 2, 3, 4 - номер частоты) и схемы формирования этих двухполюсников из последовательно соединенных двух параллельных контуров (Фиг.4) и значений параметров контуров) осуществлен по критерию обеспечения баланса амплитуд и баланса фаз путем реализации равенства нулю знаменателя коэффициента передачи устройства многофункционального устройства в режиме частотной демодуляции на первых трех из четырех частотах заданного диапазона изменения частоты генерируемого сигнала и трех значениях амплитуды низкочастотного управляющего сигнала соответственно и по критерию обеспечения заданных отношений модулей и разностей фаз передаточной функции на четвертой (несущей) частоте входного высокочастотного гармонического сигнала и двух значениях амплитуды низкочастотного управляющего сигнала в режиме амплитудной и фазовой модуляции.The proposed device according to claim 2 (figure 2), which implements the proposed method according to claim 1, contains a three-pole non-linear element-1 with preset values of the elements of the resistance matrix $$r_{\mathrm{eleven}n}^{*}$$

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{\mathrm{eleven}n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

in the frequency modulation mode and with the given values of the elements of the resistance matrix $$r_{\mathrm{eleven}}^{I,II},$$

$$r_{12}^{I,II},$$

$$r_{21}^{I,II},$$

$$r_{22}^{I,II},$$

$$x_{\mathrm{eleven}}^{I,II},$$

$$x_{12}^{I,II},$$

$$x_{21}^{I,II},$$

$$x_{22}^{I,II}$$

in two states in the mode of amplitude and phase modulation at specified frequencies, connected to a source of low-frequency control voltage with a constant component of-9 and turned on at a high frequency according to a circuit with a common one of three electrodes between the output of a four-terminal device (matching filtering device (SFU)) - 3 and load-10 with resistance z _нn = r _нn + jx _нn at given frequencies. Four-terminal-3 is made in the form of an overlapped T-shaped connection of four two-terminal (Fig. 3) with resistances x _1n -11, x _2n -12, x _3n -13, x _4n = x _3n -14. A four-terminal-8 complex with a resistance z _0n = r _0n + jx _0n at three given frequencies simulating the resistance of a high-frequency oscillation source in the frequency modulation mode is connected to the input of a four-terminal-3 in parallel (during analysis and synthesis, instead of a high-frequency signal source, it is necessary to take into account a short-circuit jumper) arising when you turn on the source of low-frequency control voltage with a constant component of-9 at the time of an abrupt change in the amplitude of its voltage and the resistance of the input of the high-frequency signal in the amplitude and phase modulation mode z _0an = r _0an + jx _0an at the fourth frequency. The imaginary component of the resistance of a complex bipolar is formed by a bipolar from a sequential oscillatory circuit connected in parallel with the capacitance. The synthesis of this two-terminal device was carried out according to the criterion of ensuring all modes using a single device (see below). Synthesis of a four-terminal network (selection of resistance values -11, 12, 13, 14 of the first, second, third, and fourth two-terminal networks of a closed T-shaped connection (Figure 3) at four given frequencies (n = 1, 2, 3, 4 - frequency number) and circuits for the formation of these two-terminal circuits from two parallel parallel circuits (Fig. 4) and the values of the circuit parameters) is carried out according to the criterion for ensuring the balance of amplitudes and phase balance by implementing the denominator of the transmission coefficient of the multifunction device in zero mode frequency demodulation at the first three of the four frequencies of a given frequency range of the generated signal and the three values of the amplitude of the low-frequency control signal, respectively, and according to the criterion for ensuring the given ratios of modules and phase differences of the transfer function at the fourth (carrier) frequency of the input high-frequency harmonic signal and two values of the amplitude of the low-frequency control signal in the amplitude and phase modulation mode.

The proposed device operates as follows. In the frequency modulation mode, when the low-frequency control voltage source with a constant component of 9 is turned on, oscillations occur over the entire circuit due to the abrupt change in the amplitude, the spectrum of which occupies the entire frequency radio frequency range. The amplitudes of these oscillations decay quickly. However, due to the presence of feedback, in the three-pole non-linear element-1, negative differential resistance occurs, which, due to the synthesis of the four-terminal-3 according to a given criterion, compensates for losses in the entire circuit. The amplitude of the oscillation with a given frequency is amplified to a certain level and then limited. The synthesis of four-terminal-3 was carried out according to the criterion for the coincidence of the real frequency dependences of the resistances of all two-terminal at four frequencies with optimal characteristics that provide a change in the frequency of the generated signal according to the law corresponding to the law of change in the amplitude of the variable component of the signal (low-frequency control signal) of source-9. Due to this, the oscillation with a given carrier frequency is amplified until the amplitude of this oscillation is limited by the non-linearity of the current-voltage characteristic. There is a stationary mode. In this mode, the change in the real and imaginary components of the resistance of the nonlinear element-1 under the action of the variable component of the signal source-9. leads to a change in the frequency of the generated signal according to the law of change in the amplitude of this signal. Source-9 can be replaced by two sources - a source of constant voltage and a source of low-frequency control signal. In the amplitude and phase modulation mode, the specified ratios of the modules and the phase differences of the transfer function are provided at two values of the amplitude of the low-frequency control signal and at the carrier frequency of the input high-frequency harmonic signal. A continuous change in the amplitude of the low-frequency control signal from one state to another provides modulation of the amplitude and phase of the output high-frequency harmonic signal according to the law of change in the amplitude of the low-frequency control signal at the carrier frequency.

Let us prove the feasibility of implementing these properties.

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{11}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

от частоты в заданном диапазоне изменения частоты генерируемого сигнала, соответствующие закону изменения амплитуды низкочастотного управляющего сигнала. Таким образом, каждому заданному значению амплитуды низкочастотного сигнала соответствуют определенные значения элементов матрицы сопротивлений трехполюсного нелинейного элемента $$r_{11}^{*}$$

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{11}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

, соответствующие определенному значению частоты генерируемого сигнала на заданном диапазоне ее изменения. Для простоты записи аргументы ω=2πf (круговая частота) и U, I (напряжение или ток амплитуды низкочастотного сигнала) опущены.Let the frequency dependence of the source resistance of a high-frequency signal Z ₀ = r ₀ + jx ₀ on frequency be known in the frequency modulation mode. The dependence of the load resistance-11 Z _n = r _n + jx _n on frequency is also known. In addition, the dependences of the real and imaginary components of the resistance matrix of a three-pole nonlinear element are known $$r_{\mathrm{eleven}}^{*}$$

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

from the frequency in a given range of changes in the frequency of the generated signal, corresponding to the law of change in the amplitude of the low-frequency control signal. Thus, each given value of the amplitude of the low-frequency signal corresponds to certain values of the elements of the resistance matrix of a three-pole nonlinear element $$r_{\mathrm{eleven}}^{*}$$

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

corresponding to a certain value of the frequency of the generated signal over a given range of its change. For simplicity of writing, the arguments ω = 2πf (circular frequency) and U, I (voltage or current amplitude of the low-frequency signal) are omitted.

Thus, the transistor resistance matrix is known:

или $$r_{12}^{*}$$

имеют отрицательный знак [Батушев В.А., Вениаминов В.Н., Мирошниченко А.И. Электронные элементы военной техники связи. М., Воениздат, 1984. С.424.], поэтому при определенных условиях можно генерировать собственный высокочастотный сигнал.Items $$r_{2\mathrm{one}}^{*}$$

or $$r_{\mathrm{one}2}^{*}$$

have a negative sign [Batushev V.A., Veniaminov V.N., Miroshnichenko A.I. Electronic elements of military communications equipment. M., Military Publishing House, 1984. P.424.], Therefore, under certain conditions, you can generate your own high-frequency signal.

The sign * is introduced in the interest of distinguishing the corresponding constituent elements of the resistance matrix of a three-pole nonlinear element in the frequency modulation mode from the elements of the known resistance matrix of a reactive four-port network and from the elements of the resistance matrix of a nonlinear element in the amplitude and phase modulation mode.

Let the quadrupole contain only reactive elements. Thus, taking into account the reciprocity condition (x ₁₂ = -x ₂₁ ), the SFU can be characterized by a resistance matrix

последнее выражение изменяется а₁=r_н; b₁=x_н.After denormalizing the transmission coefficient (6) by multiplying by $$\sqrt{\frac{z_n}{z_o}}$$

the last expression changes a ₁ = r _n ; b ₁ = x _n

.The denormalized transmission coefficient is associated with a physically feasible transfer function as follows H $$\left(j\omega \right)=\frac{\mathrm{one}}{2}{S}_{21}^{*}$$

.

The condition for ensuring the stationary generation regime (the condition of the balance of amplitudes and phase balance) corresponds to the equalization of the denominator of the transmission coefficient (6). After dividing the complex equation formed from this equality into real and imaginary parts, we get a system of two equations:

In the interest of further reasoning, by using the known relations between the elements of the resistance matrix and the elements of the classical transmission matrix, we write the relationships (8) in terms of the elements of the classical transmission matrix (the order of the equations obtained in the future decreases):

$$\alpha =\left(x_0-E\right)\gamma -D;\beta =F\gamma -E-x_0,\left(9\right)$$

; $$\beta =\frac{b}{d}$$

; $$\gamma =\frac{c}{d}$$

; a, b, c, d - элементы классической матрицы передачи СФУ.Where $$\alpha =\frac{a}{d}$$

; $$\beta =\frac{b}{d}$$

; $$\gamma =\frac{c}{d}$$

; a, b, c, d - elements of the classical transmission matrix of SFU.

$$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{11}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

являются оптимальными аппроксимирующими функциями частотных зависимостей соответствующих элементов матрицы сопротивлений СФУ.The resulting relationship (9), taking into account the given frequency dependences r ₀ , x ₀ , r _n , x _n , $$r_{\mathrm{eleven}}^{*}$$

$$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

are optimal approximating functions of the frequency dependences of the corresponding elements of the matrix of resistances of SFU.

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{11}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

в двух состояниях, определяемых двумя уровнями управляющего воздействия, от частоты. Полоса частот в этом режиме отличается от полосы частот в режиме частотной модуляции.Suppose that in a mode of the amplitude and phase modulation depending source known high harmonic signal _0a z = r + jx _{0a 0a,} load _nA z = r + jx _{nA nA} and the real and imaginary components of the elements of the matrix resistors tripolar managed nonlinear element $$r_{\mathrm{eleven}}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{\mathrm{eleven}}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

in two states determined by two levels of control action, from frequency. The frequency band in this mode is different from the frequency band in the frequency modulation mode.

It is required to determine the frequency characteristics of the SFU and two-terminal parameters forming the four-terminal network, the minimum number of elements and the values of the parameters of the matching filtering device (SFU) on the reactive elements, in which the switching of the controlled element from one state to another would unambiguously lead to a change in the module and phase of the transfer coefficient according to the following law:

$$S_{21}^I=m_{21}\left(\cos {\varphi }_{21}+j\sin {\varphi }_{21}\right)S_{21}^{II}\left(10\right)$$

; $${\varphi }_{21}={\varphi }_{21}^I-{\varphi }_{21}^{II};$$

$$M=\frac{1-m_{21}}{1+m_{21}}$$

, $$m_{21}<1;$$

$$M=\frac{m_{21}-1}{m_{21}+1}$$

, $$m_{21}>1;$$

$$\Delta \varphi =\frac{{\varphi }_{21}}{2}$$

- требуемые частотные зависимости отношения модулей, разности фаз коэффициентов передачи $$S_{21}^I$$

, $$S_{21}^{II}$$

в двух состояниях управляемого нелинейного элемента, коэффициента амплитудной модуляции и девиации фазы. При m₂₁=1 имеем чисто фазовую модуляцию, а при φ₂₁=0 - амплитудную.Where $${\text{m}}_{\text{21}}=\left|S_{21}^I\right|/\left|S_{21}^{II}\right|$$

; $${\varphi }_{21}={\varphi }_{21}^I-{\varphi }_{21}^{II};$$

$$M=\frac{\mathrm{one}-m_{21}}{\mathrm{one}+m_{21}}$$

, $$m_{21}<\mathrm{one};$$

$$M=\frac{m_{21}-\mathrm{one}}{m_{21}+\mathrm{one}}$$

, $$m_{21}>\mathrm{one};$$

$$\Delta \varphi =\frac{{\varphi }_{21}}{2}$$

- the required frequency dependencies of the ratio of the modules, the phase difference of the transmission coefficients $$S_{21}^I$$

, $$S_{21}^{II}$$

in two states of a controlled nonlinear element, amplitude modulation coefficient and phase deviation. For m ₂₁ = 1, we have pure phase modulation, and for φ ₂₁ = 0, we have amplitude modulation.

Given the reciprocity condition (x ₁₂ = -x ₂₁ ), the SFU can be characterized by a resistance matrix (3) and the corresponding classical transmission matrix (4).

Let the transistor resistance matrix in two states, determined by two levels of the low-frequency control signal, be known at a fixed frequency

In the interest of further reasoning, by using the known relations between the elements of the resistance matrix and the elements of the classical transmission matrix, we write the relationships (8) in terms of the elements of the classical transmission matrix (the order of the equations obtained in the future decreases):

$$\alpha =\left(x_0-E_m\right)\gamma -D_m;\beta =F_m\gamma -E_m-x_0,\left(17\right)$$

; $$\beta =\frac{b}{d}$$

; $$\gamma =\frac{c}{d}$$

; a, b, c, d - элементы классической матрицы передачи СФУ.Where $$\alpha =\frac{a}{d}$$

; $$\beta =\frac{b}{d}$$

; $$\gamma =\frac{c}{d}$$

; a, b, c, d - elements of the classical transmission matrix of SFU.

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{11}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

являются также оптимальными по критерию (10) аппроксимирующими функциями частотных зависимостей этих элементов.Relations (17) taking into account the frequency dependences r_0a, x_0a, r_on, x_on, $$r_{\mathrm{eleven}}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{\mathrm{eleven}}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

are also optimal according to criterion (10) by approximating functions of the frequency dependences of these elements.

In order for the same device to perform the functions of an amplitude, phase, and frequency modulator, it is sufficient that the optimal relationships (9) and (17) are equal in pairs (the solutions obtained for the frequency modulation mode and for the amplitude and phase modulation mode are stitched together). From these equalities and the conditions of physical realizability (reciprocity conditions (α + βγ) d ² = 1), there are restrictions on the frequency characteristics of two more elements of the classical transmission matrix and the imaginary component of the load resistance:

$$\gamma =\frac{E_a-E+x_{0\mathrm{but}}-x_0}{F_a-F}=\frac{D-D_a}{E_a-E-x_{0a}+x_0};d=\frac{\mathrm{one}}{\pm \sqrt{\alpha +\beta \gamma }};x_0=x_{0a}\pm \sqrt{{\left(E-E_a\right)}^2+\left(F-F_a\right)\left(D-D_a\right)}.\left(\mathrm{eighteen}\right)$$

Relationships (9), (18) or (17), (18) in addition, mean that for the implementation of approximating functions it is necessary that the SFU contain at least three independent two-terminal networks, the frequency dependences of the resistances of which should be determined from the solution of the systems of three equations, formed on the basis of relationships (9), (18) or (17), (18). To do this, it is necessary to take a sample typical SFU scheme, find the transfer matrix of this scheme and the elements α, β, γ found in this way (the element d is dependent on the reciprocity condition), expressed through the parameters of the scheme, substitute in (9), (18) or (17), (18) and solve the formed system of three equations with respect to the resistances of the selected three two-terminal networks.

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{11}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

, r_0a, x_0a, r_нa, x_на, $$r_{11}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{11}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

и оставшихся двухполюсников СФУ (если число двухполюсников больше трех) могут быть выбраны произвольно или исходя из каких-либо других физических соображений.The frequency characteristics of the remaining parameters r ₀ , x ₀ , r _n ,, $$r_{\mathrm{eleven}}^{*}$$

, $$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

, R _0a, x _0a, r _{nA, in the} x, $$r_{\mathrm{eleven}}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{\mathrm{eleven}}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

and the remaining two-terminal SFUs (if the number of two-terminal more than three) can be chosen arbitrarily or on the basis of any other physical considerations.

In accordance with the above algorithm, expressions are obtained for finding optimal approximations of the frequency dependences of the resistances of the first, second, and third (equal to the resistance of the fourth) two-terminal SFUs in the form of an overlapped T-shaped connection of four reactive two-terminal devices:

$$x_{\mathrm{one}n}=\frac{\left(\alpha +2-3Q\right)\left(\alpha -Q\right)}{\left(Q-\mathrm{one}\right)\gamma };x_{2n}=\frac{\alpha -2Q}{\gamma };x_{3n}=x_{\mathrm{four}n}=\frac{3Q-\alpha -2}{\gamma };Q=\pm \sqrt{\alpha +\beta \gamma },\left(19\right)$$

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{11n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

, r_0an, x_0an, r_нan, x_нan, $$r_{11n}^{I,II}$$

, $$r_{12n}^{I,II}$$

, $$r_{21n}^{I,II}$$

, $$r_{22n}^{I,II}$$

, $$x_{11n}^{I,II}$$

, $$x_{12n}^{I,II}$$

, $$x_{21n}^{I,II}$$

, $$x_{22n}^{I,II}$$

, m_21n, φ_21n и другие.where n = 1, 2 ... are the numbers of the interpolation frequencies. The radical expression in (19) is always positive. The index n must be entered into the other given and calculated quantities r _0n , x _0n , r _нn , x _нn , $$r_{\mathrm{eleven}n}^{*}$$

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{\mathrm{eleven}n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

, r _0an , x _0an , r _nan , x _nan , $$r_{\mathrm{eleven}n}^{I,II}$$

, $$r_{12n}^{I,II}$$

, $$r_{21n}^{I,II}$$

, $$r_{22n}^{I,II}$$

, $$x_{\mathrm{eleven}n}^{I,II}$$

, $$x_{12n}^{I,II}$$

, $$x_{21n}^{I,II}$$

, $$x_{22n}^{I,II}$$

, m _21n , φ _21n and others.

To ensure that the optimal frequency dependences (19) coincide with the real frequency characteristics, it is necessary to form two-terminal networks with resistances x _1n , x _2n , x _3n = x _4n from at least N (the number of interpolation frequencies) of the reactive elements, find expressions for their resistances, and equate their optimal values of the two-terminal resistances at given frequencies determined by formulas (19) and solve the system of N equations thus formed that relates to the N selected reactive element parameters. This is an interpolation method. The values of the parameters of the remaining elements can be chosen arbitrarily or on the basis of any other physical considerations, for example, from the condition of physical realizability. Let each of the two-terminal networks with resistances x _1n , x _2n , x _3n = x _{4n be} formed from two parallel-connected parallel circuits L _1k , C _1k , L _2k , C _2k (k = 1, 2, 3, 4 - the number of the two-terminal network (Fig. .four)). For N = 4, we compose three (the fourth system is equivalent to the third) system of four equations:

A similar problem must be solved with respect to ensuring that the optimal frequency dependence (18) coincides with the imaginary component x _{0 of the} resistance of the imaginary source of the high-frequency signal that occurs when the DC voltage source is turned on, with real frequency characteristics at three frequencies in the frequency modulation mode. Let the two-terminal network with an imaginary component x _{0 of the} resistance of the signal source be formed from a sequential oscillatory circuit with parameters L ₁ , C ₁ connected in parallel with the capacitance C ₀ (Fig. 5). We compose a system of three equations:

At the fourth frequency, the imaginary component of the load resistance in the amplitude and phase modulation mode can take an arbitrary value x _0a .

The implementation of the optimal approximations of the frequency characteristics of the two-terminal circuits of the four-terminal network in the form of an overlapped T-link (19) using (21) and the optimal approximations of the frequency characteristics x ₀ (18) using (23) provides an increase in the frequency range of the generated signal, since it implements the condition of amplitude balance and phase balance at three frequencies of a given modulation characteristic or a given range of frequency changes in the frequency modulation mode. This allows for a reasonable choice of the positions of the first three preset frequencies relative to each other to expand the linear portion of the modulation characteristic. In the amplitude and phase modulation mode, the specified ratios of the modules and the phase difference of the transfer function in two states, determined by two values of the amplitude of the low-frequency control signal, at the carrier frequency of the high-frequency harmonic signal, will be realized. With a reasonable choice of two values of the amplitude of the low-frequency control signal and with a continuous change in the amplitude of the low-frequency control signal from the first value to the second, the amplitude and phase modulation mode will be implemented according to the law of change of the amplitude of the low-frequency control signal at the carrier frequency.

The proposed technical solutions are of an inventive step, since it does not explicitly follow from the published scientific data and the known technical solutions that the claimed sequence of operations (performing a four-terminal reactive in the form of the four two-terminal connected in the above manner, forming the first, second and third and fourth equivalent third, two-terminal from two parallel circuits connected in series, the choice of values of their parameters from the conditions of provision I stationary generation at three predetermined frequencies when changing the state of a nonlinear three-pole element connected between the output of the reactive four-terminal according to a circuit with a common one of three electrodes and the load, connecting a complex two-terminal parallel to the input of a four-terminal, forming a two-terminal, characterizing the imaginary component of the resistance of a complex two-terminal, from a serial oscillatory circuit parallel to the capacitance) provides modulation of the frequency of the generator signal under the law of variation of the amplitude of the low-frequency signal in the frequency modulation mode, and also implements a given ratio of modules and a given phase difference of the transfer function in two states determined by two values of the amplitude of the low-frequency control signal, and modulation of the amplitude and phase of the high-frequency signal at the fourth frequency according to the law of change the amplitude of the low-frequency control signal when it continuously changes from the first value to the second in the amplitude and phase modulation mode.

The proposed technical solutions are practically applicable, since for their implementation three-pole non-linear elements commercially available by the industry, for example, transistors, inductors and capacitors, formed into the claimed reactive four-terminal circuit, can be used. The values of the parameters of the inductances and capacitances of the oscillatory circuits can be uniquely determined using mathematical expressions given in the claims.

The technical and economic efficiency of the proposed method and device consists in providing frequency modulation of a high-frequency signal in one frequency band and amplitude and phase modulation in another frequency band according to the law of changing the amplitude of a low-frequency signal using one device by optimizing the values of the parameters of the reactive elements according to the criterion of ensuring the listed functions , which reduces the nomenclature of radio devices and unifies them in the interests of production.

Claims (2)

1. The method of amplitude, phase and frequency modulation of a high-frequency signal based on the interaction of high-frequency and low-frequency signals with a multifunctional device of amplitude, phase and frequency modulation of a high-frequency signal made of a nonlinear element matching a four-terminal network and a load, and in the frequency modulation mode, the energy of a constant source is converted voltage into the energy of a high-frequency signal, organize feedback, fulfill the conditions for the excitation of a stationary signal the generation frequency in the form of a balance of amplitudes and phase balance, which respectively determine the amplitude and frequency of the generated high-frequency signal, and the conditions for matching the non-linear element with the load using the matching four-terminal, change the frequency of the generated high-frequency signal by changing the phase balance according to the law of the amplitude of the low-frequency control signal, in the mode amplitude and phase modulation change the amplitude and phase of the input high-frequency signal under the influence of low-frequency control o signal, characterized in that a three-pole non-linear element is used as a non-linear element, connected between the output of the four-terminal and the load according to a circuit with a common one of three electrodes, a complex two-terminal is connected parallel to the input of the four-terminal, in the frequency modulation mode, the frequency of the generated high-frequency signal is changed and conditions are met coordination by changing the elements of the resistance matrix of a three-pole nonlinear element under the action of a low-frequency control signal and providing the conditions for a stationary generation mode in the form of equal to zero the denominator of the transmission coefficient over the entire range of changes of the elements of the resistance matrix of a three-pole nonlinear element from the amplitude of the low-frequency control signal and for a given first range of changes in the frequency of the generated signal, in the amplitude and phase modulation mode change the amplitude and phase of the output high-frequency signal according to the law of changing the amplitude of the low-frequency control signal by implementing the specified relations modules and phase differences of the transfer function of the multifunctional device in two states, determined by two values of the amplitude of the low-frequency signal, on a given second range of frequency changes by selecting the optimal frequency characteristics of the parameters of the four-terminal network from the condition of ensuring the physical realizability of the above operations in accordance with the following mathematical expressions:

a, b, c, a - elements of the classical quadrupole transmission matrix; α, β, γ are the optimal frequency dependences of the relations of the corresponding elements of the classical quadrupole transmission matrix in both modes; d is the optimal frequency dependence of the corresponding element of the classical quadrupole transmission matrix in both modes; r ₀ , x ₀ is the given frequency dependence of the real and the optimal frequency dependence of the imaginary components of the resistance of the complex two-terminal network in the first frequency range in the frequency modulation mode that simulates the resistance of the source of high-frequency signals that occur when the DC voltage source is turned on; r _n , x _n - given frequency dependences of the real and imaginary components of the load resistance in the first frequency range in the frequency modulation mode; $$r_{\mathrm{eleven}}^{*}$$

$$r_{12}^{*}$$

, $$r_{21}^{*}$$

, $$r_{22}^{*}$$

, $$x_{\mathrm{eleven}}^{*}$$

, $$x_{12}^{*}$$

, $$x_{21}^{*}$$

, $$x_{22}^{*}$$

- the given dependences of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element on frequency in the first range of changes in the frequency and amplitude of the low-frequency control signal in the frequency modulation mode; r _0a , x _0a - given frequency dependences of the real and imaginary components of the resistance of a complex two-terminal network in the second frequency range in the amplitude and phase modulation mode, which coincides with the resistance of the source of a high-frequency harmonic signal; r _on , x _on - the given frequency dependences of the real and imaginary components of the load resistance in the second frequency range in the amplitude and phase modulation mode; $$r_{\mathrm{eleven}}^{I,II}$$

, $$r_{12}^{I,II}$$

, $$r_{21}^{I,II}$$

, $$r_{22}^{I,II}$$

, $$x_{\mathrm{eleven}}^{I,II}$$

, $$x_{12}^{I,II}$$

, $$x_{21}^{I,II}$$

, $$x_{22}^{I,II}$$

- the given dependences of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element in two states, determined by two values of the amplitude of the low-frequency control signal, on the frequency in the second frequency range in the amplitude and phase modulation mode; m ₂₁ , φ ₂₁ are the given frequency dependences of the ratio of the modules and the phase difference of the transfer functions in two states determined by two values of the amplitude of the low-frequency control signal in the second frequency range in the amplitude and phase modulation mode; the remaining notation has the meaning of intermediate notation in the interests of simplifying mathematical expressions. 2. A multifunctional device for amplitude, phase and frequency modulation of a high-frequency signal, consisting of a constant voltage source, a nonlinear element, a reactive four-terminal device, a load and a low-frequency control signal source, characterized in that a three-pole nonlinear element connected between the output of the four-terminal device and used is a nonlinear element the load according to the circuit with a common one of the three electrodes, parallel to the input of the four-terminal integrated complex two-terminal, source the low-frequency control signal is connected to a three-pole nonlinear element, the imaginary component of the resistance of the complex two-terminal is realized by a series oscillatory circuit with parameters L ₁ , C ₁ connected in parallel with the capacitance C ₀ , the reactive four-terminal is made in the form of an overlapped T-shaped connection of four two-terminal, made in the form of two connected in parallel parallel circuits of elements with parameters L _1k , C _1k , L _2k , C _2k , the values of these parameters are determined in accordance Twi with the following mathematical expressions:

a, b, c, d - elements of the classical quadrupole transmission matrix; α, β, γ are the optimal values of the ratios of the corresponding elements of the classical four-terminal transmission matrix in both modes at the given four frequencies ω _n = 2πf _n ; n = 1, 2, 3, 4 - frequency number; d are the optimal values of the corresponding element of the classical quadrupole transmission matrix in both modes at given four frequencies; r _0n , x _0n are the set values of the real and optimal values of the imaginary components of the resistance of the complex two-terminal network in the first frequency range at the given first three frequencies in the frequency modulation mode that simulates the resistance of the source of high-frequency signals that occur when the DC voltage source is turned on; r _nn , x _nn - set values of the real and imaginary components of the load resistance at the given first three frequencies in the frequency modulation mode; $$r_{\mathrm{eleven}n}^{*}$$

, $$r_{12n}^{*}$$

, $$r_{21n}^{*}$$

, $$r_{22n}^{*}$$

, $$x_{\mathrm{eleven}n}^{*}$$

, $$x_{12n}^{*}$$

, $$x_{21n}^{*}$$

, $$x_{22n}^{*}$$

- the set values of the real and imaginary components of the resistance matrix of a three-pole non-linear element at the given first three frequencies and the corresponding three values of the amplitude of the low-frequency control signal in the frequency modulation mode; r _0an , x _0an - set values of the real and imaginary components of the resistance of the complex bipolar at a given fourth frequency in the mode of amplitude and phase modulation, which coincides with the resistance of the source of a high-frequency harmonic signal; r _нan , x _наn - set values of the real and imaginary components of the load resistance at a given fourth frequency in the amplitude and phase modulation mode; $$r_{\mathrm{eleven}n}^{I,II}$$

, $$r_{12n}^{I,II}$$

, $$r_{21n}^{I,II}$$

, $$r_{22n}^{I,II}$$

, $$x_{\mathrm{eleven}n}^{I,II}$$

, $$x_{12n}^{I,II}$$

, $$x_{21n}^{I,II}$$

, $$x_{22n}^{I,II}$$

- the set values of the real and imaginary component elements of the resistance matrix of a three-pole nonlinear element in two states, determined by two values of the amplitude of the low-frequency control signal, at a given fourth frequency in the amplitude and phase modulation mode; m _21n , φ _{21n are the} set values of the ratio of the modules and the phase difference of the transfer functions in two states determined by two values of the amplitude of the low-frequency control signal at a given fourth frequency in the amplitude and phase modulation mode; x _1n , x _2n , x _3n = x _4n are the optimal resistance values of the two-terminal circuits of the blocked T-shaped connection of four two-terminal networks at given four frequencies; k = 1, 2, 3, 4 - numbers of two-terminal circuits of the closed T-shaped connection; the remaining notation has the meaning of intermediate notation in the interests of simplifying mathematical expressions.

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