RU2083995C1 - Radar set - Google Patents

Abstract

FIELD: radar engineering; applicable in radar sets if independent and command control stations intended for detection of signals from targets and measurement of their coordinates at an existence of natural interference and jamming. SUBSTANCE: the radar set carries out the check of existence of spot jamming at the carrier frequency in the given repetition period, detection of one or several frequencies free of spot jamming in the process of frequency returning from period to period, operation at one of these frequencies in the coherent condition with Doppler frequency resolution, measurement of the spectrum width of interperiod fluctuations of the complex amplitude of reflected signals, and selection of signals from passive jamming of the shaft cloud type in the spectrum width of interperiod fluctuations. EFFECT: enhanced effectiveness. 7 cl, 10 dwg

Description

 The invention relates to radar and can be used in radar stations (radar) autonomous and command control systems designed to detect signals from targets and measure their coordinates in the presence of natural and organized interference.

 The development of radar technology is aimed at further improving the quality of radar, especially the detection range, resolution and noise immunity in relation to natural and organized interference. An important step in this direction is the use of complex signals, i.e. signals with intrapulse modulation, among which the most promising, especially for radars of autonomous and telecontrolled control systems, are signals with intrapulse phase shift keying (FM) with binary multi-bit code, which allow the organic use of digital methods for generating and processing signals.

 Known radar according to the application of the United Kingdom N 1514158, IPC G 01 S 9/233, publication 14.06.78, which contains a transceiver capable of emitting and receiving signals with phase shift keying or frequency modulation, a signal limiting block, a pulse compression device and a threshold block. In a known radar, the signals reflected from the target, after being limited in amplitude, are compressed in time in a matched filter constructed on the basis of a delay line with taps, and then are detected in a threshold block. The disadvantage of this radar is the operation at one frequency and, as a result, insufficient noise immunity with respect to impact noise interference.

 Known radar according to US patent N 4338604, IPC G 01 S 13/24, publication 07/06/82, which is the closest in technical essence to the proposed device and adopted as a prototype. The prototype device allows the tuning of the carrier frequency from pulse to pulse according to an arbitrary law and uses signals with intrapulse phase shift keying binary multi-bit code. The radar is built on a coherent principle and contains a serially connected synchronizer, transmitter, antenna switch and antenna, a receiver and an output display device connected to the third arm of the antenna switch, the transmitter being made on the basis of a series-connected exciter, phase manipulator and power amplifier controlled by a frequency tuning unit, a code generator and a pulse modulator, respectively, and the receiver contains a high-frequency amplifier, a decoding device, a second mixer and a second mixer (phase detector), the frequency tuning unit being connected to the control input of the exciter, the code generator connected to the control inputs of the phase manipulator and the decoding device, the output of the local oscillator frequency of the exciter connected to the heterodyne input of the mixer, and the output of the reference frequency of the exciter with the input of the reference frequency detector phase.

 Due to the use of complex FM signals with tuning of the carrier frequency from pulse to pulse, this radar has high noise immunity in relation to reciprocal and aiming interference, but its noise immunity in relation to organized passive interference - clouds of dipole reflectors (DOs), as well as in complex interfering situation, when both active aiming in frequency interference and DO are applied at the same time, is insufficient. Another disadvantage of the radar prototype, which also ultimately leads to insufficient noise immunity, is the introduction of an FM signal compression device ("decoding" device) into the receiver and its inclusion directly behind the high-frequency amplifier, so that the FM signal is compressed in the prototype the frequency of received signals, which limits the possibility of its implementation by the relatively short durations of complex signals (up to 10-20 μs).

 An object of the invention is to increase the noise immunity of the radar when operating in difficult jamming conditions: the simultaneous presence of response and impact-oriented interference frequencies, as well as organized passive interference.

 To achieve the claimed technical result in the radar, the presence of impact interference on the carrier frequency in a given repetition period is checked, in the process of frequency tuning from period to period, one or several frequencies free of impact interference are detected, the radar operates at one of these frequencies in a coherent mode with resolution by Doppler frequencies, measuring the spectral width of interperiodic fluctuations of the complex amplitude of the reflected signals and selecting signals from passive interference of the form of a cloud DO by the spectral width of period fluctuations.

 The essence of the invention lies in the fact that in a radar containing a sequence connected synchronizer, frequency adjustment unit, exciter, phase manipulator, power amplifier, antenna switch and antenna, series-connected high-frequency amplifier, mixer, intermediate frequency amplifier, block of phase detectors, and a code generator and a pulse modulator, and the input of the high-frequency amplifier is connected to the third arm of the antenna switch, the code generator and the pulse modulator are connected to With the input inputs of the phase manipulator and the power amplifier, respectively, the output of the local oscillator frequency of the pathogen is connected to the heterodyne input of the mixer, and the output of the reference frequency of the exciter with the input of the reference frequency, a series-connected amplitude detector, an interference detector, an analysis and frequency control unit, connected in series along two channels, a digital matched filter, a range gating unit, a complex envelope shaper, and a multi-channel filter up to Plerov frequencies, series-connected quadrature combining unit, first threshold comparison unit, primary processing device, secondary processing device, range finder, second threshold comparison unit and classifier connected in series, as well as a multi-channel frequency component detector, the input of which is connected via n channels to the output multi-channel Doppler filter, and the output with the input of the second block comparison with the threshold. The input of the amplitude detector is connected to the output of the amplifier of the intermediate frequency of the receiver, the output of the analysis and frequency control unit to the second input of the frequency adjustment unit, the second output of which is connected to the second input of the analysis and frequency control unit, the third input of which is connected to the third output of the secondary processing device, the second output which is connected to the second input of the antenna, the second output of which is connected to the second input of the primary processing device, the third input of which is combined with the first inputs of the pulse modulator and code generator and connected to the third output of the synchronizer, the second output of which is connected to the third input of the code generator, 4 inputs of the primary processing device, range finder, digital matched filter, the third input of which is connected to the output of the code generator, and the outputs to the combining unit quadrature. The output of the quadrature combining unit through the first comparison unit with a threshold is connected to the second input of the range finder, the output of which is connected to the third control input of the range gating unit. The outputs of the phase detector are connected to the corresponding inputs of the digital matched filter, the output of the classifier is connected to the second input of the secondary processing device. The fourth synchronizer output is connected to the second input of the code generator and the third input of the range finder, and the fifth synchronizer output is connected to the second input of the intermediate frequency amplifier and the second input of the interference detector.

The causative agent contains nf crystal oscillators connected to the corresponding gated amplifiers, the control inputs of which are connected to the first output of the frequency tuning unit, and the outputs are connected to the input of the frequency multiplier by n ₁ , the output of which is connected to the inputs of the first multiplier by n ₂ and the mixer, the second input of which connected to the output of the quartz oscillator of the reference frequency, the other output of which is connected to the input of the third frequency multiplier by n ₂ , and the output of the mixer is connected to the input of the second frequency multiplier by n ₂ the output of which is the first (signal) output of the pathogen. The outputs of the second and third frequency multipliers by n ₂ serve, respectively, as the outputs of the local oscillations and the reference frequency of the pathogen.

 The radar frequency tuning block is implemented on the basis of a series-connected noise generator, limiter amplifier, switch, the control input of which serves as the second input of the frequency tuning block, counter, I circuit, register and decoder, the output of which is the first output of the frequency tuning block, whose second output is the output of the register, and the first input is the control input of the circuit I.

 The frequency analysis and control unit contains an AND circuit, the control input of which through an inverter is connected to the first input of the frequency analysis and control unit, the second input of which is connected to the signal input of the And circuit, and the third input and output, respectively, to the input and output of random access memory, the second input which is connected to the output of circuit I.

 The primary processing device contains n-1 series-connected registers, the signal input of the first of which serves as the first input of the device, the inputs and outputs of each register are connected to the corresponding separate inputs of the adder, the output of which through a digital comparator is connected to the input of the evaluation unit, the outputs of which are connected to the signal inputs range meter and azimuth meter. The outputs of both meters are connected to the corresponding inputs of the random access memory device, the output of which is the output of the primary processing device, the second and third inputs of which are the second inputs, respectively, of the azimuth and range meters, the third input of which, connected to the control inputs of the shift registers, serves as the fourth input devices.

 The first input of the range finder is connected to the installation input of the reverse counter and controls the input of the key circuit, the output of which is connected to the counting input of the reverse counter, and the input with the output of the range discriminator, the first input of which is the second input of the range finder, the third and fourth inputs of which are, respectively, the second and the third inputs of the converter are a code-time interval, the first input of which is connected to the output of the reverse counter, and the output serves as the output of the range finder and is connected to the second input of the discriminate range ora.

 Figure 1 presents the structural diagram of the radar; figure 2 structural diagram of the pathogen (B); figure 3 is a structural diagram of a frequency adjustment unit (BCH); in FIG. 4 block diagram of the synchronizer (C); in Fig.5 waveforms of the signals at the outputs of the synchronizer; Fig.6 is a structural diagram of a block analysis and frequency control (BAUCH); 7 is a structural diagram of a digital matched filter (CSF); on Fig structural diagram of the primary processing device (UPR); in FIG. 9 is a block diagram of an algorithm for a secondary processing device (SVR) implemented on a digital computer; figure 10 is a structural diagram of a range finder (D).

, а общий частотный диапазон, перекрываемый МФДЧ, равен F_n; 21 блок объединения квадратур (БОК), состоящий из двух квадраторов (функциональных преобразователей, выполняющих возведение в квадрат) и сумматора; 22 первый блок сравнения с порогом (БСП₁), который реализуется на основе компаратора; 23 устройство первичной обработки (УПО), представляющее собой устройство обнаружения пачек импульсов (по правилу "k" из "n") и измерения координат цели в процессе обзора (дальности и азимута), которое может быть выполнено по схеме, приведенной на фиг.8; 24 устройство вторичной обработки (УВО), в котором производится накопление результатов первичного обнаружения за M обзоров и определяются усредненные координаты целей и которое может быть выполнено в виде ЦВМ, реализующей алгоритм, представленный на фиг.9; 25 дальномер (Д), функциональная схема которого приведена на фиг. 10; 26 многоканальный детектор частотных составляющих (МДЧС), представляющий собой совокупность из n амплитудных детекторов, подключенных к выходам соответствующих фильтров МФДЧ 20; 27 второй блок сравнения с порогом (БСП₂), реализуемый на основе компаратора, вход которого с помощью электронного коммутатора подключается поочередно к n выходам МДЧС; 28 - классификатор (Кл), который может быть реализован на основе счетчика со сбросом при наличии пропуска в последовательности импульсных сигналов превышения порога, если число следующих подряд импульсов не превосходит l₀, в противном случае формирующего сигнал переполнения.In figure 1, the following notation: 1 antenna (A); 2 antenna switch (AP), made, for example, in the form of a ferrite Y-circulator; 3 power amplifier (UM) A pulse-modulated microwave amplifier that is implemented depending on the required power and the band of amplified frequencies on the basis of an electrovacuum device (amplitron, traveling wave lamp, multi-beam klystron, etc.) or a semiconductor device (see, for example, The reference book on radar / under the editorship of M. Skolnik. M. Sov.radio. 1979.v.3, p.19-52); 4 phase manipulator (FM), made, for example, according to the scheme described in the description of US patent N 4338604, and a segment of a strip waveguide switched by microwave diodes that are controlled by pulses from a code generator can be used as a delay line (see below); 5 pathogen (B), the structural diagram of which is presented in figure 2; 6 - pulse modulator (IM), depending on the AM circuit, is implemented according to well-known schemes (Radar Reference, v.3. P.103-107, figs. 43-45); 7, the code generator (GK) is implemented according to a scheme containing a synchronously-driven clock pulse gate and a shift register with feedbacks through modulo 2 adders to form a pseudo-random M-sequence (see Yakovlev VV Fedorov RF Stochastic computers. L Engineering, 1974, pp. 147-153); 8 block frequency adjustment (BFC), a structural diagram of which is shown in figure 3; 9 synchronizer (C), the structural diagram of which is shown in figure 4, and figure 5 shows the waveforms of the signals at its outputs; 10 high-frequency amplifier (UHF), implemented as a transistor microwave amplifier; 11 mixer (SM), made in the form of a balanced mixer (Reference radar, t.3, p.144); 12 intermediate frequency amplifier (IFA); 13 block phase detectors (PD), which is a block of two identical phase detectors (with video amplifiers at the outputs), to which the reference voltage is applied with a shift of 90 ^o (one relative to the second); 14 amplitude detector (HELL); 15 an interference detector (OP), which can be made in the form of a serial connection of a threshold block (based on a comparator), gated by control signals from a synchronizer 9, and a counter of the number of threshold excesses (the presence of at least “k” threshold excesses in “m” moments time during one repetition period in a non-working range interval is a sign of the presence of continuous interference at a given frequency); 16 block analysis and frequency management (BAUCH), a structural diagram of which is shown in Fig.6; 17 digital matched filter (CSF), a structural diagram of which is shown in Fig.7; 18 block range gating (BDS), which is a combination of two identical gated video amplifiers; 19 complex envelope shaper (FCF), consisting of two identical channels, each of which contains a bipolar peak detector, an expander and a low-pass filter connected in series; 20 is a multi-channel Doppler filter (MFDCH), which is a collection of n narrow-band filters with adjacent frequency characteristics, and the passband of one filter is equal to

and the total frequency range covered by the MFDCH is F _n ; 21 block combining quadratures (BOK), consisting of two quadrators (functional converters that perform squaring) and the adder; 22 the first block comparison with the threshold (BSP ₁ ), which is implemented on the basis of the comparator; 23 primary processing device (UPR), which is a device for detecting bursts of pulses (according to the rule "k" from "n") and measuring the coordinates of the target during the survey (range and azimuth), which can be performed according to the scheme shown in Fig. 8 ; 24 a secondary processing device (SVR), in which the results of primary detection are accumulated for M surveys and the average coordinates of the targets are determined and which can be performed in the form of a digital computer that implements the algorithm shown in Fig. 9; 25 rangefinder (D), the functional diagram of which is shown in FIG. ten; 26 multichannel detector of frequency components (MFES), which is a collection of n amplitude detectors connected to the outputs of the respective filters MFD 20; 27, the second threshold comparison unit (BSP ₂ ), implemented on the basis of a comparator, the input of which is connected using the electronic switch in turn to the n outputs of the MDCS; 28 - classifier (C), which can be implemented on the basis of a counter with a reset if there is a gap in the sequence of pulse signals exceeding the threshold, if the number of consecutive pulses does not exceed l ₀ , otherwise generating an overflow signal.

 In the diagram of Fig. 1, a synchronizer 9, a frequency tuner 8, an exciter 5, a phase manipulator 4, a power amplifier 3, an antenna switch 2 and an antenna 1 are connected in series, a high-frequency amplifier 10 connected to the third arm of the antenna switch 2 is connected in series 11, an intermediate frequency amplifier 12, a phase detector unit 13, an amplitude detector 14, an interference detector 15 and a frequency analysis and control unit 16 are connected in series, digitally matched through two channels filter 17, range gating unit 18, complex envelope former 19, multi-channel Doppler filter 20, quadrature combining unit 21, first threshold comparison unit 22, primary processing device 23, secondary processing device 24 and range finder 25 are connected in series a second comparison threshold unit 27 and a classifier 28, wherein n outputs of the multi-channel Doppler filter 20 are connected through a multi-channel detector 26 of frequency components with corresponding inputs and a second comparator 27 with a threshold input of the amplitude detector 14 is connected to the output of amplifier 12, intermediate frequency. The output of the frequency analysis and control unit 16 is connected to the second input of the frequency tuning unit 8, the second output of which is connected to the second input of the frequency analysis and control unit 16, the third input of which is connected to the third output of the secondary processing device 24, the second output of which is connected to the second input of the antenna 1, the second output of which is connected to the second input of the primary processing device 23, the third input of which is combined with the first inputs of the pulse modulator 6 and the code generator 7 and is connected to the third output of the sync isator 9, the second output of which is connected to the third input of the code generator 7, the fourth input of the primary processing device 23, the fourth input of the range finder 25 and the fourth input of the digital matched filter 17, the third input of which is connected to the output of the code generator 7, and the outputs to the quadrature combining unit 21 . The output of block 21 through the first comparison block 22 with a threshold is connected to the second input of the range finder 25, the output of which is connected to the third input of the range gating unit 18. The outputs of the phase detector 13 are connected to the corresponding inputs of the digital matched filter 17. The output of the classifier 28 is connected to the second input of the secondary processing device 24, the fourth output of the synchronizer 9 to the second input of the code generator 7 and the third input of the range finder 25, and the fifth output of the synchronizer 9 to the second input of the amplifier 12 intermediate frequency and the second input of the detector 15 interference. The second input of the mixer 11 is connected to the output of the local oscillations of the pathogen 5, the output of the reference frequency of which is connected to the second input of the phase detector 13.

In FIG. 2 presents a structural diagram of the pathogen 5, where it is indicated:
29 ₁ , 29 _nf crystal oscillators (KG ₁ , KG _nf );
30 ₁ , 30 _nf gated amplifiers (U ₁ , U _nf );
31 frequency multiplier by n ₁ (xn ₁ );
32 ₁ , 32 ₂ frequency multipliers (for heterodyne and signal oscillations) by n ₂ (xn ₂ );
33 crystal oscillator for forming a reference frequency (KG _o );
34 mixer (CM);
35 frequency multiplier (for the formation of reference oscillations) by n ₂ (xn ₂ ).

In FIG. 2 crystal oscillators 29 ₁ .29 _{nf are} connected through respective amplifiers 30 ₁ .30 _nf , the control inputs of which form the input of the exciter 5, with the input of the frequency multiplier 31 by n ₁ . The output of the multiplier 31 is connected to the inputs of the first frequency multiplier 32 ₁ by n ₂ and the mixer 34, the second input of which is connected to one of the outputs of the crystal oscillator (KG ₀ ) 33, the second output of which is connected to the input of the frequency multiplier 35 by n ₂ . The output of the mixer 34 is connected to the input of the second frequency multiplier 32 ₂ by n ₂ , the output of which is the first (signal) output of the exciter 5, the second output (heterodyne oscillations) and the third output (reference frequency) of which are the outputs of the frequency multipliers 32 ₁ and 35 by n ₂ respectively.

 In FIG. 3 is a structural diagram of a frequency tuning unit (BFCH) 8, which contains a serially connected noise generator (GS) 36, a limit amplifier (UO) 37, a switch (Km) 38, the control input of which is the second input of the BPC 8, and a counter (MF ) 39, the outputs of which are bitwise connected to the inputs of the AND 40 circuit, the control input of which is the first input of the BPC 8, and the outputs of the And 40 circuit are bitwise connected to the input of the register (P) 41, the outputs of which are connected to the decoder (L) 42. The outputs of the decoder 42 and register 41 are the first and second outputs and BPC 8, respectively.

 In FIG. 4 is a structural diagram of a synchronizer (C) 9, where it is indicated: 43 master oscillator (ZG); 44 frequency divider (DF); 45 - counter (MF); 46 decoder (DS); 47 block of triggers (BTR).

 The output of ЗГ 43 is connected to the input of the frequency divider 44, the first output of which is connected to the second counter 45, and the other two outputs are the second and fourth outputs of the synchronizer 9. The outputs of the counter 45 are bitwise connected to the corresponding inputs of the decoder 46, and the outputs of the latter are connected to the inputs of the block 47 RS flip-flops, the outputs of which are the outputs 1,3, 5 of the synchronizer 9.

и длительностью τ₂≪τ_и на выходе 2 синхронизатора, предназначенные для управления генератором 7 кода, цифровым согласованным фильтром 17, устройством 23 первичной обработки и дальномером 25;
50 импульсы с частотой повторения F_п=1/Т_п, с длительностью τ₃= T_и на выходе 3 синхронизатора, предназначенные для управления импульсным модулятором 6, генератором 7 кода и устройством 23 первичной обработки;
51 импульсы с частотой повторения F_п=1/Т_п, с длительностью τ₄≪T_и на выходе 4 синхронизатора 9, предназначенные для управления генератором 7 кода (запуск) и дальномером 25;
52 серия из m₁ (например, m₁ 3) импульсов с частотой повторения F_п=1/Т_п, с длительностью импульсов τ₅≪τ_f на расстоянии τ₆ друг от друга (τ₅≪τ₆≪τ_f) и упреждением относительно начала периода зондирующих импульсов, равным m₁τ₅+(m₁-1)τ₆+τ_f на выходе 5 синхронизатора 9, предназначенные для управления усилителем 12 промежуточной частоты и обнаружителем 15 помехи.In FIG. 5 shows the timing diagram of the voltages at the outputs of the synchronizer, namely:
48 pulses with a repetition rate F _p = 1 / T _p with a lead of a tuning time τ _f relative to the beginning of the probe pulse period and with a duration τ ₁ <τ _f at the output 1 of the synchronizer 9, designed to control the frequency tuning unit 8;
49 pulses with a frequency

and duration τ ₂ ≪τ _and at the output 2 of the synchronizer, designed to control the code generator 7, matched digital filter 17, the primary processing device 23 and the range finder 25;
50 pulses with a repetition rate F _p = 1 / T _p , with a duration of τ ₃ = T _and at the output 3 of the synchronizer, designed to control the pulse modulator 6, the code generator 7 and the primary processing device 23;
51 pulses with a repetition rate F _p = 1 / T _p , with a duration of τ ₄ ≪T _and at the output 4 of the synchronizer 9, designed to control the code generator 7 (start) and the range finder 25;
52 series of m ₁ (for example, m ₁ 3) pulses with a repetition rate F _p = 1 / T _p , with a pulse duration of τ ₅ ≪τ _f at a distance of τ ₆ from each other (τ ₅ ≪τ ₆ ≪τ _f ) and a lead relative to the beginning of the period of the probe pulses, equal to m ₁ τ ₅ + (m ₁ -1) τ ₆ + τ _f at the output 5 of the synchronizer 9, designed to control the intermediate frequency amplifier 12 and the interference detector 15.

 In FIG. 6 is a structural diagram 16 of frequency analysis and control (BAUCH), where it is indicated: 53 inverter (Inv); 54 scheme And (And); 55 - random access memory (RAM).

 In the diagram of FIG. 6, input 1 of BAUCH 16 is connected through an inverter 53 to the control input of circuit I, whose signal input forms input 2 of BAUCH 16, and the output is connected to RAM 55. The control input of RAM 55 is input 3 of BAUCH 16, and the output of RAM 55 is its output.

In FIG. 7 is a structural diagram of a digital matched filter (CSF) 17, where it is indicated:
56 ₁ , 56 ₂ amplitude quantizers (AK ₁ , AK ₂ );
57 ₁ , 57 ₂ shift registers (CP _s , CP _c );
58 ₁ , 58 ₂ ) random access memory codes (RAM ₁ , RAM ₂ ) with inverters;
59 ₁ , 59 ₂ adders (Σ _s , Σ _c ).

The inputs 1 and 2 of the CSF 17 through amplitude quantizers 56 ₁ , 56 _{2 are} connected to the signal inputs of the shift registers 57 ₁ , 57 ₂ , the control inputs of which are interconnected and form the input 4 of the CSF. The outputs CP _s 57 ₁ and CP _c 57 _{2 are} bitwise connected through RAM ₁ , 58 ₁ , RAM ₂ 58 _2, respectively, to the inputs of the adders 59 ₁ , 59 ₂ , the outputs of the latter form the outputs 1.2 of the DSP 17, respectively, and the control inputs of RAM ₁ 58 ₁ and RAM ₂ 58 ₂ form the input 3 CSF 17.

In FIG. 8 is a functional diagram of a primary processing device (UPR) 23, where it is indicated: 60 ₁ .60 _n-1 shift registers (CP ₁ , CP _n-1 ); 61 adder (Σ); 62 digital comparator (CC); 63 evaluation unit (BO); 64 range meter (ID); 65 - azimuth meter (IA); 66 random access memory device (RAM).

In the diagram of Fig. 8, the input 1 of the UPR 23 is the signal input of the first of the chain of n-1 series-connected shift registers 60 ₁ , 60 ₂ , 60 _n-1 , the inputs and outputs of which are connected to the corresponding n inputs of the adder (S) 61, the output which through a digital comparator (CC) 62 is connected to the input of the evaluation unit 63 (BO), the outputs of the BO 63 are connected to the signal inputs of the range meter 64 (ID) and the azimuth meter 65 (IA), the outputs of which are connected to the random access memory device (RAM) 66, the output of which is the output of the UPR 23. The second inputs of IA 65 and ID 64 vlyayutsya respectively second and third inputs UPR 23, and the third input ID 64 connected to the control inputs CP _1, CP ₂ .CP _n-1, 60 _1, 60 _n-1 forms the fourth input 23 UPR.

In FIG. 9 is a block diagram of a digital computer algorithm that implements a secondary processing device (SVR) 24, the operation of which consists in sequentially solving the problems presented in the block diagram, namely:
1. secondary (inter-review) processing of information, consisting in the accumulation of decisions made according to the results of each review after their identification by coordinate signs and the final decision on the presence or absence of signals from targets in the review area, for example, according to the "K" criterion M "(at least K decisions about the presence of a signal from a given target in a series of M images), with measuring the coordinates of targets by averaging (smoothing) estimates of their coordinates in separate surveys. After the end of the cycle of M reviews, it is checked whether the number of detected targets reaches a certain predetermined number N ^* (in particular, N ^* = 1), if not, then the review continues, if so, then proceeds to the next step 2;
2. issuing the coordinates R _{i of the} i-th detected target (i = 1,2,) from the output of I UVO 24 to the input 1 of the range finder (D) 25 and the coordinates j _i from the output 2 of the UVO 24 to the input 2 of the antenna 1 to stop scanning and setting the antenna pattern in the direction to the i-th target;
3. termination of carrier frequency tuning by command from output 3 of UVO 24, which is input to input 3 of BAUCH 16, and of operation at one of the fixed frequencies, free from the effects of impact noise or sinusoidal interference;
4. obtaining information from the classifier (Cl) 28 about the class of the i-th target (true or false). If the target is false, the corresponding attribute is assigned to it (or its coordinates are deleted from the memory of UVO 24), i.e. classification of the i-th goal;
5. the transition to claim 2 with the replacement of i by i + 1 and the execution of the next cycle of claims. 2-5, (i = 1,2, L-1).

 In FIG. 10 is a structural diagram of a range finder (D) 25, where it is indicated: 67 reverse counter (RS); 68 key scheme (C); 69 - range discriminator (DD); 70 Converter "code-time interval" (PCVI).

 In the diagram of Fig. 10, the first input of the range finder 25 is connected to the installation input of the reverse counter (PC) 67 and the control input of the key circuit 68, the output of which is connected to the counting input of the PC 67, and the output with the output of the range discriminator (DD) 69, the first input of which is the second input of the range finder 25, the second input of the DD 69 connected to the output of the code-time interval converter (PCVI) 70, is the output of the range finder 25. The first input of the PKVI 70 is connected to the output of PC 67, and its second and third inputs respectively serve as the third and the fourth inputs of the rangefinder 25.

 The proposed radar operates as follows.

Возбудитель 5 работает следующим образом (фиг.2). Кварцевые генераторы 29₁,29_nf излучают непрерывные колебания, каждый на своей частоте F_ki, где i= 1,2,nf. Эти колебания проходят через стробируемые усилители 30₁,30_nf соответственно, из которых в данном периоде повторения открыт только один, именно тот, на который со входа возбудителя 5 поступает единственный ненулевой разряд параллельного nf-разрядного кода, формируемого в БПЧ 8. Эти колебания умножаются по частоте в умножителя 31 и 31₁ на n₁•n₂ и, таким образом, образуют колебания гетеродинной частоты F_ri=n₁•n₂•f_ki (i∈1,...nf), одновременно колебания частоты n₁f_ki в смесителе 34 смешиваются с колебаниями частоты f_ko, поступающими от кварцевого генератора 33, результирующие колебания умножаются по частоте на n₂ в умножителе 32₂, и так образуются колебания частоты сигнала f_ci=(n₁f_ki+f_ко)n₂. С другого выхода кварцевого генератора 33 колебания частоты f_ко попадают на умножитель 35 частоты на n₂, и так образуются колебания опорной частоты f_оп=n₂F_ко. Как нетрудно видеть,

Соотношение, которое неизменно выдерживается независимо от перестройки частоты f_сi, F_ri.The causative agent 5 of the transmitting device generates continuous fluctuations in the frequency of the signal F _ci , the local oscillator F _ri and the intermediate (reference) frequency F _op , while the frequencies F _ci , F _{ri are} highly stable during one repetition period T _{n of the} radar probe pulses, but can change stepwise from the period to the period according to a random law under the action of block 8 of the frequency adjustment, taking one of the nf values (i = 1,2.nf), and so that the relation always holds

The causative agent 5 works as follows (figure 2). The crystal oscillators 29 ₁ , 29 _nf emit continuous oscillations, each at its own frequency F _ki , where i = 1,2, nf. These oscillations pass through gated amplifiers 30 ₁ , 30 _nf, respectively, of which only one is open in this repetition period, namely the one to which the only nonzero discharge of the parallel nf-bit code generated in the BPC 8 comes from the input of the exciter 5. These oscillations are multiplied in frequency in the multiplier 31 and 31 ₁ by n ₁ • n ₂ and, thus, form oscillations of the heterodyne frequency F _ri = n ₁ • n ₂ • f _ki (i∈1, ... nf), simultaneously the oscillations of the frequency n ₁ f _ki are mixed in a mixer 34 with oscillations of frequency f _ko, coming from the quartz generators pa 33, the resulting oscillations multiplied in frequency by ₂ n ₂ in multiplier 32, and so the vibration frequency generated signal f _ci = (n ₁ f _ki + f _to) n _2. From another output of the crystal oscillator 33, the oscillations of the frequency f _ko fall on the frequency multiplier 35 by n ₂ , and so the oscillations of the reference frequency f _op = n ₂ F _{ko are formed} . How easy it is to see

A ratio that is invariably maintained regardless of the frequency tuning f _сi , F _ri .

Frequency tuning f _ci and f _{ri is} performed using the frequency tuning unit 8 (frequency tuning), working as follows (Fig. 3).

The noise voltage generator (GS) 36, built, for example, on the basis of a noise diode, generates noise fluctuations with a spectral width significantly exceeding the repetition frequency (Δf _w ≫ F _p ), then these oscillations are amplified and limited in the limiting amplifier (UO) 37 and they arrive through the switch 38 to the counter 39, which counts, for example, positive edges modulo nf and thus has nf equiprobable states. At the moment determined by the clock pulses arriving through the repetition period T _n from the output 1 of the synchronizer 9 with a lead time of τ _f relative to the beginning of the next period, the readings of the counter 39 through the And circuit are recorded in the register (P) 41 and converted in the decoder 42 into a parallel code with the number of digits nf, where only one of the nf digits is nonzero, which is retained for at least one repetition period and determines the frequencies f _ci and f _ri in the next repetition period.

Fluctuations in the frequency of the signal f _ci enter the phase manipulator (FM) 4, where they are phase-controlled by a binary multi-bit code (with the number of bits N) generated in the code generator 7 (GC), amplified by the power in the power amplifier 3 (AM), forming the action of a pulse modulator (MI) 6, controlled by pulses 50 (Fig. 5), coming from the output 3 of the synchronizer 9, probing pulses with a duration T _and with intrapulse phase shift keying (FM) N bit binary code. The probe pulses through the antenna switch (AP) 2 fall into the antenna 1 and are emitted into space. Moreover, in the detection mode, the antenna 1 drive operates autonomously, performing a sector (or circular) overview of the space (commands to the input A 1 do not arrive).

t_i= iτ_и, i=1,2. моменты квантования.The received signals, passing through the AP 2 and the high-frequency amplifier 10 of the receiving device, pass through a mixer 11, which converts to an intermediate frequency into an intermediate frequency amplifier (IFA) 12, using the oscillator oscillator frequency f _ri coming from the output 2 of the pathogen 5 and then to the input of the phase detector (PD) block 13, its other input comes as frequency reference oscillations f _op = f _pc from the pathogen 5. At the outputs of block 13 (PD), quadrature components of bipolar video signals are formed, the polarity of which changes according to the FM code of the received signals. These signals are fed into a digital matched filter (CSF) 17, at the inputs 1 and 2 of which in each quadrature amplitude quantizers AK 56 ₁ , 56 ₂ are included (Fig. 7), which carry out a transformation of the form
η $\genfrac{}{}{0ex}{}{\text{(s, c)}}{\text{i}}$ = sign [ε ^{(s, c)} (t _i )],
where indicated:

t _i = iτ _and , i = 1,2. quantization moments.

, поступающих с выхода 2 синхронизатора 9 через вход 4 ЦСФ 17 на управляющие входы сдвиговых регистров 57₁, 57₂, происходит их заполнение двоично- квантованными сигналами η $\genfrac{}{}{0ex}{}{\text{(s,c)}}{\text{i}}$ , приходящими на сигнальные входы CP_s, CP_c с выходов соответствующих АК 56₁ и 56₂. В блоках 58₁, 58₂ оперативных запоминающих устройств кодов с инверторами (ОЗУК₁, ОЗУК₂) происходит поразрядное умножение чисел η $\genfrac{}{}{0ex}{}{\text{(s,c)}}{\text{i}}$ на весовые коэффициенты h_j= (-1)^νN-j соответствующие кодовым символам ν_j приходящим от генератора 7 кодов на вход 3 ЦСФ 17 в начале каждого периода повторения, так что в сумматорах Σ_s,Σ_c 59₁, 59₂ образуются сигналы

которые проходят на выходы 1,2 ЦСФ 17. В режиме обнаружения эти сигналы с блоке 21 объединения квадратур образуют по правилу "сумма квадратов" сигнал ξ $\genfrac{}{}{0ex}{}{\text{2}}{\text{i}}$ , который не зависит от неизвестной начальной фазы
ξ $\genfrac{}{}{0ex}{}{\text{2}}{\text{i}}$ = [ξ $\genfrac{}{}{0ex}{}{\text{(s)}}{\text{i}}$ ]²+[ξ $\genfrac{}{}{0ex}{}{\text{(c)}}{\text{i}}$ ]²
Этот сигнал сравнивается с порогом в первом блоке 22 сравнения с порогом (БСП₁), и при наличии превышения порога нормированный сигнал поступает на вход 1 устройства 23 первичной обработки (УПО) и на вход 2 дальномера 25. Одновременно квадратурные составляющие ξ $\genfrac{}{}{0ex}{}{\text{(s)}}{\text{i}}$ и ξ $\genfrac{}{}{0ex}{}{\text{(c)}}{\text{i}}$ сжатого сигнала поступают на сигнальные входы блока 18 стробирования по дальности (БСД), на управляющий вход 3 которого поступает стробирующий импульс с выхода дальномера 25.Under the influence of clock pulses 49 (Fig. 5) with a frequency

coming from the output 2 of the synchronizer 9 through the input 4 of the CSF 17 to the control inputs of the shift registers 57 ₁ , 57 ₂ , they are filled with binary-quantized signals η $\genfrac{}{}{0ex}{}{\text{(s, c)}}{\text{i}}$ coming to the signal inputs CP _s , CP _c from the outputs of the corresponding AK 56 ₁ and 56 ₂ . In blocks 58 ₁ , 58 ₂ random access memory codes with inverters (RAM ₁ , RAM ₂ ) is bitwise multiplication of numbers η $\genfrac{}{}{0ex}{}{\text{(s, c)}}{\text{i}}$ by weight coefficients h _j = (-1) ^νN-j corresponding to the code symbols ν _j coming from the generator 7 of the codes to the input 3 of the CSF 17 at the beginning of each repetition period, so that signals are generated in the adders Σ _s , Σ _c 59 ₁ , 59 ₂

which pass to the outputs of 1.2 CSF 17. In the detection mode, these signals from block 21 combining quadratures form the signal ξ according to the rule "sum of squares" $\genfrac{}{}{0ex}{}{\text{2}}{\text{i}}$ which is independent of the unknown initial phase
ξ $\genfrac{}{}{0ex}{}{\text{2}}{\text{i}}$ = [ξ $\genfrac{}{}{0ex}{}{\text{(s)}}{\text{i}}$ ] ² + [ξ $\genfrac{}{}{0ex}{}{\text{(c)}}{\text{i}}$ ] ²
This signal is compared with a threshold in the first comparison block 22 with a threshold (BSP ₁ ), and if the threshold is exceeded, the normalized signal is fed to input 1 of the primary processing device 23 (UPR) and to input 2 of the range finder 25. At the same time, the quadrature components ξ $\genfrac{}{}{0ex}{}{\text{(s)}}{\text{i}}$ and ξ $\genfrac{}{}{0ex}{}{\text{(c)}}{\text{i}}$ the compressed signal is fed to the signal inputs of the range gating unit 18 (BSD), the control input 3 of which receives a gating pulse from the output of the range finder 25.

через вход 4 УПО 23 с выхода 2 синхронизатора 9, а на информационный вход измерителя 65 азимута через вход 2 УПО 23 код текущего значения угла поворота диаграммы направленности антенны 1 с выхода антенны 1. Измеренные таким путем координаты целей попадают в ячейки оперативного запоминающего устройства 66 целей (ОЗУЦ), выход которого соединен с входом 1 устройства 24 вторичной обработки (УВО), осуществляющего межобзорное накопление и измерение координат, как об этом уже упоминалось выше.The normalized signal from BSP ₁ 22, getting to input 1 of the UPR 23 (Fig. 8), passes to a chain of n-1 series-connected shift registers 60 ₁ , 60 ₂ , 60 _n-1 , from the outputs of which, as well as directly, the signals go to adder 61, which accumulates signals in each range quantum for n repetition periods, i.e. during the pack. The accumulated signal from the output of the adder 61 is supplied to a digital comparator (CC) 62, where a comparison is made with a digital threshold, in accordance with the detection criterion "k" from "m". Further, the signals that exceeded the threshold level from the output of the CK 62 fall into the evaluation unit BO 63, where the central pulse of the burst from the accumulated pulses is allocated, which is used to calculate the distance in the range meter (ID) 64 and the target azimuth in the azimuth meter (IA) 65. In order to make this possible, pulses with a repetition frequency F _p through input 3 of the UPR 23 from the output of 3 synchronizer 9 and with a frequency of

through the input 4 of the UPR 23 from the output 2 of the synchronizer 9, and to the information input of the meter 65 azimuth through the input 2 of the UPR 23 code of the current value of the angle of rotation of the radiation pattern of the antenna 1 from the output of the antenna 1. The coordinates of the targets measured in this way fall into the cells of random access memory 66 of the goals (RAM), the output of which is connected to the input 1 of the device 24 secondary processing (SVO), carrying out inter-review accumulation and measurement of coordinates, as mentioned above.

с выхода 2 синхронизатора 9. В момент времени

(С скорость света) относительно начала периода повторения на выходе ПКВИ 70 образуется стробирующий импульс (строб), который поступает одновременно на выход дальномера 25 и на второй вход дискриминатора 69 дальности, на первый вход которого через вход 2 дальномера 25 происходит нормированный импульс сигнала от цели, а квантованный сигнал ошибки с выхода ДД 69 через Кл 68 поступает на счетный вход PC 67, корректируя значение дальности до сопровождаемой цели и через ПКВИ 70 - положение строба. На первый вход блока 16 анализатора и управления частотами (БАУЧ) через инвертор 53 поступает сигнал обнаружения помехи с выхода обнаружителя 15 помехи (ОП), в случае отсутствия этого сигнала (т.е. когда помехи нет) на управляющий вход схемы И 54 поступает разрешающий сигнал, и соответствующее значение несущей частоты, поступающей с выхода 2 БПЧ 8 с регистра 41 на вход 2 БАУЧ 16, записывается в ОЗУ 55. Одновременно со стробированием эхо-сигналов от первой цели по дальности и азимуту по команде, поступающей с выхода 3 УВО 24 на вход 3 БАУЧ 16, прекращается перестройка несущей частоты путем подачи с выхода БАУЧ 16 сигнала на коммутатор (Км) 38 БПЧ 8 и записывается в Сч 39 значение частоты из ОЗУ 55 БАУЧ 16, свободный от помех.After the end of the detection, if the number of detected targets is large enough (in particular, not less than 1), the detected targets are classified according to the UVO 24 commands. At the same time, the rangefinder’s range loop 25 closes, and its input 1 receives the range value of the first detected target R ₁ from output 1 of the UVO 24, and its azimuth value ψ ₁ goes to input 2 of the antenna 1 from output 2 of the UVO 24, providing a turn of antenna 1 towards the first goal. The range value R _{1 is} written in the form of a code in the reverse counter (PC) 67 of the range finder 25 and from it it comes to the code-time interval converter (PCVI) 70, to the control inputs of which 2.3 through the inputs 3.4 of the range finder 25 respectively pulses with a frequency F _p from the output 4 of the synchronizer 9 and the frequency

from output 2 of synchronizer 9. At time

(With the speed of light) relative to the beginning of the repetition period, a strobe pulse (strobe) is generated at the output of the PCVI 70, which is fed simultaneously to the output of the range finder 25 and to the second input of the range discriminator 69, the first input of which through the input 2 of the range finder 25, a normalized signal pulse from the target and the quantized error signal from the output of DD 69 through Cl 68 is supplied to the counting input of PC 67, adjusting the value of the distance to the target being tracked and, through PKVI 70, the position of the strobe. At the first input of the analyzer and frequency control unit (BAUCH) 16 through the inverter 53, an interference detection signal is received from the output of the interference detector 15 (OP), in the absence of this signal (i.e., when there is no interference), the control input of AND circuit 54 receives the signal and the corresponding value of the carrier frequency coming from the output 2 of the BCH 8 from the register 41 to the input 2 of the BAUCH 16 is recorded in the RAM 55. Simultaneously with the gating of the echo signals from the first target in range and azimuth by the command coming from the output of 3 UVO 24 input 3 BAUCH 16, ceases to adjustment of the carrier frequency by applying a signal from the output of the BAUCH 16 to the switch (Km) 38 of the BPCH 8 and the frequency value from the RAM 55 of the BAUCH 16, which is free from interference, is recorded in Mm 39.

где ΔF полоса пропускания одного канала,
F_п частота повторения,
nT_п время когерентной фильтрации, численно совпадает с числом когерентно накапливаемых периодов повторения n.The quadrature components of the compressed signals from the gated target, which, when operating at the same carrier frequency, become coherent from period to period, having passed the range gating unit 18, performing range gating in both quadrature channels using a strobe supplied to the BSD 18 input from the output of the range finder 25 , fall into the formation block 19 of the complex envelope (FCO), which forms the complex envelope by expanding the pulses (using peak detection) and low-pass filtering (in quadrature channels). The quadrature components of the complex envelope of the received signal thus formed are then filtered by the Doppler frequency in a multi-channel filter of 20 Doppler frequencies, the number of channels of which is equal to

where ΔF is the bandwidth of one channel,
F _p repetition rate,
nT _n coherent filtering time, numerically coincides with the number of coherently accumulated repetition periods n.

From the outputs of all n channels of the MFDCH 20, the filtered signals enter a multi-channel detector 26 of the frequency components, in which the amplitude detection of signals in all n channels takes place, so that the blocks 20 and 26 form essentially a spectrum analyzer. Further, all outputs of the MDCH 26 are compared in block 27 of comparison with the threshold (BSP ₂ ) with a predetermined level, the numbers of those frequency channels in which the threshold level has been exceeded, then go to the classifier (C) 28, in which a decision is made about the target class by the rule:
if the number of consecutive channel numbers l, in which the threshold level has been exceeded, is greater than some predetermined number l ₀ , i.e. l> l ₀ , then the corresponding target is false, and if l≅ l ₀ , then it is true.

 The sign of the goal (true or false) from the output of Cl 28 goes to input 2 of the SVO 24. After the classification of the i-th target (i = 1,2, L-1) by the commands of the SVO 24, as described above, the transition to observation and the classification of the (i + 1) -th goal, and so on until the last (L-th) goal.

 The operation of the synchronizer (C) 9 (Fig. 4) consists in generating control signals (Fig. 5), while the signals 49 and 51 are generated by dividing the frequency of the pulses generated by the master oscillator 43, the required number of times, and other signals using the counter 45, the decoder 46 and the block of RS-flip-flops 47, generating signals of the required duration and delay (lead) relative to the beginning of the repetition period.

 The technical advantage of the claimed radar is to increase the noise immunity by expanding the class of interference from which the radar is protected, and the implementation of the ability to work in difficult interference conditions: with the simultaneous exposure to organized active and passive interference type of clouds of dipole reflectors.

 Using the information presented in the application materials, the proposed radar can be manufactured in production using known materials, elements, units and technology, and used to detect signals from targets and measure their coordinates, which proves the industrial applicability of the object of the invention.

 In accordance with the application materials, a prototype of the device was manufactured, the tests of which confirmed the achievement of the technical result indicated in the application materials.

Claims (7)

 1. A radar station containing a serially connected synchronizer, a frequency tuner, an exciter, a phase manipulator, a power amplifier, an antenna switch and an antenna, a serially connected high-frequency amplifier, a mixer, an intermediate frequency amplifier, a block of quadrature phase detectors, and a code generator and a pulse a modulator, and the input of the high-frequency amplifier is connected to the third arm of the antenna switch, the code generator and the pulse modulator are connected to the control by the steps of the phase manipulator and power amplifier, respectively, the output of the local oscillator frequency of the pathogen is connected to the heterodyne input of the mixer, and the output of the reference frequency of the exciter with the reference frequency input of the block of quadrature phase detectors, characterized in that an amplitude detector, an interference detector, an analysis unit, and frequency control, series-connected digital matched filter, range gating unit, complex envelope shaper and multi-channel th Doppler frequency filter, serially connected quadrature combining unit, first threshold comparison unit, primary processing device, secondary processing device and range finder, second threshold comparison unit and classifier connected in series, as well as a multi-channel frequency component detector, the input of which is connected to the multi-channel outputs filter Doppler frequencies, and the output with the inputs of the second block comparison with a threshold, and the input of the amplitude detector is connected to the output of the amplifier intermediate frequency, the input and output of the control signals to stop the frequency tuning of the analysis and frequency control unit are connected to the output and input of the secondary processing device and the frequency adjustment unit of the same name, the second output of which is connected to the input of the driving frequency in the current sensing period of the frequency analysis and control unit, output bearing of the target of the secondary processing device is connected to the second input of the antenna, the second output of which is connected to the information input of the primary processing device, input hour the pulse repetition frequencies of the probe pulses of which and the same inputs of the pulse modulator and code generator are connected to the third output of the synchronizer, the second output of the clock frequency of which is connected to the clock inputs of the code generator, primary processing device, range finder and digital matched filter, the input of code symbols of which is connected to the output of the code generator and the outputs of the quadrature components of the compressed signal with the block combining quadrature, the output of which through the first block comparison with the threshold is connected to the normalized rangefinder signals, the range gate output of which is connected to the control input of the range gating block, the outputs of the quadrature phase detector block are connected to the corresponding inputs of the digital matched filter, the classifier output is connected to the target indication input of the secondary processing device, the fourth synchronizer output is connected to the second generator input codes and the third input of the range finder, and the fifth output of the synchronizer to the second input of the intermediate frequency amplifier and the second input bnaruzhielya interference.  2. The station according to claim 1, characterized in that the frequency tuning unit comprises a noise generator, a limiter amplifier, a switch, the control input of which is an input of the control signals to stop the frequency tuning, and a counter whose outputs are bitwise connected to the inputs of circuit I, the control input of which is connected to the synchronization input of the frequency tuning unit, and the outputs of the AND circuit are bitwise connected to the inputs of the register connected to the decoder, the discharge outputs of which form the first output of the rear frequency in the current sensing period of the frequency tuning block, the second output of which is the register output. 3. The station according to claim 1, characterized in that the exciter contains a quartz reference frequency generator, a mixer, a multiplier by n ₁ , three multipliers by n ₂ and n _f crystal oscillators connected to the corresponding gate amplifiers, the control inputs of which are connected to the outputs of the discharges the decoder of the frequency adjustment unit, and the outputs are connected to the input of the frequency multiplier n ₁ , the output of which is connected to the inputs of the first frequency multiplier by n ₂ and the mixer, the second input of which is connected to the output of the reference frequency crystal oscillator, another the output of which is connected to the input of the third frequency multiplier by n ₂ , the mixer output is connected to the input of the second frequency multiplier by n ₂ , the output of which is the signal output of the pathogen, the outputs of the local oscillations and the reference frequency of which are the outputs of the first and third frequency multipliers by n _2, respectively where n _{f is the} number of operating points of the frequency adjustment, n ₁ and n _{2 are} the multiplication factors.  4. The station according to claim 1, characterized in that the frequency analysis and control unit comprises an inverter, circuit I and random access memory, and the input of the interference detection signal of the frequency analysis and control unit through an inverter is connected to the control input of circuit I, the signal input which is the input of the driving frequency in the current sensing period, and the output is connected to the random access memory, the second input and output of which are the input and output of the control signal to stop the frequency tuning of the analysis unit and a frequency control.  5. The station under item 1, characterized in that the primary processing device contains n 1 series-connected shift registers, an adder, a digital comparator, an evaluation unit, a range meter, an azimuth meter and random access memory device, and the signal input of the first of the shift registers is connected to the input of the normalized signals of the primary processing device, the inputs and outputs of each shift register are connected bitwise to the inputs of the adder, the output of which is connected through a digital comparator to the input of the unit pricing, the two outputs of which are connected to the signal inputs of the range meter and the azimuth meter, the outputs of which are connected to the two inputs of the target memory, the output of which is the output of the primary processing device, the information input of which is connected to the second input of the azimuth meter, the input of the pulse repetition frequency connected to the second input of the range meter, the third input of which is combined with the control inputs of the shift registers and connected to the clock input x preprocessing unit pulses.  6. The station according to claim 1, characterized in that the range finder comprises a range discriminator, a code, a time interval, a key circuit and a reversible counter, the first input of the range finder coordinate being connected to the installation input of the reversing counter and the control input of the key circuit, the output of which is connected to a counting input of a reversible counter, and a signal input with an output of a range discriminator, the first input of which is an input of normalized rangefinder signals, the synchronization and clock frequencies are th connected to second and third inputs of the code converter timeslot, a first input coupled to an output of down counter and an output connected to a second input of the discriminator and the output range gate range rangefinder.  7. The station according to claim 1, characterized in that the block combining the quadratures contains two quartertravers, the inputs of which are the inputs of the block combining the quadratures, and an adder whose inputs are connected to the outputs of the quadrants, and the output is the output of the block combining quadratures.

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