KR102014147B1 - Motor driving apparatus and home appliance including the same - Google Patents

Abstract

The present invention relates to a motor drive device and a home appliance having the same. A motor driving apparatus according to an embodiment of the present invention includes a capacitor, a three-phase phase arm switching element and a lower arm switching element, and converts a DC power source into an AC power source by a switching operation, and outputs the converted AC power source to the motor. And an output current detector configured to detect an output current flowing through the motor, and a first dead band, which is a current non-sensing region of one phase in one switching period, for the phase-arm switching element. And an inverter controller for controlling the turn-on time for the phase-arm switching element to be shifted in the second dead band, which is the current non-sensing region of the two phases within one switching period, without shifting the on time. Accordingly, in the space vector based pulse width variable control, the shift in the dead band can be minimized and the phase current can be detected accurately.

Description

Motor driving apparatus and home appliance having the same {Motor driving apparatus and home appliance including the same}

The present invention relates to a motor driving device and a home appliance having the same. More particularly, in a space vector based pulse width variable control, a motor capable of minimizing a shift in a dead band and accurately detecting a phase current can be obtained. A drive device and a home appliance having the same.

A home appliance is a device used for user convenience.

In addition, home appliances such as clothes dryers, washing machines, refrigerators, and air conditioners used in homes each perform unique functions and operations according to a user's operation.

On the other hand, the motor drive device is a device for driving a motor having a rotor and a coiled stator in a rotational motion, in particular can be used to drive a motor in a home appliance.

In the control method of the motor drive device, there is a sensor type motor drive device using a sensor. Recently, a sensorless motor drive device has been widely used due to a reduction in manufacturing cost.

In order to drive the sensorless motor driving device stably, a control method capable of detecting a phase current in a dead band is required.

On the other hand, conventionally, PWM (Pulse Width Modulation) shift of one phase is performed in the first dead band where the current of one phase is not detectable, and PWM shift of the two phases is performed in the second dead band where the current of the two phases is not detectable.

However, conventionally, in order to sense the current of two phases in the second dead band, the shift time of the switching vector has to be set long, so that in the vector control, the distortion of the voltage vector occurs and the current ripple is There is a problem that increases.

In addition, in the conventional control method, the synthesis vector for one PWM period is the same as the value calculated by the control result, but the effective vector for the half cycle is different from the value obtained by the control result, resulting in an inaccurate result of phase current sensing. There is also a problem.

Disclosure of Invention An object of the present invention is to provide a motor driving apparatus capable of minimizing a shift in a dead band and accurately detecting a phase current in a pulse width variable control based on a space vector, and a home appliance having the same.

In order to achieve the above object, a motor driving apparatus according to an embodiment of the present invention includes a capacitor, a three-phase phase arm switching element, and a lower arm switching element, and converts a DC power source into an AC power source by a switching operation, and converts the power source. In the first dead band which is disposed between the inverter for outputting the alternating current AC power to the motor, the output current detector for detecting the output current flowing through the motor, and the current non-sensing region of one phase in a switching cycle And an inverter controller for controlling the turn-on time for the phase-arm switching element to be shifted in the second dead band, which is a current sense region of the two phases within a switching period, without shifting the turn-on time for the phase-arm switching element. do.

In order to achieve the above object, a home appliance according to another embodiment of the present invention includes a capacitor, a three-phase phase arm switching element, and a lower arm switching element. In the first dead band which is disposed between the inverter for outputting the alternating current AC power to the motor, the output current detector for detecting the output current flowing through the motor, and the current non-sensing region of one phase in a switching cycle And an inverter controller for controlling the turn-on time for the phase-arm switching element to be shifted in the second dead band, which is a current sense region of the two phases within a switching period, without shifting the turn-on time for the phase-arm switching element. do.

The motor driving apparatus according to the embodiment of the present invention does not shift the turn on time for the switching device in the first dead band, but shifts the turn on time for the switching device in the second dead band, thereby minimizing the PWM shift. There is an advantage that it can.

In addition, the motor driving apparatus can minimize the PWM shift, thereby reducing the distortion and the current ripple of the voltage vector due to the PWM shift.

In addition, the motor driving apparatus can reduce the distortion of the voltage vector and the current ripple, thereby reducing the electrical noise.

In addition, since the motor driving device shifts the turn-on time of the switching element only for the second dead band, its implementation is easy.

In addition, the motor driving apparatus, in the second dead band, calculates the application time of the two valid vectors, and compares the effective vector application time of the second switching vector and the effective vector application time of the other switching vector, Since the turn-on time of the second turn-off switching vector is controlled to be shifted left or right, efficient control in PWM shift is possible.

In addition, since the motor driving device secures the minimum effective vector application time by shifting the turn-on time of the switching element in the second dead band, phase current detection of one phase is possible even in the second dead band.

In addition, since the motor driving device minimizes the shift time in order to sense the phase current of one phase in the second dead band, it is possible to reduce the distortion and the current ripple of the synthesized voltage vector.

In addition, the motor driving device calculates the minimum effective vector application time in consideration of not only dead time, settling time, and analog digital conversion time but also switching margin and analog digital conversion time margin, thereby enabling more stable phase current detection.

In addition, the motor driving device has an advantage of enabling accurate phase current estimation due to stable phase current sensing.

In addition, since the motor drive device detects the phase current by time division using one shunt resistor element, the manufacturing cost is reduced and its installation is easy.

The home appliance according to the embodiment of the present invention does not shift the turn-on time for the switching device in the first dead band, but shifts the turn-on time for the switching device in the second dead band, and thus, pulse width modulation (PWM) The advantage is that the shift can be minimized.

1 is an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention.
FIG. 2 is an example of an internal circuit diagram of the motor drive device of FIG. 1.
3 is an internal block diagram of the inverter control unit of FIG. 2.
4 is a diagram illustrating an example of the output current detection unit of the motor drive autonomous according to the embodiment of the present invention.
5A to 5C are diagrams referred to for describing a current estimation technique.
6 is a diagram referred to explain the minimum valid vector application time.
7A to 7D are views referred to for describing the dead band.
8A to 8D are diagrams illustrating a switching timing shift technique of the motor driving apparatus according to the embodiment of the present invention.
9 is a flowchart illustrating a method of operating a motor driving apparatus according to an embodiment of the present invention.
FIG. 10 is a diagram referred to for describing the operation method of FIG. 9.
11 is a view showing a clothes dryer as an example of a home appliance according to an embodiment of the present invention.
12 is a schematic view of the clothes dryer of FIG. 11.
13 is a view showing an air conditioner as another example of a home appliance according to an embodiment of the present invention.
14 is a schematic diagram of the outdoor unit and the indoor unit of FIG. 13.
15 is a view illustrating a refrigerator that is another example of a home appliance according to an embodiment of the present invention.
FIG. 16 is a diagram schematically illustrating a configuration of the refrigerator of FIG. 15.

Hereinafter, with reference to the drawings will be described the present invention in more detail.

The suffixes "module" and "unit" for components used in the following description are merely given in consideration of ease of preparation of the present specification, and do not impart any particular meaning or role by themselves. Therefore, the "module" and "unit" may be used interchangeably.

Terms including ordinal numbers such as first and second may be used to describe various components, but the components are not limited by the terms. The terms are used only for the purpose of distinguishing one component from another.

In this application, the terms "comprises" or "having" are intended to indicate that there is a feature, number, step, operation, component, part, or combination thereof described in the specification, and one or more other features. It is to be understood that the present invention does not exclude, in advance, the existence or the possibility of adding numbers, steps, operations, components, parts, or combinations thereof.

The motor driving apparatus 220 described in the present specification has a rotor position of a motor by a sensorless method, in which a sensing unit is not provided, such as a hall sensor that senses a rotor position of a motor. It is a motor drive device that can be estimated. Hereinafter, a sensorless motor drive device will be described.

1 is an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention, and FIG. 2 is an example of an internal circuit diagram of the motor driving apparatus of FIG.

Referring to the drawings, the motor driving apparatus 220 according to the exemplary embodiment of the present invention is for driving a motor in a sensorless manner, and may include an inverter 420 and an inverter controller 430.

In addition, the motor driving apparatus 220 according to the embodiment of the present invention may further include a converter 410 for converting the input AC power to DC power and outputting the same.

In addition, the motor driving device 220 according to the embodiment of the present invention, the input current detector (A), reactor (L), dc terminal capacitor (C), dc terminal voltage detector (B), output current detector (E) It may further include.

Meanwhile, the inverter controller 430 according to an exemplary embodiment of the present invention may control the switching element in the inverter 420 by controlling a pulse width modulation (PWM) variable based on a space vector.

In particular, the inverter controller 430 does not shift the turn-on time of the switching element in the first dead band which is the current non-sensing region of one phase, and in the second dead band which is the current non-sensing region of the two phases, The turn on time of the switching element can be shifted.

Accordingly, the turn-on time shift of the switching element can be minimized, thereby reducing the distortion of the voltage vector and the current ripple.

In addition, the inverter controller 430 may estimate the phase current based on any one of the switching vectors having the effective vector applying time of the minimum effective vector applying time or more in the first dead band.

In addition, the inverter control unit 430 has a phase current based on any one switching vector having an effective vector applying time that is equal to or greater than the minimum effective vector applying time in a state where the turn-on time of the switching element is shifted in the second dead band. Can be estimated.

For example, the motor driving device 220 may further include one shunt resistor element disposed between the dc terminal capacitor C and the inverter 420, and the inverter control unit 430 may include a first resistor. In one dead band or the second dead band in which the turn-on time of the switching element is shifted, it is possible to sense the current of one phase.

In addition, the inverter controller 430 may estimate the phase current of the other phase based on the detected slope of the current of the phase and the voltage vector application time by the voltage command value.

However, the motor driving device 220 according to the present invention is not limited to the above-described example as long as it is a method of estimating the current of the other phase in a state of sensing the current of one phase.

 The inverter controller 430 may calculate a minimum effective vector application time in consideration of not only dead time, stable time, and analog conversion time, but also switching time margin and analog digital conversion time margin. .

Accordingly, the inverter controller 430 increases the minimum effective vector application time due to the switching time margin and the analog to digital conversion time margin, thereby enabling the phase current to be detected more accurately.

The inverter controller 430 may calculate the remaining one phase current based on the two phase currents calculated in the first dead band or the second dead band. In this case, the inverter controller 430 may calculate the remaining one phase current using the phase balance theory.

Hereinafter, the operation of each component unit in the motor driving device 220 of FIGS. 1 and 2 will be described.

The reactor L may be disposed between the input AC power supply 405 and the converter 450 to perform a power factor correction or a boosting operation. In addition, the reactor (not shown) may perform a function of limiting harmonic currents due to high speed switching of a converter or the like.

The input current detector A can detect the input current is input from the commercial AC power supply 405. To this end, as the input current detector A, a current transformer (CT), a shunt resistor, or the like may be used. The detected input current is, as a discrete signal in the form of a pulse, may be input to the inverter controller 430.

The converter 410 converts the commercial AC power supply 405 which passed through the reactor L into DC power, and outputs it to a dc terminal. Although the commercial AC power supply 405 is shown as a single phase AC power supply in the figure, it may be a three phase AC power supply. The internal structure of the converter 410 may also vary according to the type of the commercial AC power source 405.

Meanwhile, the converter 410 may be formed of a diode or the like without a switching element, and may perform rectification without a separate switching operation.

For example, in the case of single phase AC power, four diodes may be used in the form of a bridge, and in the case of three phase AC power, six diodes may be used in the form of a bridge.

On the other hand, the converter 410, for example, a half-bridge type converter that is connected to two switching elements and four diodes may be used, and in the case of a three-phase AC power supply, six switching elements and six diodes may be used. . In this case, the converter 410 may be referred to as a rectifier.

When the converter 450 includes a switching element, the boosting operation, the power factor improvement, and the DC power conversion may be performed by the switching operation of the switching element.

The dc terminal capacitor C is connected across dc and smoothes and stores the input power. In the figure, one device is exemplified by the dc terminal capacitor C, but a plurality of devices may be provided to ensure device stability.

On the other hand, in the figure, but is illustrated as being connected to the output terminal of the converter 410, but is not limited to this, the DC power may be directly input. For example, direct current power from a solar cell may be directly input to a dc terminal capacitor (C) or may be input by direct DC / DC conversion. Hereinafter, the parts illustrated in the drawings will be mainly described.

On the other hand, since the DC power is stored at both ends of the dc terminal capacitor C, this may be referred to as a dc terminal or a dc link terminal.

The dc end voltage detector B may detect a dc end voltage Vdc that is both ends of the dc end capacitor C. To this end, the dc terminal voltage detector B may include a resistor, an amplifier, and the like. The detected dc terminal voltage Vdc may be input to the inverter controller 430 as a discrete signal in the form of a pulse.

The inverter 420 includes a plurality of inverter switching elements, converts the smoothed DC power supply Vdc into three-phase AC power supplies va, vb and vc of a predetermined frequency by turning on / off an operation of the switching device, It may output to the synchronous motor 230.

Inverter 420 is a pair of upper arm switching elements Sa, Sb, Sc and lower arm switching elements S'a, S'b, S'c, which are connected in series with each other, and a total of three pairs of upper and lower arms The switching elements are connected in parallel with each other (Sa & S'a, Sb & S'b, Sc & S'c). Diodes are connected in anti-parallel to each of the switching elements Sa, S'a, Sb, S'b, Sc, and S'c.

The switching elements in the inverter 420 perform on / off operations of the respective switching elements based on the inverter switching control signal Sic from the inverter controller 430. As a result, the three-phase AC power supply having the predetermined frequency is output to the three-phase synchronous motor 230.

The inverter controller 430 may control a switching operation of the inverter 420 based on a sensorless method. To this end, the inverter controller 430 may receive an output current io detected by the output current detector E. FIG.

The inverter controller 430 outputs an inverter switching control signal Sic to the inverter 420 to control the switching operation of the inverter 420. The inverter switching control signal Sic is a switching control signal of the pulse width modulation method PWM, and is generated and output based on the output current io detected by the output current detector E. FIG.

The output current detector E detects the output current io flowing between the inverter 420 and the three-phase motor 230. That is, the current flowing through the motor 230 is detected. The output current detector E may detect all of the output currents ia, ib, and ic of each phase, or may detect the output currents of the two phases by using three-phase equilibrium.

The output current detector E may be located between the inverter 420 and the motor 230, and a current trnasformer (CT), a shunt resistor, or the like may be used for current detection.

When a shunt resistor is used, three shunt resistors are located between the inverter 420 and the synchronous motor 230 or the three lower arm switching element elements S'a, S'b, S'c of the inverter 420. It is possible to connect one end to each).

Alternatively, two shunt resistors may be used to calculate the current of the remaining one phase using three phase equilibrium.

More preferably, one shunt resistor may be disposed between the dc terminal capacitor C and the inverter 420. This method may be referred to as a 1-shunt method.

According to the one shunt method, the output current detection unit E flows to the motor 230 at the time division of the lower arm switching element of the inverter 420 by using one shunt resistor element (Rdc in FIG. 4). It is possible to detect a phase current which is an output current io.

The detected output current io may be applied to the inverter controller 430 as a discrete signal in the form of a pulse, and the inverter switching control signal Sic is generated based on the detected output current io. do. Hereinafter, it may be described in parallel that the detected output current io is the three-phase output current ia, ib, ic.

On the other hand, the three-phase motor 230 is provided with a stator and a rotor, each phase AC power of a predetermined frequency is applied to the coil of the stator of each phase (a, b, c phase), the rotor rotates Will be

Such a motor 230 may be, for example, a Surface-Mounted Permanent-Magnet Synchronous Motor (SMPMSM), an Interidcr Permanent Magnet Synchronous Motor (IPMSM), and a synchronous clock. Synchronous Reluctance Motor (Synrm) and the like. Of these, SMPMSM and IPMSM are permanent magnet synchronous motors (PMSMs) with permanent magnets, and synrms have no permanent magnets.

The load 231 is for performing an operation implemented in the home appliance 100 and may be configured differently for each home appliance 100.

For example, when the clothes dryer 100a of FIG. 16 includes the motor driving device 220, the load 231 may be a blowing fan (not shown) for supplying compressed air.

As another example, when the air conditioner 100b of FIG. 16 includes the motor driving device 220, the load 231 may be an indoor fan 109ab or an outdoor fan 105ab.

As another example, when the refrigerator 100c of FIG. 16 includes the motor driving device 220, the load 231 may be a refrigerator compartment fan (not shown) or a freezer compartment fan 144c.

More preferably, the motor driving device 220 of the present invention is for driving a compressor in the home appliance 100, and the load 231 of FIG. 1 may be a compressor for compressing a refrigerant.

3 is an internal block diagram of the inverter control unit of FIG. 2.

Referring to the drawings, the inverter controller 430 may include an axis converter 310, a speed calculator 320, a current command generator 330, a voltage command generator 340, an axis converter 350, And a switching control signal output unit 360.

The axis conversion unit 310 can convert the output currents (ia, ib, ic) detected by the output current detection unit (E) into two-phase currents (iα, iβ) of the stationary coordinate system.

On the other hand, the axis conversion unit 310 can convert the two-phase current (iα, iβ) of the stationary coordinate system into a two-phase current (id, iq) of the rotary coordinate system.

)를 추정하고, 추정된 위치를 미분하여, 속도(

)를 연산할 수 있다. The speed calculating unit 320 is based on the position value (based on the output current (ia, ib, ic) detected by the output current detecting unit (E).

), The derivative of the estimated position,

) Can be calculated.

)와 속도 지령치(ω^* _r)에 기초하여, 전류 지령치(i^* _q)를 생성한다. 예를 들어, 전류 지령 생성부(330)는, 연산 속도(

)와 속도 지령치(ω^* _r)의 차이에 기초하여, PI 제어기(335)에서 PI 제어를 수행하며, 전류 지령치(i^* _q)를 생성할 수 있다. 도면에서는, 전류 지령치로, q축 전류 지령치(i^* _q)를 예시하나, 도면과 달리, d축 전류 지령치(i^* _d)를 함께 생성하는 것도 가능하다. 한편, d축 전류 지령치(i^* _d)의 값은 0으로 설정될 수도 있다. On the other hand, the current command generation unit 330 has a calculation speed (

) And the current command value i ^* _q based on the speed command value ω ^* _r . For example, the current command generation unit 330 has a calculation speed (

) Based on the difference between the speed command value ω ^* _r and the PI controller 335, the PI control may be performed, and the current command value i ^* _q may be generated. In the drawing, although the q-axis current command value i ^* _q is illustrated as a current command value, it is also possible to generate | generate a d-axis current command value i ^* _d unlike a figure. On the other hand, the value of the d-axis current command value i ^* _d may be set to zero.

On the other hand, the current command generation unit 330 may further include a limiter (not shown) for restricting the level so that the current command value i ^* _q does not exceed the allowable range.

Next, the voltage command generation unit 340 includes the d-axis and q-axis currents i _d and i _q which are axis-converted in the two-phase rotational coordinate system by the axis conversion unit, and the current command value in the current command generation unit 330 ( Based on i ^* _d , i ^* _q ), the d-axis and q-axis voltage command values v ^* _d and v ^* _q are generated. For example, the voltage command generation unit 340 performs the PI control in the PI controller 344 based on the difference between the q-axis current i _q and the q-axis current command value i ^* _q , and q The axial voltage setpoint v ^* _q can be generated. In addition, the voltage command generation unit 340 performs the PI control in the PI controller 348 based on the difference between the d-axis current i _d and the d-axis current command value i ^* _d , and the d-axis voltage. The setpoint (v ^* _d ) can be generated. On the other hand, the voltage command generation unit 340 may further include a limiter (not shown) for restricting the level so that the d-axis and q-axis voltage command values (v ^* _d , v ^* _q ) do not exceed the allowable range. .

On the other hand, the generated d-axis and q-axis voltage command values v ^* _d and v ^* _q are input to the axis conversion unit 350.

)와, d축, q축 전압 지령치(v^* _d,v^* _q)를 입력받아, 축변환을 수행한다.The axis conversion unit 350 may be a position calculated by the speed calculating unit 320 (

), And the d-axis and q-axis voltage command values (v ^* _d , v ^* _q ) are input, and axis conversion is performed.

)가 사용될 수 있다.First, the axis conversion unit 350 converts from a two-phase rotation coordinate system to a two-phase stop coordinate system. At this time, the position calculated by the speed calculating unit 320 (

) Can be used.

In addition, the axis conversion unit 350 performs a transformation from the two-phase stop coordinate system to the three-phase stop coordinate system. Through this conversion, the axis conversion unit 1050 outputs the three-phase output voltage command values v ^* a, v ^* b, v ^* c.

The switching control signal output unit 360 generates the switching control signal Sic for the inverter based on the pulse width modulation (PWM) method based on the three-phase output voltage command values (v ^* a, v ^* b, v ^* c). To print.

The output inverter switching control signal Sic may be converted into a gate driving signal by a gate driver (not shown) and input to the gate of each switching element in the inverter 420. As a result, each of the switching elements Sa, S'a, Sb, S'b, Sc, and S'c in the inverter 420 performs a switching operation.

On the other hand, the motor driving device 220, through the control of the inverter 420, in order to perform the vector (vector) control for driving the motor 230 can detect the output current flowing through the motor 230, in particular, the phase current have.

The inverter controller 430 may control the motor 230 at a desired speed and torque through the current command generator 330 and the voltage command generator 340 using the sensed phase current. .

4 is a diagram illustrating an example of an output current detection unit of the motor driving apparatus according to the embodiment of the present invention.

Referring to the drawings, the output current detector E may include a shunt resistor element Rdc disposed between the dc terminal capacitor C and the inverter 420.

The inverter controller 430 may calculate the current flowing in the motor 230 based on the current flowing through the dc stage resistance element Rdc, and control the inverter 420 based on the calculated motor current.

As shown in the drawing, a current acquisition method using a shunt resistor element Rdc is called a shunt algorithm.

The shunt algorithm is classified into 1-shunt, 2-shunt, and 3-shunt according to the position and the number of shunt resistor elements. The motor driving device 220 of the present invention may use a 1-shunt method. The 1-shunt method is described below.

According to this one-shunt method, three-phase currents (a, b, c phase currents) flowing through the motor 230 are obtained using only one shunt resistor element disposed in the dc stage.

Therefore, it is possible to detect phase current without a current sensor, and to reduce peripheral circuits such as a voltage amplifier and an A / D port, as compared with the two-shunt and three-shunt methods. In addition, the manufacturing cost and volume of the motor driving device 220 may be reduced.

The motor drive device 220 can detect the phase current using one shunt resistor element Rdc. In this case, the inverter controller 430 may control the switching element in the inverter 420 by controlling the variable width of the pulse vector based on the space vector.

On the other hand, when the application time of the effective vector, which will be described later, is smaller than the minimum effective vector application time, a dead band may be generated. In this case, the inverter controller 430 may determine whether to shift according to the type of the dead band.

In particular, the inverter control unit 430 does not shift the three-phase vector in the first dead band, which is the current non-sensing region of one phase, but left or right the three-phase vector in the second dead band, which is the current non-sensing region of the two phases. Can be shifted symmetrically.

The inverter controller 430 may estimate another phase current based on one phase current sensed in the first dead band. In addition, the inverter controller 430 may estimate another phase current in the second dead band based on one phase current sensed in a state in which the three phase vector is sheeted. In addition, the inverter controller 430 may calculate the three-phase current using the three-phase balance based on the calculated two-phase current.

5A to 5C are diagrams referred to for describing a current estimation technique.

More specifically, FIG. 5A is a diagram illustrating switching of each switching element in the inverter 420 corresponding to the first valid vector and the second valid vector, and FIG. 5B is a current path in the first valid vector. It is a figure which illustrates.

Referring to the drawings, a space vector based voltage vector may be generated according to a switching combination of each switching element in the inverter 420.

As shown in FIGS. 7A to 7B, when all of the phase arm switching elements Sa, Sb, and Sc in the inverter 420 are On, they correspond to the zero vector of V0 111 and have lower arm switching. When the elements S'a, S'b and S'c are all On, they correspond to the zero vector of V7 (000). In other words, two zero vectors exist in the space vector region 800.

In addition, six effective vectors (V1 through V6) exist on the space vector except two zero vectors.

Meanwhile, the voltage vector v * may be generated by combining the first valid vector V1 and the second valid vector V2. The voltage vector v * may be generated by the voltage command generator 340 of FIG. 3.

The 1-shunt method detects a phase current from the shunt resistor element Rdc when an effective vector is applied in a control period Ts for a space vector based PWM (SVPWM) and converts the detected phase current into analog digital ( A / D) conversion, and the gate signal generation unit (not shown) in the switching control signal output unit 360 (Fig. 3) determines the current sector and the effective vector, and restores the phase current. At this time, since the vector is applied within one period Ts, two phase currents can be restored, and the other one phase current is obtained by using the sum of three phase currents equal to zero.

In FIG. 5A, the region S51 is a region in which the first phase arm switching element Sa is turned on, the second phase arm switching element Sb is turned off, and the third phase arm switching element Sc is turned off. Corresponds.

In FIG. 5B, the first lower arm switching element S'a, the second lower arm switching element S'b, and the third lower arm switching element S'c are attached to each of the upper arm switching elements Sa, Sb, and Sc. Complementary operation, the input current is input via the first upper arm switching element Sa, so that the motor 230, the second lower arm switching element S'b and the third lower arm switching element S'c Via is applied to the shunt resistor element Rdc. In the figure, a first current path Path 1 is illustrated.

Therefore, the output current detector Edc detects ia, which is a phase current, during T2 / 2 time, which is the application time of the first effective vector V1.

The output current detector Edc may detect -ic, which is a c-phase current, for a time T1 / 2 which is an application time of the second effective vector V2 in the same manner.

The inverter controller 430 may obtain ib, which is the remaining b-phase current, through an internal calculation.

5C is a diagram illustrating the state of the motor current detected by the output current detector Edc for each vector.

Referring to the drawings, for the first valid vector in sector 1, a current Ias, which is a phase current, is detected through the shunt element Rdc, and for the second valid vector in sector 2, the shunt resistor element Rdc. The -Ics current, which is the c phase current, is detected, and the Ibs current, which is the b phase current, is detected, via the shunt resistor element Rdc, for the third effective vector in the sector 3, and the fourth effective vector in the sector 4 With respect to the shunt resistor element Rdc, a phase current of -Ias current is detected, and for the fifth effective vector in sector 5, through the shunt resistor element Rdc, the c phase current Ics current is detected. For the sixth effective vector in sector 6, the -Ibs current, which is the b phase current, is detected via the shunt resistor element Rdc.

On the other hand, current detection is impossible through the shunt resistor element Rdc for the V0 and V7 vectors, which are zero vectors.

6 is a diagram referred to explain the minimum valid vector application time.

Referring to the drawings, as described above, the inverter controller 430 may detect the current flowing through the shunt resistor element Rdc in the effective vector section, and detect the phase current.

At this time, when the interval to which the effective vector is applied is short, that is, when the application time of the effective vector is smaller than the minimum valid vector application time Tmin, a problem occurs in detecting phase current.

The inverter controller 430 may include a dead time Td for preventing an arm short of the switching element in the inverter 420, and a ringing occurring when switching of the switching element in the inverter 420. The minimum effective vector application time Tmin can be calculated in consideration of the settling tie Ts and the analog-to-digital conversion time Tad during sampling.

In particular, the inverter control unit 430 considers the switching time margin Tm1 due to the switching of the switching element in the inverter 420 and the analog-to-digital conversion time margin Tm2 at the time of sampling to be the minimum effective. The vector application time Tmin can be calculated.

As a result, the minimum valid vector application time Tmin is calculated as shown in Equation 1 below.

That is, the minimum vector application time Tmin is a dead time Td for preventing arm short of the switching element in the inverter 420, and occurs when switching the switching element in the inverter 420. The settling tie Ts according to the ringing phenomenon, the analog-to-digital conversion time Tad at sampling, the switching time margin Tm1 due to the switching of the switching elements in the inverter 420, and It may correspond to the sum of the analog-digital conversion time margin Tm2 at the time of sampling.

For example, the minimum vector application time (Tmin) is a dead time (Td) 2us, settling time (Ts) 3us, analog digital conversion time (Tad) 2us, switching time margin (Tm1) 0.5us and analog digital conversion time The margin (Tm1) may be 8us plus 0.5us.

Accordingly, the motor driving device 220 considers not only the dead time Td, the settling time Ts, the analog digital conversion time Tad, but also the switching margin Tm1 and the analog digital conversion time margin Tm2. Since the minimum effective vector application time (Tmin) is calculated, more stable phase current detection is possible.

On the other hand, the case where the application time of the effective vector is smaller than the minimum effective vector application time Tmin will be described with reference to Figs. 7A to 7D.

7A to 7D are views referred to for describing the dead band.

Referring to the drawings, FIG. 7A illustrates a case where an application time of one valid vector is less than a minimum effective vector application time Tmin in a switching period in a space vector based PWM (SVPWM) hexagon.

According to FIG. 7A, in the region around the first to sixth valid vector, a region S71 in which the current of one phase is undetectable is generated through the shunt resistor element Rdc, which is the first non-measurable region or the first effective vector. It can be called a dead band.

FIG. 7B illustrates a case where the application time of two valid vectors within a switching period is smaller than the minimum effective vector application time Tmin in a space vector based PWM (SVPWM) hexagon.

 According to FIG. 7B, in the region around the zero vector, a region S72 in which the two phase currents are not detectable is generated through the shunt resistor element Rdc, and the second measurement is distinguished from the non-measurable region. It may be called an impossible region or a second dead band.

FIG. 7C is a diagram illustrating the switching of each switching element in the inverter 420 corresponding to the voltage vector, which is unable to detect current in the first dead band.

In FIG. 7C, the section S74 by the first valid vector V1 is larger than the minimum valid vector application time Tmin, while the section S73 by the second valid vector V2 is the minimum valid vector application time. It becomes smaller than (Tmin). Accordingly, in the period S74, current detection of phase a is possible, but in phase S73, current detection of phase c is impossible.

FIG. 7D is a diagram illustrating switching of each switching element in the inverter 420 corresponding to the voltage vector, in which the current cannot be detected in the second dead band.

In FIG. 7D, both the section S75 by the first valid vector V1 and the section S76 by the second valid vector V2d are smaller than the minimum valid vector application time Tmin. Accordingly, in the sections S75 and S76, current detection of phase a and phase c is impossible.

On the other hand, in such a dead band, when the current detection is not performed, accurate motor control cannot be performed.

In order to prevent such an undetectable region from occurring, the switching vector of one phase is shifted in the first dead band, and the switching vector of two phases is shifted in the second dead band.

However, such a method has a problem that a frequent shift of the switching vector causes distortion in the voltage vector, which may cause noise.

The present invention proposes a method for minimizing shift in dead band and accurately detecting phase current in spatial vector based pulse width variable control.

8A to 8D are diagrams illustrating a switching timing technique of the motor driving apparatus according to the embodiment of the present invention.

More specifically, FIGS. 8A to 8D are diagrams for explaining the shift of the switching vector in the second dead band.

The inverter controller 430 may control the turn-on time with respect to the phase cancer switching elements Sa, Sb, and Sc in the second dead band.

The inverter controller 430 controls the turn-on time corresponding to the first switching-off switch vector in the switching period of the three-phase switching vector to the left in the second dead band, and shifts the third shifting period to the left. The turn on time corresponding to the switching vector to be turned off may be controlled to be shifted to the right.

8A to 8D, in the switching cycle, the third phase arm switching element Sc is first turned off, the second phase arm switching element Sb is turned off the second time, and the first phase arm switching element is turned off. Illustrate that (Sa) is turned off a third time.

8A to 8D, the inverter controller 430 may shift the turn on time corresponding to the switching vector of the third phase arm switching element Sc, which is turned off first, to the left within one switching period. .

In addition, the inverter controller 430 may shift the turn-on time corresponding to the switching vector of the first phase arm switching element Sa, which is turned off for the third time, to the right within a period of switching.

Inverter control unit 430, in the second dead band, the turn on time corresponding to the second switching-off switching vector in the switching period of the three-phase switching vector, the smaller than the minimum effective vector application time (Tmin) two Based on the application time of the effective vector, it can be controlled to shift left or right.

The inverter control unit 430 determines that the valid vector applying time Tb of the switching vector turned off the second of the valid vectors applying time of the two valid vectors smaller than the minimum valid vector applying time Tmin is the other valid vector applying time. If greater than Ta (Tb> Ta), the turn-on time corresponding to the second turn-off switching vector is shifted in the same direction as the moving direction of the switching vector having the smaller value among the two effective vector application times. Can be controlled.

In FIG. 8A, since the effective vector applying time Tb of the second turn-off switching vector is greater than the other valid vector applying time Ta, the inverter controller 430 performs a second operation within a switching period. The turn-on time corresponding to the switching vector of the second upper arm switching element Sb which is turned off may be controlled to be shifted to the right in the same direction as the shift direction of the first upper arm switching element Sa.

The inverter control unit 430 determines that the valid vector applying time Tb of the switching vector turned off the second of the valid vectors applying time of the two valid vectors smaller than the minimum valid vector applying time Tmin is the other valid vector applying time. If less than (Ta) (Tb <Ta), the turn-on time corresponding to the second turn-off switching vector is the opposite of the direction of travel of the switching vector, which has the greater value, during the application time of the two effective vectors. It can be controlled to be shifted.

In FIG. 8C, since the effective vector applying time Tb of the second turn-off switching vector is smaller than the other valid vector applying time Ta, the inverter controller 430 performs a second operation within a switching period. The turn on time corresponding to the switching vector of the second upper arm switching element Sb which is turned off may be controlled to be shifted to the left side opposite to the shift direction of the first upper arm switching element Sa.

That is, the inverter controller 430 compares the application time of the two valid vectors in the second dead band, and determines the shift direction of the second switching vector to be turned off, thereby providing efficiency of the shift control.

At this time, the shift time Tsh is determined by the following equation (2).

In Equation 2, Tx is the application time of the effective vector having the smaller value among the application times of the two effective vectors in the second dead band.

For example, in FIG. 8A, the application time of the effective vector having the smaller value among the application time of the two valid vectors is Ta, and thus Tx may be Ta.

As another example, in FIG. 8C, since the application time of the effective vector having a smaller value among the application time of the two valid vectors is Tb, Tx may be Tb.

Accordingly, the inverter controller 430 shifts the turn-on time for the phase-arm switching element in the second dead band, but the application time of the effective vector having the smaller value among the application time of the two effective vectors, and the minimum effective vector. The difference in the applied time can be calculated and controlled to shift by half of the calculated time difference. In addition, a code | symbol means the shift direction of a switching vector, + means a right side, and-means a left side.

In FIG. 8B, the inverter controller 430 shifts the switching vector of the first upper arm switching element Sa to the right by Tsh, and shifts the switching vector of the third upper arm switching element Sc to the left by Tsh. As a result of shifting the switching vector of the two phase arm switching element Sb to the right by Tsh, the effective vector application time Tb 'of the second phase arm switching element Sb satisfies the minimum effective vector application time Tmin (Tb). '= Tmin).

In addition, in FIG. 8D, the inverter controller 430 shifts the switching vector of the first upper arm switching element Sa to the right by Tsh, and shifts the switching vector of the third upper arm switching element Sc to the left by Tsh. As a result of shifting the switching vector of the second phase arm switching element Sb to the left by Tsh, the effective vector application time Ta 'of the first phase arm switching element Sb satisfies the minimum effective vector application time Tmin. (Ta '= Tmin).

8B and 8D, since the switching vector of one phase secures the minimum effective vector applying time Tmin, the inverter controller 430 may detect the current of one phase and estimate the current of the other two phases.

For example, the inverter controller 430, in the second dead band, shifts the turn-on time for the phase arm switching element, senses the current of one phase, and converts the current of the other phase based on a switching pattern, an application time, and the like. , Can be estimated. In addition, the phase equilibrium theory can be used to calculate the total three-phase current.

On the other hand, in the past, the shift was performed to detect the current of the two phases in the second dead band, the motor drive device 220 of the present invention, in order to detect the current of one phase in the second dead band, Do it at a minimum.

In addition, since the motor driving device 220 of the present invention determines the shift time Tsh by considering the switching time margin Tm1 and the analog-digital conversion time margin Tm2, the current of one phase is stably sensed. Accurate total three-phase currents can be estimated.

9 is a flowchart illustrating a method of operating a motor driving apparatus according to an embodiment of the present invention, and FIG. 10 is a view referred to for describing the operation method of FIG. 9.

Referring to the drawings, the inverter controller 430 may control the switching element in the inverter 420 by controlling the pulse width variable based on the space vector.

The inverter controller 430 may calculate whether the first dead band is present at the sampling time point of the switched cycle (S910).

Inverter control unit 430, the first dead band in any one of the effective vector application time is less than the minimum effective vector application time (Tmin) within the switching period, for the phase arm switching elements (Sa, Sb, Sc) You can not shift the turn on time.

Accordingly, the motor driving device 220 may minimize the shift of the switching vector, reduce distortion of the voltage vector and current ripple, and reduce electrical noise.

The inverter controller 430 may sense the one-phase current in the first dead band based on any other valid vector greater than the minimum valid vector application time Tmin (S911).

The inverter controller 430 may estimate and calculate currents of the other two phases based on the sensed one-phase current (S913).

When the sampling point of the switched period is not the first dead band, the inverter controller 430 may calculate whether it corresponds to the second dead band (S920).

The inverter controller 430 may sense the two-phase current at the sampling time point of the switched cycle, if it does not correspond to the second dead band (S921), and calculate the total three-phase current using the phase equilibrium theory. There is (S923).

Inverter control unit 430, the second dead band, any two effective vector application time in the switching period is less than the minimum effective vector application time (Tmin), for the phase arm switching elements (Sa, Sb, Sc) The turn on time can be shifted.

In more detail, the inverter controller 430 may calculate an effective vector application time of the switching vector (S930).

In addition, the inverter controller 430 may calculate the shift direction based on the effective vector application time of the switching vector (S940).

The inverter controller 430 may calculate that the shift direction of the first switching vector turned off in one cycle of the three-phase switching vectors is left.

The inverter controller 430 may calculate that the shift direction of the third switching vector that is turned off within one cycle of the three-phase switching vector is the right side.

The inverter controller 430 may calculate the shift direction of the second switching vector that is turned off within one cycle of the three-phase switching vector as the left or the right based on the effective vector application time.

The inverter controller 430 may shift the turn on time of the switching vector based on the calculated shift direction (S950).

The inverter controller 430 may symmetrically shift the first switching-off vector in the switching cycle and the third switching vector in the switching cycle among the three-phase switching vectors.

That is, the inverter controller 430 may control the turn-on time corresponding to the first switching-off vector in the switching cycle among the three-phase switching vectors to be shifted to the left.

The inverter controller 430 may control the turn-on time corresponding to the third turn-off switching vector in the switched period to be shifted to the right.

The inverter controller 430 may control the turn-on time corresponding to the second turn-off switching vector of the three-phase switching vector to be shifted left or right based on the application time of the two valid vectors. Can be.

The inverter controller 430 may turn on a corresponding turn vector corresponding to the second turn off when the valid vector application time of the second switching vector is greater than the other valid vector application time within one switching period. The time may be controlled to be shifted in the same direction as the moving direction of the other switching vector.

The inverter controller 430 may turn on the corresponding switching vector to be turned off when the valid vector applying time of the second switching vector is less than the other valid vector applying time within one switching period. The time may be controlled to be shifted in a direction opposite to the moving direction of the other switching vector.

At this time, the shift time Tsh is determined by the above expression (2). In addition, the inverter controller 430 may shift the difference between the minimum effective vector application time Tmin and Tx to the left and the right by half, respectively. That is, in the motor drive device of the present invention, since the shift amount is reduced in the second dead band, current ripple is reduced and electrical noise is reduced.

The inverter controller 430 may sense the one-phase current based on any one of the effective vectors having the minimum valid vector application time Tmin by shifting the switching vector (S960).

The inverter controller 430 may estimate and calculate currents of the other two phases based on the sensed one-phase current (S913).

FIG. 10 is a diagram referred to the description of FIG. 9.

More specifically, FIG. 10A is an experimental result of shifting a switching vector by a conventional motor drive device to detect a two-phase current in a second dead band, and FIG. 10B illustrates a motor drive device 220 of the present invention. ) Is an experimental result of shifting a switching vector to sense current in one phase in the second dead band.

Referring to the drawings, in FIG. 10A, the conventional motor driving apparatus shifts the switching vector in order to sense current in two phases in the second dead band.

In contrast, in FIG. 10B, the motor driving apparatus of the present invention shifts the switching vector in order to sense the current of one phase in the second dead band. At this time, the inverter controller 430 divides half of the total shift time into left and right sides to control the switching vector to be shifted.

Therefore, compared with FIG. 10A, the shift amount of FIG. 10B is reduced. On the other hand, the current ripple according to the PWM shift control of the conventional motor drive device is 640mA, the current ripple according to the PWM shift control of the motor drive device 220 of the present invention is 457.5mA.

That is, the motor driving apparatus 220 of the present invention may reduce the current ripple by minimizing the shift of the switching vector. In addition, due to current ripple reduction, electrical noise can be reduced.

11 is a view showing a clothes dryer as an example of a home appliance according to an embodiment of the present invention.

Referring to the drawings, the clothes dryer (100a) according to the present invention is a cabinet (10), a drum disposed in the interior of the cabinet (30) of the laundry (foam) is accommodated and rotated therein, the drum A drive unit for rotating the 30, a heat pump module for heating the air circulated in the drum 30 to dry the laundry, heating the air circulated, and a blowing fan for circulating the air of the drum 30 (Fig. 12, 12), an intake duct through which the air circulated from the drum 30 is sucked, a heater (69 in FIG. 12) for heating the air introduced into the drum 30, and a circulation passage for guiding the flow of air. .

The cabinet 10 forms the exterior of the dryer and provides a space in which the drum 30 and other components are arranged. The cabinet 10 is formed in a rectangular parallelepiped shape as a whole.

The cabinet 10 has a door 20 disposed at the front thereof, and the door 20 is rotated in a left and right direction to open and close the inside of the cabinet 10.

The front cover 11 is provided with an inlet (not shown), and is provided with a door 20 for opening and closing the inlet. The inlet is in communication with the drum 30.

The control panel 17 may be disposed above the front cover 11. The control panel 17 includes a display (for example, LCD, LED panel, etc.) indicating the operating state of the dryer, and an operation unit (for example, a button, a dial, a touch screen, etc.) that receives an operation command for the dryer from the user. A speaker (not shown) for outputting a voice guidance, an effect sound or a warning sound for an operation state is included.

The drum 30 is disposed inside the cabinet 10, and the blower fan 64 and the heat pump module are disposed under the drum 30 to maximize the capacity of the drum 30.

Drum 30 is formed in a cylindrical shape, the front and the back is open and the front surface is in communication with the inlet. In addition, the drum 30 has an inlet (not shown) is formed in the back so that air is introduced, the inlet is connected to the circulation passage for air circulation.

The drum 30 is provided with a lifter therein, the lifter is rotated to lift the laundry therein, and then free fall. The drum is supported by a supporter (not shown) provided in the cabinet.

The drive unit includes a motor fixed to the base 14 of the cabinet 10. The motor provides power for rotating the drum, and is also connected to the blowing fan 64 to rotate the blowing fan. The motor is a biaxial motor, the drum 30 and the blowing fan 64 are connected to each drive shaft.

The blowing fan 64 may be rotated by the motor of the driving unit. When the blowing fan 64 is rotated, air discharged from the drum 30 is guided to the intake duct and supplied to the blowing fan 64. The intake duct is coupled to the front surface of the front supporter and is in communication with the intake port of the blower fan 64. The blowing fan 64 circulates the air so that the air sucked from the drum is introduced into the drum again through the heat pump module through the circulation passage.

When the drum 30 rotates forward, air is introduced into the inside from the rear side, and the air is discharged to the front side. In addition, during the reverse rotation of the drum, air flows into the front side, and the air can be discharged to the rear side.

The circulation passage may be configured in various ways according to the embodiment. The circulation passage guides the air discharged from the blower fan to flow into the heat pump module, and guides the air discharged from the heat pump module to flow into the drum through the heater. The circulation passage is also provided on the rear side of the drum to guide the heated air to the drum 30.

The filter assembly 19 is installed in the inlet to collect lint contained in the air discharged from the drum 30 and introduced into the suction duct.

The laundry contained in the drum 30 is dried by heated air supplied to the drum 30. The air discharged from the drum 30 is introduced into the circulation passage by collecting moisture evaporated from the laundry during the drying process, heated through the heat pump module, and then supplied to the drum again.

The heat pump module includes a compressor (50 in FIG. 12), a condenser (52 in FIG. 12), an evaporator (53 in FIG. 12), and an expansion valve.

In the heat pump module, the compressor 50, the condenser 52, and the evaporator 53 are connected to the refrigerant pipe so that the heated air is supplied to the drum through circulation of the refrigerant, and heat exchange between the refrigerant and the air in the condenser and the evaporator. do. In some cases, the heat pump module may exchange heat through a medium other than a refrigerant.

The evaporator 53 recovers the amount of air discharged by heat-exchanging the refrigerant and the air introduced from the drum 30 through the blower fan 64. In addition, the evaporator 53 condenses moisture impregnated in the introduced air.

The condenser 52 heat-exchanges the refrigerant having passed through the evaporator 53 with the refrigerant, and discharges the heated air to the drum. The low temperature and low humidity air passing through the evaporator flows into the condenser and is heat-exchanged with the refrigerant to be supplied to the drum in the state of high temperature and low humidity.

The refrigerant discharged from the condenser passes through the evaporator and is recovered to the compressor. The compressor 50 compresses the evaporated refrigerant and discharges it to the condenser, and the expansion valve expands the refrigerant condensed in the condenser 52 in the evaporator. The condenser 52 and the evaporator 53 are heat exchangers.

Since the hot and humid air discharged from the drum 30 has a higher temperature than the refrigerant of the evaporator 53, the heat amount of air is condensed and cooled by heat exchange with the refrigerant while passing through the evaporator. The hot humid air is thus dehumidified and cooled by the evaporator. Condensate generated during the air condensation may be collected and drained to a separate condensate housing (not shown).

In addition, the heat pump module may further include an auxiliary heat exchanger (not shown) and a cooling fan (not shown). The secondary heat exchanger (not shown) is constituted by a separate condensing module that is separate from the condenser 52. The auxiliary heat exchanger and the cooling fan may be configured as one module and may be separated from each other.

An auxiliary heat exchanger (not shown) is installed in the refrigerant pipe extending from the condenser to the expansion valve based on the flow direction of the refrigerant to cool the refrigerant discharged from the condenser.

The cooling fan cools the auxiliary heat exchanger by blowing outside air or internal air into the auxiliary heat exchanger.

12 is a schematic view of the clothes dryer of FIG. 11.

More specifically, FIG. 12 is a view referred to for explaining the air circulation and the refrigerant circulation of the dryer of FIG.

Referring to the drawings, as shown in FIG. 12, the air supplied to the drum 30 is heated by heating the laundry and discharging moisture evaporated from the laundry.

Air is circulated by the blower fan 64. Air flows into the evaporator 53 through the drum by the blowing fan 64, condenses in the evaporator, and flows into the condenser 52 in a state of low temperature and low humidity. The air is heat-exchanged with the refrigerant in the condenser 52, heated, and then flows back into the drum 30. The air may be further heated through the heater 69 installed on the circulation passage.

Either one of the heat pump module and the heater 69 can be selectively operated, and can be operated simultaneously. The air moves in the order of the drum 30, the evaporator 53, and the condenser 52.

The refrigerant is discharged to the condenser 52 in a state of high temperature and high pressure by the compressor 50, heat exchanged with air in the condenser, and then flows into the evaporator 53 and evaporates. An expansion valve 59 is installed between the condenser and the evaporator. The expansion valve expands the condensed refrigerant at low temperature and high pressure and delivers it to the evaporator. The expanded refrigerant is evaporated in the evaporator 53, flowed into the compressor 50 in a state of low temperature and low pressure, and then discharged into the condenser 52 in a state of high temperature and high pressure.

The compressor 50 of FIG. 12 may be driven by the motor driving device 220 as shown in FIG. 1 driving the compressor motor.

13 is a view showing an air conditioner as another example of the horn appliance according to the embodiment of the present invention.

As shown in FIG. 13, the air conditioner 100b according to the present invention may include an indoor unit 31b and an outdoor unit 21b connected to the indoor unit 31b.

The indoor unit 31b of the air conditioner may be any of a stand type air conditioner, a wall-mounted air conditioner, and a ceiling type air conditioner, but the drawing illustrates the stand type indoor unit 31b.

Meanwhile, the air conditioner 100b may further include at least one of a ventilation device, an air cleaning device, a humidifier, and a heater, and may operate in conjunction with the operation of the indoor unit and the outdoor unit.

The outdoor unit 21b includes a compressor (not shown) for receiving and compressing a refrigerant, an outdoor heat exchanger (not shown) for exchanging refrigerant and outdoor air, and an accumulator for extracting a gas refrigerant from the supplied refrigerant and supplying it to the compressor (not shown). And a four-way valve (not shown) for selecting a flow path of the refrigerant according to the heating operation. In addition, although a plurality of sensors, valves and oil recovery device, etc. are further included, the description of the configuration will be omitted below.

The outdoor unit 21b operates a compressor and an outdoor heat exchanger provided to supply refrigerant to the indoor unit 31b by compressing or heat-exchanging the refrigerant according to a setting. The outdoor unit 21b may be driven by the demand of the remote controller (not shown) or the indoor unit 31b. In this case, as the cooling / heating capacity is changed corresponding to the indoor unit being driven, the number of operation of the outdoor unit and the number of operation of the compressor installed in the outdoor unit may be changed.

At this time, the outdoor unit 21b supplies the compressed refrigerant to the connected indoor unit 31b.

The indoor unit 31b receives a coolant from the outdoor unit 21b and discharges cold air into the room. The indoor unit 31b includes an indoor heat exchanger (not shown), an indoor fan (not shown), an expansion valve (not shown) in which the refrigerant supplied is expanded, and a plurality of sensors (not shown).

At this time, the outdoor unit 21b and the indoor unit 31b are connected by a communication line to transmit and receive data, and the outdoor unit and the indoor unit are connected to a remote controller (not shown) by wire or wirelessly and operate under the control of a remote controller (not shown). can do.

The remote controller (not shown) may be connected to the indoor unit 31b to input a user's control command to the indoor unit, and receive and display state information of the indoor unit. At this time, the remote control may communicate by wire or wirelessly according to the connection form with the indoor unit.

14 is a schematic diagram of the outdoor unit and the indoor unit of FIG. 13.

Referring to the drawings, the air conditioner 100b is largely divided into an indoor unit 31b and an outdoor unit 21b.

The outdoor unit 21b includes a compressor 102b that serves to compress the refrigerant, a compressor electric motor 102bb that drives the compressor, an outdoor side heat exchanger 104b that serves to radiate the compressed refrigerant, and an outdoor unit. An outdoor blower 105b disposed on one side of the heat exchanger 104b and including an outdoor fan 105ab for promoting heat dissipation of the refrigerant and an electric motor 105bb for rotating the outdoor fan 105ab, and an expansion for expanding the condensed refrigerant The mechanism 106b, the cooling / heating switching valve 110b for changing the flow path of the compressed refrigerant, and the accumulator 103b for temporarily storing the gasified refrigerant to remove moisture and foreign matter and then supplying a refrigerant of a constant pressure to the compressor. And the like.

The indoor unit 31b is an indoor side heat exchanger 109b disposed indoors to perform a cooling / heating function, and an indoor fan 109ab and an indoor side disposed on one side of the indoor side heat exchanger 109b to promote heat dissipation of the refrigerant. The indoor blower 109b etc. which consist of the electric motor 109bb which rotates the fan 109ab are included.

At least one indoor side heat exchanger 109b may be installed. The compressor 102b may be at least one of an inverter compressor and a constant speed compressor.

In addition, the air conditioner 100b may be configured as a cooler for cooling the room, or may be configured as a heat pump for cooling or heating the room.

The compressor 102b in the outdoor unit 21b of FIG. 14 may be driven by a motor driving device 220 such as FIG. 1 which drives the compressor motor 102bb.

Alternatively, the indoor fan 109ab or the outdoor fan 105ab may be driven by the motor driving device 220 as shown in FIG. 1 which drives the indoor fan motor 109bb and the outdoor fan motor 150bb, respectively.

15 is a view showing a refrigerator as another example of a home appliance according to an embodiment of the present invention.

Referring to the drawings, the refrigerator 100c according to the present invention, although not shown, has a case 110c having an inner space partitioned into a freezer compartment and a refrigerator compartment, a freezer compartment door 120c that shields the freezer compartment, and a refrigerator compartment. A rough appearance is formed by the refrigerating compartment door 140c.

In addition, the front surface of the freezer compartment door 120c and the refrigerating compartment door 140c is further provided with a door handle 121c protruding forward, so that the user can easily grip and rotate the freezer compartment door 120c and the refrigerating compartment door 140c. Make it work.

On the other hand, the front of the refrigerator compartment door 140c may be further provided with a home bar 180c, which is a convenient means for allowing a user to take out a storage such as a beverage contained therein without opening the refrigerator compartment door 140c.

In addition, the front of the freezer compartment door 120c may be provided with a dispenser 160c, which is a convenience means for allowing the user to easily take out ice or drinking water without opening the freezer compartment door 120c, such a dispenser 160c. An upper side of the control panel 210c may be further provided to control the driving operation of the refrigerator 100c and to show a state of the refrigerator 100c being operated on the screen.

Meanwhile, although the dispenser 160c is illustrated as being disposed on the front surface of the freezer compartment door 120c, the present invention is not limited thereto, and the dispenser 160c may be disposed on the front side of the refrigerator compartment door 140c.

On the other hand, the inner upper portion of the freezer compartment (not shown) is an ice maker 190c for making water supplied using cold air in the freezer compartment, and an ice bank mounted inside the freezer compartment (not shown) so that the ice iced from the ice maker is iced and contained therein. 195c may be further provided. In addition, although not shown in the drawing, an ice chute (not shown) may be further provided to guide the ice contained in the ice bank 195c to fall into the dispenser 160c.

The control panel 210c may include an input unit 220c including a plurality of buttons, and a display unit 230c for displaying a control screen and an operation state.

The display unit 230c displays information such as a control screen, an operating state, and a temperature inside the refrigerator. For example, the display unit 230c may display a service type (eg, ice, water, or flake ice) of the dispenser, a set temperature of the freezer compartment, and a set temperature of the refrigerator compartment.

The display unit 230c may be implemented in various ways, such as a liquid crystal display (LCD), a light emitting diode (LED), and an organic light emitting diode (OLED). In addition, the display unit 230c may be implemented as a touch screen capable of performing the function of the input unit 220c.

The input unit 220c may include a plurality of operation buttons. For example, the input unit 220c may include a dispenser setting button (not shown) for setting a service type of the dispenser (ice cube, water, ice cubes, etc.) and a freezer compartment temperature setting button (not shown) for setting a freezer temperature. And, it may include a refrigerator compartment temperature setting button (not shown) for setting the freezer compartment temperature. The input unit 220c may be implemented as a touch screen that can also perform the function of the display unit 230c.

Meanwhile, the refrigerator according to the embodiment of the present invention is not limited to the double door type shown in the drawings, but is a one door type, a sliding door type, a curtain door type. (Curtain Door Type) and other forms.

FIG. 16 is a diagram schematically illustrating a configuration of the refrigerator of FIG. 15.

Referring to the drawings, the refrigerator 100c is provided with a compressor 112c, a condenser 116c for condensing the refrigerant compressed by the compressor 112c, and a refrigerant condensed by the condenser 116c, and evaporated. A freezer compartment evaporator 124c disposed in a freezer compartment (not shown) and a freezer compartment expansion valve 134c for expanding the refrigerant supplied to the freezer compartment evaporator 124c may be included.

On the other hand, in the drawing, but illustrated as using one evaporator, it is also possible to use each evaporator in the refrigerating chamber and freezing chamber.

That is, the refrigerator 100c is a three-way valve for supplying a refrigerator evaporator (not shown) arranged in the refrigerator compartment (not shown) and a refrigerant condensed in the condenser 116c to the refrigerator compartment evaporator (not shown) or the freezer compartment evaporator 124c. (Not shown) and a refrigerator compartment expansion valve (not shown) for expanding the refrigerant supplied to the refrigerator compartment evaporator (not shown).

In addition, the refrigerator 100c may further include a gas-liquid separator (not shown) in which the refrigerant passing through the evaporator 124c is separated into a liquid and a gas.

In addition, the refrigerator 100c further includes a refrigerator compartment fan (not shown) and a freezer compartment 144c that suck cold air that has passed through the freezer compartment evaporator 124c and blow it into a refrigerator compartment (not shown) and a freezer compartment (not shown), respectively. can do.

In addition, the compressor driving unit 113c for driving the compressor 112c, a refrigerator compartment fan (not shown) and a refrigerator compartment fan driver (not shown) and a freezer compartment driver 145c for driving the freezer compartment 144c may be further included. have.

Meanwhile, according to the drawing, since a common evaporator 124c is used in the refrigerating compartment and the freezing compartment, in this case, a damper (not shown) may be installed between the refrigerating compartment and the freezing compartment, and the fan (not shown) is one evaporator. The cold air generated in the air may be forced to be supplied to the freezing compartment and the refrigerating compartment.

The compressor 112c of FIG. 16 may be driven by a motor drive device 220, such as FIG. 1, which drives a compressor motor.

The accompanying drawings are only for easily understanding the embodiments disclosed in the present specification, and the technical idea disclosed in the present specification is not limited by the accompanying drawings, and all modifications and equivalents included in the spirit and scope of the present invention are provided. It should be understood to include water or substitutes.

Likewise, although the operations are depicted in the drawings in a specific order, it should not be understood that such operations must be performed in the specific order or sequential order shown in order to obtain desirable results, or that all illustrated operations must be performed. . In certain cases, multitasking and parallel processing may be advantageous.

In addition, although the preferred embodiment of the present invention has been shown and described above, the present invention is not limited to the specific embodiments described above, but the technical field to which the invention belongs without departing from the spirit of the invention claimed in the claims. Of course, various modifications can be made by those skilled in the art, and these modifications should not be individually understood from the technical spirit or the prospect of the present invention.

220: motor drive unit
230: motor
231: load
410: converter
420: inverter
430: inverter control unit

Claims (10)

Capacitors;
An inverter having a three-phase phase arm switching element and a lower arm switching element, and converting a DC power source into an AC power source by a switching operation, and outputting the converted AC power source to a motor;
An output current detector disposed between the capacitor and the inverter and detecting an output current flowing through the motor; And
In the first dead band which is the current non-sensing region of one phase in a switching cycle, in the second dead band which is the current non-sensing region of the two phases in the switching cycle, without shifting the turn-on time for the phase arm switching element. And an inverter controller configured to control a turn on time of the phase-arm switching element to be shifted.
The inverter control unit,
In the second dead band, the turn-on time corresponding to the first switching-off switching vector in the switching period of the three-phase switching vector is controlled to be shifted to the left, and the third turn-off in the switching period. The turn-on time corresponding to the switching vector to be shifted to the right, and the effective vector application time of the second switching-off switching vector in the switching period and the third turn-off in the switching period of the switching vector And controlling the second turn-off switching vector to be shifted left or right based on an effective vector application time. delete delete The method of claim 1,
The inverter control unit,
If the effective vector application time of the second turn-off switching vector is greater than the effective vector application time of the third turn-off switching vector, turn on time corresponding to the second turn-off switching vector to the right. A motor drive device, characterized in that the control to be shifted. The method of claim 1,
The inverter control unit,
When the effective vector application time of the second turn-off switching vector is less than the effective vector application time of the third turn-off switching vector, the turn-on time corresponding to the second turn-off switching vector is leftward. A motor drive device, characterized in that the control to be shifted. The method of claim 1,
The inverter control unit,
Shifting a turn on time for the phase arm switching element in the second dead band, wherein the effective vector application time of the second vector is turned off within the switched period and the third turn off within the switched period, The motor drive, characterized in that for calculating the difference between the application time of the effective vector having a smaller value and the minimum effective vector application time of the effective vector application time of the switching vector, and controlling to shift by half of the calculated time difference Device. The method of claim 6,
The minimum valid vector application time is,
Dead time for preventing arm short of the switching element in the inverter, settling time according to a ringing phenomenon occurring during switching of the switching element in the inverter, switching time margin, sampling time The motor drive device, characterized in that the sum of the analog to digital conversion time, the margin of the analog-to-digital conversion time. The method of claim 1,
The control unit,
In the first dead band,
And estimating a phase current based on any one of the switching vectors having an effective vector application time that is greater than or equal to the minimum effective vector application time. The method of claim 1,
The control unit,
In the second dead band, estimating a phase current based on any one of the switching vectors having an effective vector application time that is greater than or equal to a minimum effective vector application time while shifting a turn-on time for the phase-arm switching element. A motor drive device characterized by the above-mentioned. 10. A home appliance comprising the motor drive device according to any one of claims 1 and 4.

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