JPS6323512B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION [Field of Application of the Invention] The present invention relates to a method and apparatus for testing seismic exploration equipment. Viewed from a first aspect, the present invention relates to a seismic survey system in which a plurality of remote geophone monitoring devices are coupled to a central control and recording station by a two-way radio frequency (RF) link. Viewed from another aspect, the present invention utilizes a two-way RF link to provide a central control and recording station with information regarding the operating status of a plurality of remote and geo-monitoring devices, thereby increasing the reliability of seismic surveying equipment. Relates to testing of exploration equipment. Viewed from yet another aspect, the present invention provides a two-way RF connection for coupling a central control recording station to a plurality of remote geofon monitoring devices using error detection and retransmission of the data required to correct the detected errors. Concerning the testing of seismic equipment to increase the reliability of data transmitted by the link.

[Background of the invention]

Seismic methods of mapping the earth's geological formations involve the use of seismic energy sources and the reception of the seismic energy by an array of seismic detectors, commonly referred to as geofons. When used on land, seismic energy sources are typically high explosives that are electrically detonated in boreholes placed at selected grid points throughout the area, or they can deliver a series of impacts to the earth's surface, such as those used in seismic motion devices. possible energy source. Acoustic waves generated underground by an explosion or impact are reflected at different strata boundaries and reach the surface after a variable amount of time depending on the length and characteristics of the strata traveled. These reflected acoustic waves are detected by GeoFon,
This geophon converts reflected acoustic waves into display electrical signals. The plurality of geophons are arranged in a predetermined manner to most effectively detect the returning acoustic waves and generate electrical signals representative of the acoustic waves from which data regarding the geological formations of the earth are obtained.

Many different types of geophones are commercially available. It is preferable to use the Mark L15B geophonon manufactured by Mark Products in this seismic exploration device.

It is now common to use 48 or more geofone stations simultaneously at each detonation location. Geoff-on stations are commonly located in a line called the "seismic propagation line." 48 Channel propagation typically spans 7 to 9 miles (11.2 to 14.4 km). In many seismic devices currently used for seismic exploration, the geofon station is electrically connected to a central recording station by a long multiconductor or coaxial cable. Electrical signals generated by the geofon stations are coupled via cables to a central recording station.

It is well known that there are many problems with using long cables to bring signals from a geostation to a central recording station. Resistive losses are extremely high; lines tend to pick up excess electrical noise; cables tend to encourage geofon arrays to be linear; geofon spacing is fixed by the cable configuration; It is a big undertaking in wetlands and swamps; cables are subject to attack by humans as well as animals; cables are subject to water penetration and mechanical damage;
Cables are expensive and require repair, maintenance, and spare parts at remote locations.

There have been many attempts to develop improved geological seismic instruments that, among other things, eliminate the use of long cables. The most common attempt is to replace the long cables used previously.
It was the development of an RF link. Many of these efforts center on the use of remote geofon monitoring equipment equipped with radios that can transmit data obtained at the geofon stations to a central recording station. However, there have been many problems when using wireless communication devices in seismic exploration equipment. The main problem that arose was the lack of reliability of the data received at the central recording station. Under noisy conditions, data can be lost in transmission, and if data is received in error, the data recorded at the central recording station will be subject to an unacceptable error rate. Also, under noisy conditions, the detonation time due to the seismic energy source is uncertain, thus resulting in deterioration of the seismic data.

In an effort to correct for these problems created by the use of RF links between multiple remote geofon monitors and a central recording device, many modern systems employ recording devices for remote geofon monitors. The remote geofon monitors are controlled via a one-way RF communication link between the central controller and the remote geofon monitors. The data received by the GeoFon is converted into digital data by the remote GeoFon monitoring device and recorded by a recording device that is part of the remote GeoFon monitoring device. After the investigation is complete, the recording devices are simply picked up and transported to a central location.

Although the use of a one-way RF communications link with the recording device eliminated the problem of transmitting data from remote geofone monitoring devices to the central recording device, it created other problems that were undesirable for seismic exploration devices. The major problems inherent in such devices are that there is no way for the operator to determine if the remote geofion monitoring device is active, and that seismic surveys are not possible because the data obtained is not available until the survey is complete. There is no way for the operator to determine if the device is working. Equipment imperfections can result in loss of time, if the remote geofion monitoring device is not working, or if a particular set of geofons is not working, or if the recording device of the remote geofion monitoring device is not working. thus leading to economic losses. Defects in other sub-devices also lead to data loss. Since no data is available to the operator during the investigation, loss of this data or equipment inoperability cannot be determined during the investigation. Therefore, even though the use of a one-way RF link to control a remote geofon monitoring device overcomes the problems inherent in the use of cables, the reliability of the device is greatly reduced.

[Purpose of the invention]

SUMMARY OF THE INVENTION Accordingly, it is an object of the present invention to provide a method and apparatus for testing a seismic survey system in which a plurality of remote geofon monitoring devices are coupled to a central recording control station by a two-way RF link. It is another object of the present invention to provide a seismic survey system using a two-way RF link to provide a central recording and control station with information regarding the operating status of a plurality of remote geofon monitoring devices to increase the reliability of the seismic survey system. The purpose of the present invention is to provide a test method and apparatus for the test. Still another object of the present invention is to provide a two-way RF link connecting a central recording station to a plurality of remote geofon monitoring devices using error detection and retransmission of data necessary to correct detected errors. An object of the present invention is to provide a testing method and device for a seismic exploration device that increases the reliability of data.

[Summary of the invention]

According to the present invention, the invention includes a seismic energy source that generates acoustic waves traveling underground, and a plurality of geofon monitoring devices, each of which is located in relative proximity to one or more geofon stations. A method and apparatus for testing seismic exploration equipment is provided. Each geoffon station is connected by a short conductor to an associated remote geoffon monitoring device so that electrical signals generated by the geoffon of the geoffon station are transferred from the geoffon station to the associated remote geoffon monitoring device. Remote geofon monitoring devices are also used to control seismic energy sources.

The central recording controller is linked by a two-way RF link to a plurality of remote geofon monitors, including a remote geofon monitor that controls the seismic energy source. Control of the seismic survey equipment is initiated from a central recording controller, and data obtained during a seismic survey are recorded for processing at the central recording controller.

Before each explosion or impact from a seismic energy source,
The central recording controller interrogates only the remote geofion monitoring devices used to record a particular explosion and determines whether the remote geofion monitoring devices are operational and available for recording. Each remote geofone monitoring device has a specific address. When addressed by the central recording control station, the remote geofon monitoring device performs a self-test and communicates the results of the self-test to the central recording control station. Each remote geofon monitor is tested in this manner until all of the remote geofon monitors used to record seismic data from a particular explosion or impact have been tested. If any remote geofion monitoring device fails its self-test and indicates that the remote geofion monitoring device is not operational, the remote geofion monitoring device is Activation of the seismic energy source is deferred until replaced.

After configuring the operability of all remote geofon monitoring equipment used to record a particular explosion or impact,
A central recording and control station issues an ignition command to a remote geofon monitoring device controlling the seismic energy source. In response to the ignition command, the seismic energy source is activated and energy is delivered into the earth.

The reflected energy is detected at the geofon station, converted to an electrical signal, and transmitted to a remote geofon monitoring device, where the seismic data is recorded in memory in digital form.

After the data is stored in the memory of the plurality of remote geo-on monitoring devices, the first remote geo-on monitoring device is addressed by the central recording control station and commanded to transmit the data stored in the memory to the central recording control station. . Data is retrieved from remote geofon monitor memory and transmitted via RF link to a central recording control station. Error detection is used to verify that the data received at the central recording control station is valid. If the error rate is unacceptable, the central recording control station instructs the remote geofon monitor to retransmit the data. The retransmitted data is used to replace the erroneous data of the first transmission and the process continues until the error rate of the seismic data transmitted from the first remote geofon monitoring device is acceptable. After receiving acceptable data from the first remote geofion monitoring device and recording it at the central recording control station, the data is received from the remaining plurality of remote geofon monitoring devices in the same manner as described above for the first remote geofion monitoring device. search for. After all data from an explosion or impact has been recorded at the central recording and control station, the process described in the previous steps is repeated until the seismic survey of the required area is completed. Different remote geo-on monitoring devices may be used to change the propagation mode as needed.

Other objects and advantages of the invention will be apparent from the detailed description of the invention and the appended claims, taken together with the detailed description of the drawings.

[Embodiments of the invention]

Overall configuration of an embodiment The overall configuration of an embodiment of a seismic exploration device including a test device according to the present invention will be described.

Referring to the drawings, and in particular to FIG. 1, a portion of a geoion propagation line is illustrated. Geo-on station 13
a-d, 14a-d, 15a-d, 17a-d,
19a-d are comprised of a plurality of individual geofluorescence sensors arranged in a predetermined manner to provide maximum noise cancellation and maximum signal resolution. Multiple remote geo-monitoring units (hereinafter referred to as RTUs)
Each of 11a-e is associated with a respective group of geostations. In the preferred embodiment, each group consists of four geostations. Each RTU 11a-f is equipped with a radio antenna and associated transmitter.

A detonation point 20 with an RTU 11f and an associated geophonic station 18 is used to deliver seismic energy into the ground. In this preferred embodiment, the explosion point is 20
is an explosive charge placed in the blast hole, although other types of seismic energy sources may be used if desired. The operation of the seismic survey device is controlled through the use of a central recording control system (hereinafter referred to as CRS) 23 conveniently located in a motor vehicle 24. CRS 23 also has an antenna and an associated receiver. CRS 23 is designed to be portable and may be placed in other facilities such as a helicopter, boat, or any desired structure.

For convenience, only a portion of the geoion propagation line is shown in FIG. Using a typical geo-on propagation line with 48 geo-on stations, the preferred embodiment of the present invention uses 12 RTUs to monitor the 48 geo-on stations, with the output of the 4 geo-on stations being sent to each RTU. 13th to control the detonation point
An RTU is required and can be used to monitor two other geostations if required. Modern seismic technology places hundreds of geofon stations on one long line or on two or more substantially parallel lines. If necessary, additional geofons can be placed in the transverse line section. If only 48 geophonic stations are used to monitor each explosion, then the 12 geophonic stations associated with the 48 geophonic stations used to monitor this particular explosion
Only the RTU and the RTU associated with the detonation point are activated by the CRS 23 located on the truck 24.
The first explosion is ignited and seismic data is recorded on the CRS 23 located on the car 24. A different set of RTUs is then activated to record the next explosion.
This process continues until the seismic survey is completed.
The vehicle 24 can be easily moved and remain within range of the RTU used to monitor a particular explosion.

When using multiple geo-ion propagation lines, one explosion is ignited and the result is recorded for the first propagation line, and the first explosion is ignited for the first propagation line while a second explosion is prepared for the first propagation line. The CRS 23 placed in the track 24 can record the results by igniting two propagation lines.
In this way, the use of seismic exploration equipment can be enhanced.

As illustrated in FIG. 1, the device of the present invention is particularly useful where there is considerable geographic variation. CRS2
3 and multiple RTUs 11a-f. This allows the use of RF links between
It provides a means by which changing areas can be surveyed without placing cables over rivers, jungles or other similar areas. individual geofon stations and related
The RTU is installed as shown in Figure 1, and the CRS
23 can move to a convenient location and monitor and control the seismic exploration equipment.

All operations are performed by CRS23 located in car 24
is started by. When it is desired to ignite an explosive to collect seismic data, the CRS 23 turns on the RTU associated with the geophion used during its deployment and used to monitor the particular detonation being ignited. CRS23 then sends a message to each of these RTUs.
Query to determine if RTU is running. If any of the RTUs are found to be inoperative, they are repaired or replaced before igniting the explosives. all selected
When the RTU is operating, the CRS 23 issues an ignition command to the RTU 11f controlling the seismic energy source 20. In response to the ignition command, the explosion is ignited and the reflected energy is transmitted to the geo-on stations 13a-d, 1.
4a-d, 15a-d, 17a-d, 19a-d
Detected by Geo-on stations 13a-d, 1
4a-d, 15a-d, 17a-d, 19a-d
converts reflected acoustic waves into analog electrical signals and transmits these electrical signals representing seismic data to RTU11a.
- Send to e. The analog electrical signal is sampled and the sampled values are converted to digital data and stored in the memory of each of the RTUs 11a-e.

After storing the seismic data in the memory of RTUs 11a-e, CRS 23 first interrogates RTU 11f to determine the time the explosive was ignited (uphole data). Geo-on station 18 provides "uphole" data to RTU 11f. After obtaining this information, CRS 23 begins interrogating RTUs 11a-e to obtain seismic data stored in RTUs 11a-e's memory. The RTU 11a is addressed first and receives commands to transmit the seismic data stored in the memory of the RTU 11a. In response to this command, data is transmitted from the RTU 11a to the CRS 23. CRS 23 examines this data to determine if there are any errors in the data. RTU1
If the error rate transmitted from 1a is greater than a specified limit, CRS 23 instructs RTU 11a to retransmit the data. In response to a resend command
The data is retransmitted from the RTU 11a, and the retransmitted data is checked again for errors. Retransmissions are used to replace erroneous data from the first transmission. CRS2
This process continues until the seismic data stored in the memory of 3 has an acceptable error rate.

After obtaining seismic data from RTU11a, CRS2
3 issues a shutdown command to the RTU 11a, shutting off all functions of the RTU 11a except for the function of monitoring commands from the CRS 23, and conserving battery power. CRS 23 then instructs RTU 11b to transmit the seismic data stored in the memory of RTU 11b. RTU1 by the method described above for RTU11a.
Seismic data is obtained from 1b and this process continues until data is obtained from all RTUs that were used to record seismic data from a particular explosion that was ignited.

All seismic data from a particular explosion in CRS2
3, a second explosive is ignited to obtain a second set of seismic data. Explosion point 20
is moved and records the explosion using the same RTU used to record the explosion or a different RTU. It is most common to shut off RTU 11a and turn on RTU 11g, not shown, to extend the propagation line used to record an explosion without actually moving the geostation or RTU. This technique is commonly referred to as "roll along."

The process described in the previous paragraph is repeated for the second explosion and any number of subsequent explosions until the seismic survey is complete. CRS23
The seismic data stored in memory is transported or taken to a central processing facility where the seismic data can be interpreted.

The seismic survey system of the present invention illustrated in FIG. 1 has the advantage of providing a reliable two-way RF link that facilitates compilation of seismic data at a central location while avoiding the need for long cable runs. Error detection techniques are used to increase the reliability of the two-way RF link, and equipment status checks are used to increase the reliability of the seismic equipment and ensure that the seismic equipment is operational during a seismic survey. RTU11a-e
The data obtained from and sent to CRS23 is
CRS2 allows operators to determine whether the equipment is working without processing seismic data.
3. Additionally, an alarm is provided in the CRS 23 to indicate when a part of the device is malfunctioning, so that remedial action can be taken immediately.

DETAILED DESCRIPTION OF THE EMBODIMENTS A seismic survey apparatus including a test apparatus according to the present invention is most generally illustrated and described in FIG. A more detailed explanation will be given below. A detailed description of the seismic exploration equipment is a single RTU11a and CRS23
It is written about. Control of seismic energy source 20 is also described in detail.

The CRS 23 shown in FIG. 1 is illustrated in block diagram form in FIG. 2a. The RTU 11a illustrated in FIG. 1 is illustrated in block diagram form in FIG. 2b. Illustrated in FIG. 1 as controlling the detonation point 20 and the geophonic station 18
Note that RTU 11f can be identical to RTU 11a. Figure 2b can therefore be used not only for monitoring geofon stations, but also for describing the control of seismic energy sources used to deliver energy underground. Figures 2a and 2b represent a complete illustration of the seismic exploration device of the invention in block diagram form. In the following description, the seismic survey device of the present invention illustrated in FIGS. 2a and 2b will be described as a unitary device, and therefore FIGS. 2a and 2b will be referred to alternately throughout the following description.

Referring to Figures 2a and 2b, the seismic survey device is under the control of a computer unit 51 located in the CRS shown in Figure 2a. The operator accesses the computer device 5 from the operator control display panel 41.
Enter the information in step 1. Device operation is initiated from the operator control display panel 41. To begin the seismic survey, the CRS, illustrated in Figure 2a, is first energized. The operator then performs the operations shown in Figure 2b.
Transport the RTU to the required location. The operator deploying the RTU can communicate with the CRS operator via the handset connector 102.

After placing the RTU, shown in Figure 2b, in the desired position, the operator of the CRS, shown in Figure 2a,
and four station numbers to each RTU. The RTU number and four station numbers are stored in the memory of the computer device 51. When a CRS operator wants to communicate with a specific RTU, he inputs the RTU number into the computer device 51, and then
1 issues the correct address to the RTU with which you want to set up communication.

When the station number is input into the computer device 51,
The computer device 51 automatically issues a command for a test called a normal test to test whether devices such as the RTU are in a normal state. Successful tests are input to command formatter 52 via bus 54 which is connected to computer bus 56. Computer bus 56 connects computer device 51 to computer-to-computer interface 58.
Extends to. Normal test command is command formatsuta 52
The parallel data is converted into serial data, and the data is input to the RF transmitter 59 via the signal line 61.
A transmit/receive (t/r) switch 63 is located in the transmitting section, and the normal test command is transmitted by the RF transmitter 59 via the antenna 64 to the RTU shown in FIG. 2b. The normal test command is received by the antenna 104 and sent to the RF receiver 1 via the t/r switch 107.
Passed to 06. The t/r switch 107 is in normal receive mode. Normal test command is RF receiver 10
6 to the RF interface 108 via the signal line 109. RF interface 10
8 to computer device 111 via bus 113 connected to computer bus 115.
A normal test command is input to.

In response to the normal test command, the computer device 1
11 conducts many tests of RTU. The four geofon stations connected to the RTU via geofon connectors 121, 122 are tested for continuity, response, and leakage. Basic performance test with GeoFon
Performed on the RTU and tested all power supply voltages.
Ensure that there is sufficient power for RTU operation.

Test interface 201 and calibration card 21
1 provides the necessary voltage levels and control signals used for normal testing. The test interface 201 and the calibration card 211 essentially act as an interface for the computer device 111, allowing the computer device 111 to control the execution of normal tests.

Data obtained during a normal test is sent to an analog-to-digital (A/D) converter 141 and associated multiplexer. This analog data is sampled and the samples are retained and converted from analog to digital format. The generated digital data is stored in memory device 125.

During normal testing, the temperature of the RTU is checked.
The RTU is designed to operate from -20°C to +70°C. Temperature sensor 148 sends a signal 149 representative of the temperature of the RTU to a multiplexer associated with A/D converter 141. Signal 149 is RTU
temperature indication, thus allowing the CRS operator to determine whether the RTU temperature is within design limits.

The battery voltage provided by power supply and regulator 186 is provided as an input to a multiplexer associated with A/D converter 141. These signals are illustrated in Figure 2b and are labeled as signals 188-199. The voltage levels of signals 188-199 are described in more detail below in conjunction with a detailed description of power supply and regulator 186. This test provides CRS operators with information regarding power availability to the RTU.

A/D converter 141 is also calibrated during normal test procedures. A series of input voltages are sent by calibration card 211 via signal 203 to A/D converter 141 to test the linearity of the A/D converter's response. The response of A/D converter 141 is stored in memory, which allows A/D converter 1 to be
41 provides the means by which it is calibrated. Gain range amplifier device 171 is calibrated by providing signal 205 from calibration card 211 that is applied to a multiplexer associated with gain range amplifier device 171 . Signal 205 represents a percentage of the total scale input to gain range amplifier unit 171. Gain range amplifier device 171 amplifies signal 205 at each stage,
These amplified signals are sent to the A/D via signal line 175.
The converter 141 is applied to a multiplexer associated with the converter 141. This test data is converted to digital form, stored, and used to calibrate the gain range amplifier unit 171 during subsequent RTU data acquisition.

Leakage tests, continuity tests, and floating tests are applied to GeoFon equipment. These tests provide information to the operator regarding the operability of the GeoFon device.

After the computer device 51 issues the normal test command, sufficient time is allowed for the RTU to complete the normal test. The amount of time spent is determined by a CRS countdown 65 connected to computer bus 56 via bus 66. CRS countdown 6 that the RTU has successfully completed the test
5, the computer device 51 receives the RTU
command to send test data. This command is sent to the command formatter 52, RF transmitter 59, and thus to the RTU in the same manner as previously described for the normal test command.
It is forwarded to the RF receiver 106. In response to the data transmission command, computer device 111 retrieves normal test data from memory device 125 via memory controller 124, and the normal test data is sent to RF interface 108. The normal test data is converted from parallel to serial format and sent from RF interface 108 via signal line 126 to RF transmitter 127. T/R switch 107 is set to transmit mode and normal test data is transmitted by antenna 104 from RF transmitter 127 to antenna 64. Therefore, normal test data is transmitted via the t/r switch 63 in the normal reception mode.
The signal is sent to an RF receiver 68. Normal test data is sent to data formatter 71 via signal line 69. Normal test data is converted from serial to parallel format by data formatter 71, which also performs a parity check to detect errors in the data sent from the RTU to the CRS. The normal test data is then sent to computer device 74 via bus 72 which is connected to computer bus 75. Computer bus 75 extends from computer 74 to computer-to-computer interface 58.

Computer device 74 maintains a count of the number of errors in normal test data transmitted from the RTU. This count is on the computer bus 75, computer-to-computer interface 58.
and is sent to computer device 51 via computer bus 56. Computer device 51 then makes a decision as to whether the error rate of the normal test data transmitted from the RTU is acceptable. If the error rate is acceptable, computer unit 51 sends a confirmation command to the RTU, which shuts off all power except for the function monitoring commands from the CRS in order to conserve battery power. When the error rate is not acceptable, computer device 51 does not send a confirmation command but sends a retransmission command.
In response to the retransmission command, the RTU transmits normal test data again. Formats 71 for retransmitted normal test data in the same manner as described above.
A parity check is performed. Correct data blocks in the retransmitted normal test data are substituted for erroneous data blocks in the originally transmitted normal test data stored in the memory of computer device 74, thus reducing the error rate. is decreasing.

The ability to detect errors in data transmitted from the RTU and command retransmission of data with unacceptable error rates is used to increase the reliability of the RF link connecting the RTU to the CRS. As previously mentioned, the lack of RF link reliability is a significant problem in prior art devices, and the use of error detection and retransmission of successful test data can significantly reduce the reliability of the RF link between the CRS and the RTU. is one of the key features of the present invention that provides an improvement over the prior art in that the

The error count of the new successful test data, which is a compilation of the originally transmitted successful test data and the retransmitted successful test data, is checked again.
It is checked whether the error rate is acceptable.
If the error rate is acceptable, a confirmation command is sent from the computer device 51 to the RTU and the RTU cuts off power. If the error rate is again unacceptable, a retransmission command is issued and the operator determines that the data is acceptable until acceptable data is obtained from the RTU or even if some errors still exist in the data. This process continues until it is determined that there is.

The process outlined in the above steps continues until all RTUs and geostations are located. All of
After placing the RTU, the operator can select the RTU to monitor for a particular explosion.
Also, by selecting a specific explosion point, a specific propagation line shape is set. After setting the propagation line shape, the operator performs the second normal test from the operator control display panel 41. The second normal test command is sent to the switch and display interface 43 via the signal line 44.
and thus to the computer device 51 via the bus 46 which is connected to the computer bus 56. In response to a second normal test command from the operator control display panel 41, the computer device 51 performs all tests selected as part of a particular propagation line shape.
Address RTU and send normal test command to all selected RTUs. This directive is similar to the above
RTUs and all RTUs simultaneously perform the same normal test described above. After the time has elapsed for the RTU to complete the normal test, the computer equipment 5
1 continuously addresses the RTU of the selected propagation shape to obtain normal test data in the same manner as described above. If normal test data from all of the selected RTUs indicates that all RTUs of a particular propagation geometry are operating, computer unit 51 indicates to operator control display panel 41 that the apparatus is operating. Notify the operator via. The operator is also informed of any abnormal operation of the RTU, thus ensuring the operability of the entire system before commencing a seismic survey. This is the second feature of the present invention, which greatly increases the reliability of the seismic exploration device implementing the present invention.

After successfully testing the RTU of a particular propagation line, the seismic device is ready to ignite the explosive and record data from the explosion. In preparing to ignite the explosive, the operator first controls the detonation point.
The RTU is tested and the required explosion point is
Verify that it is connected to the RTU and that the detonation point is in the required location. Explosion point RTU
A test execution command for the test is sent to the explosion point RTU by the computer device 51 in the manner described above for the normal test command. The explosion point RTU test data is also sent back to the CRS in the manner described above. The test data tells computer system 51 that the detonation point location is accurate. The detonation point is connected to one of the inputs of geoffon connector 121 or 122. The explosion point is RF transmitter 127 and RF receiver 10
Addressed via signal lines 131 and 132 connected to 6. Data is sent from the detonation point RTU to the A/D converter 141 in the same manner as described above for normal test data from the geo-on station.

After the testing of the RTUs connected to the detonation point is completed and the test results are verified by the computer device 51, the computer device 51 automatically sends a detonation preparation command to all RTUs of a particular propagation line shape. Explosion preparation commands are sent to all selected RTUs.
command to turn on the power and prepare to receive data. At the same time that the explosion preparation command is sent to the RTU, the computer device 51 instructs the computer device 74 to prepare for data reception. Computer device 74 instructs data formatter 71 to prepare for data reception. After the RTU is ready to receive data, a detonation command is issued from the computer device 51, and the explosive is ignited in response to the detonation command. After the explosion command is sent from the computer device 51, all the selected
RTU begins data collection.

The seismic data detected by the geofon stations is converted into analog electrical signals and sent from the four geofon stations to the geofon connectors 121, 122 and the signal line 13.
6-139 to four channels of preamplifier unit 135. The analog seismic data is amplified by a factor of 64 by a preamplifier 135;
Notch filter 1 via signals 143-146
51 multiplexer input. The seismic data is not multiplexed by the notch filter 151 and is sent as four separate channels of data through the notch filter 151 to the alias filter 161 via signal lines 153-156. Notch filters are used to attenuate 60Hz interference originating from power lines and other 60Hz sources. Alias filter 161 is used to prevent aliasing phenomena resulting from the sample function of the data acquisition device. Elias filter 161 is well known in communications technology and is simply similar to a low pass filter.

Seismic data is sent from the Elias filter 161 to the gain range amplifier device 171 via signal lines 162-16.
5 is given as 4-channel data. Gain range amplifier device 171 in combination with digital gain range amplifier device 173 multiplexes four channels of seismic data into a single channel of seismic data;
This signal is amplified as necessary to provide a full range input to A/D converter 141. Single channel seismic data is sampled and A/D converter 1
41 converts the analog data into digital data. The digital data obtained in this way
Data is sent to memory controller 124 via bus 177 and bus 178, which is connected to computer bus 115 and which is connected to bus 178.
is computer bus 115 and memory controller 1
24. A digital gain range amplifier unit 173 is also connected to computer bus 115 via bus 181. Digital gain range amplifier device 173 and A/D converter device 14
1 to the memory controller 124 are digital signals representing both the analog seismic data and the amount of gain applied by the gain range amplifier device 171. This seismic data is given from the memory control device 124 to the memory 125 via the signal line 182 and is stored in the memory 125.

After sufficient time has passed for the RTU's data input process to complete, the CRS first obtains uphole and time break information from the RTU controlling the detonation point. The time break and uphole information are based on specified equipment limits (in this preferred embodiment
15 milliseconds), the computer device 51
begins addressing the RTU for a particular propagation line shape. The RTU is addressed and data is sent from memory in exactly the same manner as described above for sending normal test commands and sending normal test data from the RTU to the CRS. The data is checked for errors as described above and stored in the memory of computer device 74. If the data has an acceptable error rate, the data is transferred from the memory of computer unit 74 to magnetic tape interface 78 via computer buses 75 and 77. The seismic data is transferred from the magnetic tape interface 78 to the magnetic tape device 79 via the signal line 81 and stored on the magnetic tape of the magnetic tape device.
Header data and other control data necessary for the magnetic tape device 79 are transferred to the magnetic tape device 79 via a signal line 86.
It is provided from a magnetic tape panel 83 connected to a panel interface 84. Magnetic tape panel interface 84 is connected to computer bus 56 via bus 87. Magnetic tape panel 83 command inputs are transferred to magnetic tape controller 88 via bus 89, which is connected to computer bus 56. The magnetic tape controller 88 is connected to the magnetic tape panel 8
3, and controls the magnetic tape device 79 and magnetic tape interface 78 based on the commands sent on the signal line 91. All command inputs from magnetic tape panel 83 are processed by computer system 51 before being transferred to magnetic tape controller 88. In CRS, all commands are
Processed by a computer device 51 that controls the CRS.

Earthquake data is also sent to the computer via bus 94.
Data display panel 93 connected to bus 75
displayed to the operator. Basically, the data display is used to display seismic data so that the operator can determine if the equipment is working, and also to confirm that the RF link is working. It is also used to test the RF link between The format of the data and the manner in which it is displayed is controlled from a data display control panel 95 which is connected by signal lines 96 to a data display control panel interface 97. Data display control panel interface 97 is connected to computer bus 75 by bus 98. Command inputs from the data display control panel 95 are transferred to the computer device 51 via the data display control panel interface 97 and then from the computer device 51 to the data display device 93.

Self-scanning interface 33 is connected to computer bus 56 by bus 35 and to operator control display panel 41 via signal line 36. Self-scanning interface 33 connects computer device 51 to operator control display panel 41.
Provides an interface for information sent to.

Roll-along panel interface 37 connects to computer bus 56 via bus 38.
connected to. roll along panel
Interface 37 is connected to operator control display panel 41 via signal line 39. A roll-along panel interface 37 is provided for displaying information from the computer device 51 and primarily indicates which RTUs are associated with a particular propagation line shape.
assists the operator in setting the propagation line shape by giving an indication of what is available.

Power is supplied to the RTU from a power supply and regulator device 186. Power supply and regulator device 1
86 is connected to the computer device 11 by a signal line 187.
Controlled from 1. The power levels available from the power supply and regulator device are described in detail below in the detailed description of the power supply and regulator device 186.

Voice communication between the CRS and the RTU is provided by a handset located on the operator control display panel 41 and a handset connected to the handset connector 102. The audio signal is transmitted from the operator control display panel 41 to the signal line 50.
is applied to the RF transmitter 59 via the RF transmitter 59. The audio signal is provided from the RF receiver 68 via the signal line 60 to the operator control display panel 41. RF transmitter 12 from a handset connected to handset connector 102
7 and from the RF receiver 106 to the handset connector 1
Audio to the handset connected to 02 is provided via signal lines 131 and 132 providing a two-way signal path.

Using an antenna 110 called an anti-theft antenna, a signal indicating that the RTU is tilted is transmitted to the CRS.
Send to. Such tilting may result from wind, animals kicking the RTU, or mishandling. RTU
A signal indicating that the is tilted is generated at the RF interface 108. Tilting of the RTU causes antenna mismatch, which prevents the signal transmitted from antenna 104 from propagating very far;
It is important to know when the RTU is tilted as this indicates the possibility of RTU theft.

The communication link between the CRS shown in FIG. 2a and the RTU shown in FIG. 2b is shown in FIG. It is formed by the illustrated RF transmitter 127, RF receiver 106, transmit/receive switch 107, and antenna 104. The antennas 64 and 104 are preferably parasitic element antennas commonly called Yagi antennas.
Yagi antennas make it possible to obtain high gain with physically small dimensions. The Yagi design used in the seismic probe of the present invention provides a gain of 6 db. Between the RF transmitter 59 and the RF receiver 106 and the RF transmitter 1
All data transmission between 27 and RF receiver 68 is done digitally using narrowband frequency modulation. The communication device operates in the VHF band, starting at 216MHz.
It is desirable to operate at a power level of 8±1 Watt within the 220MHz frequency band. At this frequency and power level, and using the antenna gain described above, the seismic probe of the present invention transmits well with over 160 db path loss representing a distance of 8 to 10 miles (12.8 to 16 km) when used in a typical regional environment. can.

The communication device used in the seismic exploration device of the present invention is
Since it operates in the VHF range, radio waves propagate by direct waves. Therefore, it is desirable to maintain line of sight between receiving antenna 104 and transmitting antenna 64. However, due to the significant amount of radio refraction and bending that occurs in the lower atmosphere, it is also possible to place the receive antenna 104 below the horizon and receive the transmission. However, the strength of the received signal is reduced, which poses a problem when associated with large distances or when local or weather conditions are unfavorable. Radio waves in the VHF frequency range are also interfered with or reflected by objects with large dimensions compared to the wavelength. In the VHF frequency range, with frequencies above 100 MHz, objects such as trees and buildings significantly block or reflect radio waves.

Due to the characteristics of radio waves in the VHF frequency range, the communication equipment used in the seismic survey device of the present invention should be carefully configured to avoid obstacles that block or reflect radio waves and, if possible, to avoid below-the-horizon communications. This is very important. In this way, radio waves with maximum signal strength are received by the RF receivers 106, 68, which enhances the reliability of the seismic exploration device of the present invention.

Examples of Elements of Embodiments An embodiment of a seismic exploration device including a test device according to the present invention has been described with reference to the functional block diagrams shown in FIGS. 2a and 2b. A preferred embodiment of each functional block of FIGS. 2a and 2b will be described with reference to FIG. 73. Many different circuit configurations are available to perform the functions illustrated in Figures 2a and 2b. Although the following circuits illustrated in FIGS. 3 to 74 are preferred for performing the functions of the seismic exploration device of the present invention,
The invention is not limited to these specific circuits illustrated in Figures 3-73.

Computer device 111 is illustrated in FIG. 2b.
Forms the heart of RTU. computer device 1
11 is 6800 manufactured by Motorola Semiconductor.
A microprocessor device is preferred. The 6800 microprocessor is a well-documented device.
A complete description of the 6800 microprocessor can be found in 481-481 of ``Microprocessor Basic Design'' by John B. Peatman, published by McGraw-Hill, 1977.
494 pages and ``Microprocessors and Microcomputers'' by Branko Suchiek, published by John Whaley & Sons in 1976.
Found on pages 299-340. These documents, along with programming the 6800 microprocessor device,
The implementation of the 6800 microprocessor device is discussed. Many references are provided by Motorola Semiconductor. These are M6800 Microcomputer System Design Data (1976), M6800 Microprocessor Application Manual (1976), and M6800 Programming Manual (1976).

Figure 3 mainly shows the RF receiver 10 shown in Figure 2b.
6, RF transmitter 127, RF interface 10
8 is illustrated. As described with reference to FIG. 2b, the t/r switch 107 illustrated in FIG. 3 is in the normal receive mode. Commands from the CRS are sent from the t/r switch 107 via the communication antenna 104.
The signal is sent to the RF receiver 106. Commands from the CRS are then transmitted via signal line 109 to serial data shift.
register 225, digital phase lock clock 227, and command shift register 229. Each command from CRS includes a preamble, a synchronization byte,
It consists of an address and a command word. The preamble is simply used to alert the RTU that the command is coming from the CRS. Synchronous byte with CRS
Provides synchronization between the RTU and the address identifies the particular RTU addressed by the CRS. The command word tells the RTU6800 microprocessor which RTU function to perform. Digital phase lock clock 227 detects that a carrier is detected by RF receiver 106 and provides a 6.25 KHz clock signal 231 to serial data control 233 and serial data shift register 225. The 6.25KHz frequency represented by signal 231 is equal to the data rate of transmission from the CRS.

Serial data is shifted through serial data shift register 225 in response to clock signal 231. Serial data is provided by signal line 235 from serial data shift register 225 to serial data monitoring logic 237 . Serial data monitoring logic 237 is also provided with a signal 239 representing the unique address of a particular RTU. Signal 239 is also provided as one input to multiplexer 241.

Control register 244 is connected to 6800 microprocessor data bus 200. Signal 246, which is a command from the 6800 microprocessor to load data into control register 244, is provided to control register 244 from memory location write control 409, illustrated in FIG. Blaster control signal 24
0 is provided as an output from control register 244 and is connected to RF transmitter 127 as shown in FIG.
RF receiver 106. Signal 247 is routed from control register 244 to serial data monitoring logic 237.
given as output to . using signal 247
This allows the RTU to respond not only to its specific address, but also to all RTU addresses from the CRS.

Serial data monitoring logic 237 is used to determine if the address from the CRS is the same as the RTU's unique address. It is also used to synchronize received data and determine whether the correct preamble is being sent. If the address from the CRS is correct, serial data monitoring logic 237 provides an enable signal 251 to serial data control 233. In response to enable signal 251 and clock signal 231, serial data control 233 provides clock signal 253 to command shift register 229. Clock signal 253 enables command shift register 229 to load command words from CRS. CRS
The command word from command shift register 229 is provided to multiplexer 241 via signal line 225, and from multiplexer 241 by bus 200 connected to multiplexer 241.
6800 microprocessor. A signal 257, which is a command to read data from the multiplexer 241, is sent to the memory location read control 4 shown in FIG.
01 to the multiplexer 241. In this way, the CRS provides commands to the RTU's 6800 microprocessor, which performs specific functions in response to commands from the CRS.

The clock signal of the RTU is the oscillator and controller 2.
It is given from 61. Oscillator and control device 261
is from the 1.6MHz crystal 263 via the signal line 265.
A 1.6MHz signal is given. In response to the 1.6MHz signal, the oscillator and controller 261 generates the 800KHz signal 2.
66, 400KHz signal 267 and 3.125KHz signal 26
Give 9. The 3.125KHz signal is provided as an input to counter 230. 3.125KHz signal 269
The preferred embodiment is an F4020 14 stage binary counter manufactured by Fairchild Semiconductor. Counter 230 provides multiple outputs having different periods. Signal 271 from counter 230 has a period of 640 microseconds, AND
Applied as one input to gate 281.
Signal 273 from counter 230 has a period of 0.6586 milliseconds and is provided as a second input to NAND gate 283. Signal 2 from counter 230
74 has a period of 0.1647 milliseconds and is provided as a clock signal to decoder 285, which is a flip-flop. Signal 275 from counter 230
has a period of 1.3172 seconds and is provided as the first input to AND gate 287. Signal 276 from counter 230 has a period of 2.62 seconds and is provided as the second input to AND gate 287. Signal 277 from counter 230 has a period of 5.24 seconds and is provided as one input to NOR gate 289.

Output signal 291 from switching device 293
is provided as one input to AND gate 295. The signal line 291 is connected to + via the resistor 297.
Coupled to 5V power supply 296. +5V power supply 296 is connected to the second AND gate 295 through resistor 299.
Combined as input. The output signal 301 from AND gate 295 is provided as the third input to NAND gate 283 and is also provided to the data bus driver illustrated in FIG.

Output signal 303 from NAND gate 283 is provided to the data input of flip-flop 285. Output signal 305 from AND gate 287 is applied to the set input of flip-flop 285.

The Q output of flip-flop 285, represented as signal 308, is provided as one input to NOR gate 289 and is also provided as one input to NAND gate 311. The output of flip-flop 285, represented as signal 309, is provided as a second input to AND gate 281 and is also provided as an input to inverter 312. Output signal 315 from NOR gate 289
is provided as one input to the RF transmitter 127. The output signal from AND gate 281 is provided as a second input to RF transmitter 127.

If the RTU is tilted using switch 293
Give an alert to CRS. In a wireless communication device, such as that implemented in the seismic survey device of the present invention, to ensure that the communication antenna is properly aligned.
It is important that the RTU is upright. It is also possible that animals, wind, or other external forces can tip the RTU after it is placed. Also, Hunter and other humans
It is also possible to simply pick up the RTU and attempt to remove it, thinking it has been abandoned. When these conditions occur, the switch 293
Provide a means to alert the CRS operator or person in the field to this condition so that recovery actions can be taken.

An alarm indicating that the RTU is tilted is the circuit card retention switch 293 as long as the RTU is in place.
is prohibited to be in horizontal position. When the device tilts at least 15 degrees in either direction, switch 293 opens and energizes the tilt alarm circuit.
When the RTU tilts, switch 293 opens, allowing the input of AND gate 295 connected to signal line 291 to go high in response to +5V voltage supply 296. Both inputs of AND gate 295 are therefore high, and signal 301 is high.

When signal 301 from AND gate 295 goes high, both signals 272 and 273 go high and output signal 303 from NAND gate 283 goes low. This has the effect of providing a low input to the data input of flip-flop 285. Similarly, when signals 275 and 276 go high, AND
Output signal 305 from gate 287 goes high and a high signal is provided to the set input of flip-flop 285. While flip-flop 285 is in this state, the next time signal 274 goes high, flip-flop 285 will toggle. Basically, as long as switch 293 is open, the Q output of flip-flop 285 will toggle low for 81.92 milliseconds each time the permutation of counter 230 goes into the decode state. Output signal 308 having a period of 81.92 milliseconds is provided to NAND gate 311 to energize the transmitter with signal 321 connecting NAND gate 311 to transmitter 127 .

Output signal 309 from flip-flop 285
is the output signal 30 from flip-flop 285.
It becomes high state when 8 is low state. counter 230
The signal 271 from the flip-flop 285 and the output signal 309 from the flip-flop 285 are combined by an AND gate 281 and output from the output of the AND gate 281 to the transmitter 1.
A 1.5625KHz signal 317 to 27 is provided. signal 3
17 is a data signal sent to the CRS to indicate that the RTU is tilted. Signal 309 is also inverted by inverter 312 and used to drive the RTU's audible alarm transducer. This audible alarm is used to scare away animals or
Used to indicate to the person picking up the RTU that it has not been abandoned. NOR gate 289 combines output signal 308 from flip-flop 285 and output signal 277 from counter 230 to provide tilt command signal 315. Tilt command signal 315 is sent to RF transmitter 127 to enable RF transmitter 127 to transmit via auxiliary antenna 110.

The transmit data control logic 331 illustrated in FIG.
It is used to send data to be sent from the RTU to the CRS to the RF transmitter 127. Transmit data control logic 331 is provided with a transmitter clock enable signal 333 from memory control register 336 shown in FIG. The transmit data control logic is also provided with a 100 KHz signal 338 and a 400 KHz signal 269, both provided from the oscillator and controller 261. Transmission data control logic 331 is supplied with data from write buffer 343 shown in FIG. 6 through signal line 341. In response to the input signal, transmit data control logic 331 provides serial data line 345 as one input to NOR gate 347. The RTU6800 microcomputer provides signal 349 which is the enable signal for RF transmitter 127 as the second input to NOR gate 347 and as the second input to NAND gate 311. A signal line 351 connecting the output of the NOR gate 347 to the RF transmitter 127
The serial data transmitted to is sent to RF transmitter 127. When it is desired to transmit data from the RTU to the CRS, the signal 321 energizes the RF transmitter 127;
Data provided by signal line 351 is transmitted from RF transmitter 127 to CRS via communication antenna 104. When it is desired to transmit data from the RTU to the CRS, the t/r switch 107 is set to transmit mode.

RF transmitter 127, RF receiver 106, transmit/receive switch 1 illustrated in FIGS. 2b and 3
07, Transmission antenna 104 and anti-theft antenna 1
10 is illustrated in more detail in FIG. RF
Transmitter 127 and RF receiver 106 will be described hereafter in block form that will be familiar to those working in wireless communications design. Specific designs and examples of the block illustrated in FIG. 4 can be found in many publications. Two references are "Radio Engineer's Handbook" by Tellman Frederick Emmons, published by McGraw-Hill in 1943;
and 1969 Howard, D., Sams, Inc.
ITT "Reference Data for Radio Engineers" 5th edition is available.

The RF signal from the RF transmitter 59 shown in FIG.
It is applied to RF amplifier 2525 via transmit/receive switch 107, which is preferably an N3SAV1068A2. The position of the transmit/receive switch 107 is determined by the transmission command signal 321 and tilt command signal 315 shown in FIG.
controlled by RF amplifier 2525 provides image cancellation and also establishes a low device noise value of 4 db.
The amplified signal of the RF amplifier is provided to a first mixer stage 2528. The first mixer stage is also provided with a local oscillator signal 2531 from a first local oscillator 2529. The local oscillator signal 2531 is 10.7MHz above the RF input signal, so the first mixer 2528
Generates an intermediate frequency (IF) of 10.7MHz. 10.7M
The Hz signal is applied from the first mixer 2528 to the second mixer 2533 via the 10.7 MHz band filter 2532. The second mixer 2533 is also provided with a signal 2534 having a frequency of 10.245 MHz from a second local oscillator 2535. Therefore, the second mixer 25
The IF frequency generated by No. 33 is 455KHz.
The 455KHz signal from the second mixer 2533 is 455KHz
IF amplifier 253 via bandpass filter 2537
given to 8. 455KHz band filter 2537
sets the receiver's IF band and gives high attenuation to adjacent channel signals. IF amplifier 2538-455K
The Hz signal is provided to a frequency modulation (FM) detector 2539. FM detector 2539 is a phase lock loop detector circuit. Therefore, command data from the CRS is transmitted from the FM detector 2539 via signal line 109, which is illustrated in both Figures 2b and 3.
Given to RTU.

The audio part of the transmission from the CRS is handled by the audio amplifier 25.
41 and transformer 2545 to the handset by the handset connector 102 shown in FIG. 2b. The output side of the audio amplifier 2541 is also the transmitter 12
7 to an audio amplifier 2542 forming part of 7. The detonation data and control signals 240 from the control register 244 illustrated in FIG.
541. In this manner, detonation data and control signals 240 are provided to the detonator via audio amplifier 2541 and transformer 2545, which provide detonation data and command signals 240 to the detonator by signal lines 131 and 132 illustrated in FIG. 2b. It will be done. Explosion data and command signals 240 are also coupled to audio amplifier 254 to audio amplifier 2542.
1 to the RF transmitter 127.

A slope data signal 317, shown in FIG. 3, is also provided as an input to audio amplifier 2542.
Either the slope data signal or the signal from the handset is amplified by audio amplifier 2542 and sent to oscillator 2.
543. Oscillator 2543 provides a frequency modulated (FM) output to frequency tripler 2544. The FM signal from the frequency tripler is sent to the phase modulator 25
46. The phase modulator 2546 has a third
Seismic data from the RTU is also provided by the signal line 351 shown in the figure. The seismic data in digital form is passed through an integrator 2547 to a phase modulator 254.
given to 6. Signal 3 using integrator 2547
The digital waveform of 51 is converted into a triangular wave used by phase modulator 2546. Phase modulator 2546
The signal from is phase modulated and applied to the output of the transmitter. Thus, a handset used by the RTU's operator, a tilt data signal, or seismic data from the RTU can energize the transmitter.

The phase modulated signal from phase modulator 2546 is applied to power amplifier 2552 via frequency tripler 2549 and frequency doubler 2551. Power amplifier 2552 boosts the signal to be transmitted to the required power level and passes the signal through low pass filter 2553 to antenna 104 via transmit/receive switch 107 . When transmitting slope data, the transmitted data is applied to antenna 110 via transmit/receive switch 107.

The preferred specifications for the transmitter and receiver shown in FIG. 4 are as follows.

Receiver a Frequency = 220MHz, crystal control b Center frequency stability = ±0.001% (-30 to +
70℃) c Sensitivity = -115 dbm for S+N/N ratio of 10 db or more (8 KHz deviation, 1 KHz modulation rate) d Silence sensitivity = -110 dbm for silence of 20 db or more e Modulation acceptance = 0.2 to 7 KHz, peak deviation f Squelch to 15KHz - 5 to 10 ms adjustable start time - 50 to 70 ms recovery time - Audio only (not data) squelch - Logic output, +5V CMOS, available as active lowg data・Acceptance = 6.25KB/S,
FSK/FM h Data output = CMOS + 5V i Audio output = 100mV RMS on the handset terminal
(1Hz, 8KHz deviation) j Explosion data audio stream (signal to detonator) Input: CMOS, +5V, FSK@2.4/4.8KHz Output (adjustable): 150mV RMS on geophone/handset line with handset attached Transmitter a Frequency = 216 to 220MHz crystal control b Frequency stability = ±0.0005%, -30 to +50°C c Power output = 8-10 watts nominal d = DC power = 1.5 amps max, +18.75Vdc e Spurious emission suppression = 60db or more f Audio modulator (oscillator 2543) - Direct FM (premodulation clipping/amplifier on RCVR board) - Deviation = peak 5KHz (1KHz modulation rate) - Modulation sensitivity = 2.5KHz/volt - Input impedance = min. 100KΩ g Data Modulator (Phase Modulator 2546) - Indirect FM (Phase Modulator) - Speed = 100KB/S - Code = 2 Phase (Manchiesta) - Input Level = T ² L - Modulation Index = 1.2 with 50KHz square wave input - Input Impedance =10KΩ min. The digital phase lock clock 227 shown in FIG. 3 is shown in detail in FIG. As shown in FIG. 5, the 100KHz signal 338 is
It is applied to the clock input of a HEX-D flip-flop 361, which in the preferred embodiment is a 74C174 manufactured by National Semiconductor, and is basically constructed as a shift register. Data signal 109 is D1 of HEX-D flip-flop 361.
given to input. In this preferred embodiment, the exclusive
OR gate 360 provides a 10 millisecond wide pulse in response to changes in data signal 109. This pulse is
It is delayed by being shifted through another stage of HEX-D flip-flop 361. HEX
A signal 363 from the Q6 output of -D flip-flop 361 is applied to both inputs of NAND gate 362. In the preferred embodiment, NAND gate 362 is manufactured by National Semiconductor.
It is 74C00. Output signal 365 from NAND gate 362 is applied to the load input of binary counter 367, which in the preferred embodiment is manufactured by National Semiconductor.
It is 74C163. Clock signal 231, described in FIG. 3, is provided from the _QD output of binary counter 367.

The transmit data control logic 331 illustrated in FIG. 3 is illustrated in more detail in FIG. The transmit clock enable signal 333 is applied to the D of flip-flop 381.
The flip-flop 381, which is provided to the input, is a 74C74 manufactured by National Semiconductor in the preferred embodiment. Transmission clock signal 338
is applied to the clock input of flip-flop 381, and is applied to the 4-bit static register 38.
3 and as one input to exclusive OR gate 385. In the preferred embodiment, the 4-bit static register is a 4015
It is half of Exclusive OR gate 385 is a 74C86 manufactured by National Semiconductor. 100KHz
Clock signal 269 is applied to the clock input of flip-flop 387, which is equivalent to flip-flop 381.

The set input of flip-flop 381 and the set input of flip-flop 387 are both connected to the +5V power supply. Q of flip-flop 381
The output goes to the clear input of flip-flop 387,
Also provided to the clear input of 4-bit register 391, which in the preferred embodiment is a 74C175 manufactured by National Semiconductor. The output of flip-flop 381 is a 4-bit static register 383.
is given to the master reset.

4-bit static register 383
Q0 output is 4-bit output via inverter 393.
It is coupled to the D input of static register 383. 4-bit static register 38
The Q1 and Q2 outputs of 3 are provided as inputs to NAND gate 395. In this preferred embodiment,
NAND gate 395 is a 9LS00 manufactured by National Semiconductor. NAND gate 395
The output of is applied to the shift/load (S/L) input of 4-bit register 391. data signal 3
41 are 4-bit registers 391 A, B, C,
given to the D input.

_QD output of 4-bit register 391 is exclusive OR
Provided as a second input to gate 385. The output of exclusive OR gate 385 is flip-flop 3.
87's D input. flipflop 3
The Q output of 87 corresponds to a serial data line 345, and the data is provided by signal line 345 to the RF transmitter 127 illustrated in FIG.

The memory controller 124 illustrated in FIG. 2b is illustrated in more detail in FIG. The main function of memory controller 124 is to control memory 125;
6800 microprocessor 111 and memory 125. Additionally, memory controller 124 provides part of the interface between 6800 microprocessor 111 and RF interface 108. Referring now to Figure 7, the 6800 microprocessor
Portions of address bus 100 are provided as inputs to memory location read control 401, memory location decoder 403, and holding register 405. The A0 and A1 address lines are provided to memory location read control 401 and holding register 405. The A2-A4 address lines are provided to memory location decoder 403. These address lines, provided by address bus 100, provide read and write commands as well as locations where data is written or data is read. In response to the address, the memory location decoder 4
03 provides an enable signal 407 to the memory read control 401 and also provides an enable signal 408 to the holding register 405 and memory location write control 409. Enable signal 407 causes memory location read control 401 to decode the address from the 6800 microprocessor to determine where to read the data from. Four control signals are provided by memory location read control 401. Signal 257 is a command to read data from memory location 800C/E corresponding to multiplexer 241 shown in FIG. Signal 257 is provided to multiplexer 241 shown in FIG. Signal 411 is a command to read data from memory location 800D corresponding to state logic unit 416. signal 4
12 is the position 800F corresponding to the reading buffer 418
This is a command to read data from. Signal 411,4
12 is provided from memory location read control 401 to data bus driver 459. The signal 414 from the memory location read control 401 is sent to the read buffer 4.
18 to shift and output data from the read buffer 418.

Data connected to holding register 405
Bus 200 provides data from the microphone processor to memory controller 124 . signal 408
In response to this, the address provided from address bus 100 and the data provided from data bus 200 are shifted out of holding register 405.
The address is provided to memory location write control 409 by signal line 421. Data is transferred via signal line 423 to memory control register 336, read address and
Provided to counter 425 and write buffer 343.

In response to the address and enable signal 408 provided by signal line 421, memory location write control 4
09 provides four output command signals that allow data to be written to specific locations. Signal 246 from memory location write control 409 is provided to control register 244 illustrated in FIG.
This is a command to write data to 44. The signal 428 from the memory location write control 409 is sent to the write buffer 3.
43 to write data to the write buffer 343. Signal 431 from memory location write control 409 is read address counter 425
This is a command to write data to the read address counter 425. Memory location write control 4
The signal 433 from 09 is the memory control register 33
6 and is a command to write data to the memory control register 336.

In response to data provided by signal line 433 and commands to write data to memory control register 336, memory control register 336 provides a plurality of output signals for controlling various functions of the memory controller. Signal 411 is a state reset signal and is provided as an input to state logic 416. Signal 442 is an enable signal for write buffer 343 and is provided as an input to write buffer 343 . Signal 443 is an enable signal for read buffer 418 and is provided as an input to read buffer 418 . Signal 443 also connects state logic 416 and read access request logic 446.
It is also given to Signal 444 is a clear signal for write address counter 451 and read address counter 425. Signal 444 is the write address.
Read address counter 425 with counter 451
given as input to both. Signal 333 from memory control register 336 was previously described;
Provided as an input to transmit control logic 331 illustrated in FIG.

Data from memory 125 is sent to read buffer 418 by signal line 455. When data is available to be read from read buffer 418, output ready signal 457 from read buffer 418 provides an indication to data bus driver 459 that data is available. Data is sent by signal line 461 from read buffer 418 to state logic 416 and data bus driver 459. signal 4
57, the data bus driver 459
switches to data line 461 and data is sent to 6800 microprocessor data bus 200 by data bus driver 459.

When read buffer 418 is ready to receive data, signal 463 is used to indicate this to read access request logic 466. In response to signal 463, read access request logic 466 issues signal 469.
This signal 469 indicates to memory cycle control logic 468 that data can be read into read buffer 418 . In response to signal 469, memory cycle control logic 468 provides a confirm signal 471 to read address counter 425, state logic 416, and read buffer 418. In response to signal 471, data, if available, is shifted into read buffer 418.

Read address counter 425 stores read address 473 in a two-to-one relationship with read access request logic 466.
(2/1) Send to multiplexer device 475. Read address signal 473 is sent to read address counter 425 in response to the inputs described above.

The write buffer 343 is basically the read buffer 4.
It operates similarly to 18. A signal 477 from the write buffer is sent to data bus driver 459 to indicate to the 6800 microprocessor that data can be written to write buffer 343. Signal 479 from write buffer 343 is sent to write access request logic 453 and
gives an indication that it is ready to send data. In response to signal 479, write access request logic 453
connects signal 481 to memory cycle control logic 468
send to Signal 481 is the data write buffer 3.
43 to the memory cycle control logic 468. Memory cycle control logic 468 causes signal 483 to cause current data at the output of write buffer 343 to be stored in CCD memory 1.
Confirm that it has been forwarded to 25. signal 48
3 is sent to both write buffer 343 and write address counter 451. In response to confirm signal 483, write address counter 451 outputs write address signal 485 to write access request logic 45.
3 and 2/1 multiplexer device 475. The address is sent to the memory 125 by the signal line 489.
given to. 2/1 multiplexer device 475
is switched to the write address line represented by signal 485 in response to control signal 491 sent from memory cycle control logic 468.

The 800 KHz signal 266 from the oscillator and control section 261 shown in FIG. In response to the 800 KHz signal 266, counter and status decoder 494 provides a signal 496 having a pulse width of 10 microseconds to time address counter 499. Counter and status decoder 494 also transfers clock signal 501 to four-phase memory clock logic 495 and memory cycle control logic 4.
Send to 68. In response to signal 496, time address counter 499 sends a count signal 503 to read access request logic 466 and write access request logic 453 and a count signal 508 to four phase memory clock logic 495. Time address counter 499 also sends signal 504 having a pulse width of 160 microseconds and signal 506 having a pulse width of 2560 microseconds to data bus driver 459.

In response to signal 266 and signal 501, four-phase memory clock logic 495 generates control signal 509 which is used to provide logic and control of four-phase clock driver 511 illustrated in FIG.

In response to the inputs described above, memory cycle control logic 468 generates a memory control signal 514 that is sent to the input of buffer 516 illustrated in FIG. Depending on whether information is being written to or read from memory, control signal 514 initiates a read or write operation, respectively.

In response to the inputs described above, state logic 416 generates two output signals that are sent to data bus driver 459. Signal 518 is a word available indication and provides an indication to the 6800 microprocessor when 20 bits have been shifted into read buffer 418. Signal 519 is a parity count that provides an indication of the number of ones in the binary data sent from memory 610 on signal line 455. This parity count allows the 6800 microprocessor to add parity bits as needed.

The memory location write control 409 illustrated in FIG. 7 is illustrated in more detail in FIG. Address line 421 is coupled to the A0 and A1 inputs of 1-to-4 decoder 522. Clock signal 408 is sent to the enable input of 1-to-4 decoder 522. In the preferred embodiment, 1-to-4 decoder 522 is an F4555 manufactured by Fairchild Semiconductor.

In response to address 421, one-to-four decoder 5
22 provides four output signals labeled 0-3. The 0 output is provided as the first input to AND gate 527. 1 output is provided as the first input to AND gate 525. AND gate 52
The second input of both 5 and AND gate 527 is +5V
Coupled to the high state of power supply 529. AND gates 525 and 527 are preferably 9LS00 manufactured by National Semiconductor. The output of AND gate 525 is the signal 4 shown in FIG.
It is 33. The output of AND gate 527 is signal 246, illustrated in FIG.

The output labeled 2 from 1-to-4 decoder 522 corresponds to signal 431 illustrated in FIG. The three outputs from 1-to-4 decoder 522 are sent as signal 428 illustrated in FIG.

Write address counter 45 illustrated in FIG.
1 is illustrated in more detail in FIG. Signal 483, shown in FIG. 7, is sent to the clock pulse input of seven-stage binary counter 531. clear signal 4
44 is sent to the reset input of the 7-stage binary counter 531 and also to the master reset input of the 12-stage binary counter 532. 7-stage binary counter 53
The Q7 output of 1 is sent to the clock pulse input of a 12 stage binary counter 532. 7-stage binary counter 5
7 outputs of 31 and 12 of 12 stage binary counter 532
Eleven of the outputs of the book are used to provide the 18 bits that make up the signal 485 shown in FIG.

The 7-stage binary counter is F4024 manufactured by Fairchild Semiconductor. The 12-stage binary counter 532 is an F4024 manufactured by Fairchild Semiconductor.

Read address counter 42 illustrated in FIG.
5 is illustrated in more detail in FIG. Signal 471 is sent to the clock pulse input of 12 stage binary counter 541. Signal 444 is sent to the master reset input of 12-stage binary counter 541 and also to the master reset input of 4-bit binary counters 543 and 544.
Also sent to reset. Signal 431 is sent to the load inputs of binary counters 543,544. The data signal 423 is the binary counter 543, 544.
Sent to D0−D3 inputs. 12-stage binary counter 54
Ten of the outputs from 1 are sent as part of signal 473 illustrated in FIG. In addition, the Q9 output from the 12-stage binary counter 541 is output from the NAND gate 54.
5 to both inputs. NAND gate 54
The output of 5 is sent to the count-up input of a 4-bit binary counter 543. The countdown input of the 4-bit binary counter 543 is connected to the +5V power supply 546.
is coupled to the high state of The Q0-Q3 outputs from binary counter 543 further constitute signal 473.
Gives data bits of the book. The carry output of 4-bit binary counter 543 is sent to the count-up input of 4-bit binary counter 544. The countdown input of 4-bit binary counter 544 is coupled to the high state of +5V power supply 548. 4
The Q0-Q3 outputs from bit binary counter 544 constitute the remaining four data bits of signal 473.

The state logic 416 illustrated in FIG. 7 is illustrated in more detail in FIG. Signal 471 is passed through inverter 551 to 4-bit shift register 5.
53 clock input. Signal 443 is 4
Sent to master reset input of bit shift register 553. The Q1 and Q2 outputs of 4-bit shift register 553 are sent as inputs to NOR gate 554. The output of NOR gate 554 is sent to the D input of 4-bit shift register 553 and also to the clock input of flip-flop 556. This configuration produces a positive transition at the output of NOR gate 554 for every five pulses of signal 471.

The data and set inputs of flip-flop 556 are coupled to the high state of +5V power supply 557. Signal 441 is sent to the clear input of flip-flop 556 and also to the clear input of flip-flop 558. Signal 461 is sent to both the J and K inputs of flip-flop 558. The signal 518 illustrated in FIG.
is output from the output of Signal 519, shown in FIG. 7, is output from the Q output of flip-flop 558.

4-phase memory clock logic 4 illustrated in FIG.
59 is shown in more detail in FIG. Signal 508 is provided as one input to NOR gate 561 and as both inputs to NOR gate 563. The signal 501 is
The second input of NOR gate 561 and NOR gate 56
7 and the other goes to both first inputs of NOR gates 568 and 569. The output of NOR gate 563 is
Provided as a second input to NOR gate 567. The output of NOR gate 561 is coupled to the D0 input of D-type flip-flop 571. The output of NOR gate 569 is the output of D-type flip-flop 571.
Sent to D1 input. The output of NOR gate 567 is sent to the D2 input of D-type flip-flop 571. The output of NOR gate 568 is sent to the D3 input of D-type flip-flop 571.

Signal 266 is sent to the clock input of D-type flip-flop 571. D-type flip-flop 5
The clear input of 71 is coupled to the high state of +5V power supply 573.

The inverted Q0 output of D-type flip-flop 571 is sent as an input to the I1 input of non-inverting buffer 575 and also as the first input to AND gate 576. The non-inverting Q1 output from D-type flip-flop 571 is also sent to the I2 input of non-inverting buffer 575. The inverted Q1 output from D-type flip-flop 571 is provided as one input to AND gate 578. D type flip-flop 57
The inverted Q2 output from 1 is the output of the non-inverted buffer 575.
I3 input and also as the second input of AND gate 578. The non-inverting Q3 output is sent to the I4 input of non-inverting buffer 575. The inverted Q3 output from D-type flip-flop 571 is sent as the second input to AND gate 576.

The output from AND gate 578 is NOR gate 5
69 as the second input. The output from NOR gate 563 is the second output to NOR gate 567.
Sent as input. The output from AND gate 576 is sent as the second input to NOR gate 568.

The D1-D4 outputs from non-inverting buffer 575 are used to provide signal 509 shown and described in FIG.

Memory cycle control logic 4 illustrated in FIG.
68 is illustrated in more detail in FIG. The signal 501 is the first of both AND gates 581 and 582.
Sent as input. Signal 481 is sent as a second input to AND gate 581. signal 469
is sent as the second input to AND gate 582. The output of AND gate 581 is sent to the D0 input of HEX-D flip-flop 584. The output of AND gate 582 is sent to the D1 input of HEX-D flip-flop 584.

Signal 266 is sent as the first input to NAND gates 586 and 587. NAND gate 58
The second input of 7 is coupled to the high state of +5V power supply 589. The output of NAND gate 587 is HEX-D
It is sent to the clock input of flip-flop 584.

The Q0 output of HEX-D flip-flop 584 is
Provided as the first input to NAND gate 591. From HEX-D flip-flop 584
The Q0 output is also of the HEX-D flip-flop 584.
It is sent as the D3 input and the first input to NOR gate 593. The Q1 output from HEX-D flip-flop 584 is sent as the first input to NAND gate 594 and as the second input to NOR gate 593.

The second input of NAND gate 594 is +5V power supply 5
96. The output from NAND gate 594 is signal 491a, which forms part of signal 491 illustrated in FIG. NAND gate 5
A second input to 91 is coupled to the high state of +5V power supply 590. The output from NAND gate 591 is signal 491b, which forms the second portion of signal 491 illustrated in FIG. NOR gate 593
The output from HEX-D flip-flop 584
is coupled to the D2 input of

The Q2 output from HEX-D flip-flop 584 provides a portion of the signal 514 illustrated in FIG.
It is also sent as the first input to NOR gate 598. Q3 from HEX-D flip-flop 584
The output is used to set the signal 483 illustrated in FIG. The Q3 output is also sent as the second input to NOR gate 598 and as the second input to NAND gate 586. The output from NAND gate 586 forms the second portion of signal 514 illustrated in FIG. The output from NOR gate 598 is HEX
-D is sent to the D4 input of flip-flop 584.

The Q4 output of HEX-D flip-flop 584 is
It is coupled to the D5 input of HEX-D flip-flop 584. The signal 47 illustrated in FIG. 7 using the Q5 output from HEX-D flip-flop 584
Form 1. HEX-D flip-flop 58
4 master reset is coupled to +5V power supply 599.

The memory device 125 illustrated in FIG.
This is illustrated in more detail in the figure. The memory used is a charge-coupled device (CCD) memory. The particular CCD memory used in the preferred embodiment of the present invention is the P2416 manufactured by Intel Corporation. Sixteen memory chips are used in the preferred embodiment of the invention. Up to 4 cards can be used, each with 16 chips (4 banks of 4 chips each). Although only one memory bank of one card is shown in FIG. 14 for convenience, the operation of all memory banks is the same.

Referring to FIG. 14, the 2/2 shown in FIG.
Address signal 48 from 1 multiplexer 475
9 is sent as an input to decoder 601, decoder 603, and level converter 604. Two bits of address signal 489 are sent to decoder 601 and two bits are sent to decoder 603. The remaining six bits of address signal 489 are sent to level converter 604, and from level converter 604 via signal line 606 to the A0-A5 inputs of CCD memory 610. Data is sent from the memory controller illustrated in FIG. 7 by signal line 341 connected to buffer 516. Control signals from memory cycle control logic 468, illustrated in FIG. 7, are sent to buffer 516 by signal line 514.

Decoder 601 decodes the two address bits provided by signal line 489 to determine which memory card to address. Four activation signals 611-614 are sent from decoder 601 to each memory card. As shown in FIG. 14, signal 611 is connected to CCD memory 61
, and specifically to buffer 516 and register 616.

In response to signal 611, buffer 516 sends an enable signal 618 to decoder 603. signal 618
In response, decoder 603 decodes the two address bits sent to decoder 603 by signal line 489 and sends four address bits to each of the four CCD memory banks located on the addressed card.
Provide book activation signals 621-624. signal 62
1-624 are sent to level converters 625-628, and from level converters 625-528 to each CCD memory. As shown in FIG. 14, signal 621 is output from level converter 625 to CCD
is sent to the energization input of memory 610. Data is,
A signal 631 connected to the data input of CCD memory 610 sends signals from buffer 516 to CCD memory 610 . The control signal is also transferred to the buffer 51 by a signal line 633 which is sent to the write enable input of the CCD memory 610 via a level converter 635.
6 to the CCD memory 610.

The logic signals of the 4-phase clock driver 511 are the 4-phase memory clock logic 495 illustrated in FIG.
is applied from signal line 509 via buffer 637. Buffer 637 is coupled to four-phase clock driver 511 by signal line 639.
Output 641 from 4-phase clock driver 511
are sent to the φ1-φ4 inputs of CCD memory 610.

A signal line 643 connected to register 616 sends data from the CCD memory to the data output of the CCD memory. Signal lines 644-646 connected to register 616 also carry data from other memory banks located on a particular card. In response to enable signal 611, data is shifted from register 616 and sent on data line 455 to read buffer 418 illustrated in FIG.

Test interface 20 illustrated in Figure 2b
1 is illustrated in more detail in FIG. As previously mentioned, the primary function of test interface 201 is to provide control signals to calibration card 211 and preamplifier 135, illustrated in FIG.
35 to provide a voltage source for testing. Referring now to FIG. 15, the 6800 microprocessor address lines 100 are coupled to a decoder 651. Decoder 651 decodes the address from the microprocessor and provides a plurality of decoded address signals, represented at 652, to data holding latches 653-657. The 6800 microprocessor data line 200 is also routed to data retention latches 654-657 and data retention latch 653.

In response to data input from the 6800 microprocessor data line 200, the data retention latch 65
3 generates two control signals 661 and 662.
Control signal 661 from data retention latch 653 is sent to multiplexer 711 shown in FIG. 16 and is used to control the switching of multiplexer 711. Data retention latch 653
The signal 662 from the switch 71 is sent as a control signal to the switch 715 shown in FIG.
5 is used to control the selection of voltage inputs provided to 5.

Data retention latches 654-657 are activated in response to an address provided through the 6800 microprocessor address line 100 and data provided through the 6800 microprocessor data line 200.
each provide two output control signals. Data retention latch 654 is connected to preamplifier 1 shown in FIG. 2b.
A control signal 665 is given to channel 4 of 35. Data retention latch 654 also provides a control signal 666 to switch 669 which controls the channel to which the voltage applied to switch 669 is applied. Similarly, data retention latch 655 is connected to preamplifier 135.
control signal 671 to channel 3 of preamplifier 135;
A control signal 672 is applied to the data holding latch 65.
7 is a control signal 6 to channel 1 of the preamplifier 135.
Gives 74. Signal 674 is specifically sent to switch 751, illustrated in FIG. Data retention latch 655 also provides a control signal 676 to switch 669. Control signal 676 functions to control the supply of reference voltage to channel 3 of preamplifier 135 by switch 669. Data retention latch 6
56 also provides a control signal 678 to switch 681. Control signal 678 controls application of the reference voltage to channel 2 of preamplifier 135 by switch 681. Data retention latch 657 also sends a control signal to switch 681, which controls the application of the reference voltage to channel 1 of preamplifier 135.

The output signal from the reference voltage source 684 is connected to the resistor 685.
- Switching device 669, 68 via 688
given as input to 1. Reference voltage source 684
The output signals from are then routed to the required channels of the preamplifier by control signals 666, 676, 678, 683 as described above. Signal 691 from switch 669 is channel 4 of preamplifier 135.
to be used as a test or reference voltage. Signal 692 from switch 669 is provided as a test voltage to channel 3 of preamplifier 135. Signal 693 from switch 681 is provided as a test voltage to channel 2 of preamplifier 135. Signal 694 from switch 681 is sent to preamplifier 135
channel 1, and in particular as an input to multiplexer 751 shown in FIG. Signal 694 is also provided to multiplexer 951 shown in FIG. Reference voltage source 684 includes output signals 846 from the preamplifier illustrated in FIG. 18 and signals 851-8 representing output signals from the preamplifier channels as illustrated in FIG. 2b.
58 is given.

The calibration card 211 shown in FIG. 2b is the 16th
This is illustrated in more detail in the figure. As previously mentioned, the calibration card 211 is illustrated in FIG. 2b.
Provides a circuit that generates accurate voltages for RTU analog circuit calibration. The calibration card 211 is also the second
It is also used to obtain the test voltage for the notch filter 151 shown in Figure b. Referring now to FIG. 16, pin 2 of voltage regulator 701 is coupled to +15V power supply 703. In this embodiment of the invention, voltage regulator 701 is a REF01AJ manufactured by Precision Monolithics.
Pin 4 of voltage regulator 701 is grounded. Pin 5 of voltage regulator 701 is coupled to the wiper of potentiometer 704. The output of the voltage regulator 701 is connected to the buffer amplifier 70.
6 and to ground via potentiometer 704.

Voltage regulator 701 provides an output signal having a voltage level of 10V to buffer amplifier 706. Buffer amplifier 706 is voltage regulator 7
01 and provides an output signal 708 with a voltage level of 10V. buffer amplifier 70
The output signal 708 from 6 is also output to buffer amplifier 70
It is also coupled to the inverting input of 6. Signal 708 is sent to potentiometer 709, which together with resistor 712 forms a voltage divider circuit. Resistor 712 is potentiometer 70
9 wiper input. A voltage divider circuit consisting of potentiometer 709 and resistor 712 is ratioed such that resistor 712 provides an output signal 714 having a voltage level of +8.3V. Signal 714 is sent as one input to the switch.

Signal 714 is also sent to the inverting input of inverting amplifier 718 via resistor 716. Inverting amplifier 71
The non-inverting input of 8 is grounded. Inverting amplifier 7
Output signal 719 from 18 has a voltage level of -8.3V and is sent as the second input to switch 715. Output signal 719 from inverting amplifier 718
It is also fed back through resistor 721 and potentiometer 720 to the inverting input of inverting amplifier 718.

In response to a control signal 662 provided to switch 715 from data retention latch 653 shown in FIG. 15, switch 715 selects either signal 719 or signal 714 to be sent as an output. Thus, switch 715 provides output signal 723 having a voltage level of ±8.3V in response to commands from control signal 662.

Output signal 723 from switching device 715
is sent to the non-inverting input of buffer amplifier 724. A buffer amplifier 724 is provided to prevent loading of switch 715 and provides an output signal 726 having a value of ±8.3V depending on the value of signal 723. Signal 726 from buffer amplifier 725 is provided as an input to voltage divider circuit 728 and is also provided to the inverting input of buffer amplifier 724.
Additionally, signal 726 is provided to multiplexer 711.

Voltage divider circuit 728 provides multiple output signals to multiplexer 711 . Voltage divider circuit 728
Output signals 731-745 from represent signal 726 divided by a power of two. Therefore, signal 731 has a value of ±4.15V depending on the value of signal 726. Signal 732 has a value of ±2.075V depending on the value of signal 726. The signal continues to decrease by a power of two, providing multiple input voltages to multiplexer 711.

In response to a control signal 661 provided by data retention latch 653 illustrated in FIG. 15, multiplexer 711 selects one of the input voltages to be sent as an impulse voltage or a calibration voltage to the analog circuitry illustrated in FIG. 2b. . The output voltage 747 from multiplexer device 711 is sent to the non-inverting input of buffer amplifier 748. Buffer amplifier 748 prevents loading of multiplexer 711. The output signal from buffer amplifier 748 is fed back to the inverting input of buffer amplifier 748, and is also fed back to the inverting input of buffer amplifier 748.
The signal is sent to the notch filter 151, gain range amplifier device 171, and A/D converter device 141 shown in FIG. In particular, signal 749 is connected to multiplexer 801 illustrated in FIG. 19, multiplexer 851 associated with a gain range amplifier arrangement illustrated in FIG.
This is also provided as an input to multiplexer 951 associated with the A/D converter shown in FIG.

The divider circuit 728 illustrated in FIG. 16 is illustrated in more detail in FIG. For convenience, the resistor illustrated in FIG. 17 will be referred to as having first and second terminals. The first terminal is always referred to as the left or bottom terminal of the resistor shown in FIG. The second terminal of the resistor is referred to as the right or top terminal of the resistor illustrated in FIG.

Referring now to FIG. 16, signal 726, described above in FIG. 16, is sent to the first terminal of resistor 751. A first terminal of resistor 752 is coupled to a second terminal of resistor 751 similar to signal line 731 . resistance 75
The second terminal of 2 is a resistor 753 similar to the signal line 732.
This signal line 732 is also coupled to a first terminal of a resistor 754 . resistance 753
The second terminal of is grounded.

A second terminal of resistor 754 is coupled to a first terminal of resistor 756 as well as signal line 733. resistance 756
A second terminal of resistor 757 is coupled to a first terminal of resistor 757, as is signal line 734, which is also coupled to a first terminal of resistor 758. The second terminal of resistor 757 is grounded.

A second terminal of resistor 758 is coupled to a first terminal of resistor 759 as well as signal line 735. resistance 759
A second terminal of resistor 761 is coupled to a first terminal of resistor 761, as is signal line 736, which is also coupled to a first terminal of resistor 762. The second terminal of resistor 761 is grounded.

A second terminal of resistor 762 is coupled to a first terminal of resistor 763 as well as signal line 737. resistance 763
A second terminal of resistor 764 is coupled to a first terminal of resistor 764, as is signal line 738, which is also coupled to a first terminal of resistor 766. A second terminal of resistor 764 is grounded.

A second terminal of resistor 766 is coupled to a first terminal of resistor 767 as well as signal line 739. resistance 767
A second terminal of resistor 768 is coupled to a first terminal of resistor 768, as is signal line 740, which is also coupled to a first terminal of resistor 769. A second terminal of resistor 768 is grounded.

The second terminal of resistor 769 is coupled to the first terminal of resistor 771 in the same way as signal line 741, and this signal line 7
41 is also coupled to a first terminal of resistor 773. The second terminal of resistor 771 is grounded.

A second terminal of resistor 773 is coupled to a first terminal of resistor 774, as is signal line 742, which is also coupled to a first terminal of resistor 775. The second terminal of resistor 774 is grounded.

A second terminal of resistor 775 is coupled to a first terminal of resistor 777, as is signal line 743, which is also coupled to a first terminal of resistor 778. The second terminal of resistor 777 is grounded.

A second terminal of resistor 778 is coupled to a first terminal of resistor 781, as is signal line 744, which is also coupled to a first terminal of resistor 783. The second terminal of resistor 781 is grounded.

The second terminal of the resistor 783 is grounded via the resistor 782 similarly to the signal line 745.

The preamplifier 135 illustrated in FIG.
The figures are shown in more detail. As shown in FIG. 2b, preamplifier 135 is comprised of four channels. Each of the four channels is identical and independent, so for convenience only one channel is designated as the first channel.
This is illustrated in Figure 8. This one channel description applies to all channels of preamplifier 135.

Referring to FIG. 18, the signal lines 674 from data retention latch 657 shown in FIG. 15 are actually four signal lines. As shown in FIG. 18, signal line 674a connects switching device 7.
51 A1 input. Signal line 674b is provided to the A2 input of switching device 751. The signal line 674c is the switching device 751
is given to the A3 input. The signal line 674d is applied to the A4 input of the switching device 751. Signal lines 674a-d each connect to inverter 80.
1-804 and inverter 801-804.
The outputs of are used to control switches S1-S4, respectively.

Switching device 751 is preferably a HI analog switch manufactured by Harris Semiconductor. A portion of the internal circuitry of switch 751 is illustrated in FIG. 18 to specifically illustrate the test functions performed by switching device 751.

A signal line 694, which is a test line provided from switching device 681 shown in FIG. 15, is provided to both input 1 and input 2 of switching device 751. Input 1 is coupled to switch S1 and input 2
is coupled to switch S2.

One pair of inputs is provided by each geophonon. Geooff line 807 is applied to the non-inverting input of operational amplifier 811 via resistor 809. Geooff line 807 is also coupled to a first output of switching device 751. 2nd line 812 from GeoFon
is applied to the fourth input of switching device 751 and also applied via resistor 814 to the non-inverting input of operational amplifier 816. Geooff-on signal line 81
2 is also coupled to a first output of switching device 751 via resistors 818 and 819.

The first output of switching device 751 is resistor 81
9,821 to the third output of switching device 751. The third input, second output and fourth output from switching device 751 are all grounded. A third input of switching device 751 is coupled to switch S3, and a third input of switching device 751 is coupled to switch S3.
A fourth input of is coupled to switch S4. A fourth output of switching device 751 is coupled to each of switches S1-S4.

The positive side of capacitor 823 is coupled to the non-inverting input of operational amplifier 811. capacitor 823
The negative side of is grounded. The cathode side of diode 824 and the anode side of diode 826 are both coupled to the non-inverting input of operational amplifier 811. The anode side of the diode 824 is the cathode of the diode 827,
It is coupled to the anode of diode 828, the cathode of diode 826, and the cathode of Zener diode 829. The cathode of 826 is also coupled to the cathode of Zener diode 829, the cathode of diode 827, and the anode of diode 828. The anode of diode 829 is coupled to the anode of Zener diode 831. The cathode of the Zener diode 831 is grounded. The anode of diode 828 is coupled to the anode of diode 827. The anode of diode 827 is coupled to the non-inverting input of 816, as is the cathode of diode 828. The positive side of capacitor 833 is also coupled to the non-inverting input of anti-op amplifier 816. The negative side of capacitor 833 is grounded.

The inverting input of the operational amplifier 811 is a variable resistor 835
to the inverting input of operational amplifier 816. The output of operational amplifier 811 is coupled through resistor 836 to the non-inverting input of operational amplifier 838. The output of operational amplifier 811 is also fed back through resistor 839 to the inverting input of operational amplifier 811.
The output from operational amplifier 816 is coupled through resistor 841 to the inverting input of operational amplifier 838. The output of operational amplifier 816 is also coupled through resistor 843 to the inverting input of operational amplifier 816.

The non-inverting input of operational amplifier 838 is connected to ground via resistor 844 . Output signal 864 from operational amplifier 838 is provided as the channel 1 input to multiplexer 801 illustrated in FIG. The multiplexer 801 shown in FIG.
It corresponds to the multiplexer associated with the notch filter 151 illustrated in the figure. Signal 846 from operational amplifier 838 is also coupled to the inverting input of operational amplifier 838 via resistor 848 and variable capacitor 849. Signal 846 from operational amplifier 838
Alternatively, the S/H multiplexer 9 shown in FIG.
Sent to 51.

Operational amplifiers 811 and 816 together with resistors 839 and 843 and variable resistor 835 constitute a differential input to differential output operational amplifier. The gain of the differential input to differential output operational amplifier is mainly determined by the variable resistor 835 and fixed resistor 8.
It is determined by the value of 39,843. Only differential signals are amplified; common mode signals are passed through without being amplified.

The differential outputs comprising the output signals from operational amplifiers 811, 816 are provided to operational amplifier 838, which functions as a differential input to a single-ended output amplifier. The common mode signal is rejected by operational amplifier 838 and only the differential signal is amplified. The input section of the differential input-to-differential output amplifier composed of operational amplifiers 811 and 816 has resistors 818 and 819,
821. Resistor 818, 819, 8
21 provides a DC path to ground while maintaining a balanced input impedance. A resistor/diode circuit consisting of resistors 89, 814, diodes 824, 826, 827, 828, and Zener diodes 829, 831 is connected to operational amplifiers 811, 81.
A clip circuit is constructed to provide transient protection for a dual operational amplifier consisting of 6. This circuit is primarily provided to provide protection against lightning. Capacitors 823 and 833 simply act as high frequency filters.

When the RTU illustrated in FIG. 2b is in data acquisition mode, switches S1, S2, S4 illustrated in switching device 751 are open and switch S3 is closed. Geooff-on input signal 8
07 and 812 are directly provided as inputs to a differential input-to-differential-output differential amplifier composed of differential amplifiers 811 and 816. The difference between signals 807 and 812 is amplified with a differential input to differential output operational amplifier;
The amplified signal is provided to a differential input to a single-ended output amplifier comprised of operational amplifier 838. Amplifier 838 provides a single output signal 846 representing seismic data detected by the GeoFon device.
Signal 846 is sent directly to multiplexer 801, illustrated in FIG. 19, when the RTU is in data acquisition mode.

Three types of tests are performed on the GeoFon device when the RTU is in test mode. The three types of tests are called leak tests, continuity tests, and floating tests. The leakage test measures the leakage resistance between the geophonic wire and the ground. During a leak test, command signals provided by signal lines 674a-d cause switch S1 to close and switches S2, S3, and S4 to open. Test line 694
A voltage is applied to the switching device 751 by the switching device 751 . This voltage is passed from the geo-on input line 807 to the geo-on line via closed switch S1. Current leakage from the geoffon wire to ground creates a voltage divider effect that has the effect of reducing the test voltage sent through test wire 694. The difference between the reference voltage sent to switching device 681 shown in FIG. 15 and the test voltage sent to S/H multiplexer 951 by signal line 694 represents the leakage resistance from the geooff line to ground.

The continuity test measures the internal resistance between the input terminals represented by signal lines 807 and 812. To perform a continuity test, command signals sent through signal lines 674a-d close switches S1 and S4 and open switches S2 and S3. The reference voltage is again sent to switching device 751 via test line 694, and the reference voltage is sent to the geo-on device via signal line 807 through switch S1. Since switch S4 is closed, current from the reference voltage flows through the geooff line. The voltage developed on the geoffon by this current is amplified by a preamplifier device as described above in the data acquisition procedure. The amplified voltage proportional to the internal resistance of the geo-off line is connected to the S/S signal line 846 as shown in FIG.
It is given as an input to H multiplexer 951.

The floating test applies regulated voltages on the input terminals of the geo-on device, represented by signal lines 807, 812, to levitate the geo-on device suspended mass from its normally resting position. When the voltage is released and the mass drops, a damped vibration signal is generated, which is ultimately analyzed to determine the performance parameters of the geo-on device. To start the floating test, signal line 6
Command signals provided by 74a-d cause switches S1 and S4 to close and switches S2 and S3 to open. Test line 694 sends voltage to switching device 751 . This voltage is applied to switch S1
The signal is sent to the geo-on device via a signal line 807. Current flows from the geoion device to ground through switch S4. The voltage thus developed on the geo-on device is amplified by the preamplifier as described above and sent by signal line 846 to the reference voltage source 684 shown in FIG. 15. Reference voltage source 684 compares the preamplifier output provided by signal line 846 to the original reference voltage and generates an error voltage. The error voltage is amplified and sent to the geo-on device by test line 694 in the same manner as described above for the reference voltage. The voltage sent to the geoffon device is thus adjusted to match the voltage sent from the geoffon represented by signal 846 and signal 6.
94.

Opening switches S1 and S4 removes voltage from the geo-off. When the voltage is removed from the geo-on device, the mass of the geo-on coil oscillates about its original position, creating a damping motion in the aforementioned signal, which is transmitted to signal line 80.
7,812. The response signal generated by the geo-on device is amplified by the preamplifier as described above and sent to the 20th channel by signal line 846.
It is provided as an input to the S/H multiplexer 951 shown in the figure.

The notch filter 151 and alias filter 161 shown in FIG. 2b are illustrated in more detail in FIG. 19. Notch filter 151 and Elias filter 161 are provided with four identical channels, but again for convenience only one channel is shown in FIG. The data of the four channels are sent to multiplexer 801. Signal 846 is sent to the channel 1 input from operational amplifier 838 shown in FIG. Multiplexer 81 also includes buffer amplifier 7 shown in FIG.
A reference voltage signal 749 from the output of 48 is provided. Signal 749 is routed to 4 by multiplexer 801.
channels. Output signal 861 from multiplexer 801 represents the channel 1 output from multiplexer 801. Similarly,
Output signals 862-864 are multiplexer 801
represents channel 2-channel 4 output from.

Signal 861 from multiplexer 801 is sent to potentiometer 871 via resistors 867 and 868.
wiper arm 874. resistance 86
7,868 are coupled together by signal line 873. Signal 861 is from variable resistor 871 to resistor 872
to the non-inverting input of operational amplifier 878. A capacitor 879 coupled to signal line 873 is provided as a high frequency filter.
The positive side of capacitor 881 is coupled to signal line 873. The negative side of capacitor 881 is coupled to the negative side of capacitor 883. capacitor 88
The positive side of 3 is coupled to the non-inverting input of operational amplifier 878. Output signal 8 from operational amplifier 878
85 is coupled to the inverting input of operational amplifier 878. Output signal 885 is also sent to the non-inverting input of operational amplifier 887 through a voltage divider circuit comprised of resistors 888 and 889. operational amplifier 8
The output signal 891 from 87 is fed back to the inverting input of operational amplifier 887. Output signal 891 is also coupled to the negative side of capacitor 893. The positive side of capacitor 893 is coupled to wiper arm 874 of potentiometer 871. Output signal 8
91 and operational amplifier 887 are also potentiometer 89
6 wiper arm 895. Potentiometer 896 is coupled to the negative side of capacitors 881 and 883 via resistor 897.

Output signal 885 from operational amplifier 878 is also sent to wiper arm 902 of potentiometer 904 via resistor 901. Potentiometer 904 is coupled to the non-inverting input of operational amplifier 906 via resistor 907. operational amplifier 878
The signal 885 from is also sent to the positive side of capacitor 909. The negative side of capacitor 909 is coupled to the negative side of capacitor 911. capacitor 91
The positive side of 1 is coupled to the non-inverting input of operational amplifier 906. Output signal 9 from operational amplifier 906
12 is fed back to the inverting input of operational amplifier 906. The output signal 912 from operational amplifier 906 is also passed through a voltage divider circuit comprised of resistors 914 and 915 to the non-inverting input of operational amplifier 917. Output signal 919 from operational amplifier 917 is fed back to the inverting input of operational amplifier 917 and also applied to the negative side of capacitor 921 . The positive side of capacitor 921 is coupled to wiper arm 902 of potentiometer 904 . Operational amplifier 91
The output signal 919 from 7 is also the potentiometer 9
It is also sent to wiper arm No. 24. Potentiometer 924 is connected to capacitor 9 via resistor 925.
09,911 to the negative side.

Signal line 912 is provided as an output to alias filter 161 from the notch filter illustrated in FIG. 2b. The notch filter shown in FIG. 19 is a double-T notch filter that uses active feedback to increase the Q of the circuit. It is known to use a double-T filter as a notch filter. Increasing the Q of the circuit shown in FIG. 19 provides a very narrow stopband band. operational amplifier 87
8,887 and the associated circuitry shown in FIG.
It has a notch frequency of Operational amplifier 906,9
The double-T filter consisting of the associated circuitry shown at 17 has a notch frequency of 60.2 Hz in the preferred embodiment of the invention. Since the circuit is in series, 60
A response that blocks Hz is obtained. Blocking the 60Hz frequency is desirable because 60Hz interference is commonly caused by electrical lines that cross the area being surveyed.

The two channels of Elias filter are 2b
One is provided for each channel of data provided from the preamplifier shown in the figure. One channel, which primarily includes operational amplifier 932 and associated circuitry as shown, has a cutoff frequency of 124 Hz. The second Elias filter, which primarily includes operational amplifier 931 and associated circuitry illustrated in FIG. 19, has a cutoff frequency of 62 Hz. The Elias filter is a 12 pole Butterworth low frequency active filter. The capacitor and resistance values of each stage are selected to produce a response equivalent to a particular "pole pair" of a 12-pole Butterworth filter. Six different "pole pair" stages are cascaded to give a 12 pole Butterworth response from all filters. The circuitry included in a 12-pole Butterworth filter is well known. For this reason, only a single stage of the 12-pole Butterworth filter for each cut-off frequency is shown in FIG. operational amplifier 9
The output signal line 912 from 06 is connected to resistors 933, 93
5 to the non-inverting terminal of operational amplifier 932. Resistors 933 and 935 are both connected to the signal line 9
36. Signal line 936 is coupled to the inverting input of operational amplifier 932 via resistor 938. Capacitor 939 is operational amplifier 9
32 non-inverting inputs. The output signal 941 from the operational amplifier 932 is output from the operational amplifier 932.
is also coupled to the inverting input of 12 through resistor 943.
It is sent to the next stage of the extreme Butterworth filter.
12-pole Butterworth with cut-off frequency of 124Hz
The next stage of the filter has been deleted from FIG.
41 is shown being sent directly to the cut-off frequency selector circuit 963 shown in FIG. 20 via a resistor 943.

Signal line 912 is also routed through resistors 952 and 953 to the non-inverting input of operational amplifier 931. Resistors 952 and 953 are coupled together by signal 954. Signal line 954 is coupled to the inverting input of operational amplifier 931 via capacitor 955. Capacitor 956 is coupled to the non-inverting input of operational amplifier 931. Output signal 957 from operational amplifier 931 is fed back to the inverting input of operational amplifier 931 and is also coupled via resistor 959 to cutoff frequency selection circuit 963 shown in FIG.
The multiplexer 851 illustrated in FIG. 20 using the cut-off frequency selection circuit 963 illustrated in FIG.
Select the alias filter that will be used to provide data to. Again for simplicity, 62Hz
The next stage of the 12-pole Butterworth filter with a cutoff frequency of
9 to the cutoff frequency selection circuit 963. The next stage of the 12-pole Butterworth filter is constructed identically to that described for the stage illustrated in FIG.

Notch filter 151 and Elias filter 16 illustrated in FIG. 2b using impulse testing.
Test the response of 1. Signal line 749 sends a voltage to multiplexer 801 to perform an impulse test. Multiplexer 801 is the first
The voltage provided by signal 749 is provided as an input to the notch and alias filters illustrated in FIG. This impulse has the effect of making the notch and alias filters ring, and in this way the response of the notch and alias filters can be determined. The impulse responses of the Notch filter and Elias filter are provided via a gain range amplifier arrangement 171 to an A/D converter arrangement 141 illustrated in FIG. 2b.

Gain range amplifier device 17 illustrated in FIG. 2b
1 and the A/D converter are shown in more detail in FIG. As previously mentioned, the output signal 941 from the Elias filter has a cutoff frequency of 124 Hz to which a sampling rate of 2 ms corresponds;
The output signal 957 from the Elias filter, which has a 62 Hz cutoff frequency corresponding to a millisecond sampling rate, is sent as an input to a switching device 963. Similarly, as shown in FIG. 2b, signals 163a-b representing the channel 2 output from the alias filter are input to switching device 96.
given to 4. Signals 164a-b are provided as inputs to switching device 965, and signals 164a-b are provided as inputs to switching device 965.
5a-b are provided as inputs to switching device 966. A control signal 967 from a data retention latch 960 is applied to each switching device 963-966.
given to. Control signal 967 is used to select the channels from the Elias filters that are sent to filters 968-971. Control signal 967 selects either the 124Hz cutoff or 62Hz cutoff filter, and switching devices 963-966 pass data signals 972-975 to filters 968-97.
Give each to 1. Filters 968-971 are unipolar high pass filters used to remove DC offset from signals 972-975. Data is passed from filters 968-971 to multiplexer 8.
Sent to 51. Multiplexer 851 is also provided with a ground reference signal 978 and a voltage reference signal 749 from the output of buffer amplifier 748, illustrated in FIG. multiplexer 851
The switching of is controlled by control signal 979.

The output from multiplexer 851 is provided as an input to first stage amplifier 981. The first stage amplifier 981 is composed of four sample and hold (S/H) amplifiers 983-986. S/H amplifier 9
83 has a gain of 1, and S/H amplifier 984
-986 each have a gain of 16. The sample and hold functions of S/H amplifiers 983-986 are transferred from data hold latch 960 to each S/H amplifier 983.
-986 by control line 988.

The output signal from multiplexer 851 is S/H
As an input to amplifier 983 and S/H amplifier 9
84. The output from S/H amplifier 984 is provided as a first input to S/H amplifier 985. The output from S/H amplifier 985 is provided as a first input to S/H amplifier 986. The output from each of S/H amplifiers 983-986 is provided to multiplexer 991. In this way, gains of 1, 16, 256, 4096 are obtained from the first stage amplifier 981.

The S/H amplifier 984 also includes a current-voltage converter 9
An output signal 993 from 94 is also provided. signal 9
93 is used as a voltage offset (Vos) compensation signal, which will be explained in more detail in the following paragraphs. S/
An output signal 996 from a current-voltage converter 997 is applied to the H amplifier 985 . Similar to signal 993, signal 996 is also used as a voltage offset compensation signal. An output signal 998 from a current-voltage converter 999 is applied to the S/H amplifier 986 as a second input. Signal 998 is also used as a voltage offset compensation signal.

The output signal from first stage amplifier 981 is provided as an input to second stage amplifier 1001. The second stage amplifier 1001 is composed of three amplifiers 1003-1005, each having a gain of two. 1st
Output signal 1000 from stage amplifier 981 is provided as an input to multiplexer 1007 and also as a first input to amplifier 1003.
The output from amplifier 1003 is provided as a first input to amplifier 1004 and is also provided as an input to comparator 1009. The output from amplifier 1004 is provided as a first input to amplifier 1005. The output of each amplifier 1003-1005 is provided as an input to multiplexer 1007. Switching of multiplexer 1007 is provided by control line 10 from data retention latch 960.
11. The output of comparator 1009 is provided as an input to data bus buffer 960.

A second input signal 1014 is provided as an input to amplifier 1003 from the output of amplifier 1015.
Signal 1014, like signals 993, 996, and 998, is used as a voltage offset compensation signal.
Signal 1017 is routed from amplifier 1018 to amplifier 100
It is given as the second input to 4. signal 1021
is provided as a second input from amplifier 1022 to operational amplifier 1005. Signal 1021 is also used as a voltage offset compensation signal.

Output signal 1 from second stage amplifier complex 1001
024 is sent to multiplexer 951 via buffer amplifier 1025. buffer amplifier 10
The output from 25 is also sent as an input to comparator 1027. The output from comparator 1027 is provided as an input to data retention latch 960.

6800 applied to address decoder 1031
Address line 100 from the microprocessor provides an address to the gain range amplifier device. The address is decoded by address decoder 1031 and provided to data holding latch 960 via signal line 1032. These decoded address lines control the transfer of data between the 6800 microprocessor data bus and the gain range amplifier system latches and buffers. Data retention latch 960 to digital to analog (D/A)
Three sets of signal lines 103 to converters 1041-1043
5-1037 is given. D/A converter 104
The output from 1 is provided as an input to current-to-voltage converter 994. The output from D/A converter 1042 is provided as an input to current-voltage converter 997. The output from D/A converter 1043 is provided as an input to current-voltage converter 999.

The output from multiplexer 951 is sent to sample and hold amplifier 1051. The output from sample and hold amplifier 1051 is provided to analog to digital (A/D) converter 1052. A/D
The output from converter 1052 is provided to the 6800 microprocessor's data bus 200.

A temperature sensor 1053 is provided to provide an RTU temperature indication. Output signal 105 representing the temperature of the RTU
4 is provided as an input to multiplexer 951.

In operation, the 24 values used by the gain range amplifier system for voltage offset compensation must be calculated and stored in the 6800 microprocessor memory before the gain range amplifier system can be used for data acquisition. The voltage offset compensation value is determined by sample and hold amplifiers 984-986 and amplifier 1003-1.
005 is determined. No value is determined for sample and hold amplifier 983. To determine the required voltage offset compensation value, channel 1 is selected and its input is grounded. Multiplexers 991 and 1007 are then used to provide the output of each amplifier except sample-and-hold amplifier 983 to multiplexer 951. The output signal is sampled and
is held for a sufficient period of time to perform an A/D conversion, and the signal from A/D converter 1052 to data bus 200
to the 6800 microprocessor. A value is calculated for each of the amplifiers being tested, which when applied to each of its inputs drives the output of the amplifier to zero. These values for each amplifier are
It is stored in the 6800 microprocessor memory and is subsequently used for voltage offset compensation during the data acquisition process. Signal 1035-1 representing voltage compensation value
037 to the D/A converter 1043 and the data holding latch 960.
provides a voltage compensation value to the gain range amplifier device. D/A converters 1041-1043 and current-to-voltage converters 994, 997, and 999 are time-shared to provide compensation values to specific amplifiers being used in the data acquisition process. Four channels are scanned to collect data from the amplifiers such that four compensation values are determined for each amplifier, one for each channel. This results in a total of 24 values. These values are stored in memory for use in offset compensation.

24 Once the voltage offset value is stored in memory,
The data collection process begins. During the data acquisition process, the sample-hold amplifier of the first stage amplifier 981 acts as a sample-hold buffer and also provides most of the gain. In operation, certain channels are selected by multiplexer 851 and provided to first stage amplifier 981. Sample holding amplifier 9
All of 83-986 are placed in sample mode when the data acquisition process begins. Sample and hold amplifiers 983-986 sample for a sufficient period of time to allow stabilization, and after a sufficient period of time have elapsed control signals 988 provided by data hold latch 960 in response to an address from the 6800 microprocessor. All sample holding amplifiers 9
83-986 are simultaneously set to the holding state.
The output signal from sample and hold amplifier 983 is provided from multiplexer 991 via amplifier 1003 to comparator 1009. If the output signal from sample-hold amplifier 983 is less than 0.5V,
The output signal from comparator 1009 is 16 V without exceeding the signal output from multiplexer 851.
Instructs data bus buffer 960 that it can be amplified by a factor of twice as much. This ensures that the input voltage limit of the A/D converter (10V) is not exceeded. Typically, this is accomplished by a 6800 microprocessor by sampling the output of comparator 1009. When this signal switches to a low state, the output signal 10 from multiplexer 991
00 exceeds 0.5V.

The output signal from sample-hold amplifier 983 is
If it does not exceed 0.5V, the microprocessor switches multiplexer 991 to provide the output signal from sample and hold amplifier 984 via amplifier 1003 to comparator 1009. Again, the output from the comparator is checked to see if the output signal from sample and hold amplifier 984 exceeds 0.5V.
If the output from sample-and-hold amplifier 984 does not exceed 0.5V, the output from comparator 1009 remains high and the microprocessor sends the output signal from sample-and-hold amplifier 985 to multiplexer 991 to the output signal from multiplexer 991.
Command to select it as 000. Selection of the sample and hold amplifier is controlled by control line 988. This process is performed using the sample holding amplifier 983-9.
85 or the sample-hold amplifier 986.
continues until the output from multiplexer 991 is provided as the output from multiplexer 991. The first output from sample and hold amplifiers 983-985 that is above 0.5V is selected by the microprocessor using multiplexer 991 and the remaining sample and hold amplifiers are not tested.

The compensation values represented by signals 993, 996, and 998 are used during the data acquisition process to provide the required voltage offset compensation by adding to or subtracting from the signals normally output from sample and hold amplifiers 984-986. Sample holding amplifier 9
When 83-986 are set to sample, the compensation values of sample and hold amplifiers 984-986 are stored in three D/A converters 1041-1043.
After sample and hold amplifiers 983-986 are set to hold, the compensation values of second stage amplifiers 1003-1005 are stored in D/A converters 1041-1043. The new compensation value cannot change the voltage level held by the first stage sample and hold amplifiers 984-986 because they are in hold mode. This allows the D/A converter to be time-divided when compensating for offsets in the first and second stage amplifiers.

After the output from the first stage amplifier 981 is determined, the output is sent to multiplexer 1 as signal 1000.
Given to 007. Unamplified signal 1000 is sent to multiplexer 1007 in response to control signal 1011.
Control signal 1011 is initially provided as signal 1024 from data retention latch 960 in response to address and data from the 6800 microprocessor. multiplexer 1007
The output from is provided as an input to comparator 1027 via output buffer 1025. Comparator 1
027 is the output from multiplexer 1007.
Make a decision as to whether it is above 4V.
If the output from multiplexer 1007 does not exceed 4V, then the two coefficients can be multiplied without exceeding the 8V input limit set for A/D converter 1052. The output from comparator 1027 is provided as an input to data bus buffer 960 as described above. The output from comparator 1027 remains high until the output from multiplexer 1007 exceeds 4V. Output from multiplexer 1007 exceeds 4V, comparison 10
The output from 27 goes low and the output from multiplexer 991 is selected as the output provided to multiplexer 951. Amplifier 1003-
Each of the outputs from 1005 is provided to comparator 1027 until such time as the output of comparator 1027 goes low. The gain range setting procedure is now complete and in this way the output from the first amplifier or the output of amplifier 1005 exceeding 4V is output to multiplexer 95.
1 is given. Once the output is selected and provided to multiplexer 951, channel multiplexer 851 advances to the next channel in the gain range amplifier and the gain range setting process is repeated.

Data provided to multiplexer 951 is converted to digital form by A/D converter 1052 and provided to 6800 microprocessor data bus 200 in the same manner as described above.

Multiplexer 951 also receives signals 188- from power supply and regulator 186 illustrated in FIG. 2b.
199 will also be given. These signals representing the various voltage levels provided by the power supply and regulator are converted to digital form by A/D converter 1052 and provided from A/D converter 1052 to the 6800 microprocessor data bus.
These signals 188-199 indicate the availability of power for the RTU illustrated in Figure 2b.

The power regulator 186 shown in FIG. 2b is illustrated in more detail in FIG. 21. Referring to FIG. 21, battery pack 1101 provides four output voltages via supply lines 196-199 previously described in FIG. 2b. Supply line 196 carries +8.75V, supply line 197 carries +18.75V, and supply line 198 carries -6.25V.
, the supply line 199 supplies -18.75V. Supply line 198 is provided directly to the RTU. supply line 19
8,197,199 is voltage regulator 1103
and directly to the RTU. Voltage regulator 1103 is also provided with control signals 187 from microprocessor 111, illustrated in FIG. 2b.

In response to the voltages provided by supply lines 196, 197, 199 and the command signal provided by signal line 187, voltage regulator 1103
It provides the multiple output signals described above in Figure 2b. Signal line 188 is +12V, signal line 189 is +15V
, signal line 190 is -5V, signal line 191 is -
12V, signal line 192 -15V, signal line 193
supplies +5V, signal line 194 supplies +5V, and signal line 195 supplies +5V. Regulator 110
3 is mainly used to set and maintain each voltage level of the lines 188-195. Otherwise, the voltage level may vary due to lack of charge (characteristic discharge curve) due to use, battery life, temperature, etc.
It varies according to the variation of the voltage level given from 101.

The voltage regulator circuit illustrated in FIG. 21 is illustrated in more detail in FIGS. 22a and 22b. Referring to FIG. 22a, signal 187a from the microprocessor represents a command to turn on +15V power supply 189. Signal 187a goes high when +15V signal 189 is desired to be turned on. Signal 187a is sent to buffer amplifier 1111,
It is also grounded via a resistor 1112. The output from buffer amplifier 1111 is routed through resistor 1113 to the input of transistor 1115. +5V
Power supply 194 is coupled to the output of buffer amplifier 1111 via resistor 1118 and to the base of transistor 1115 via resistor 1113.

A power supply 197 having a voltage level of +18.75V connects transistor 1 through resistors 1121 and 1122.
115 and the collector of transistor 1119. Power supply 197 is also sent to the emitter of transistor 1124. The collector of transistor 1115 is connected to transistor 11 through resistor 1122.
It is coupled to the base of 24. transistor 111
The emitter of 5 is coupled to the base of transistor 1119. The emitter of transistor 1119 is grounded. The collector of transistor 1124 is provided as an input to voltage regulator 1126 and is also connected to ground via capacitor 1127. Ground input 11 of voltage regulator 1126
29 is grounded. The output from voltage regulator 1126 is sent as a supply voltage 189 to the RTU. The output from voltage regulator 1126 is also connected to ground via capacitor 1131. As previously mentioned, supply voltage 189 has a voltage level of +15V.

When the command signal 187a goes high, the output from the buffer amplifier 1111 goes high and reaches +5V.
Allowing current to flow from power supply 194 to the base of transistor 1115. transistor 1
115 and 1119 constitute a Darlington pair.
In response to the signal on line 187a, transistor 111
When transistor 5 is turned on, transistor 1119 is also turned on, and current flows from the base of transistor 1124. Transistor 1124 is turned on,
Voltage regulator 1 provides a regulated +15V output in response to the voltage provided by transistor 1124
Give +18.75V input to 126. capacitor 1
127 and 1131 stabilize the voltage regulator 1126.

A signal 187b from the microprocessor, which is a command to turn on the +5V power supply 193, is given as an input to the buffer amplifier 1133, and is also applied to the resistor 11.
34 to ground. buffer amplifier 113
The output from 3 is coupled to the base of transistor 1135 via resistor 1137. The +5V power supply is connected to transistor 11 via resistors 1141 and 1137.
35 and also to the output of buffer amplifier 1133 via resistor 1141. The output from buffer amplifier 1133 is also connected to ground via capacitor 1142.

The collector of transistor 1135 and the collector of transistor 1143 are connected to resistors 1145 and 1146.
is coupled to the +8.75V power supply 196 via the +8.75V power supply 196. Signal 196 is also coupled to the emitter of transistor 1148. The collectors of transistors 1135 and 1143 are connected to transistor 114 through resistor 1145.
It is coupled to the base of 8. Power supply 196 is resistor 11
46 to the base of transistor 1148. The emitter of transistor 1135 is coupled to the base of transistor 1143. The emitter of transistor 1143 is grounded. The collector of transistor 1148 is capacitor 115
1 to ground through the voltage regulator 115
given as input to 2. A ground input 1154 to voltage regulator 1152 is connected to ground via potentiometer 1155. The wiper arm of potentiometer 1155 is grounded. Ground input 1154 to voltage regulator 1152
It is also grounded via capacitor 1157. The output from voltage regulator 1152 is provided as +5V power supply voltage 193 to the RTU and is also grounded via capacitor 1159.

Signal 187b goes high when it is desired to turn on +5V power supply 193. When signal 187b goes high, the output from buffer amplifier 1133 goes high and connects transistor 11 from +5V power supply 194.
Allows power to flow to the base of the 35.
Transistor 1135 turns on in response to current from +5V power supply 194 and transistor 113
Transistor 1143, which forms a Darlington pair together with transistor 5, is also turned on. transistor 1135,
When the Darlington pair consisting of transistor 1143 is turned on, current flows from the base of transistor 1148. In this way transistor 1148
is turned on, and +8.75V power supply voltage is applied to voltage regulator 1152. In response to the input voltage, voltage regulator 1152 adjusts +
Apply 5V power supply 193 to RTU.

Capacitors 1151 and 1159 stabilize voltage regulator 1152. potentiometer 1
155 is provided to allow minute changes to be made to the voltage level of power supply 193. RTU
In some applications, +5V is slightly more than +
A level of 5V power supply 193 may be desirable.

Command signal 187c provided by the 6800 microprocessor represents a command to turn on +5V power supply 195. The signal 187c is the buffer amplifier 116
1 and is also connected to ground via resistor 1163. The output from buffer amplifier 1161 is connected to transistor 116 via resistor 1165.
It is connected to the base of 4. +5V power supply 194 is connected to transistor 1 via resistor 1168 and resistor 1165.
164 base. +5V power supply 194 is also connected to buffer amplifier 1161 via resistor 1168.
is also combined with the output of

Transistors 1 together forming a Darlington pair
The collectors of 164 and 1169 are resistors 1171 and 1.
172 to a +8.75V power supply 196. The emitter of transistor 1164 is coupled to the base of transistor 1169. The emitter of transistor 1169 is grounded.

+8.75V power supply 196 is applied to the base of transistor 1173 via resistor 1171. The collectors of transistors 1164 and 1169 are resistors 1
172 to the base of transistor 1173. +8.75V power supply 196 is also provided to voltage regulator 1175 and the emitter of transistor 1173. The collector of transistor 1173 is grounded via capacitor 1176 and is also coupled to the input of regulator 1181. Ground input 1178 to voltage regulator 1175 is grounded. The output from voltage regulator 1175 is RTU and regulator 1.
103 as a +5V power supply 194.
The output from voltage regulator 1175 is also connected to ground via capacitor 1179.

The collector of transistor 1173 is coupled to the input of voltage regulator 1181 and is also connected to ground via capacitor 1182. A ground input 1183 of voltage regulator 1181 is grounded. The output of voltage regulator 1181 is +5V power supply 19
5 and is also grounded via capacitor 1185.

+8.75V power supply 196 is voltage regulator 117
5 is given directly. The +5V power supply 194 is always on when the RTU is operating, and the RF receiver 1
06 and the RF interface 108, the command from the CRS shown in FIG.
It is possible to turn on the computer 111 shown in FIG. All other voltage sources are turned on only when in use. The command signal 187c becomes high when it is desired to turn on the +5V power supply 195. signal 1
When 87c goes high, buffer amplifier 116
1 goes high, allowing current to flow from +5V power supply 94 to the base of transistor 1164. Transistor 1164,1 in response to current to the base of transistor 1164
169 are both turned on. transistor 116
4,1169 turns on, transistor 11
Current flows from the base of 73, turning it on. When transistor 1173 turns on, +
An 8.75V power supply 196 is applied to the input of voltage regulator 1181. In response to the +8.75V power supply being applied to the input of voltage regulator 1181,
A regulated +5V power supply is provided to the RTU.

Capacitors 1176 and 1179 are used to stabilize voltage regulator 1175. Capacitors 1182 and 1185 are used to stabilize voltage regulator 1181.

Referring to Figure 22b, the command signal 187d from the 6800 microprocessor is connected to the +12V power supply 188.
Represents a command to turn on. Signal 187d is provided as an input to buffer amplifier 1191 and is also grounded via capacitor 1192. The output from buffer amplifier 1191 is coupled to the base of transistor 1194 through resistor 1195. +5V power supply 194 is coupled to the output of buffer amplifier 1191 via resistor 1197.

Transistors 1 together forming a Darlington pair
The collectors of 194 and 1199 are resistors 1201 and 1.
202 to the +18.75V power supply 197. The emitter of transistor 1194 is grounded. The collectors of transistors 1194 and 1199 are also connected to transistor 1203 via resistor 1202.
It is also given to the base of +18.75V power supply 197 is also coupled to the emitter of transistor 1203;
It is also coupled to the base of transistor 1203 via resistor 1201.

The collector of the transistor 1203 is a resistor 120
5 to the input of voltage regulator 1207. A ground input 1209 of voltage regulator 1207 is grounded. Voltage regulator 12
The power input of 07 is grounded through a capacitor 1208. The output from voltage regulator 1207 is provided as +12V power supply 188 and is grounded via capacitor 1211.

When you want to turn on the +12V power supply 188, command signal 1
87d becomes high. When command signal 187d goes high, the output from buffer amplifier 1191 goes high, allowing current to flow from +5V power supply 194 to the base of transistor 1194. In response to the current flowing into the base of transistor 1194, transistors 1194 and 1199 are both turned on, allowing current to flow from the base of transistor 1203. in this way,
Transistor 1203 turns on, switching supply voltage 197 to the input of voltage regulator 1207. In response to voltage input 197, voltage regulator 1207 provides a regulated +12V power supply 188 to the RTU.

Command signal 187 from 6800 microprocessor
e represents a command to turn on the -5V power supply 190.
Signal 187e is provided as an input to buffer amplifier 1215. The output from buffer amplifier 1215 is connected to transistor 12 through resistor 1216.
Given to 18 bases. +5V power supply 194 is connected to transistor 12 via resistors 1221 and 1216.
18 base. +5V power supply 194 is also coupled through resistor 1221 to the output of buffer amplifier 1215 and also through resistor 1222 to the input of buffer amplifier 1215. −
An 18.75V power supply 199 is coupled to the base of transistor 1218 via resistor 1225.

Transistors 1218 and 1227 form a Darlington pair. Transistors 1218, 122
The collector of 7 is coupled to the -18.75V power supply 199 through resistors 1228 and 1229. The emitter of transistor 1218 is coupled to the base of transistor 1227. The emitter of transistor 1227 is grounded.

-18.75V power supply 199 is coupled to the base of transistor 1233 via resistor 1229. −
18.75V power supply 199 is also coupled to the emitter of transistor 1233. transistor 1218,
The collector of 1227 is coupled to the base of transistor 1233 via resistor 1228. The collector of transistor 1233 is voltage regulator 1
235 and is also coupled to the input of capacitor 1236
grounded via. Voltage regulator 1235
The ground input 1237 to is grounded. The output from voltage regulator 1235 provides a -5V power supply 190 to the RTU. The output from regulator 1235 is also grounded via capacitor 1238.

When you want to turn on the -5V power supply 190, command signal 1
87e goes low. When command signal 187e goes low, current is allowed to flow from the base of transistor 1218. transistor 1
In response to the current from the base of transistor 218, both transistors 1218 and 1227 turn on, allowing current to flow to the base of transistor 1233. In this way, transistor 123
3 is turned on, switching the -18.75V power supply 199 to the input of the voltage regulator 1235. In response to the -18.75V power input, voltage regulator 1235 provides a -5V regulated output power supply 190.

The command signal 187f is a command to turn on the -12V power supply 191. Signal 187f is buffer amplifier 1
241. The output from buffer amplifier 1241 is coupled through resistor 1244 to the base of transistor 1243. +5V
Power supply 194 is coupled to the base of transistor 1243 through resistors 1246 and 1244. +5V
Power supply 194 is also coupled to the output of buffer amplifier 1241 via resistor 1246 and
8 to the input of amplifier 1241.
-18.75V power supply 199 is coupled to the base of transistor 1243 via resistor 1251.

Transistors 1243 and 1252 constitute a Darlington pair. Transistors 1243, 125
The collector of 2 is coupled to the -18.75V power supply 199 through resistors 1255 and 1256. The emitter of transistor 1252 is grounded. The base of transistor 1243 is grounded via capacitor 1258.

-18.75V power supply 199 is coupled through resistor 1255 to the base of transistor 1259. −
18.75V power supply 199 is also coupled to the emitter of transistor 1259. transistor 124
The collector of 3,1252 is coupled to the base of transistor 1259 via resistor 1256. The collector of transistor 1259 is coupled to the input of voltage regulator 1261 via resistor 1263. The input of regulator 1261 is grounded via capacitor 1265. A ground input 1266 of voltage regulator 1261 is grounded. The output from voltage regulator 1261 is
Provide -12V power supply 191 to the RTU. The output from voltage regulator 1261 is also connected to capacitor 12
67 to ground.

When you want to turn on the -12V power supply 191, command signal 1
87f becomes a low state. When command signal 187f goes low, current flows from the base of transistor 1243, turning on transistors 1243 and 1252. Turning on transistors 1243 and 1252 causes current to flow to the base of transistor 1259, which turns on transistor 1259 and connects -18.75V power supply 199 to voltage regulator 1.
Switch to 261 input. In response to voltage input,
Voltage regulator 1261 provides a -12V regulated power supply 191 to the RTU.

Signal 187g represents a command to turn on -15V power supply 192. Signal 187g is buffer amplifier 12
71. The output from buffer amplifier 1271 is applied to the base of transistor 1274 via resistor 1272. A +5V power supply 194 is coupled to the base of transistor 1274 through resistors 1276 and 1272. +5V power supply 194 is also coupled to the output of buffer amplifier 1271 via resistor 1276 and
8 to the input of buffer amplifier 1271. -18.75V power supply 199 is resistor 128
2 to the base of transistor 1274.

Transistors 1274 and 1283 form a Darlington pair. Transistors 1274, 128
3 is coupled to the -18.75V power supply 199 through resistors 1284 and 1285. The collectors of transistors 1274 and 1283 are also connected to resistor 128.
4 to the base of transistor 1288. The emitter of transistor 1283 is grounded. -18.75V power supply 199 is coupled to the base of transistor 1288 through resistor 1285;
It is also coupled to the emitter of transistor 1288. The collector of transistor 1288 is coupled to the input of voltage regulator 1291. The collector of transistor 1288 is also connected to capacitor 1293.
grounded via. Voltage regulator 1291
The ground input 1294 of is grounded. The output from voltage regulator 1291 is provided as a -15V power supply 192 to the RTU. Voltage regulator 1
The output from 291 is also grounded via capacitor 1295.

When it is desired to turn on the -15V power supply 192, the command signal 187g goes low. When command signal 187g goes low, current flows from the base of transistor 1274, causing transistors 1274 and 128
Turn on 3. Transistors 1274, 128
3 turns on, current flows from the base of transistor 1288, turning transistor 1288 on. When transistor 1288 turns on,
The -18.75V power supply is switched to the input of voltage regulator 1291 which provides a regulated -15V output power supply 192.

Due to the importance of ensuring that the remote telemetry equipment illustrated in Figure 2b is operational, the
Another test device illustrated in the figure is provided as a general purpose test device for the remote telemetry device illustrated in FIG. 2b. The main functions of the test equipment illustrated in Figure 23 are as follows:
The purpose is to provide four output signals that can be used to test the channel. Square, sawtooth, sine, and triangular waves are output by the test equipment to individually identify each channel and provide a means to determine if any of the channels of the remote telemetry device are inoperative. The test apparatus illustrated in FIG. 23 also provides a means by which frequency sweeps are generated and provided through the channels of the remote telemetry device. This frequency sweep is used to test the operation of notch filter 151 and alias filter 161 shown in FIG. 2b.

Referring to FIG. 23, gradient voltage generator 176
1 provides a slope signal that is used by voltage controlled oscillator 1762 to generate a frequency sweep signal. Gradient signal 17 output from gradient voltage generator 1761
63 causes the remote telemetry device shown in FIG. 2b to go into data acquisition mode so that the geooff-on test function is completed and before the frequency sweep is applied to the input of the preamplifier 135 shown in FIG. 2b. There will be a delay in making this possible.

Reference voltage source 1765 provides an output signal 1766 having a value of +6V and also provides an output signal 1767 having a value of -6V. Using the output signals 1765, 1765, 1766, 1767 from the reference voltage source, the voltage controlled oscillator 1762 and the gradient voltage generator 1
761 , a sine wave shaper 1769 , a sawtooth wave generator 1771 , and provides output to an output circuit 1772 . +6V signal 1766 is also a voltage controlled oscillator 176
2 to enable generation of a constant frequency output signal.

Using a switching device 1774, the output signal 1763 from the gradient voltage generator or the reference voltage source 1
Either output signal 1766 from 765 is selected as the input to voltage controlled oscillator 1762. When signal 1763 is applied to the voltage controlled oscillator via switching device 1774, the output from the voltage controlled oscillator becomes a frequency sweep. When signal 1766 is selected and applied to voltage controlled oscillator 1762 via switching device 1774, the output of the voltage controlled oscillator becomes a constant frequency signal.

Voltage controlled oscillator 1762 provides a triangular waveform output signal 1776 and a square waveform output signal 1777.
Output signal 1776 is provided as an input to sine wave shaper 1769, sawtooth wave generator 1771, and output circuit 1772. Output signal 1777 is used as an input to sawtooth generator 1771 and output circuit 17
72.

Sine wave shaper 1769 manipulates triangular waveform 1776 to form sine numbers from the triangular waveform. signal 17
This sine wave, represented as 79, is provided from a sine wave shaper 1769 to an output circuit 1772.

A sawtooth wave generator 1771 generates a sawtooth wave 1781 using a triangular wave 1776 and a rectangular wave 1777. The sawtooth wave 1781 is the sawtooth wave generator 1771
is given as an input to the output circuit 1772.

In response to the input signal, output circuit 1772 provides four output signals 1783-1786, each of which is sent to a respective channel of preamplifier 135 illustrated in FIG. 2b. Signal 1783 is a triangular wave, signal 1
784 is a sine wave, signal 1785 is a sawtooth wave, and signal 1786 is a square wave. Switching is also provided in output circuit 1772 to allow the sine wave represented by signal 1779 to be applied to all four input channels of preamplifier 135 illustrated in FIG. 2b. Therefore, either four different waveforms are applied to the four input channels of preamplifier 135, or one sine wave is applied to each of the input channels of preamplifier 135.

The remote telemeter device shown in FIG.
When testing is desired using the test equipment shown in FIG. 3, the output signal 1783- from the output circuit 1772
1786 is coupled to the input of preamplifier 135. Output signal 1766 from reference voltage source 1765
is coupled to the voltage controlled oscillator via switching device 1774. In response to +6V input signal 1766, the test apparatus illustrated in FIG. 23 provides either four different waveforms with constant frequencies or four sine waves with constant frequencies to preamplifier 135. The signal is transmitted via the data acquisition device of the remote telemetry device illustrated in FIG. 2b, as previously described, and displayed by the display device 93 illustrated in FIG. 2a. This display provides an indication of whether each channel of the remote telemetry device illustrated in Figure 2b is operational. The output voltage from the test apparatus illustrated in FIG. 23 is varied to provide an indication of the sensitivity of the remote telemetry device illustrated in FIG. 2b.

After performing this initial test, the gradient voltage generator 1
761 is connected to voltage controlled oscillator 1762 via switching device 1774. Gradient voltage generator 1761 outputs slope signal 1763 after the initial testing of the geooff-on is completed and the remote telemetry device illustrated in FIG. 2b has entered data acquisition mode. In response to this gradient signal, the test apparatus illustrated in FIG. 23 outputs either four different waveforms sweeping through a frequency band, or four sine waves sweeping through a frequency band. These signals are again provided via a remote telemetry device as previously described, and the second
The data is displayed by the data display device 93 shown in FIG. As the frequency sweep exceeds 60Hz, the waveform displayed on the data display approaches a straight line and the notch
Indicates that the filter 151 is operating.
The same phenomenon can be observed when the frequency sweep exceeds the cutoff frequency of Elias filter 161, again indicating that the Elias filter is operating.
The test setup illustrated in FIG. 23 thus provides another way in which the operability of the remote telemetering device illustrated in FIG. 2b can be guaranteed, improving the reliability of the seismic survey equipment implemented in the present invention.

The gradient generator 1761 illustrated in FIG.
This is illustrated in more detail in Figure 4. Referring to FIG. 24, the inverting input of operational amplifier 1791 is
coupled to the common point 1793 of the RTU shown in the figure,
It is also coupled to another ground 1794 via a resistor 1792. A non-inverting input of operational amplifier 1791 is grounded via resistor 1795. Operational amplifier 1
The output from 791 is coupled to the base of transistor 1797 via resistor 1796. The output from operational amplifier 1791 is also connected to potentiometer 17
99 to ground.

The emitter of transistor 1797 receives +6V signal 1766 via diodes 1802 and 1803.
is combined with A +6V signal 1766 is provided from a reference voltage source 1765 illustrated in FIG. The collector of transistor 1797 is coupled through resistor 1805 to the inverting input of operational amplifier 1806.
The inverting input of operational amplifier 1806 is also connected to resistor 1807.
is coupled to the wiper of potentiometer 1808 through resistor 1809 and to potentiometer 1811 through resistor 1809 . operational amplifier 180
The non-inverting input of 6 is grounded. One terminal of the potentiometer 1808 is connected to a -6V power supply 176 provided from a reference voltage source 1765 shown in FIG.
Combined with 7. The second terminal of potentiometer 1808 is grounded. The output signal from operational amplifier 1806 is coupled to the inverting input of operational amplifier 1814 and via diode 1815 to the inverting input of operational amplifier 1817. Operational amplifier 1
The output of 814 is also provided via diode 1815 as signal 1763 shown in FIG.

The non-inverting input of the operational amplifier 1814 is connected to the resistor 181.
8 to ground. The output from operational amplifier 1814 is coupled to one terminal of potentiometer 1811 via diode 1821. The second terminal of potentiometer 1811 is grounded. The output signal from operational amplifier 1814 is also fed back through resistor 1822 to the non-inverting input of operational amplifier 1814.

The non-inverting input of operational amplifier 1817 is coupled to the wiper of potentiometer 1799. The inverting input of operational amplifier 1817 is grounded via resistor 1823. The output from operational amplifier 1817 is fed back through resistor 1816 to the non-inverting input of operational amplifier 1791.

In the circuit illustrated in FIG.
91, 1814, 1817 are used as comparators, while operational amplifier 1806 is used as an integrator. Operational amplifiers 1791, 18 in the rest state
The output of 17,1806 is negative full scale, while the output from operational amplifier 1814 is positive full scale. In this state, the operational amplifier 17
The non-inverting input of 91 is at approximately -0.8V. The inverting input of operational amplifier 1817 is not pulled below ground by operational amplifier 1806 because of diode 1815. Since the non-inverting input of operational amplifier 1817 is held below ground by operational amplifier 1791, the output of operational amplifier 1817 is held at negative full scale, creating a stable condition.

When the remote telemeter device illustrated in FIG. 2b performs a leak test, the common feature 1794 of the test device illustrated in FIG.
It is placed above the common point 1793. Operational amplifier 17
91 detects this as a negative pulse on the inverting input. When this negative pulse drops below -0.8V, the output of operational amplifier 1791 switches to positive full scale. The non-inverting input of operational amplifier 1817 moves above ground. Therefore, the output of operational amplifier 1817 switches to positive full scale. This drives the non-inverting input of operational amplifier 1791 to approximately +0.8V. Next, two common points 179
3,1794 returns to the same potential and the circuit remains in the new state.

When the output of operational amplifier 1791 is inactive, transistor 1797 is held on. Therefore, the output of operational amplifier 1806 is held at negative full scale. In the active state, transistor 1
797 is turned off. The output of operational amplifier 1806 begins to increase linearly in voltage at a rate determined by the setting of potentiometer 1808. Operational amplifier 1
Output signal 1763 remains at zero until the output of 806 reaches approximately +0.6V. Operational amplifier 1806
When the output of 1763 reaches approximately +0.6V, the output signal 1763 from the gradient voltage generator begins to track the output of the integrator. The output of operational amplifier 1814 is approximately +6V
, so the noninverting input is at approximately +0.6V. When the output of operational amplifier 1806 is approximately +0.6V,
The output of operational amplifier 1814 switches to negative full scale. When this occurs, the rate of change of the integrator output changes by an amount proportional to the potentiometer 1811 setting. Output signal 176 until reaching the threshold set by potentiometer 1799
3 increases at this new rate. The circuit then returns to rest until another trigger pulse is received.

The gradient voltage generator illustrated in FIG. 24 provides a frequency sweep to the input of the preamplifier 135 illustrated in FIG. 2b with the test equipment illustrated in FIG. 23.
The frequency sweep is delayed until after initial testing of the RTU is completed and the RTU has entered data acquisition mode.

The reference voltage source 1765 illustrated in FIG.
This is illustrated in more detail in FIG. Preferably, two 9V batteries 1831, 1832 are used to power the test apparatus illustrated in FIG.
One of the 9V batteries 1831 has its negative side grounded. A second 9V battery 1832 has its positive side grounded. The positive side of battery 1831 is resistor 1834
to the collector of transistor 1833 and the wiper of potentiometer 1835. The positive side of battery 1831 is also coupled through resistor 1839 to the inverting input of operational amplifier 1837 and the collector of transistor 1838. battery 18
The positive side of 31 is also coupled directly to the emitter of transistor 1841. The negative side of battery 1832 is coupled directly to the emitter of transistor 1842.

The base of transistor 1833 is coupled to the collector of transistor 1833. The emitter of transistor 1833 is grounded. The collector and base of transistor 1833 are also coupled to the wiper of potentiometer 1835.
One terminal of potentiometer 1835 is grounded. A second terminal of potentiometer 1835 is coupled to the base of transistor 1838. The collector of transistor 1838 is coupled to the inverting input of operational amplifier 1837. The emitter of transistor 1838 is grounded. The non-inverting input of operational amplifier 1837 is connected to potentiometer 184.
4 wipers. The output of operational amplifier 1837 is connected to transistor 184 via resistor 1845.
1 base. transistor 1841
The collector of is connected to operational amplifier 1 via resistor 1846.
847's non-inverting input. The collector of transistor 1841 is also coupled to one terminal of potentiometer 1844 via resistor 1848. The second terminal of potentiometer 1844 is grounded. The collector of transistor 1841 also provides an output signal 1766 shown and described in FIG. One terminal of capacitors 1851 and 1852 is coupled to signal line 1766. The second terminals of capacitors 1851 and 1852 are grounded.

The inverting terminal of operational amplifier 1847 is grounded.
The output from operational amplifier 1847 is coupled to the base of transistor 1842 via resistor 1853. The collector of transistor 1842 provides an output signal 1767 shown and described in FIG. Capacitors 1855 and 1856 both have one terminal coupled to signal line 1767. capacitor 18
The second terminal of 55,1856 is grounded. The collector of transistor 1842 is also coupled to the non-inverting input of operational amplifier 1847 through a resistor-capacitor circuit comprised of resistor 1857 and capacitor 1858.

In operation, transistor 183 along with resistors 1834 and 1839 and potentiometer 1835
Operational amplifier 1837 by the combination of 3,1838
A reference voltage is set to the inverting input of. resistance 184
8 and potentiometer 1844 are operational amplifiers 18
The non-inverting input of 37 serves to set the sample voltage. Operational amplifier 183 acting as a comparator
7 has a function of detecting the difference between the reference voltage and the sample voltage. When a difference between the sample voltage and the reference voltage is detected, operational amplifier 1837 connects resistor 1
It functions to provide a correction signal to the base of transistor 1841 via 845. transistor 18
41 is turned on and has the function of varying the output voltage level represented by signal 1766 so that the sample voltage and reference voltage are equal.

Transistor 1841 can be considered similar to a variable resistor whose resistance is a function of the voltage applied to the base of the transistor. Therefore, the output voltage represented by signal 1766 will tend to decrease as the load increases or battery life decreases, and the sample voltage will also tend to decrease proportionally, as will the output voltage from operational amplifier 1837. This tends to increase the base-to-emitter voltage of transistor 1841, which in turn turns on transistor 1841 more strongly and reduces its resistance, allowing more current to flow to the load. Then, signal 176
The output voltage represented by 6 and the sample voltage tend to increase and the base-to-emitter voltage of transistor 1841 tends to decrease until the sample voltage is again equal to the reference voltage.

The regulator shown in FIG.
1,1832 and the current delivered to the load. This particular regulator is designed to operate within battery voltage limits of 9.0 to 6.2 VDC and current limits of about 0 to about 15 mA.

Transistor 183 to generate a reference voltage
The use of 31,1838 is believed to be a novel feature of the circuit illustrated in FIG. 25th
The reference voltage generator shown in the figure is designed to generate a stable reference voltage with a minimum amount of battery current, so the forward voltage-current characteristics of the base-emitter junction of a silicon transistor are the basis for generating the reference voltage. It is said that The base-emitter voltage of transistor 1833 is reduced to a level that is essentially constant within battery voltage fluctuations of 6.2V to 9.0V DC.
834 biases the current to the base-emitter junction of transistor 1833. Therefore, a constant voltage is applied to potentiometer 1835 in series with the base of transistor 1838. Therefore, the collector-emitter voltage of transistor 1838 is essentially held constant, and this collector-emitter voltage is used as a reference voltage.

The voltage controlled oscillator 1762 illustrated in FIG. 23 is illustrated in more detail in FIG. Referring to FIG. 26, signal 1763 from gradient voltage generator 1761 is provided as one input to switching device 1861. Output signal 1766 from reference voltage source 1765 is connected to potentiometer 186
It is given as an input to one terminal of 2. The second terminal of potentiometer 1862 is grounded.
The wiper of potentiometer 1862 is provided as a second input to switching device 1861.

The non-inverting input of operational amplifier 1863 is coupled to switching device 1861. operational amplifier 186
The output from 3 is fed back to the inverting input of operational amplifier 1863. The output from operational amplifier 1863 is also provided to switching device 1869 through a plurality of series connected resistors 1864-1868. The plurality of resistors 1864-1868 are connected to the operational amplifier 18.
63 to the non-inverting input of an operational amplifier 1871 coupled to a switching device 1869.

The output signal from operational amplifier 1871 is fed back to the inverting input of operational amplifier 1871 and also to the emitter of transistor 1872. The output signal from operational amplifier 1871 is also routed through resistor 1873 to the inverting input of operational amplifier 1874.
The non-inverting input of operational amplifier 1874 is grounded. The output of operational amplifier 1874 is fed back to the inverting terminal of operational amplifier 1874 via resistor 1875 and is also coupled to the emitter of transistor 1876.

The base of transistor 1872 is resistor 1878
The signal line 177 shown and described in FIG.
Combined with 7. A signal line 1777 provides a rectangular wave from the voltage controlled oscillator circuit shown in FIG. The base of transistor 1876 is also coupled to signal line 1777 via resistor 1879.
The collectors of transistors 1872 and 1876 are coupled together and via resistor 1881 to the inverting input of operational amplifier 1882. Operational amplifier 1
The non-inverting input of 882 is grounded. Operational amplifier 1
The output from 882 is fed back to the inverting input of operational amplifier 1882 via capacitor 1883. The output from operational amplifier 1882 is also output from operational amplifier 18
84, and provides a triangular wave as an output via signal line 1776 shown and explained in FIG. The non-inverting input of operational amplifier 1884 is also coupled to signal line 1777 via resistor 1886.

One terminal of potentiometer 1887 is +6V power line 177 fed from reference voltage source 1765.
6. The second terminal of potentiometer 1887 is fed from reference voltage source 1765 -
Coupled to 6V power line 1767. The wiper of potentiometer 1887 is resistor 1891, 1892
is coupled to the non-inverting input of operational amplifier 1893 through a voltage divider circuit consisting of . The output of operational amplifier 1893 is fed back to the inverting input of operational amplifier 1893. The output from operational amplifier 1893 is also provided through resistor 1894 to the non-inverting input of operational amplifier 1884, and through resistors 1894 and 1896.
is sent to signal line 1777 via.

The operation of the voltage controlled oscillator circuit illustrated in FIG. 26 is as follows. First, assume that the output of operational amplifier 1884, used as a comparator, is in a low state. Transistor 1872 is on and transistor 1876 is off. The input to operational amplifier 1882 used as an integrator is operational amplifier 18
71 is a positive voltage equal to the input voltage to the non-inverting input of 71. Therefore, the output of operational amplifier 1882 decreases linearly. The output of operational amplifier 1893 is near zero. Therefore, the non-inverting input of operational amplifier 1884 is negative at a value determined by resistors 1894 and 1886.

The output of the operational amplifier 1882 is connected to the resistor 1894,1
When it decreases to the value determined by 886, operational amplifier 1
The output of 884 switches positive and operational amplifier 188
The non-inverting input of 4 is also positive. transistor 18
76 is turned on and transistor 1872 is turned off. This causes the slope of the output from operational amplifier 1882 to change sign. operational amplifier 188
The rate of change of the output from the operational amplifier 1871 is determined by the magnitude of the voltage applied to the non-inverting input of the operational amplifier 1871. This process continues and a triangular wave 1776 and a square wave 1777 are generated. The frequencies of the triangular wave 1776 and the rectangular wave 1777 are determined by the magnitude of the voltage applied to the non-inverting input of the operational amplifier 1871. Therefore, potentiometer 1862 and resistors 1864-1868 in combination with switching device 1869
can be used to adjust the frequency of the output signal from voltage controlled oscillator 1762.

The sine wave shaper 1769 illustrated in FIG. 23 is illustrated in more detail in FIG. The sine wave shaper 1769 functions to change the triangular wave 1776 into a sine wave 1779. A triangular wave 1776 sent from a voltage controlled oscillator 1762 is applied to a non-inverting input of an operational amplifier 1902 via a resistor 1901. Signal line 1776 is grounded via resistor 1903 and potentiometer 1904. Signal line 1
776 also includes resistor 1905 and potentiometer 19
It is grounded via 06. Signal 1776 is also connected to transistors 1907 and 19 through resistor 1901.
Sent to collector 08.

The base of transistor 1907 is resistor 1911
is coupled to the wiper of potentiometer 1904 via. The emitter of transistor 1907 is grounded. Signal line 1776 also connects series connected diodes 1914, 1913, 1 through resistor 1901.
The anode terminal of diode 1912, which is connected to the cathode terminal of the diode string including 912, is grounded.

The base of transistor 1908 is resistor 1916
is coupled to potentiometer 1906 via. The emitter of transistor 1908 is grounded. Signal line 1776 also connects series connected diodes 1919, 1918, 1917 via resistor 1901.
The cathode of diode 1917 is grounded.

The non-inverting input of operational amplifier 1902 is connected to ground via potentiometer 1921. The wiper of potentiometer 1921 is also grounded. The output of operational amplifier 1902 is fed back to the inverting input of operational amplifier 1902. The output of operational amplifier 1902 is also provided as the sinusoidal signal 1779 described above in FIG.

Resistor 1901 and clipping diode 19
12-1914 and 1917-1919 serve to round off the apex of the triangular wave. potentiometer 19
21 is used to modify the slope of the triangular wave to make it more similar to a sine wave. transistor 19
07 and 1908 are further provided to round off the apex of the triangular wave and provide a sine wave output. Operational amplifier 1902 is provided as a buffer to prevent overload of the sine wave shaping circuit shown in FIG.

The sawtooth generator 1771 illustrated in FIG. 23 is illustrated in more detail in FIG. Signal 17 is a square wave output from voltage controlled oscillator 1762
77 is potentiometer 1931 and resistor 1932
is applied to the inverting input of operational amplifier 1933 via . Signal 1777 is also provided through resistor 1934 to the inverting input of operational amplifier 1935. Signal 1776, which is the triangular wave output from voltage controlled oscillator 1762, is applied via resistor 1937 to the inverting input of operational amplifier 1935. Operational amplifier 1
The non-inverting input of 935 is grounded. Operational amplifier 1
The output of 935 is fed back to the inverting input of operational amplifier 1935 via resistor 1938. Operational amplifier 1
The output from 935 is also provided via resistor 1939 to the inverting input of operational amplifier 1933 and via resistor 1941 to the inverting input of operational amplifier 1942.

The non-inverting input of operational amplifier 1942 is grounded. The output from operational amplifier 1942 is connected to resistor 194.
The inverting input of the operational amplifier 1942 and the operational amplifier 193 are connected through a resistor/diode circuit consisting of 3, 1944 and diodes 1945, 1946.
It is coupled to the inverting input of 3.

The wiper of potentiometer 1948 is resistor 19
49 to the inverting input of operational amplifier 1933. A first terminal of potentiometer 1948 is coupled to +6V power line 1766. The second terminal of potentiometer 1948 is -6V power line 17
67. +6V power line 1766 and -6V
Both power supply lines 1767 are supplied from a reference voltage source 1765 shown in FIG.

The non-inverting input of operational amplifier 1933 is grounded. The output from operational amplifier 1933 is sent as a sawtooth signal 1781 illustrated in FIG.

Amplifier 1955 functions to add the triangular wave and the rectangular wave to generate a summed output. Operational amplifiers 1942 and 1933, which together form a full wave rectifier, are used to generate a sawtooth output signal in response to the summation of the square and triangle waves. Potentiometer 1948 is adjusted to provide symmetry of the sawtooth wave around a zero voltage reference.

The output circuit 1772 shown in FIG.
This is illustrated in more detail in the figure. Sine wave shaper 1
Signal 1779, the sinusoidal output from 769, is applied to the inverting input of operational amplifier 1963 via potentiometer 1961 and resistor 1962.
The non-inverting input of operational amplifier 1963 is grounded.
The output from the operational amplifier 1963 is fed back to the inverting input via a resistance-capacitance circuit composed of a resistor 1964 and a capacitor 1965. Operational amplifier 1
The output from 963 is also provided to switching device 1974 via a resistive circuit comprised of resistors 1967-1973. A plurality of resistive paths from the output of operational amplifier 1963 to switching device 1974 are provided to provide a means for providing different voltage levels as the output from output circuit 1772.

Switching device 1974 is coupled to switching device 1976. Switching device 197
6 is connected directly to output signal line 1783 or to a voltage divider circuit made up of resistors 1977-1979. Output signal 1783 is a sine wave output from output circuit 1772. Again, resistance 1977-1 in conjunction with resistance 1967-1973
A voltage divider circuit consisting of 979 is provided as a device to attenuate the output signal 1783 as required.

The sine wave output from operational amplifier 1963 is also provided as an input to switching devices 1981-1983. Switching device 1981-19
Depending on the position of 83, either four different output signals are provided from output circuit 1772, or four sine waves are provided from output circuit 1772.

The triangular wave signal 1776 is connected to the potentiometer 198
4 and a resistor 1985 to the inverting input of an operational amplifier 1986. The non-inverting input of operational amplifier 1986 is grounded. The output from operational amplifier 1986 is connected to resistor 1987 and capacitor 1 in parallel.
988 to the inverting input of operational amplifier 1986. The output from operational amplifier 1986 is also connected to switching device 1981 and resistor 1989-
It is also applied to a switching device 1996 via a resistor circuit constructed from 1995. The resistance circuit 1989-1995 is the resistance circuit 1967 mentioned above.
- Used in the same way as 1973.

Switching device 1996 is coupled to switching device 1997. Switching device 199
7 is coupled directly to output signal line 1784 or to a voltage divider circuit comprised of resistors 1998-2000. A triangular wave output from output circuit 1772 is provided by signal line 1784. Resistance 199 again working with Resistance 1989-1995
8-2000 is used to attenuate the output signal 1784 as necessary.

Sawtooth wave 1781 is potentiometer 2001
is applied to the inverting input of operational amplifier 2003 via resistor 2002. The non-inverting input of operational amplifier 2003 is grounded. The output from the operational amplifier 2003 is connected to a parallel resistor 2004 and capacitor 2005.
is fed back to the inverting input of operational amplifier 2003 via . The output from operational amplifier 2003 is also connected to switching device 1982 and resistors 2007-201.
It is also applied to the switching device 2014 via a resistor circuit composed of 3. Again, the resistance circuits 2007-2013 are the resistance circuits 1967 described above.
- Used in the same way as 1973.

Switching device 2014 is coupled to switching device 2015. Switching device 201
5 is coupled directly to output signal line 1785 or to a voltage divider circuit comprised of resistors 2017-2019. A voltage divider circuit comprised of resistors 2017-2019 and resistors 2007-2013 is used to attenuate output signal 1785 as needed. The sawtooth wave is output from output circuit 1772 via signal line 1785.

The square wave 1777 is applied to the inverting input of the operational amplifier 2023 via the potentiometer 2021 and the resistor 2022. The non-inverting input of operational amplifier 2023 is grounded. The output from the operational amplifier 2023 is connected to a resistor 2024 and a capacitor 2025 in parallel.
is fed back to the inverting input of operational amplifier 2023 via . The output from operational amplifier 2023 is also connected to switching device 1983 and resistors 2027-203.
It is also applied to the switching device 2034 via a resistor circuit composed of 3. Resistor 2027-
Consists of 2033. The resistor circuit is used in the same manner as the resistor circuits 1967-1973 described above.

Switching device 2034 is coupled to switching device 2035. Switching device 203
5 is coupled directly to output signal line 1786 or to a voltage divider circuit comprised of resistors 2037-2039. A voltage divider circuit comprised of resistors 2037-2039 and resistors 2027-2033 is used to attenuate output signal 1786 as needed. A square wave output from output circuit 1772 is provided by signal line 1786.

The RF transmitter 59 shown in FIG. 2a is shown in more detail in FIG. 30. Illustrated in Figure 2b,
Receiver 106 and transmitter 127 as described herein
The literature applicable to is also applicable to the design of the known elements of transmitter 59 and receiver 68, illustrated in FIG. 2a and shown in more detail in FIGS. 30 and 31, respectively.

Referring to FIG. 30, audio input from operator control display panel 41 is sent to limiter circuit 2561 via signal line 50. Limiter circuit 2561 clips the audio input signal. The audio input signal is sent from the limiter circuit 2561 to the potentiometer 25.
63 to summing junction 2562.
Potentiometer 2563 provides a means to adjust the maximum audio deviation. Summing junction 2562 is a summing amplifier. From summing junction 2562, the audio signal is sent to premodulation low pass filter 2564.

Data or commands from the 6800 microprocessor are sent via signal line 61 to condition circuit 2565 in the form of a non-return-to-zero (NRZ) serial bit stream. The data or command signal is amplified by condition circuit 2565 and centered at ground potential. The ground center signal is then provided to summing junction 2562 via potentiometer 2565. potentiometer 25
66 performs deviation control of data or command signals.
From summing junction 2562, the data or command signal is provided to premodulation low pass filter 2564.

Premodulation low pass filter 2564 is a 5th order Gaussian low pass filter. Since the data rate of the transmitter illustrated in Figure 30 is 6.25 kilobits per second, the optimum -3 db for low pass filter 2564 is set to 4 KHz, which changes the amplitude of the narrowest pulse to the amplitude of the widest pulse. It is possible to make them almost equal. This filter also limits data and voice higher order sidebands and limits the RF spectrum to below 30KHz.

The output signal from premodulation low pass filter 2564 is provided as an input to oscillator 2568. Oscillator 2564 is used to frequency modulate the output signal provided by premodulation low pass filter 2564. The modulated output signal from the oscillator 2568 is transmitted to a frequency tripler 2569 and a frequency tripler 257.
1. Exciter 257 via frequency multiplier 2572
given to 3. The excitation stage 2573 drives the modulation signal approximately
Amplify from 100mW to 1W level and power amplifier 2
574 is excited. Power amplifier 2574 increases the signal level from 1W to a nominal 10W output. The output from power amplifier 2574 is provided through low pass filter 2575 to transmit/receive switch 63 shown in FIG. 2a. Output low pass filter 2575 is comprised of a three stage π-type arrangement and reduces all harmonic components of the output signal to levels below the requirements of FCC standards.

The transmit/receive switch 63 is in normal receive mode. The transmit/receive switch 63 is switched to the transmit mode in response to a signal 2576 representing activation of the transmit pushbutton switch on the handset used for voice communications. The transmit/receive switch 63 is also switched to transmit mode by a transmit command signal 2577 provided by the 6800 microprocessor. From the transmit/receive switch, the output from the transmitter shown in FIG. 30 is provided to the antenna 64 shown in FIG. 2a, and then to the RTU shown in FIG. 2b.

The specifications of the transmitter 59 illustrated in FIGS. 2a and 30 are as follows.

CRS transmitter (a) Frequency 216 to 220MHz, crystal control (b) Frequency stability = ±. 0005% (-30℃ to +70
(c) Power output = 8 to 10 watts nominal (d) Spurious emission suppression = 60 db or more (e) Audio modulation (A) Carbon/button handset, carbon microphone or high-Z
Dynamic or ceramic microphone (B) Adjustable clip level (deviation control) (C) Adjustable maximum modulation control (D) Carbon microphone bias current (5 mA) (E) High-Z microphone preamplifier (gain 2 to 100)
(F) Main oscillator direct FM (G) Deviation = max. 5KHz (f) Data modulation (A) Input = T ² L (B) Code = NRZ (C) Data rate = 6.25KB/S (D ) Varicap bias circuit (adjustable) (E) Adjustable data deviation control (up to 4
(9KHz) (F) Five-pole Betzell function preamplifier filter (G) Data-to-voice modulation circuit The RF receiver illustrated in FIG. 2a is illustrated in more detail in FIG. 31. Referring to Figure 31,
The received signal from the RTU is applied from the antenna 64 to the RF amplifier 2581 via the transmit/receive switch 63. RF amplifier 2581 and RF amplifier 258
2 has two stages before introducing the received signal to the first mixer.
Perform RF amplification. The first mixer 2583 is also provided with an input signal from an oscillator 2584 and a buffer 2585 having a frequency 10.7 MHz above the frequency of the received signal. The first mixer 2583 therefore provides an intermediate frequency (IF) signal, one component of which has a frequency of 10.7 MHz. The output signal from the first mixer 2583 is amplified by an IF amplifier 2586 and provided to a 10.7 MHz bandpass filter 2588. band filter 25
88 has a width of 240KHz centered on 10.7MHz.
The output signal from the 10.7 MHz bandpass filter 2588 is applied to an IF amplifier 2589, which forms the first stage of the data detection section of the receiver, and to a second mixer 2591, which forms the first stage of the audio detection circuit of the RF receiver. is also given.

The signal going to the data detection circuit is the IF amplifier 258
9 and provided to a discriminator 2592. Discriminator 2592 is a standard discrimination conversion circuit. The output signal from the discriminator 2592 is sent to the data decoder 2 via a low-pass filter and buffer circuit 2593.
594. The low-pass filter and buffer circuit 2593 filters harmonic components, and the discriminator 2
592 to data decoder 2594. Data decoder 2594 generates a local data clock with a frequency of 100KHz and is non-return to zero (NRZ).
Gives a serial data stream as output. Both the NRZ data and the clock signal are routed to signal line 69 via signal line 2a.
The data formatter 71 shown in FIG.

The output signal from the 10.7MHz band filter 2588 that is applied to the second mixer 2591 is
591 and a signal having a frequency of 10.245 MHz. The 10.245MHz signal is provided by oscillator 2596. From 10.7MHz band filter 2588
10.7MHz signal and 10.245MHz from oscillator 2596
The signal gives a 455KHz IF signal. 2nd mixer 2
The 455KHz signal from 591 is applied to an IF amplifier 2598 via a 455KHz bandpass filter 2597. The amplified signal provided by IF amplifier 2598 is preferably a phase lock loop detector. Provided to FM detector 2599. The audio signal from the FM detector 2599 is sent to the audio amplifier 2600.
a speaker 260, which may be a handset;
given to 1. The speaker 2601 or handset is connected to the operator control and display panel 4 shown in FIG. 2a.
1. The signal from audio amplifier 2600 is provided by signal line 60 to operator control and display panel 41 as shown in FIG. 2a.

RF receiver 68 illustrated in FIGS. 2a and 31
The specifications are as follows.

CRS receiver (a) Frequency = 216 to 220MHz, crystal control (b) Center frequency stability = ±. 001% (-30 to +
(70℃) (c) Sensitivity (data) = -102dbm at 10 ^-6 BER (bit error rate) (d) Sensitivity (audio) = -115dbm (S+N/N ratio of 10db or more, 8KHz bias, 1KHz, modulation) (e) Modulation acceptance Audio: 0.2 to 4KHz (-3db) Maximum deviation of 15KHz (nominal = maximum 5KHz) Data: 100KB/S ± 5% (2-phase coding) PCM/FM (f) Audio power output = 5 Watts (4 ohm load) (g) Audio output to handset earphone = 400m
VRMS (adjustable) (h) Data decoding (A) Matched filter, maximum depth detection scheme (sample and hold, compare and dump circuits) (B) Data clock recovery circuit (C) Data ambiguity determination circuit (50mS determination) (D) T ² L data output (100 KB/S, NRZ) (E) T ² L clock output (100 KHz, 0° phase) Computer device 51 shown in Figure 2a
and computer device 74 are illustrated in FIG. 2a.
Forms the core of CRS. computer device 5
1 is computer-to-computer as mentioned above.
Computer device 7 via interface 58
interfaced to 4.

Computer device 51 is preferably a 6800 microprocessor device manufactured by Motorola Semiconductor. Computer unit 74 is a 2900 microprocessor unit manufactured by Advanced Micro Devices. The 2900 microprocessor device features an extremely fast cycle time of 225 nanoseconds. The 2900 microprocessor device is used to reduce the load on the 6800 microprocessor device, which is the main microprocessor. The 2900 microprocessor device is also used because of its fast cycle time, which allows it to process the data rates that must be used in commercial seismic equipment. The 6800 microprocessor device cannot handle the data rates used in modern seismic surveys.

As previously mentioned, the 6800 microprocessor device is a well-documented device. The 2900 microprocessor device represented by computer device 74 shown in FIG. 2a is illustrated in more detail in FIG. Referring to FIG. 32, microprogram sequencer 2301 sends the address of the next instruction to be executed to microcontrol program memory 2302. The address of the next instruction to be executed is selected from one of the following four.

(a) Microprogram for continuous addressing
Sequencer internal program counter (b) Internal push stack for subroutine and interrupt address handling (c) Internal address register loaded directly from interrupt logic (d) Microprogram load directly from microinstruction output latch 2304 Sequencer 2301 is a 2909 microprogram sequencer manufactured by Advance Micro Devices. Microprogram sequencer 2301 is a 4-bit wide "next address" controller. The 2900 data processor is a 2909 microprogram
Sequencer 2301 is used to generate a 12-bit microprogram memory address that is sent to the microcontrol program memory. The 12-bit address from the microprogram sequencer represents the next instruction to be executed by the 2900 microprocessor device.

Interrupt logic 2305 interrupts microprogram sequencer 2301 upon receiving an external interrupt condition signal.
Used to stop. Interrupt logic 230
5 de-energizes the microprogram sequencer 2301 output driver and retains the current address information contained in the microprogram sequencer just before the interrupt. When the external interrupt is cleared, the interrupt line provided from interrupt logic 2305 to microprogram sequencer 2301 is cleared;
The main program is then allowed to continue.
Processor Bus Interrupt No. 1 and Processor Bus Interrupt No. 2 provide a means for passing external interrupts, such as device data ready signals, to interrupt logic 2305. The vector address provided from interrupt logic 2305 to microprogram sequencer 2301 provides for interrupt processing by microprogram sequencer 2301.

Microcontrol program memory 2302
There are 32 programmable read-only memories (PROMs) covering 4K. Microcontrol program memory 2302 is the core of the 2900 microprocessor device. Microcontrol program memory 2302 contains object code that controls all of the 2900 microprocessor functions. At the beginning of each microprocessor cycle, a new address is sent to the microprogram sequencer 23.
01 to the microcontroller program memory. This address from the microprogram sequencer provides access to a specific location in microcontrol program memory 2302 that outputs the specific microinstruction word to microinstruction output latch 2304 to be executed in the next instruction cycle. The microinstruction word provided from microcontrol program memory 2302 to microinstruction output latch 2304 is a 32-bit data word.

Microinstruction output latch 2304 is a 32-bit wide data latch that is loaded on the rising edge of the system clock (SCLK). A rising edge on the device clock indicates the start of each microprocessor cycle. Microinstruction Output Latch 2304 is Loaded During a particular microprocessor cycle, microprocessor output latch 2304 is loaded with object code to be executed. All microprocessor operations are performed using objects loaded into microinstruction output latch 2304 at the beginning of a microprocessor cycle.
Specified by code.

System clock generator 2307 provides a 4.45 Hz clock signal to the 2900 microprocessor system shown in FIG. Device clock generator 2307
is required if a slower clock speed is required to allow the use of slower memory elements.
A 2.22MHz clock signal can also be supplied. The 4.45 MHz device clock signal provides the basic timing for the 2900 microprocessor device illustrated in FIG.

A 32-bit instruction from microinstruction output latch 2304 is provided to multiple data sources and data destinations. Internal bus selection logic 2308 is used to decode destination or departure information from the 32-bit instruction provided by microinstruction output latch 2304. After decoding the origin and destination information, internal bus selection logic 2308 provides activation signals to the various origins and destinations of the instructions to be executed. As shown in FIG. 32, four destination enable signals S0-S3 are provided from internal bus selection logic 2308, and eight destination enable signals DES0-DES are provided.
7 is given.

Conditional branch logic 2311 is provided to detect the state of a selected input/output device or the result of an arithmetic/logic unit 2312 operation and change the next address selection of microprogram sequencer 2301 as necessary. Conditional branch logic 2311 selects one of 16 possible branch conditions on the input to microprogram sequencer 2301 as a branch condition signal.
Select one.

Emission buffer 2314 is used to place the desired data pattern on the 2900 microprocessor internal data bus. Microinstruction output latch 2304
The 32-bit instructions from 2314 can be programmed to place a desired data pattern on the 2900 microprocessor's internal data bus by energizing the output drivers of emission buffer 2314. This allows object code from microinstruction output latch 2304 direct access to the internal data bus. This allows arbitrary data words, constants, and mask bit patterns to be provided directly from program statements.

Working memory memory 2315 includes arithmetic/logic unit 2
64 words x 8 bits random access memory that serves as an extension of the 312 register storage capacity.
It's memory. Working storage memory 2315 is used as scratch storage for arithmetic/logic unit 2312 data operations. Arithmetic/Logic Unit 2312
is constructed from two 2901 4-bit bipolar microprocessor slices to form an 8-bit arithmetic/logic unit. . 2901 4-bit bipolar microprocessor slice
This is device manufacturing. The primary function of the arithmetic/logic unit 2312 is to handle data, input/output address information, memory address information, and perform arithmetic operations. Arithmetic/logic unit 2312 is connected to the upper bus
address register 2317, lower bus address register 2318, working memory memory 231
5. Data can be provided to the data bus transceiver 2321. Arithmetic/logic units use internal registers for temporary storage.

Upper bus address register 2317 and lower bus address register 2318 manage latches and buffers for all devices connected to the 2900 data processor bus. Upper bus address register 2317 and lower bus address register 2318 are both arithmetic/logic unit 23.
12 from the 2900 microprocessor internal bus.

Control bus register 2322 is loaded directly from the 32-bit instruction provided by microinstruction output latch 2304. Control bus register 232
2 provides a synchronized external control bus signal source. The control signals used are as follows.

VMA-2900 external bus legal memory address provides synchronization of STROBE-2900 external bus read operations.

DM defines read operations on the R/W-2900 microprocessor bus - when active directs input/output operations to data memory (which requires a 20-bit address). When DM is not active, only the lower 8 bits of the address (on the external bus) are valid. This allows the peripheral to decode only the bottom 8 bits for addressing.

Data bus transceiver 2321 consists of two 4-bit 2904 transceivers manufactured by Advanced Micro Devices. 2904 transceiver chips are connected in parallel to form an 8-bit data bus transceiver. Data is written from the 2900 microprocessor internal data bus to data bus transceiver 2321 on the rising edge of the device clock. This data is asserted on the 2900 microprocessor external bus by the Write signal going low. Data is on external bus
External 2900 between Read signal and Strobe signal match
Written from the microprocessor bus to data bus transceiver 2321.

The interrupt logic 2305 illustrated in FIG.
The figures are shown in more detail. The first 2900 microprocessor bus interrupt is for encoder 2323.
Coupled to I1 input. A second 2900 microprocessor bus interrupt is coupled to the I0 input of encoder 2323. The I2-I7 inputs of encoder 2323 are coupled to the high state of +5V power supply 2324. The A0-A2 address output from encoder 2323 is provided as a vector address illustrated in FIG. The group select output from encoder 2323 is sent as one input to NOR gate 2326. The output of NOR gate 2326 is coupled to the D input of flip-flop 2327. The device clock signal from device clock generator 2307, shown in FIG. 32, is sent to the clock input of flip-flop 2327. The set input of flip-flop 2327 is +5V power supply 232
Combined with a high state of 8. flipflop 23
The reset input of 27 is also coupled to the high state of +5V power supply 2329. The Q output from flip-flop 2327 is coupled to the D input of flip-flop 2331. The device clock signal is sent to the clock input of flip-flop 2331. The set input of flip-flop 2331 is +5V power supply 2.
332 high state. The reset input of flip-flop 2331 is coupled to the high state of +5V power supply 2334. flipflop 2331
The Q output from the microprogram in Figure 32 is
Sequencer address is sent to origin selection multiplexer 2301. flipflop 2331
The Q output from is shown as part of the vector address in FIG.

The output from flip-flop 2327 is coupled to the reset input of flip-flop 2335 and is also provided as the first input to AND gate 2336. The SET and D inputs of flip-flop 2335 are coupled to the high state of +5V power supply 2330. It is sent as an enable signal and a pull-up signal as well as an input to NOR gate 2338. The output of NOR gate 2338 is provided as the first input to NAND gate 2339. The interrupt activation signal is
Provided as the second input to NAND gate 2339. The output of NAND gate 2339 is provided as the first input to NOR gate 2341. The device clock signal is the second to NOR gate 2341.
given as input. The output of NOR gate 2341 is coupled to the clock input of flip-flop 2335.

The output from flip-flop 2335 is
It is coupled as a second input to NOR gate 2326 and is also provided as a second input to AND gate 2336. The output of AND gate 2336 is the interrupt signal illustrated in FIG.

The conditional branch logic 2311 illustrated in FIG. 32 is illustrated in more detail in FIG. The status line is routed to the data input of data latch 2344. The device clock signal generated by device clock generator 2307, shown in FIG. 55, is applied to the clock input of data latch 2344. The data output from data latch 2344 is coupled to a 1-to-16 decoder 2345. Arithmetic/Logic Unit 2
312 status output is data latch 2347,23
48 data inputs. The control bus logic signal is sent to the S1 select input of decoder 2349.
The interrupt enable signal is sent to the S0 selection input of decoder 2349. The device clock is sent to the enable input of decoder 2349. The Q3 output of decoder 2349 is coupled to the clock input of data latch 2347. The Q2 output of decoder 2349 is coupled to the clock input of data latch 2348. The data output of data latch 2347 is 1
Coupled as an input to pair 16 decoder 2345.
The data output of data latch 2348 is also 1:16
Coupled to the data input of decoder 2345. 1
Pair 16 decoder 2345 selects one of the data inputs sent as the branch condition signal illustrated in FIG. The control bus logic signals and interrupt enable signals forming part of the instruction word from microinstruction output latch 2304 shown in FIG. 32 are used to clock data latch 2347 and data latch 2348. When the interrupt enable signal is low and the control bus logic signal is high, data latch 2
348 is clocked. When the control bus logic signal is high and interrupt enable is high, data latch 2
347 is clocked. When the control bus logic is low during all conditional branch statements, neither data latch 2347 nor data latch 2348 is changed. These are the same set of arithmetic/
Allows execution of a series of conditional statements on logical unit status output.

The 2900 microprocessor reads data from data formatter 71 when data is available. This data is checked for errors and data words containing errors are flagged and stored in memory. If there is an error, a retransmission from one of the RTUs occurs and the retransmitted data is used to replace the erroneous data word.

Once valid data is stored in memory, the data is transferred to magnetic tape device 79. This transfer takes place under the control of the 6800 microprocessor 51. When providing data to data display 93, the 2900 microprocessor reads the data from memory, filters the data, and adjusts the gain of the data before providing the data to data display 91.

As previously mentioned, the microcontrol program memory 2302 illustrated in FIG. 32 is a programmable read only memory (PROM). PROM is non-volatile memory, which means that even if power to the memory is lost, the program it contains is not lost. Therefore, the program contained in microcontrol program memory 2302 is not lost when power is removed from the central recording pole illustrated in FIG. 2a. However, a disadvantage of using programmable read-only memory is that the program must be burned into memory, and once the program is burned into memory, it is very difficult to change the program. In some cases, the program is not changeable and the programmable read-only memory must be jettisoned and a new programmable read-only memory must be programmed to change the program. This becomes extremely costly when using devices such as the 2900 microprocessor.

The device is provided with a method to avoid the problem of reprogramming the programmable read-only memory. This method also allows the well-documented 6800 microprocessor device to be used to develop programs for use on the 2900 microprocessor.

Develop and test programs for use on the 2900 microprocessor using random access memory. Random access memory and its associated circuitry are called programmable read only memory (PROM) buggy random access memory (RAM). The PROM bug RAM is not a permanent part of the central storage station shown in Figure 2a, but provides diagnostic and fault-finding capabilities for the 2900 microprocessor. The location of the PROM bug RAM when used in the central recording station is shown in Figure 35. PROM Baku
RAM 2351 is connected to the 6800 microprocessor bus and is also connected to the 2900 microprocessor 74 bus.
Connected to J1 and J2 inputs. The J1 and J2 inputs of the 2900 microprocessor are illustrated in detail in FIG. As shown in FIG. 32, the PROM bug RAM can apply a reset signal to the microprogram sequencer 2301. The reset signal is used to initiate 2900 microprocessor program execution and the microprogram sequencer.
PROM backram 2351 can apply a stop signal to the microprogram sequencer via the J1 input. The stop signal forces the microprogram sequencer 2301 to enter high impedance (tristate). The inhibit signal is applied to microinstruction output latch 2304 via the J1 input. The prohibition signal is the microinstruction output latch 23
04 into high impedance (tristate) mode. PROM bug RAM 2351 is connected to microprogram sequencer 2301 by J1 input.
to microcontrol program memory 2302
Has a 12-bit address direct connection.
PORM bug RAM2351 is 2900 by J1 input
It is also connected to the microprocessor's internal bus.
Finally, the RPOM backram 2351 receives the 32
Coupled to bit output.

PROM bug RAM 2351 illustrated in Figure 35
is illustrated in more detail in FIG. Decode logic 2353 decodes the address from the 6800 microprocessor and provides decoded address information to peripheral interface adapter 2354. Peripheral interface adapter 235
4 is a 6820 Peripheral Interface Adapter (PIA) manufactured by Motorola Semiconductor. Peripheral Interface Adapter 2354 is a random
Controls addresses to access memory 2356. Peripheral interface adapter 2354 also provides control signals to random access memory 2356 and address input buffer 2357.
Peripheral interface adapter 2354 also provides an enable signal to tristate buffer 2358.

Random access memory 2356 is of type 354 manufactured by Fair-Child Semiconductor.
32 1K x 1 bit pieces, preferably 2.
Preferably, it is a 1K x 32 bit MOS memory composed of memory elements. When random access memory 2356 is used, the 32nd
The illustrated device clock generator 2307 is automatically switched to run at device clock/2 speed. Random access memory 2356 is used to store the program being tested.

32-bit data output with random access
From memory 2356 it is sent to random access memory output control latch 2359 and tristate buffer 2358. Tristate buffer 2358 is random access memory 2356
Output and Peripheral Interface Adapter 2354
give a separation between Tristate buffer 2358 is in a de-energized mode when an address is being sent from peripheral interface adapter 2354 to random access memory 2356 so that the random access memory output data line is connected to random access memory 2356. to prevent contention for control of the input data line to the Conversely, when peripheral interface adapter 2354 is programmed to allow data to be read from random access memory 2356, tristate buffer 2358
random access memory 2356
Output data is from peripheral interface adapter 2
354 to allow it to be read by a 6800 microprocessor.

Random access memory output control latch 2
359 receives data from random access memory 2356 and sends the data through connector J2.
2900 microprocessor instruction bus. Instructions are thus transferred from random access memory 2356 to 2900 by the 2900 microprocessor instruction bus.
given to the microprocessor. Therefore, the 32nd
Microcontrol program memory 2 illustrated in the figure
302 is bypassed, allowing random access memory 2356 to replace microcontrol program memory 2302.

Address input buffer 2357 is used by microprogram sequencer 230 during programming by the 6800 microprocessor illustrated in FIG.
This is a simple buffer that allows tristatement of the address input from 1. When you want to test the program in the random access memory 2356 for the 2900 microprocessor, use the buffer 235.
Activating 7 puts the 2900 microprocessor under control of random access memory 2356.

The decode logic 2353 illustrated in FIG. 36 is illustrated in more detail in FIG. Peripheral interface adapter 235 illustrated in FIG.
Three 6820 peripheral interface adapters are utilized to form 4. Referring to Figure 37, D0-D from the 6800 microprocessor
7 data line is peripheral interface adapter 2
361-2363 D0-D7 data lines. The A15 address line from the 6800 microprocessor is connected to buffer 23 via inverter 2364.
Sent to 66. from 6800 microprocessor
The A14-A8 address lines are sent directly as inputs to buffer 2366. All output lines from open collector buffer 2366 are coupled to the high state of +5V power supply 2367 through pull-up resistor 2368. All output lines from buffer 2366 are also connected to peripheral interface adapter 2361.
-2363 chip select 0 input (CS0).

The A4-A7 address lines from the 6800 microprocessor are provided as inputs to NAND gate 2369. The output from NAND gate 2369 is connected to peripheral interface adapter 2361-23.
63 chip select 1 input (CS1).

The A3 address line from the 6800 microprocessor is provided directly as the first input to AND gate 2371. A3 address line is also inverter 23
It is also provided as the first input to AND gate 2373 and AND gate 2374 via 72. 6800
The A2 address line from the microprocessor is also provided through inverter 2375 as a second input to AND gate 2373 and as a second input to AND gate 2371. The legal memory address (VMA) from the 6800 microprocessor is
It is provided directly as the third input to AND gates 2371, 2373, and 2374. AND gate 2
The output from 373 is coupled to the chip select 2 input (2) of peripheral interface adapter 2361. The output from AND gate 2374 is coupled to the chip select 2 input (2) of peripheral interface adapter 2362. AND gate 2
The output from 371 is coupled to the chip select 2 input (2) of peripheral interface adapter 2363.

The A1 address line from the 6800 microprocessor is connected to the peripheral interface adapter 2361-
2363's register select 1 input (RS1). The A0 address line from the 6800 microprocessor is connected to peripheral interface adapter 2361.
-2363 register select 0 input (RS0). The read/write (R/) signal from the 6800 microprocessor is sent to the read/write input of peripheral interface adapters 2361-2363. The φ2 clock from the 6800 microprocessor is connected to the peripheral interface adapter 2361-
2363's energization input. The reset input from the 6800 microprocessor is coupled to the reset input of peripheral interface adapters 2361-2363.

Illustrated as microcontrol program memory 2302. Random access memory 235 replaces programmable read-only memory
Reference should be made to FIGS. 32 and 36 for a description of the following operating procedure used in the use of 6.
While programming random access memory, the 2900 microprocessor is powered down. Once programming is complete, the 6800 interface to random access memory is de-energized and the 2900 microprocessor is activated, as if it were the microcontroller program memory 230.
2. Control random access memory as if it were 2. This allows you to run all of your 2900 microprocessor programs in a well-documented and maintained software/hardware area (6800
It becomes possible to write and operate a microprocessor device. Random access memory 2356 can be used to load and run diagnostics or programs one after another. In fact, entire instruction sets and programs can be changed in seconds. This significantly reduces the expense associated with changing programs programmed into programmable read-only memory. This also greatly simplifies the task of developing programs for 2900 microprocessor devices.

To use random access memory 2356, the reset, inhibit, and stop signals are first set to power down the 2900 microprocessor. In particular, microcontrol program memory 2302 and microinstruction output latch 2304 are both deenergized by setting them to a high impedance state.
Address input buffer 2357 is also set to a high impedance state, allowing the address of random access memory 2356 to be controlled by peripheral interface adapter 2354. Therefore, random access memory 2
The 356 is completely controlled by a 6800 microprocessor device.

Random access memory 2356 stores random access memory from a 6800 microprocessor device.
It is programmed by sending addresses and writing data to memory 2356. An output depower signal sent from peripheral interface adapter 2354 to tristate buffer 2358 is first set to depower tristate buffer 2358, thus discharging random access memory 235.
Return data from 6 is prohibited. Addresses and data are then provided to random access memory 2356 from the 6800 microprocessor device. Read/write inputs to random access memory 2356 stroke addresses and data into random access memory. The entire random access memory is programmed this way.

When data is desired to be read from random access memory 2356 by the 6800 microprocessor, the output de-energization sent from peripheral interface adapter 2354 to tristate buffer 2358 is reset and the 32 Allows the bit output to be sent back to peripheral interface adapter 2354 via tristate buffer 2358. Data is read from random access memory 2356 via peripheral interface adapter 2354 by the 6800 microprocessor.

The program is in random access memory 23
After testing the program using the 6800 microprocessor, control is transferred to the 2900 microprocessor to test the program. The 2900 microprocessor utilizes random access memory 2356 as well as microcontrol program memory 2302 which is powered down when random access memory 2356 is connected. When it is desired to transfer control to the 2900 microprocessor, tristate buffer 2358 is deenergized to inhibit the transfer of data from random access memory 2356 to peripheral interface adapter 2354. Peripheral interface adapter 2354 is programmed to specify address and data lines as inputs. This tristates the peripheral interface adapter and therefore peripheral interface adapter 23
This is equivalent to deenergizing 54. The stop signal to the 2900 microprocessor is reset, which removes the tristate condition of the microprogram sequencer 2301. This also energizes address input buffer 2357. Control is now transferred to the 2900 microprocessor, which stores the microinstruction words in random access memory 235 under the control of the 2900 microprogram sequencer 2301.
It means that it comes out from 6. Releasing the reset allows program execution to proceed.

When necessary, program changes or tests can be performed on the 6800 microprocessor device by applying a stop and reset. 6800 microprocessor device has random access memory 23
Equipped with a high speed data reader input and CRT output to facilitate testing and programming of the 56. Therefore, microcontrol program memory 2302
Random access memory 2356 allows an easy method of testing the 2900 microprocessor's program before burning the program to the 2900 microprocessor. This greatly facilitates programming the 2900 microprocessor and reduces the cost of re-burning programs in microcontrol program memory 2302 to change programs.

The computer-to-computer interface 58 illustrated in FIG. 2a is illustrated in more detail in FIG. 38. As previously mentioned, the computer-to-computer interface 58 illustrated in FIG. 2a is the circuitry that enables communication between the 6800 and 2900 microprocessors. The computer-to-computer interface 58 determines when either computer is ready to send data to the other computer.
Provides the necessary interrupts to notify the 6800 and 2900 microprocessors. Basically,
Address and command lines from the 6800 and 2900 microprocessors are used to control the operation of the computer-to-computer interface 58. The data lines from the 6800 and 2900 microprocessors are used to transfer data between the 6800 and 2900 microprocessors. 6800 microprocessor and 2900
Address and command lines from the microprocessor also generate signals that indicate when either computer can write data to the other and when each computer is ready to receive data. It is also used for

Referring to FIG. 38, the A7 address line from the 6800 microprocessor is sent as the first input to NOR gate 2481. A6 address line from 6800 microprocessor is NOR gate 2481
is sent as the second input to.

The output from NOR gate 2481 is provided as the first input to NAND gate 2482. 6800
The A5 address line from the microprocessor is
Provided as the second input to NAND gate 2482. The A4 address line from the 6800 microprocessor is provided as the third input to NAND gate 2482 via inverter 2483.
Input/output (I/O) from the 6800 microprocessor
The line is coupled as the fourth input to NAND gate 2482.

The output from NAND gate 2482 is provided as the first input to NAND gate 2484.
The A3 address line from the 6800 microprocessor passes through inverter 2485 to NAND gate 24.
84 as the second input. The output from NAND gate 2484 is provided as the first input to NAND gate 2487 through inverter 2486 and is also provided to the chip select 1 (CS1) input of peripheral interface adapter 2488.

The φ2 clock from the 6800 microprocessor is connected to the NAND gate 248 via the driver 2489.
7 and is also provided to the activation input of peripheral interface adapter 2488. The reset line from the 6800 microprocessor is routed through driver 2489 to the reset input of peripheral interface adapter 2488. The A1 address line from the 6800 microprocessor is routed through driver 2489 to register select 1 of peripheral interface adapter 2488.
(RS1) sent to input. The A2 address line from the 6800 microprocessor is routed through driver 2489 to the chip select 0 (CS0) input of peripheral interface adapter 2488 and is also provided as the third input to NAND gate 2487.
The A0 address line from the 6800 microprocessor is routed through driver 2489 to register select 0 (RSO) of peripheral interface adapter 2488.
Sent to input. The read/write (R/W) lines from the 6800 microprocessor are routed through driver 2489 to the read/write input of peripheral interface adapter 2488 and to NAND gate 24.
It is also provided as the fourth input to 87.

The output from the NAND gate is the driver 2491
It is given as an energizing signal to the E2 energizing input of.
The output from NAND gate 2487 is also provided through inverter 2492 to the E1 input of driver 2491 and as an enable input to the E1 enable input of driver 2493. driver 2493
E2 energization input is grounded.

The D0-D7 data lines from the 6800 microprocessor are coupled to the input of driver 2493 and also to the output of driver 2491. The output of driver 2493, which corresponds to the input to which the D0-D7 data lines from the 6800 microprocessor are coupled, is connected to peripheral interface adapter 2488.
is coupled to the D0-D7 data terminals of The D0-D7 data inputs of peripheral interface adapter 2488 are also provided to the input side of driver 2491. The interrupt lines from the 6800 microprocessor are routed to the Interrupt Request A (IRQA) and Interrupt Request B (IRQB) inputs of the peripheral interface adapter 2488.

The valid memory address (VMA) line from the 2900 microprocessor is coupled through inverter 2495 as the first input to NAND gate 2496. The DM line from the 2900 microprocessor is coupled as a second input to NAND gate 2496. A0− from 2900 microprocessor
The A7 address line is the 3rd line to NAND gate 2496.
~ given as the 10th input. NAND gate 2
The 11th, 12th, and 13th inputs of 496 are coupled through resistor 2498 to +5V power supply 2497. NAND
The output of gate 2496 is provided as the first input to NOR gate 2499. The strobe (STRB) line from the 2900 microprocessor is provided as a second input to NOR gate 2499.
The output of NOR gate 2499 is NAND gate 25
01 and is sent as the first input to NAND gate 2502. The read/write line from the 2900 microprocessor is provided directly as a second input to NAND gate 2502 and also provided as a second input to NAND gate 2501 via inverter 2503.

The output from NAND gate 2501 is low when data can be written from the 2900 microprocessor to the 6800 microprocessor.
The output from NAND gate 2501 is sent to the clock input of flip-flop 2503.
The output from NAND gate 2501 is also sent to the input of driver 2504, indicating that the 2900 microprocessor is ready to send data.
The output from NAND gate 2502 goes low when data can be read from the 6800 microprocessor to the 2900 microprocessor. The output from NAND gate 2502 is sent as the enable input to driver 2504 and is also sent to the input side of driver 2504 as an indication that the 2900 satellite microprocessor is cleared to receive data.

The D0-D7 data lines from the 6800 microprocessor are sent to the input of driver 2504 and also to the D input of flip-flop 2503. The clear input of flip-flop 2503 is coupled to +5V power supply 2505. The Q output from flip-flop 2503 is connected to the peripheral interface.
Coupled to adapter 2488's PA0-PA7 peripheral data lines.

The PB0-PB7 peripheral data lines from peripheral interface adapter 2488 are coupled to the input side of driver 2504. The CB2 peripheral control line from peripheral interface adapter 2488 is coupled to the input side of driver 2504 via inverter 2506. Peripheral interface adapter 2
The CB2 control line from the 488 is used to indicate to the 2900 microprocessor that data is available for transmission from the 6800 microprocessor to the 2900 microprocessor. The CA2 peripheral control line from peripheral interface adapter 2488 is coupled to the input side of driver 2504 via inverter 2507. The CA2 peripheral control line is used to indicate to the 2900 microprocessor that the 6800 microprocessor is cleared to receive data.

6800 microprocessor data ready signal and
The 6800 transmit clear signal is sent to the 2900 microprocessor via driver 2504. 2900 data preparation signal and 2900 transmission clear signal are driver 2
504 as an input to driver 2493. From the driver 2493, the 2900 data preparation signal and the 2900 transmission clear signal are sent to the peripheral interface adapter 2488. The 2900 data ready signal is sent to the CA1 interrupt input, while the 2900 clear to send signal is sent to the CB1 interrupt input.

Peripheral interface adapter 2448 provides the computer-to-computer interface illustrated in Figure 2a.
It forms the core of the interface 58. Data is sent from the 2900 microprocessor to the PA0-PA7 peripheral data lines of the peripheral interface adapter 2488. This data is connected to the 6800 microprocessor's D0-D7 data lines, which are coupled to the peripheral interface adapter 2488's D0-D7 data lines.
The D7 data line is sent from the peripheral interface adapter 2488 to the 6800 microprocessor. Similarly, from a 6800 microprocessor
The D0-D7 data lines are available to send data to peripheral interface adapter 2488 via peripheral interface adapter 2488's D0-D7 data inputs. Data from the 6800 microprocessor is transferred to the 2900 by the PB0-PB7 peripheral data lines of the peripheral interface adapter 2488.
Sent to microprocessor.

Address and command lines from the 2900 microprocessor are used to generate a write signal output from NAND gate 2501 and a read signal output from NAND gate 2502. Flip-flop 2503 using write signal 2501
clocks and transfers data from the 2900 microprocessor to the peripheral interface adapter 2488.
Send to PA0-PA7 peripheral data lines. The write signal from NAND gate 2501 is also used to provide a 2900 data ready signal indicating that data can be written from the 2900 microprocessor to the 6800 microprocessor. The 2900 ready signal is provided to the CA1 interrupt of peripheral interface adapter 2488 via driver 2504 and driver 2493. Peripheral interface adapter 2
488 is the peripheral interface adapter 248
The interrupt request (IRQ) A and interrupt request (IRQ) B lines of 8 indicate that data can be written from the 2900 microprocessor to the 6800 microprocessor.

Similarly, the read signal from NAND gate 2502 is used to clear the 2900 microprocessor and provide a 2900 transmit clear signal indicating that it can receive data from the 6800 microprocessor.
The clear signal for 2900 transmission is sent from the driver 2504 to the peripheral interface via the driver 2493.
Sent to adapter 2488's CB1 interrupt input. Peripheral interface adapter 2488 receives interrupt request (IRQ) A and interrupt request (IRQ) B output from peripheral interface adapter 2488.
Sends clear signal for 2900 transmission to 6800 microprocessor.

Address and command lines from the 6800 microprocessor are utilized to control the CB2 and CA2 control outputs from the peripheral interface adapter to generate the 6800 data ready signal and the 6800 clear to send signal. The 6800 data ready signal indicates that data from the 6800 microprocessor is ready for transfer to the 2900 microprocessor. The 6800 transmit clear signal indicates that the 6800 microprocessor is cleared to receive data from the 2900 microprocessor. The 6800 data ready signal and the 6800 send clear signal are sent to the 2900 microprocessor via driver 2504.

The command formatter 52 shown in FIG. 2a is shown in more detail in FIG. 39. Command formatter 52 is primarily used to convert commands and data from a 6800 microprocessor, shown as computer 51 in FIG. 2a, from parallel to serial format. Referring to Figure 39, the address from the 6800 microprocessor is decoded. It is sent to block 2051. In response to addresses from the 6800 microprocessor, decode block 2051 sends control and clock signals to counters 2053 and 2054, address registers 2055 and 2056, and command registers 2057 and 2058. Signal 2059 is sent from decoder 2051 to counter 2053 as an activation signal.
Signal 2061 is sent from decoding section 2501 to counter 2054 as an activation signal. signal 20
63 is sent as a clock signal to the clock inputs of address registers 2055 and 2056.
Signal 2062 is command register 2057, 2058
The decoder 2051 sends the signal to the clock input of the decoder 2051.

The D4-D7 data lines from the 6800 microprocessor are loaded into the D1-D4 data inputs of address register 2055 and the D1-D4 data inputs of command register 2057. The D0-D3 data lines from the 6800 microprocessor are in address register 20.
56 D1-D4 data input and command register 205
8 D1-D4 data inputs. The reset line from the 6800 microprocessor is the address
Registers 2055, 2056 and command register 20
57,2058 clear input. Data or commands are loaded into address or command registers in response to a clock signal from decode section 2051. Multiplexer 206 from data or command address register and command register
5-2068. The four outputs from address register 2056 are coupled to the 1C3 data input of multiplexer 2065.
The 3 outputs from address register 2056 are coupled to the 2C3 data inputs of multiplexer 2065. The two outputs from address register 2056 are provided to the 1C3 input of multiplexer 2066. One output of address register 2056 is coupled to the 2C3 input of multiplexer 2066. The four outputs of address register 2055 are coupled to the 1C3 data inputs of multiplexer 2067. The 3 outputs from address register 2055 are coupled to the 2C3 data inputs of multiplexer 2067. from address register 2055
The Q2 output is coupled to the 1C3 input of multiplexer 2068. from address register 2055
The Q1 output is coupled to the 2C3 data input of multiplexer 2068. from command register 2058
The Q4 output is coupled to the 1C2 data input of multiplexer 2065. from command register 2058
The Q3 output is coupled to the 2C2 data input of multiplexer 2065. from command register 2058
The Q2 output is coupled to the 1C2 input of multiplexer 2066. One output from command register 2058 is coupled to the 2C3 data input of multiplexer 2066. The four outputs from command register 2057 are coupled to the 1C2 data input of multiplexer 2067. The 3 data output from command register 2057 is coupled to the 2C2 data input of multiplexer 2067. from command register 2057
The Q2 output is coupled to the 1C2 data input of multiplexer 2068. from command register 2057
The Q1 output is coupled to the 2C2 data input of multiplexer 2068.

ICO of multiplexer 2065-2068,
The IC1, 2CO, 2C1 data inputs are aggregated inputs assembled in the required manner to provide the required address or preamble from the central recording station illustrated in Figure 2a to the remote telemetry equipment illustrated in Figure 2b.

Multiplexers 2065-2068 can output two out of eight input signals. Input ICO
- one of the inputs 2CO-2C3 is selected; one of the inputs 2CO-2C3 is selected; The inputs selected are from counter 2054 to multiplexers 2065-206.
Signals 2071, 2072 sent to the selection inputs of 8
Determined by. In response to signals 2071 and 2072, multiplexers 2065-2068 provide multiple output signals to multiplexer 2073. The Y1 and Y2 outputs from multiplexer 2065 are applied to the D0 and D1 data inputs of multiplexer 2073. from multiplexer 2066
Y1, Y2 output is D2 of multiplexer 2073,
Sent to D3 data input. multiplexer 20
Y1 and Y2 output from 67 is multiplexer 207
3 is given to the D4 and D5 data inputs. The Y1 and Y2 outputs from multiplexer 2068 are applied to the D6 and D7 data inputs of multiplexer 2073.

Multiplexer 2073 provides a single output signal 61, illustrated in Figure 2a. One of the D0-D7 inputs is sequentially applied to the Y2 output of multiplexer 2073 so that the parallel commands or addresses are converted to serial commands or addresses and sent to the remote telemetry device illustrated in Figure 2b. The multiplexer 2073 is controlled. The manner in which the D0-D7 inputs to multiplexer 2073 are provided as output signals is determined by control signals 2075-2077 provided from counter 2053 to the select inputs of multiplexer 2073.

The address from the 6800 microprocessor sent to decode section 2051 determines how data or commands are sent over signal line 61 to RF transmitter 59 shown in FIG. 2a. Addresses from the 6800 microprocessor are loaded into address registers 2055 and 2056 in response to control signal 2063 from decode section 2051. Similarly,
Clock signal 2062 from decoding section 2051
The command is sent to the command registers 2057 and 205 in response to
8. The address or command is then sent to multiplexers 2065-2068, and the manner in which the address or command is sent from multiplexer 2065-2068 to multiplexer 2073 is controlled by counter 2054 in response to control signal 2061 from decoder 2051. Similarly, if an address or command is sent to multiplexer 2073
The method sent from the decoder 2051 is also controlled by the counter 2053 in response to the control signal 2059 from the decoder 2051. Thus, the 6800 microprocessor not only provides addresses and commands to the command formatter 52 shown in FIG. 2a, but also controls the manner in which addresses or commands are provided from the command formatter 52 shown in FIG. 2a.

The decoding section 2051 shown in FIG.
This is illustrated in more detail in Figure 0. The I/O lines from the 6800 microprocessor along with the A1-A7 address lines from the 6800 microprocessor are provided as inputs to NAND gate 2081. A7 address line is provided via inverter 2082,
On the other hand, the A6 address line is applied via an inverter 2083. The output from NAND gate 2081 is sent via inverter 2084 as an input to NAND gates 2086-2088.
The A0 address line from the 6800 microprocessor is connected to NAND gate 20 via inverter 2089.
86 and also via inverter 2089 and inverter 2091 to NAND gate 2087
It is also given to The R/ line from the 6800 microprocessor is connected to NAND via inverter 2092.
It is sent to gate 2087 and NAND gate 2086. The R/ line from the 6800 microprocessor is also sent to NAND gate 2088 via inverter 2092 and inverter 2093.
The .phi.2 clock from the 6800 microprocessor is provided as an input to NAND gates 2086-2088 through inverters 2094 and 2095, and as part of signal 2061 shown in FIG. The output from NAND gate 2088 is the second signal 2061 shown in FIG.
constitutes the part of The output from NAND gate 2087 is provided as both signal 2059 and signal 2062 illustrated in FIG. The output from NAND gate 2086 is provided as output signal 2063 shown in FIG.

Data formatter 71 illustrated in FIG. 2a
is illustrated in more detail in FIG. Referring to Figure 41, data is provided from the RF receiver 68 on signal line 69 as shown in Figure 2a. Data is sent from RF receiver 68 to serial-to-parallel converter 2101 and parity count circuit 2102. The data is transmitted in 20 bit blocks from the remote telemeter device shown in Figure 2b. Parity counter circuit 2102 maintains a count of the number of ones in the 20-bit block and outputs this count to multiplexer 2103 via signal line 2104. Signal line 2104 is either high or low depending on the number of ones contained in the data block.

Data from RF receiver 68 is in serial form.
The data is converted to parallel format by a serial-to-parallel converter 2101. Signal 2105 from serial-to-parallel converter 2101 represents a 20 bit word in parallel form and thus represents 20 signal lines. signal 2105
The 20 signal lines from serial-to-parallel converter 2101, represented by , are sent as inputs to decode circuit 2107 and register 2108. register 2
108 is used as storage to provide extra time for processing incoming data from the remote telemetry device illustrated in Figure 2b. The decoder 2107 is used to send a clock signal to the register 2108, enable the register and load data, and send a data available signal to the multiplexer 2103 and control signal 2110 to the parity count circuit 2.
Send to 102. A data available signal, illustrated as signal line 2109, is used to inform the 2900 microprocessor that data is available. The clock signal sent from the decode section is shown as signal 2111.

A clock signal generation circuit 2100 is used to supply a clock or timing signal for the data formatter 71. Clock signal 2099 is provided from the RF receiver by signal line 69 shown in FIG. 2a. In response to signal 2099, clock signal generation circuit 2100 generates a pair of clock signals 2117 and 2118 that are 180 degrees out of phase. The clock signal 2117 is the parity count circuit 21
02 and the decoding circuit 2107. The clock signal 2118 is sent to the decoding circuit 210.
given to 7.

Output 2112 from register 2108 is sent to multiplexer 2103. Again, register 2
Output signal 2112 from 108 represents 20 signal lines.

The A0 and A1 address lines from the 2900 microprocessor are provided to multiplexer 2103 and are used to select which input signal is provided as an output to driver 2114 on signal line 2115. Output signal lines 2115 from multiplexer 2103 represent eight signal lines. driver 21
The output signal lines from 14 are connected to the D0-D7 data lines of the 2900 microprocessor.

Basically, the data formatter 71 shown in FIG. 41 is used to convert serial data from a remote telemetry device to parallel form and provide parity counts to the 2900 microprocessor. Decode circuit 2107 provides data formatter synchronization. The way data is given to the 2900 microprocessor is through the A0 and A1 address lines.
Controlled by a 2900 microprocessor.

Clock signal generation circuit 21 shown in FIG.
00 is illustrated in more detail in FIG. The clock signal 2099 from the RF receiver 68 shown in FIG.
7 as the first input. Delay section 212
The output from 6 is provided as a second input to AND gate 2127 via a voltage divider circuit composed of resistors 2128 and 2129 and an inverter 2131. The output from AND gate 2127 is the fourth
The clock signal 2117 shown in FIG. 1 is formed.

The clock signal 2099 from the RF receiver 68 shown in FIG.
32 as an input to the delay unit 2133, and
Provided as the first input to AND gate 2134. The output from the delay section 2133 is the resistor 213
6,2137 and an inverter 2138 as the second input to the AND gate 2134. AND gate 21
The output from 34 is the clock signal 2118 illustrated in FIG. As previously mentioned, clock signals 2117 and 2118 are 180° out of phase.

The decode circuit 2107 shown in FIG. 41 is shown in more detail in FIG. Referring to FIG. 43, signal 2105 from serial-to-parallel converter 2101 illustrated in FIG. 41 consists of 20 bits. These 20 bits are applied to multiple NOR gates and NAND gates as shown in FIG. Bits 19, 17, and 16 are NOR gate 2141
given as input to . Bits 11, 9, and 7 are
Provided as an input to NOR gate 2142.
Bits 5, 3, and 1 are provided to NOR gate 2143. Bit 18, 15, 14, 13, 12, 10, 8, 6
is provided as an input to NAND gate 2144. Bits 4, 2, 0 are NAND gate 214
given as input to 5. NAND gate 2
The output from flip-flop 2147 is also applied to 145 . The output from NAND gate 2144 is provided as the first input to NOR gate 2148. The output from NAND gate 2145 is provided as a second input to NOR gate 2148. The output from NOR gate 2148 is NOR
Provided as the first input to gate 2149.
The output from NOR gates 2141-2143 is also
Provided as an input to NAND gate 2149. The output from NAND gate 2149 is provided as a first input to NAND gate 2152 via inverter 2151.

Clock signal 2118 from clock signal generation circuit 2100 is applied to the second clock signal to NAND gate 2152.
It is provided as an input and also as the first input to AND gate 2153. The output from NAND gate 2152 is flip-flop 2147
clock input. The D input of flip-flop 2147 is provided with an enable pulse to indicate that data is available. Set input of flip-flop 2147, flip-flop 2
155 set inputs and flip-flop 215
All 5 D inputs are coupled to +5V power supply 2157 via resistor 2158. flipflop 21
The Q output of 47 goes to the count/load input of counter 2159, to the count/load input of counter 2161, and to the second
Combined as input. The output of AND gate 2153 is provided as one input to NAND gate 2163. The output of flip-flop 2147 is coupled as one input to NAND gate 2145 as previously described and also provides signal 2110 which forms part of signal 2110 illustrated in FIG.
Also given as A. flipflop 211
The Q output from 5 is used as the data available signal 2109 illustrated in FIG.

Clock signal generation circuit 21 shown in FIG.
The clock signal 2117 from 00 is sent to the counter 21.
59 to the first clock input. counter 2
161's A data input and clear input, as well as the A and D data inputs of counter 2159 and counter 21.
Clear input of 59 is +5V via resistor 2166
Coupled to power supply 2165. The B and C data inputs of counter 2159 are grounded. counter 21
The B, C, and D data inputs of 61 are grounded. The QA output from counter 2159 is
is also provided as the second input to NAND gate 2163. QD output from counter 2159 is output from counter 216
1 and is also provided as the third input to NAND gate 2163.
The QA output from counter 2161 is provided as the fourth input to NAND gate 2163.
The output from NAND gate 2163 is provided to the clock input of flip-flop 2155 and is also provided as signal 2110B forming the second portion of signal 2110 illustrated in FIG.

The circuit illustrated in FIG. 43 is used to indicate that data is available to the 2900 microprocessor by decoding the 20 bits of signal 2105 from the serial-to-parallel converter illustrated in FIG. The decoding circuit shown in FIG. 43 counts the number of bits with counters 2159 and 2161 and provides an indication when each 20 bit word is transmitted.

Parity count circuit 2 shown in Figure 41
102 is shown in more detail in FIG. Data signal 69 from RF receiver 68, shown in FIG. 2a, is provided to the J input of flip-flop 2171 and via inverter 2172 to the K input of flip-flop 2171. Clock signal 2117 provided from clock signal generation circuit 2100 is provided to the clock input of flip-flop 2171. Signal 2110B, shown in FIG. 43, is provided to the clock input of flip-flop 2173 via inverter 2174. Signal 2110B is also provided directly as a first input to AND gate 2175 via inverter 2174 and as a second input to NAND gate 2175 via a resistor-capacitive circuit comprised of resistor 2176 and capacitor 2177.
The output from NAND gate 2175 is provided as the first input to NOR gate 2178. 43rd
The signal 2110A shown in the figure is the NOR gate 21
78 as the second input. The output from NOR gate 2178 is the flip-flop 217
1 reset input.

The Q output from flip-flop 2171 is applied to the D input of flip-flop 2173. The set and reset inputs of flip-flop 2173 are coupled through resistor 2182 to +5 power supply 2181. The Q output from flip-flop 2173 has a parity value as illustrated and described in FIG.
It is given as a count signal 2104.

The circuit shown in FIG. 44 simply counts the number of ones in the data being transmitted in the data block from the receiver 68 shown in FIG. 2a. Preferably, even parity is used and the Q output from flip-flop 2171 is used. If odd parity is required, the output from flip-flop 2171 can be used. Signal 2104 indicates whether the number of ones transmitted in a particular data block is an even number. If the number of ones is not even, signal 2104 indicates to the 2900 microprocessor that an error has occurred during the particular block of data being transmitted.

The magnetic tape unit 79, magnetic tape controller 88, and magnetic tape interface 78 illustrated in FIG. 2a are illustrated in more detail in FIG. 45. Control blocks 1511 and 1512 are the second a
Corresponds to the magnetic tape controller illustrated in the figure. Interface block 1514 is the second
Magnetic tape interface 7 shown in figure a
Corresponds to 8. Formatter 1515 and tape unit 1516 correspond to magnetic tape unit 79 illustrated in FIG. 2a. In a preferred embodiment of the invention,
Forumatsuta 1515 is Kennedy Model 921
8 and the tape device 1516 is a Kennedy Model 98.
It is 00.

As far as possible, the signal lines shown in FIG. 45 are named consistent with the specifications of formatter 1515 and tape device 1516. Forumatsuta 151
The general manner in which tape device 5 and tape device 1516 are interfaced with a 2900 microprocessor and a 6800 microprocessor is illustrated in FIG. Formatsuta 1515 and tape device 151
The main problem encountered when interfacing 6 to a 2900 microprocessor and a 6800 microprocessor is that the tape device 1516 and the two microprocessors are running asynchronously.
A device had to be developed to determine whether the data transferred from the 2900 microprocessor was completely transferred to the tape device 1516. or,
A device must also be developed to alert the control computer, which is a 6800 microcomputer, that an error has occurred during data transfer from the 2900 to the tape device 1516.

Control section 1511 and control section 1512 are coupled to the 6800 microprocessor by bus line 89 as shown in Figure 2a. Control unit 151
1 is an interface 1514 and a control unit 1512
Give multiple output signals to. Signal 1517 is provided to interface 1514 and is used to clear an error indication previously set at interface 1514. The master reset signal 1519 is sent from the control section 1511 to the control section 15.
12 and used to reset the logic chip located in the control section 1512. The final word signal 1521 is sent from the control unit 1511 to the control unit 1.
521 to indicate that the last word of the data block has been transmitted from the 2900 microprocessor to the tape device 1516. The strobe signal 1523 is sent from the control unit 1511 to the control unit 1512.
given to. Strobe signal 1523 is a plurality of clock signals used to clock the logic circuitry of control section 1512.

The controller 1512, which is also coupled to the 6800 microprocessor by bus line 89, includes a formatter 1515, a tape device 1516, and a controller 151.
1. Provide multiple outputs to interface 1514. Read signal 1524 and write signal 1525 are sent from controller 1512 to interface 1514 to control the direction of data transfer. Write clock signal 1526 is routed from control block 1512 to control block 1511 and interface 1514.
given to. Write clock signal 1526 is used to clock data to tape device 1516. A command strobe signal 1528 is provided from controller 1512 to controller 1511 and is used to clear the status and error flip-flops and to generate a clear error signal 1517. The command reset signal 1529 is sent to the control unit 15
12 to a control section 1511 and used to generate a master reset signal 1519. A standby signal 1531 is given from the control unit 1512 to the control unit 1511 to indicate that the power-on procedure for the tape device 1516 has been completed. A write data signal line 1533 is applied from the control section 1512 to the formatter 1515. Write data line 15
33, 1544 writes data from the 2900 microprocessor to formatter 1515.
The device activation signal 1534 is given from the control unit 1512 to the formatter 1515.
It is used to power all 15 interfaces, drivers and receivers. The offline signal 1535 is sent from the controller 1512 to the formatter 15.
15 and is used to place tape device 1516 under manual control. Command control signal 153
6 is given from the control unit 1512 to the formatter 1515 to indicate that a command has been issued from the 6800 microprocessor. Data available strobe 1538 is provided from controller 1512 to formatter 1515 and is a pulse sent to formatter 1515 for each character written to tape device 1516. The standby power line 1539 is connected to the control unit 1
512 to cheap device 1516 and is used to control tape device 1516 into operation or standby mode.

Interface 1514 is coupled to the 2900 microprocessor bus by bus line 77 as shown in FIG. 2a. interface 15
14 provides a plurality of outputs to the control section 1511 and the control section 1512. A speed error signal 1541 is given from the interface 1514 to the control section 1511, and from the 2900 microprocessor to the tape device 1.
Indicates whether an error occurred during data transfer to 516. A read clock signal 1543 is provided from an interface 1514 to controllers 1511 and 1512. Read clock signal 15
43 clocks the reading of characters from tape device 1516 and increments the character counter in controller 1511.

A write data signal line 1544 is provided from interface 1514 to controller 1512 and provides a means for transferring data from the 2900 microprocessor to controller 1512 and thus to formatter 1515.

Forumatsuta 1515 is Forumatsuta 1515
Provide multiple input and output signals as described in the specifications. Only the output signals essential to understanding how to interface tape device 1516 to the 6800 and 2900 microprocessors are described. The read data line 1546 is connected from the formatter 1515 to the interface 1514.
and provides a means for transferring data from tape device 1516 to interface 1514. Read clock signal 1547 is formatter 1
515 to interface 1514 and from tape device 1516 to interface 1.
514 to provide a clock signal to read the data.
The write clock signal 1549 is output from the formatter 151.
5 to the control unit 1512, and the tape device 1
used to clock the writing of data to 516. A load point signal 1551 is given from the formatter 1515 to the control section 1512. The load point signal 1551 indicates that the tape device is selected;
online, not rewound, and tape
It shows that the load point marker is below the optical sensor. Online signal 1552 is given from formatter 1515 to control section 1511. Online signal 1552 indicates whether the selected tape transport is remote or locally controlled. The tape busy signal 1553 is sent to the formatter 151.
5 to the control unit 1511, and the tape device 1
516, indicating that it is not ready to receive data. The rewind signal 1554 is the formatter 15
15 to the control unit 1511 to instruct that the tape device 1516 is being rewound. A plurality of output signals represented by an error signal 1556 are sent from the formatter 1515 to the controller 1511.
given to. Error signal 1556 identifies various error conditions that occur during operation of tape device 1516. Status signal 155 representing a plurality of signals
7 is given from the formatter 1515 to the control unit 1511 and provides operational status information of the tape device 1516.

The control section 1511 shown in FIG. 45 is shown in more detail in FIG. 46. Input/output selection signal 1 from 6800 microprocessor to decoder 1562
561 is given. Input/output selection signal 1561
is obtained by decoding the high order eight bits of the address from the 6800 microprocessor. The decoded signal is then ANDed with the legal memory address (VMA) from the 6800 microprocessor.
is decoded to provide an input/output selection signal 1561 (this decoding is done by computer 51 shown in FIG. 2a). Decoder 1562 also receives data from the 6800 microprocessor via a plurality of address lines, represented as address lines 1564.
A4-A7 address bits are also provided. In response to input/output selection signal 1561 and the A4-A7 address bits, decoder 1562 selects decoder 156.
A tape device selection signal 1565 is applied to the device 6. Decoder 1566 is also provided with A0-A3 address lines from the 6800 microprocessor by a plurality of address lines represented as address lines 1567. Decoder 1566 also receives read/write (R/) signals 156 from the 6800 microprocessor.
8 and φ2 clock signals 1569 are also provided. Tape device selection signal 1565, address bit
In response to A0-A3, read/write signal 1568, and φ2 clock signal 1569, decoder 1566 controls control unit 1511 and control unit 151 shown in FIG.
Provides multiple clock signals for use in 2. Sixteen clock signals called strobe signals are provided by a plurality of signal lines represented by signal line 1523. Select read signal 1571 and interrupt clock signal 1572 are also provided from decoder 1566.

The D0-D7 data lines from the 6800 microprocessor are provided as inputs to counter 1574 and counter 1575. A seventh strobe signal from decoder 1566 is provided to the load input of counter 1574. A sixth strobe signal from decoder 1566 is applied to the load input of counter 1575. Read clock signal 1543 is provided to the up clock input of counter 1574. Write clock signal 1526 is output to counter 157.
4 down clock input. Eight output lines from count 1574 are provided to multiplexer 1577 and are represented as signal lines 1578. Similarly, eight output lines are connected to counter 157.
5 to multiplexer 1577 and is represented by signal line 1579.

Counter 1574 and counter 1575 together constitute an up/down character counter. Character counters are used for both read and write operations. In a write operation, a character counter is preset to the number of characters to be written to the tape device 1516 shown in FIG. The character counter is decremented by the write clock signal 1526 as each character is written to the tape;
Therefore, a count of the number of characters written to the tape is provided to multiplexer 1577. counter 1575
The borrow output from is used as a signal to controller 1512 that the last word of the data block has been written to the tape device. This signal is called the final word signal 1521.

In a read operation, the character counter is preset to zero and is incremented by read clock signal 1543 as each character is read from tape device 1516.
At the end of the read operation, the contents of the character counter are examined to determine the number of characters read from the tape device. The number of characters read from the tape device is 1578 signal lines,
1579 to multiplexer 1577. This information is stored on D0− of the 6800 microprocessor.
It is sent from multiplexer 1577 to the 6800 microprocessor via buffer 1581 coupled to the D7 data line. Buffer 1581 receives selected read signal 1571 from decoder 1566.
Powered by the φ2 clock from the 6800 microprocessor.

Multiplexer 1577 is 6800 computer
One of four 8-bit words is selected depending on the state of the A0 and A1 address bits on the bus. Of the four available words, the first word is the output of counter 1574 represented by signal 1578;
The word is signal 1579. The third word is various status signals represented by 1557. The fourth word is 1
556 and provides error information.

The Q output from flip-flop 1583 is set by error signal 1556 to tape drive 1.
Indicates that an error occurred during operation of 516.
The Q output from flip-flop 1583 is AND
Clear error signal 151 from gate 1584
Remains set in error state until cleared by 7. Status signal 1577, rate
Error signal 1541 and error signal 1556 are D0
Multiplexer 1 by -D7 data line 1580
557 and buffer 1581 to the 6800 microprocessor.

Command strobe signal 1528 is AND gate 1
584 as one input. AND
A master reset signal 1519 provided from gate 1587 is also provided as an input to AND gate 1584. Clear error signal 1517 is master reset 1519 or command strobe 1
528 goes low. The low state of clear error signal 1517 is used to clear an error condition in flip-flop 1583, and is also used to clear an error set in interface 1514, shown in FIG.

Online signal 1552 is one shot 159
given to 1. The output from one shot 1591 is provided as the first input to AND gate 1599. Tape busy signal 1553 is provided to one shot 1592. One shot 1
The output from 592 is provided as a second input to AND gate 1599 and also to control section 1512 as formatter busy signal 1518. Rewind signal 1554 is one shot 159
given to 3. The output from one shot 1593 is provided as the third input to AND gate 1599. Standby signal 1531 is one shot 1
594. Output 1597 from one shot 1594 is provided as the fourth input to AND gate 1599.

Output signal 1561 from AND gate 1599
is applied to the set inputs of flip-flops 1602 and 1603. flipflop 1602,
The D input of 1603 is grounded. Interrupt clock signal 1572 is provided to the clock input of flip-flop 1602. Select read signal 1571 energizes buffer 1581 and clears interrupt flip-flop 1603. Master reset signal 1
519 is given as a reset signal to flip-flop 1602. Clear error signal 1517 provided from AND gate 1584 is provided as a reset signal to flip-flop 1603. The Q output from flip-flop 1602 is provided as one input to NAND gate 1605. The Q output from flip-flop 1603 is provided as an interrupt bit signal 1605 to multiplexer 1577;
577 and buffer 1581 to the 6800 microprocessor.

The twelfth strobe signal from decoder 1566 is provided to the set input of interrupt enable flip-flop 1607. The D input of flip-flop 1607 is grounded and the clock input of flip-flop 1607 is coupled to the thirteenth strobe signal from decoder 1566. Provided as master reset signal 1519 and reset signal to flip-flop 1607. flipflop 1
The output from 607 is provided as the second input to NAND gate 1605. NAND gate 1
The output from 605 is coupled to the 6800 microprocessor's interrupt request (IRQ) line.

4 status signals, i.e. online 155
2, tape busy 1553, rewind 1554,
Wait 1531 can initiate an interrupt request to the 6800 microprocessor. Interrupt request is NAND gate 1
The output from 605 is provided to the 6800 microprocessor. Any state signal can trigger the one shot associated with each state signal to generate a pulse. This pulse is applied via AND gate 1599 to the set inputs of flip-flops 1602 and 1603. A signal indicating that an interrupt has been requested is sent from flip-flop 1602.
It is applied to the 6800 microprocessor through NAND gate 1605 and from flip-flop 1603 through multiplexer 1577.

The conditions for generating an interrupt are as follows.

1 When the tape device is brought online manually or
On-line status signal 1552 goes low to generate an interrupt when a device enable command is received from the 6800 microprocessor.

2 Tape busy signal 155 upon completion of each command.
3 goes high to generate an interrupt and indicate that the tape device is ready to receive the next command.

3 Rewind signal 1554 goes high indicating completion of the rewind procedure.

4 Approximately after the tape device power-on command is issued
After 1.5 seconds, standby signal line 1531 goes high indicating that the power-up procedure is complete.

The reset signal from the 6800 microprocessor is
Provided as the first input to AND gate 1587. Command reset signal 1529 is provided as a second input signal to AND gate 1587. Power on signal 1611 from power on detector 1612
is applied and provides a reset signal when power is applied to the logic section. Output signal 1519 from AND gate 1587 is master reset signal 1519
It is.

The control section 1512 shown in FIG.
and 47b in more detail. Fourth
Referring to Figure 7a, the D0-D7 data lines from the 6800 microprocessor are connected to command register 1614,
1615 data input. A fourth strobe output from decoder 1566, shown in FIG. 46, is applied to the clock input of command register 1614. A fifth strobe output from decoder 1566 is provided to the clock input of command register 1615. Output signals 1617, 1618 from command registers 1614, 1615 are sent to multiplexer 1619, NAND gate 1621, flip-flop 1622, one shot 1623,
NAND gate 1624, NAND gate 1625
is combined with Signal 1617 is command register 16
8 output lines from 14 are shown. Similarly, signal 1
618 represents eight output lines from command register 1615. Of the 16 output lines from command register 1614 and command register 1615, 8 output lines are sent to multiplexer 1619, 5 output lines are sent to NAND gate 1621, and 1 output line is sent to flip-flop. Sent to 1622,
One output line is sent to one shot 1623,
One output line is NAND gate 1624, 162
5 will be sent to both. A clear register signal 1627, output from AND gate 1629, is applied to the reset inputs of both command registers 1615 and 1614.

Write data signal 154 representing eight data lines
4 is sent as the second set of input signals to multiplexer 1619. A command select plus signal 1631 provided from flip-flop 1632 shown in FIG. 47b is provided to the select input of multiplexer 1619. Command selection plus signal is 6800
It is used to select between commands provided by the D0-D7 data lines from the microprocessor or data from the 2900 microprocessor provided to formatter 1515 by data line 1544. Eight output signal lines from multiplexer 1619, represented as signal lines 1634, are provided as inputs to NAND gate 1636. NAND gate 1636 has 8 NANDs
Represents a gate. Outputs from a plurality of NAND gates, represented by NAND gate 1636, are provided as eight write data lines to formatter 1515. Remaining 5 write data lines 153
3 is provided by NAND gate 1621 representing five NAND gates.

Flip-flop 163 illustrated in FIG. 47b
The command selection minus signal given from 2 is AND
Provided as the first input to gate 1638.
Flip-flop 1641 illustrated in FIG. 47a
The write signal 1525 set by is provided as the second input to AND gate 1638.
The output from AND gate 1638 is inverter 1
NAND gate 1636 and NAND through 639
is applied to a NAND gate represented by gate 1621. The output signal from inverter 1639 is used to energize NAND gates represented by NAND gates 1636 and 1621.

Output signal 16 from flip-flop 1622
42 is applied to both inputs of NAND gate 1643. The output from NAND gate 1643 is device enable signal 1543. Output signal 1644 from one shot 1623 is connected to NAND gate 1645
is given to both inputs. NAND gate 1645
The output from is the offline signal 1535.

Command strobe signal 1 provided as output from one shot 1646 illustrated in Figure 47b.
528 is provided to both inputs of NAND gate 1648 and as a second input to NAND gate 1624 and NAND gate 1625.
The output from NAND gate 1648 is control command signal 1536. The output from NAND gate 1624 is provided to the set input of flip-flop 1651. The output from AND gate 1652 is provided to the reset input of flip-flop 1651. Formatter busy signal 1518 and master reset signal 1519 are AND gate 1
652. The output from flip-flop 1651 is read signal 1524.

Formatter write clock signal 1549 is applied to delay section 1656 via inverter 1654. The output from inverter 1654 is write clock signal 1526. The output from delay section 1656 is provided as a first input to NAND gate 1656. The output from NAND gate 1625 is provided to the set input of flip-flop 1541. The final word signal 1521 is sent to the inverter 16
57 to the reset input of flip-flop 1641. flip flop 1641
The D input of is grounded. flip flop 164
The Q output from 1 is provided as the second input to NAND gate 1655. NAND gate 165
The output from 5 is the data available signal 1538. The output from flip-flop 1641 is write signal 1525.

Referring to FIG. 47b, the fourth strobe signal from decoder 1566 illustrated in FIG.
Provided as the first input to AND gate 1661. The fifth strobe output from decoder 1566 is provided as the second input to AND gate 1661. The output signal 1662 from AND gate 1661 is provided as an input to one shot 1647 and to the set input of flip-flop 1632.

The output from one shot 1647 is command strobe signal 1528. One shot 1657
The output from is also provided to one shot 1664. The output from one shot 1664 is NAND
Provided as one input to gate 1667. Load point signal 1551 is NAND gate 16
67 as the second input. Load point signal 1551 is also provided as an input to one shot 1668. The output from one shot 1688 is provided as the first input to AND gate 1669. The output from NAND gate 1667 is provided as a second input to AND gate 1669. The output from AND gate 1669 is AND
Provided as the first input to gate 1629.
Master reset signal 1519 is AND gate 1
629 as the second input. The output signal from AND gate 1629 is clear register signal 1627. Signal 1627 is also provided to the reset input of flip-flop 1632 as well as command register 1614 and command register 1615. The Q output from flip-flop 1632 is the command select plus signal 1631 sent to multiplexer 1619. flipflop 1632
The output from is the command select minus signal provided as an input to AND gate 1638.

from decoder 1566 illustrated in FIG.
The 10 strobe signal is sent to the set input of flip-flop 1671. The 11th strobe signal from decoder 1566 is applied to flip-flop 1671.
1672 and as an input to timer 1672. Master reset signal 1
519 is applied to the reset input of flip-flop 1671. D of flip-flop 1671
Input is grounded. The Q output from flip-flop 1671 is provided as the first input to NOR gate 1673 and also to both inputs of NAND gate 1675. The output from timer 1672 is provided as a second input to NOR gate 1673. Timer 1672 is primarily used to provide a delay while powering up tape device 1516. Power supply 1676 connects output 153 from NAND gate 1675 through resistor 1678.
Combined to 9. The output from NAND gate 1675 forms standby power signal 1539. NOR
Output from gate 1673 is tape device 1516
A standby signal 1531 is generated to indicate that the power-on procedure is complete.

Referring to Figures 45, 46, 47a and 47b, when a write command is issued from the 6800 microprocessor, write flip-flop 1641 is set. The contents of command registers 1614 and 1615 are sent to formatter 1515. The formatter sets the tape device 1516 at a constant speed, writes the preamble to the tape device 1516, and at an appropriate time the formatter 1515 outputs the formatter write clock signal 1.
549 is generated. This signal is transmitted by delay device 1656
The data available signal 1538 is NANDed with the output from the write flip-flop 1641 and provided to the formatter as the data available signal 1538. Data available signal 1538 causes the formatter to accept data characters on write data line 1533.

Write clock signal 1526, derived from formatter write clock signal 1549, decrements character counters 1574, 1575 shown in FIG. The writing process continues until the character counter provides the last word output signal 1641. Last word output signal 1521 clocks write flip-flop 1641. There is no signal applied to data available line 1538 because write flip-flop 1641 is reset before delayed formatter write clock signal 1549 arrives. If the data available signal 1538 is not received within a specified time following the formatter write clock signal 1549,
Formatally interpreted as the completion of a write operation.

When a read command is issued, the read flip-flop is set. Read data 1546 and read clock 1547 are sent directly from formatter 1515 to interface 1514. Read clock signal 154 from interface 1514
3 is the counter 1574, 15 shown in FIG.
Increase 75. The end of a data block is detected by the formatter 1515 and the formatter busy signal 151 goes high (false).
8 gives a signal to the control section 1512. Upon completion of the read operation, the read flip-flop 165
1 is reset by the formatter busy signal 1518 going high (false).

Interface 1514 illustrated in FIG.
is illustrated in more detail in FIG. The D0-D7 data lines from the 2900 microprocessor are provided to buffer 1681. A write address signal 1682 from a decoder 1684 is also applied to the buffer 1681. Write address signal 16
82 is provided as an enable pulse to buffer 1681 and also as the first input to NAND gate 1685. NAND gate 1685 also has
Strobe signal 1 from 2900 microprocessor
686 is also given. Buffered data from the 2900 microprocessor is transferred to data latch 1 by multiple data lines represented by data line 1687.
687. The output from NAND gate 1685 is provided as the clock input to data latch 1689. data latch 1689
The eight outputs from the controller 1 shown in FIG.
512 and data is written to the tape device from the 2900 microprocessor via write data lines 1544 and 1533.

Read data line 1546, read clock 154
7. All read signals 1524 are sent to buffer 1691. Read data lines 1546 represent eight data lines. The read signal 1524 is the buffer 169
It is given as a biasing signal to 1. The buffered data is transferred from the buffer 1691 to the latch 16 by an output data line 1693 from the buffer 1691.
Given to 92. Data lines 1693 represent eight data lines. Read clock signal 1543 is provided to the clock input of data latch 1692 and is also provided as an input to gate 1695. The read clock signal 1543 also controls the control section 151.
1 and is also given to the control unit 1512. data line 1
Eight data lines from latch 1692, represented by 697, are provided to buffer 1699. The buffer 1699 has a decoder 16 as an activation signal.
A read address signal 1701 from 84 is provided. The output from buffer 1699 is coupled to the D0-D7 data lines from the 2900 microprocessor. The D0-D7 data line of the 2900 microprocessor provides a buffer of 169 to the 2900 microprocessor.
1, read data line 1546 provided through latch 1692 and buffer 1699 allows data to be read from tape device 1516 to the 2900 microprocessor.

Gate 1695 receives write signal 1525, write clock signal 1526, and read clock signal 1543.
is given. A set interrupt output 1703 from gate 1695 is generated in response to any input signal to gate 1695. Set interrupt output 170
3 is provided as a clock signal to flip-flop 1704 and flip-flop 1705.

A0-A7 represented as address lines 1707
Address lines are provided to decoder 1684 from the 2900 microprocessor. Similarly, the valid memory address (VMA) signal 1708, DM signal 1709, and
A read/write (R/) signal 1710 and a strobe signal 1711 are provided to a decoder 1684.
In response to addresses from the 2900 microprocessor, decoder 1684 provides as outputs read address signal 1701, write address signal 1682, and address strobe 1712. Read address signal 1701 and write address signal 1712 are used as described above. Address strobe signal 1712 is provided as one input to AND gate 1714.

Reset signal 1 from 2900 microprocessor
715 is provided as the second input to AND gate 1714 and as the first input to AND gate 1716. The output from AND gate 1714 is provided to the reset input of flip-flop 1704. The D input to flip-flop 1704 is coupled to +5V power supply 1718. The Q output from flip-flop 1704 is connected to NAND gate 17.
19 and is also coupled to both inputs of flip-flop 1.
It is also given to the D input of 705. The output from NAND gate 1719 is an interrupt request signal to the 2900 microprocessor. (The 2900 microprocessor does not respond to interrupt requests as interrupts, but periodically polls the line.) Clear error signal 1517 is applied to AND gate 1.
716 as the second input. The output from AND gate 1716 is the flip-flop 17
05 and the reset input of flip-flop 1723. The Q output from flip-flop 1705 is provided to the clock input of flip-flop 1723. D of flip-flop 1723
The input is coupled to +5V power supply 1724. The output from flip-flop 1723 is provided as the first input to NOR gate 1721. The Q output from flip-flop 1704 is provided as the second input to NOR gate 1721. NOR
The output from gate 1721 is rate error signal 1541.

Interface 1514 illustrated in FIG.
The logic in detects that a write operation has been initiated by write signal 1525 going low. Write signal 1525 is used to generate set interrupt signal 1703.

Set interrupt signal 1703 clocks interrupt request flip-flop 1704 and rate error flip-flop 1705. The 2900 microprocessor is pre-initialized by the 6800 microprocessor for write operations, so the 2900
The microprocessor responds to interrupt requests generated in response to set interrupt 1703 by placing tape data characters on the data bus and generating appropriate address and control signals. The data characters are buffered by buffer 1681 and latched into data latch 1689. The latched character data is provided to a formatter 1515 via a control section 1512. interface 1
The logic at 514 outputs the first write clock signal 15.
It remains in this state until 26 occurs. Before the write clock signal 1526 is generated, there is a delay of approximately 17 mS during which the tape device 1516 brings the tape to constant speed and writes the 41 character preamble. Write clock signal 1
526 propagates through gate 1695 and the set interrupt signal 1703 is again generated. The set interrupt signal 1703 is again sent to the interrupt request flip-flop 170.
4 and rate error flip-flop 1705
clock. This causes interrupt request flip-flop 1704 to be set indicating that the previous data character was accepted by formatter 1515 and the next data character is required. After an initial delay, write clock signal 1526 occurs approximately every 25 mS.

An address strobe 1712 generated by decoder 1684 for a 2900 microprocessor read or write operation is applied as a first input to gate 1714. Since the output of gate 1714 resets interrupt request flip-flop 1704, the Q output of flip-flop 1704 is low before the next set interrupt clock 1703, so that flip-flop 1705 is not set. If the 2900 microprocessor does not provide data to interface 1514 before the next write clock 1526 or read clock 1546, the Q output of flip-flop 1704 is high and flip-flop 1705 is set. Setting flip-flop 1705 sets flip-flop 1723. Flip-flop 1705 is cleared by a subsequent data transfer, but flip-flop 1723 remains set until cleared by clear error 1517 or a reset signal.

A tape read operation causes read signal 15 to go high.
24 and energizes the read data bus buffer 1691. Read data signal 1546
and the read clock signal 1547 is transferred to the buffer 1691.
and is latched into data latch 1692. Read clock signal 1547 is used to clock data into latch 1692, incrementing a character counter comprised of counters 1574 and 1575 shown in FIG. 46, and generating a set interrupt signal 1703 for read operations. Set interrupt signal 1
703 is the interrupt request flip-flop 1704 again.
and rate error flip-flop 1705.

In response to the setting of interrupt request flip-flop 1704, the 2900 microprocessor activates address and control signals to cause read address signal 1701 to be generated by decoder 1684. Read address signal 1701 energizes buffer 1699 and places the character from read data line 1546 onto the 2900 microprocessor data bus. After a short delay, the 2900 microprocessor issues a strobe pulse 1711 indicating that a data character has been received. strobe pulse 1711
The decoder 1684 then generates an address strobe 1712 that clears the interrupt request flip-flop 1704.

Read clock pulses 1547 are generated at an average rate of 25 mS until the read operation is complete. Fourth
Character counters 1574 and 1575 illustrated in Figure 6
determines the number of characters read from the tape by the 6800 microprocessor.

2900 microprocessor and Formatsuta 151
Data transfer between the two devices is an asynchronous process, with both devices operating at different speeds. The maximum number of characters transferred in one data block is 65536. The transfer must be complete, or at least 1
It must be known that an error has occurred.

The rate error logic illustrated in FIG.
Each character read from the tape is 2900 within the allowed time frame.
Verify that it was accepted by the microprocessor and that the character was available to formatter 1515 for writing to tape device 1516 within the allowed time. If either of these conditions is not met, the rate error flip-flop 170
5 is set.

The rate error detection logic requires three flip-flops. Set interrupt signal 1703 clocks interrupt request flip-flop 1704 and rate error flip-flop 1705. Since interrupt request flip-flop 1704 is initially in reset state, rate error flip-flop 1705 remains in reset state.
If for any reason the strobe signal from the 2900 microprocessor does not occur before the next set interrupt signal, rate error flip-flop 1705 is set. Rate error flip-flop 1705 receives reset signal 171
The output flip-flop 17 remains set until it receives a 5 or clear error signal 1517.
Clock 23. It is possible that the final character will not be accepted by the 2900 microprocessor. Therefore, the Q output from interrupt request flip-flop 1704 is OR'ed with the Q output from flip-flop 1723 and the rate error signal 1 is sent to multiplexer 1577 shown in FIG.
541 is generated.

2900 microprocessor to tape device 151
If an error occurs during a data transfer to 6 or from tape device 1516 to the 2900 microprocessor, the 6800 microprocessor commands a retransmission of the data to correct the error that occurred in the previous data transfer.

Gate 1695 illustrated in FIG. 48 is illustrated in more detail in FIG. 49. The read clock signal 1543 is converted to NAND via an inverter 1731.
Provided as the first input to gate 1732.
Write signal 1525 is passed through inverter 1733.
Provided as the first input to NAND gate 1734. The write clock signal 1526 is also connected to an inverter 1735, a resistance/capacitance circuit consisting of an inverter 1735, a resistor 1736, and a capacitor 1737, and an inverter 173.
8 as the second input to NAND gate 1734. The output from NAND gate 1734 is provided as a second input to NAND gate 1733. The output from NAND gate 1732 is the set interrupt signal 170 illustrated in FIG.
It is 3.

The decoder 1684 shown in FIG.
The figures are shown in more detail. The A0 address bit from the 2900 microprocessor is provided as the first input to NAND gate 1742 through inverter 1741. The A1 address line from the 2900 microprocessor is provided as the second input to NAND gate 1742 through inverter 1743. from 2900 microprocessor
The A2-A7 address lines are provided directly as third through eighth inputs to NAND gate 1742. NAND
The output signal from gate 1742 is sent to inverter 17
45 as the first input to NAND gate 1746 and as the first input to NAND gate 1747.

Valid memory address (VMA) line 1708 is connected to NAND gate 17 via inverter 1749.
As the second input to 46, also the NAND gate 17
47 as the second input. DM signal 1709 from the 2900 microprocessor passes through inverters 1751 and 1752 to NAND gate 1.
As the third input to 747, also NAND gate 1
746 as the third input.

Read/write (R/) signal 1710 is provided as a fourth input to NAND gate 1746 via inverter 1753. Read/Write (R/
W) Signal 1710 passes through inverter 1753 and inverter 1755 to NAND gate 1747.
is sent as the fourth input to.

The output signal from NAND gate 1746 is the fourth
This is the write address signal 1682 shown in FIG. The write address signal is used as shown in FIG. 48 and is also provided as the first input to NAND gate 1757. NAND gate 17
The output from 47 is the read address signal 1701 illustrated in FIG. Read address signal 170
1 is used as shown in FIG.
Also provided as a second input to NAND gate 1757.

The output from NAND gate 1757 is sent as the first input to NAND gate 1758. 2900
Strobe signal 171 from microprocessor
1 is sent as the second input to NAND gate 1758 via inverter 1759. NAND
The output from gate 1758 is the address strobe signal 1712 shown in FIG.

The data display device 93 shown in FIG.
This is illustrated in more detail in Figure 1. Referring to Figure 51, data bus line 94 is connected to computer data bus line 75 illustrated in Figure 2a.
Earthquake data is sent to the buffer 1301. Seismic data transmitted from the RTU to the CRS shown in FIG. 2a is provided in parallel form from the computer device 74 to the data display device 93. Seismic data is sent from buffer 1301 via data line 1303 to parallel-to-serial (P/S) converter 1304. P/S converter 1304 converts the seismic data into serial format and sends the seismic data to charge coupled device (CCD) memory 1307 via signal line 1308.

When you want to display earthquake data, the earthquake data stored in the CCD memory 1307 is connected to the signal line 131.
1 to a serial-to-parallel (S/P) converter 1309. The seismic data from the CCD memory, which is in serial format, is converted to parallel format by S/P 1309, and is converted into first-in first-out (FIFO) data by signal line 1314.
It is sent to memory 1312. FIFO memory 131
2 is provided to compensate for the speed difference between the recirculation speed of CCD memory 1307 and the recorder speed of recorders 1321 and 1322. FIFO memory 1312 is composed of two buffers.
While one of the buffers is being read and its data displayed, the other buffer is loaded with data from CCD memory 1307.

Earthquake data is sent from FIFO memory to signal line 1317
Digital to analog (D/A) converter 1
316. Earthquake data is provided by D/A converter 1
316 into analog format and sent to a plurality of sample and hold (S/H) circuits represented by S/H circuits 1318 and 1319. In a preferred embodiment of the invention, data is sent from a digital-to-analog (D/A) converter 1316.
There are 72 S/H circuits. Two S/H circuits 1318, 1319 are shown for convenience and because the principle of the device can be illustrated using only two S/H circuits. The number of S/H circuits to which data is sent from D/A converter 1316 is determined by the number of data channels being monitored by the RTU used in the seismic survey system of the present invention. A data channel corresponds to a geooffline monitored by a particular RTU. In the present invention, four geophonic lines can be monitored by each RTU, and multiple RTUs can be monitored by 72
Used to monitor channels.

Earthquake data is sent from S/H circuits 1318 and 1319 to recorders 1321 and 1322 via low-pass filters 1324 and 1325, respectively. S/H circuit 1 using low-pass filters 1324 and 1325
The sampling frequencies of 318 and 1319 are suppressed to provide a smooth response. Recorder 1321,1
322 is preferably an oscilloscope that provides a write trace of data provided from the S/H circuits 1318 and 1319.

Data is also sent from D/A converter 1316 to data display controller 1326. Earthquake data is
Acceptable input signal 13 to CRT monitor 1329
The format is adjusted by the data display control unit 1326 to give 28.

Data display device 93 is controlled by control logic 1331. Control logic 1331 provides a plurality of control and timing signals that control the operation of data display device 93 as illustrated in FIG. Control signal 1333 is sent from control logic 1331 to buffer 1
301. Similarly, control signal 1334
is applied to the parallel-to-serial converter 1304, a control signal 1335 is applied to the CCD memory 1307,
A control signal 1336 is given to the data display control section 1326, and a control signal 1337 is given to the S/P converter 13.
09, a control signal 1338 is given to the FIFO memory 1312, and a control signal 1339 is given to the D/
A control signal 1341 is applied to the A converter 1316.
is applied to S/H circuits 1318 and 1319, and a control signal 1342 is applied to recorders 1321 and 1322.

When you want to display data obtained from RTU,
Seismic data obtained from RTU is captured by CCD channel.
Provided to memory 1307. All of the channel 1 data is sent to the CCD memory and stored, and then all of the channel 2 data is sent to the CCD memory and stored. All data from the final channel used in a particular detonation procedure is stored in the CCD memory 13.
This process continues until 07 is stored.

Data is read from CCD memory 1307 in samples. That is, sample 1 of channel 1
is read from CCD memory 1307 and sent to S/H circuit 1318. Channel 2 sample 1
is read from CCD memory 1307 and sent to the S/H circuit used for channel 2. The first sample of the final data channel is the CCD memory 130.
This continues until it is read from 7 and sent to the S/H circuit used for the final data channel.
As shown in FIG. 51, the final S/H circuit corresponds to S/H circuit 1319. After the first sample of each data channel is read from CCD memory 1307, the second sample of each channel is read from CCD memory in the same manner as described above for sample 1. all samples of all data channels are read from CCD memory 1307;
This process continues until recording is performed by a plurality of recording devices represented by recorder 1321 and recorder 1322.

A plurality of S/H circuits represented by the S/H circuit 1318 and the S/H circuit 1319 are connected to the CCD memory 13.
07 provides a means for separating the seismic data into its respective channels.

When it is desired to display data on a CRT monitor instead of recorders 1321 and 1322, recorders 1321 and 1322 are deenergized and seismic data is sent to data display control section 1326. Seismic data is displayed by CRT monitor 1329 to a particular channel number, and this display provides a quick visual indication of the operation of the seismic probe implemented in the present invention.

The data display device (DDS) is shown in Figures 52 and 5.
This can be understood in detail by referring to the timing diagram shown in FIG. FIG. 52 illustrates how data is written to the CCD memory 1307 shown in FIG. 51. CCD clock start signal 1351 is sent from the 6800 microprocessor 51 shown in Figure 2a. CCD clock start signal 1351 energizes the CCD memory illustrated in FIG. A data monitor ready signal 1353 is sent from the data display 93 to the 2900 microprocessor 74 shown in FIG. 2a. The data monitoring preparation signal 1353 is connected to the signal line 1333 shown in FIG.
is sent to bus line 94 by. A write strobe signal 1354 is sent to the data display from the 2900 microprocessor shown in Figure 2a. Data is written from the 2900 microprocessor to CCD memory 1307 in response to write strobe signal 1354.

CCD memory 1307 and data display device are CCD
Energized when clock start signal 1351 goes low. After the CCD clock start signal goes low, 150 mS is allowed to warm up the CCD memory, and then the data watch ready signal 1353 goes low indicating that data can be written to the CCD memory 1307. Data monitoring ready signal 1353 is transmitted to the 2900 microprocessor. In response to the Data Monitor Ready signal 1353 going low, the 2900 microprocessor first
Write four header words to the register associated with CCD memory 1307. Hezda language CCD memory 130
Writing to 7 causes signal 1354 to go low. Each time the write strobe signal goes low, the data monitor ready signal goes high for 8.2 μS to 16.4 μS.
After this time has elapsed, the Data Monitor Ready signal goes low indicating that the second header word can be written. This process continues until four Hebrew words have been written.

4 After writing the Hezdic language, the earthquake data will be transferred to the CCD.
Written to memory 1307. FIG. 52 illustrates writing two channels of data, each having three samples, to CCD memory 1307.
After writing 4 head words to CCD memory 1307,
An undetermined amount of time passes before data is written to CCD memory 1307. Channel 1 sample 1
Writing to CCD memory 1307 causes write strobe signal 1304 to go low. At the same time, the data monitoring ready signal remains high for a maximum of 2.1 mS.
Activate CCD memory 1307 and place sample 1 of channel 1 in the exact sector that must be written. After being placed in the correct sector, the data monitor ready signal goes low and sample 2 of channel 1 must be written to CCD memory 1307 within 1.6 μS from the time the data monitor ready signal goes low. Channel 1 sample 2
After writing to CCD memory 1307, the data monitor ready signal goes high for a maximum of 8.5 μS and then returns to low again, at which time sample 3 of channel 1 must be written to CCD memory 1307 within 1.6 μS. Must be. This process continues until all samples of channel 1 have been written to CCD memory 1307.

All samples of channel 1 are stored in CCD memory 1
307, then write all samples for channel 2 in the same way as described above for channel 1.
Write to CCD memory 1307. This process continues until all channels of data have been written to the CCD memory 1307 shown in FIG.

All channels of data are stored in CCD memory 130
7, the recorder 1 shown in FIG.
Data is read to 321, 1322 and CRT monitor 1329. A method of reading data from CCD memory 1307 is illustrated in FIG.

FIG. 53 can be easily understood in conjunction with FIG. 54. As mentioned above, the FIFO shown in Figure 51
Memory 1312 consists of two FIFO registers. As shown in FIG. 54, the output signal 1 from the S/P converter 1309 shown in FIG.
314 is provided as an input to both FIFO register 1358 and FIFO register 1359. both
Outputs from FIFO registers 1358 and 1359 are provided to register 1361. register 136
The output signal 1317 from 1 is provided to a D/A converter 1316 as shown in FIG.
The FIFO register determines the time required to read data from the CCD memory 1307 and the D/A converter 131.
This is provided to compensate for the difference in time required for the S/H devices 1318 and 1319 to sample and hold the data given from 6. As shown in FIG. 53, the data is stored in the CCD memory 13.
07 at a rate of 8 μS per sample.
Therefore, reading 72 samples from CCD memory 1307 takes 576 μS. As mentioned earlier, all samples 1 of all data channels are
Data is read from the CCD memory as sample 1 of channel 1, sample 1 of channel 2, sample 1 of channel 3, etc. until read from CCD memory 1307. If 72 channels are available, 72 samples are available and all samples 1 are read from the CCD memory before sample 2 of channel 1 is read from the CCD memory 1307.

All samples 1 of all data channels
After reading from CCD memory 1307, it takes about 160 seconds for CCD memory to find sample 2 of channel 1.
It takes 200μS from Therefore, every sample 1 of the data channel is read from the CCD memory 1307 and stored in the CCD memory 130 within a 1 mS sample rate, illustrated as the sample rate clock in FIG.
7 is ready to output sample 2 of the data channel. Every sample 1 of the data channel is stored in FIFO register 1358. All samples 2 of each data channel are stored in FIFO register 1359. When the sample rate clock goes high, the sample on channel 1
From CCD memory 1307 to FIFO register 1358
is read to. Every sample 1 of the data channel must be read from CCD memory 1307 to FIFO memory 1358 before the sample rate clock completes its cycle.

After the earthquake data represented by the first and second samples are stored in FIFO registers 1358 and 1359, respectively, the earthquake data is stored in FIFO register 1358 and 1359, respectively.
58, 1359 to S/H circuits 1318, 1319 shown in FIG. FIFO register 1358,1 has a period of 12.8 μS and is responsive to the channel update clock illustrated in FIG.
Samples are read from 359. Sample 1 is
It is applied to S/H circuit 1318 for a period of 12.8 μS, and at the end of this period S/H circuit 1318 is set to hold mode. This process continues until all available samples 1 are provided to the S/H circuits represented by S/H circuits 1318 and 1319. The first sample of every available data channel is read into the S/H circuit within a 1 mS period of the sample rate clock. As the sample rate clock cycles through, all samples 2 of the available data channels are stored in FIFO register 135.
9 to the S/H circuit, during which all samples 3 of the available data channels are simultaneously
FIFO buffer 1358 from CCD memory 1307
is read to. In this way the data is always S/
It can be supplied to the H circuit, and the speed of sending data to the S/H circuit and the speed of reading data from the CCD memory 1307 are compensated.

FIG. 55 illustrates how S/H circuits, of which S/H circuits 1318 and 1319 are representative, are addressed. The channel update clock shown in FIG. 53 is sent as one input to counter 1365. The counter 1365 has a reset input 1366.
is also given. In response to the channel update clock and reset input 1366, counter 1365 counts the number of available data channels and then begins counting again. The output from counter 1365 is provided to read only memory (ROM) 1368 and decoders 1371-1373.
Output control signals from ROM 1368 are also provided to decoders 1371-1373.

As mentioned above, 72 S/H circuits are used in data display devices. Only three S/H circuits are illustrated in FIG. The S/H circuit has three
It is divided into PC cards, each card holding 24 S/H circuits. Basically, for the first 24 channels, ROM 1368 operates to select the first PC card. For the second 24 channels, ROM 1368 selects the second PC card;
For the third 24 channels, the ROM1368
Select 3PC card. Each PC card has three decoders 1371-1373. ROM13
68 also selects which decoder to activate. Three decoders 1371 illustrated in FIG.
-1373 is on the 1st PC card, ROM1368 stores channels 1 to 8.
When reading from CCD memory 1307, decoder 1371 is selected, when channels 9 to 16 are being read from CCD memory 1307, decoder 1372 is selected, and channels 17 to 16 are selected.
When channel 24 is being read from CCD memory 1307, decoder 1373 is selected.

After the PC card and decoder are selected by the ROM 1368, the three least digit bit output from the counter 1365 is used to select which S/H circuit to activate. As shown in FIG. 55, each decoder controls eight S/H circuits. If channel 4 is being sent to the S/H circuit, decoder 1371 causes switch 1375 to close;
This also allows channel 4 to be routed to S/H circuit 1376. Similarly, each data channel
When outputting from CCD memory 1307, the specific S/H circuit of each data channel is activated in this manner. Channel 4 data is given from the CCD memory 1307 and the S/H circuit 1 consists of an operational amplifier 1378 and a capacitor 1379.
When energizing 376 and sampling the data provided by seismic data line 1320, switch 1375, which is an example of 72 switches used in the data display, is closed for 12.8 μS. After 12.8μS,
S/H circuit 1376 is set to hold mode,
The data is sent to the low pass filter associated with that particular S/H circuit as illustrated in FIG.

As before, switch 1381 is closed and operational amplifier 1384 and capacitor 1385 are closed.
The seismic data is sent to the S/H circuit 1383 consisting of. Switch 1387 is closed and data is sent to S/H circuit 1388 consisting of operational amplifier 1389 and capacitor 1391. The data from the specific channel related to each switch is
Only when data is being sent from memory 1307, 72 switches represented by switches 1375, 1381, and 1387 are closed.

The control logic 1331 illustrated in FIG.
This is illustrated in more detail in the figure. Oscillator 1401
is a 10MHz oscillator in the preferred embodiment of the invention. Output signal 1402 from oscillator 1401 is provided as a clock input to counter 1403, counter 1404, holding register 1405, and frequency divider 1407. Counter 1403 receives 10MHz output signal 1402 from oscillator 1401.
Acts as a frequency divider to divide into 18.125KHz signal 1411. Signal 1411 corresponds to the clock signal shown in FIG. 53 having a period of 12.8 μS.

Frequency divider 1407 which is a plurality of counters
acts to divide the 10MHz signal 1402 into a 2KHz signal 1412. A 2KHz signal 1412 is sent from frequency divider 1407 to counter 1414. In response to the 2KHz signal 1412, counter 1
414 provides multiple output signals with different periods. Signal 1416 from counter 1414 has a period of 8 mS, signal 1417 has a period of 4 mS, signal 1418 has a period of 2 mS,
Signal 1419 has a period of 1 mS. Signals 1416-1419 from counter 1414 are provided as inputs to multiplexer 1421. One of signals 1416-1419 is selected by multiplexer 1421 and sent as sample rate clock 1423. Sample rate clock 1423 corresponds to the sample rate clock signal illustrated in FIG.

A signal 1419 with a period of 1 mS is also sent to a frequency divider 1425. The frequency divider is
Signal 1419 having a frequency of 1000 Hz is divided by 10 to provide an output signal 1426 having a frequency of 100 Hz. Signal 1426 is used to provide line marks for recorder 1321 and recorder 1322 illustrated in FIG.

A plurality of output signals 14 from counter 1404
31 is sent as an input to ROM 1432.
Multiple outputs from ROM 1432 are provided to holding register 1405. Holding register 1405
, multiple outputs 143 from ROM 1432
7 is given as a control signal for the data display device shown in FIG.

A plurality of output signals 14 from counter 1404
31 is also sent as an input to ROM 1433. Multiple output signals 14 from ROM 1433
38 is provided as an input to the data input of counter 1404. The counter 1404 also receives data represented by a signal line 1438.
A signal 1439 representing a command to load into 04 is also sent. The counter 1404 also has a ROM 1432
A clear input 1441 from is also sent.

ROM 1432 is programmed to provide the necessary output signals in response to the count input from counter 1404. Each time the counter 1404 reaches a certain count, the ROM 1432
One of the output signals 1435 is driven to a high or low state as necessary to control the data display shown in the figure. The particular control signal output from ROM 1432 is repeated each time the counter repeats. In this manner, the numerous clock and control signals necessary to control the data display shown in FIG. 51, particularly the CCD memory 1307, are provided.

ROM 1433 is provided to allow counter 1404 to skip a portion of the count. This feature is used when it is desired to speed up certain operations on CCD memory 1307. ROM1433
It is easy to skip a portion of a count by programming and commanding counter 1404 via data line 1438 to cause counter 1404 to skip a certain count when a particular count is reached. For example, read-only memory 1433 can be programmed to cause counter 1404 to skip a count of 80 when a count of 10 is output from counter 1404.

Data display control section 1326 illustrated in FIG.
is illustrated in more detail in FIG. 51st
Signal 1 from the D/A converter 1316 shown in the figure
320 is provided as an input to amplifier 1451. Amplifier 1451 produces an output signal 1452 representing seismic data from the RTU, illustrated in FIG.
Provided to the Y input of CRT monitor 1329.

Signal 1411 from counter 1403 illustrated in FIG. 56 is sent as an input to counter 1453. Signal 1411 has a period of 12.8 μS.
In response to input signal 1411, counter 1453
provides a plurality of output signals represented as signals 1454. The output signal from the counter 1453 is sent to a comparator 1456 and a digital gain ranger 145.
8, comparator 1459, given as input to register 1461. Output 1 from comparator 1459
463 is provided as a clock signal to register 1461. A plurality of outputs from register 1461, shown as signal lines 1464, are provided as inputs to comparator 1459 and ROM 1466.

As previously mentioned, the data is shown in FIG. 51 as sample 1 of channel 1, sample 1 of channel 2, sample 1 of channel 3, etc. until sample 1 of the final channel is read from D/A converter 1316. It is output from the D/A converter 1316. Signal 1454 illustrated in FIG. 57 represents the particular channel being read from D/A converter 1316. Therefore, the A input to comparator 1459 represents the channel count. Comparator 1
The output from 459 is used as a clock signal 1463 for register 1461. register 146
1 is also provided with a channel output signal 1454.

As an example of the operation of comparator 1459 and register 1461, consider a seismic survey device having only three channels. When D/A converter 1316 provides sample 1 of channel 1 as an output, channel indication signal 1454 represents 1. This 1 is comparator 1459
is applied to the A input of However, the register does not pass the channel count signal 1454 to the comparator 14.
The B input of comparator 1459 is still 0 since it is not clocked to feed into comparator 1459. Therefore, the A input is greater than the B input, and clock signal 1463 energizes register 1461 to transfer the input count represented by channel count signal 1454 to the B input of comparator 1459. After this transfer A
Input is equal to B input.

Sample 1 of channel 2 is D/A converter 131
6, the A input to comparator 1459 becomes 2. The A input is again greater than the B input and clock signal 1463 enables register 1461 to load count signal 1454 to the B input of comparator 1459. When this is done,
The A input is again equal to the B input. Sample 1 of channel 3 is digital to analog converter 131
6, the A input of comparator 1459 becomes 3. Again, the A input is greater than the B input, and clock signal 1463 causes register 1461 to output channel count signal 1454 to comparator 1459's B input.
Allows loading into input. This again makes the A input equal to the B input.

After sample 1 of channel 3 is read from digital-to-analog converter 1316, channel 1
Sample 2 is digital-to-analog converter 13
16, the channel count signal 14
54 returns to the count of 1. A input is B again
Note that the output signal 1464 from register 1461, which is not greater than the input, therefore represents the maximum number of channels being sent from the RTU. In response to signal 1464, read only memory 1466 provides a plurality of output signals 1467 to digital gain ranger 1458 representing the number of available channels.

The digital gain ranger 1458
It is represented by count signal 1454 and provides a sweep signal for automatic gain control (AGC) circuit 1471. If the output from digital gain ranger 1458 is always sent to the least significant bit input of D/A converter 1472, the output level from D/A converter 1472 will be equal to the number of channels of data being provided to the data display device. , the output from D/A converter 1472 has a dynamic range that is too large for AGC circuit 1471. Channel count signal 1454 is sent to D/A converter 147
Digital gain ranger 1458 addresses this dynamic range problem by controlling how it is applied to 2. Channel count signal 145 if only some channels of data are available
4 is the control signal 14 from the read-only memory 1466
67, it is applied to the maximum digit bit input of the D/A converter 1472. Digital gain ranger 1458 essentially consists of a plurality of gates controlled by an output signal 1467 from read-only memory 1466 to energize a channel count signal applied to a particular input of D/A converter 1472. . Using the most significant bit input of D/A converter 1472 provides a signal with a dynamic range that meets the input requirements of AGC circuit 1471.

Regardless of the number of channels of data available
It is desirable to completely fill the CRT screen.
To do this, the voltage swing of the sweep voltage must be the same regardless of whether some data is available or 72 channels are available. This is the CRT shown in Figure 51.
Output signal 147 from D/A converter 1472 to provide a constant sweep voltage 1470 to monitor 1329
AGC circuit 1 that provides constant voltage fluctuation in response to 3.
This is accomplished by using 471.

Input to CRT monitor 1329 is used to highlight particular data channels of interest. This is accomplished by applying channel count signal 1454 to the B input of comparator 1456. A second input 1474 representing the desired channel to be emphasized is provided to the A input of comparator 1456. In a preferred embodiment of the invention, signal 1474
is applied by a thumbwheel switch. Output signal 147 from comparator 1456 when channel count signal 1454 is equal to signal 1474
5 is energized. Signal 1475 is provided to a DC to DC converter 1476 which provides an output signal 1478 to the Z input of CRT monitor 1329.

The AGC circuit 1471 shown in FIG.
This is illustrated in more detail in FIG.

A signal 1473 from the D/A converter 1472 shown in FIG. The output from full wave rectifier 1481 is provided to integrator 1482. Integrator 148
The output signal 1480 from 2 is sent as one input to divider 1483. A reference voltage 1484 is also given as an input to the divider 1483. Reference voltage 1484 is divided by the output from integrator 1482 to provide an output signal 1486 from divider 1483 which is provided as a second input to multiplexer 1485. The output from multiplexer 1485 is the signal 1 shown and described above in FIG.
It is 470.

Since the signal 1473 is basically the reference voltage 1484 divided to give the signal 1486,
As the signal strength of signal 1473 increases, signal 14
The signal level at 86 decreases. Similarly, signal 14
As the signal strength of signal 73 decreases, the signal strength of signal 1486 increases. In this manner, a substantially constant sweep signal 1470 may be provided to the CRT monitor 1329 illustrated in FIG.

Divider 1 AD532 manufactured by Analog Devices
483 and multiplexer 1485. The circuitry available for the full wave rectifier 1481 and integrator 1482 shown in FIG. 58 is shown in FIG.

Referring to FIG. 59, signal 1473 is sent to the inverting input of operational amplifier 1491. The output of operational amplifier 1491 is connected to diode 1492 and resistor 14.
It is grounded via 93. The non-inverting input of operational amplifier 1491 is also grounded via resistor 1493.
The output from operational amplifier 1491 is also connected to diode 1
Operational amplifier 149 via 496 and resistor 1497
It is also coupled to the inverting input of 5. Operational amplifier 149
The non-inverting input of 5 is connected to ground via resistor 1498. As shown in FIG. 58, the output from operational amplifier 1495 forming signal 1480 is connected to resistor 1
499 and capacitor 1501 to the inverting input of operational amplifier 1495.
Output signal 1480 from operational amplifier 1495 is also fed back through resistor 1502 to the inverting input of operational amplifier 1491.

The CRS countdown circuit 65 shown in FIG. 2a is illustrated in more detail in FIG. 60.
CRS countdown circuit 65 is used to provide status and interrupt signals to the 6800 microprocessor, shown as computer unit 51 in FIG. 2a. Status and interrupt signals provided by CRS countdown circuit 65 are provided in response to addresses and commands from the 6800 microprocessor. Basically, the CRS countdown circuit 65 is used to prevent a complete shutdown of the 6800 microprocessor due to a failure of some portion of the seismic survey apparatus illustrated in FIGS. 2a and 2b. 6800 microprocessor CRS
The time required for a certain operation is loaded into the countdown circuit 65. CRS countdown circuit 65 provides an interrupt and status signal at the end of this time.

Referring to Figure 60, as illustrated in Figure 2a
Addresses and commands from the 6800 microprocessor to energize CRS countdown circuit 65 are provided to decode circuit 2201. In response to the address and command from the 6800 microprocessor, the decode circuit 2201 sends an activation signal 2213 to the counter 2202 and an activation signal 221 to the counter 2203.
4. Give an energizing signal 2211 to the energizing circuit 2204 and an energizing signal 2212 to the output circuit 2205.
Counter 2202 is a 6800 microprocessor.
1μsφ2 clock signal to 1mS clock signal 22
15. counter 22
A 1 mS clock signal 2215 from 02 is provided as a clock signal to counter 2203.

The data line from the 6800 microprocessor is the 6th
It is used to load the time required for a certain operation into the CRS countdown circuit 65 shown in FIG. The data line is sent to inversion circuit 2206.
Basically, it is supplied by National Semiconductor.
The inverting circuit 2206, which is a group of 74LS04, connects the data line from the 6800 microprocessor to the signal line 2217.
is given to the counter 2203 by counter 22
03 counts the time loaded by the data line from the 6800 microprocessor. counter 2
When 203 reaches a certain count, an output signal 2219 is sent from the counter 2203 to the output circuit 220.
5 and is sent to the energizing circuit 2204. Energizing signal 2211 from decoding circuit 2201 and counter 22
In response to the output from 03, energizing circuit 2204 energizes output circuit 2205 via signal line 2221 and sends interrupt signal 2207 and status signal 2208 to 6800.
Give it to the microprocessor. Interrupt signal 2207
is provided to the 6800 microprocessor by the interrupt request (IRQ) line. Status signal 2208 is provided to the 6800 microprocessor by the D7 data line.

The energizing circuit 2204 also sends an energizing signal 2222 to the counter 2202. Output 2220 from output circuit 2205 is coupled to enable circuit 2204 .

Decode circuit 2201 shown in FIG. 60 is shown in more detail in FIG. 61. Referring to Figure 61, the A7 address line from the 6800 microprocessor is routed through inverter 2224 to the NAND
Provided as the first input to gate 2225.
The A6 address line from the 6800 microprocessor passes through inverter 2226 to NAND gate 22.
It is given as the second input to 5. The A4 and A5 address lines from the 6800 microprocessor are
Provided directly as third and fourth inputs to NAND gate 2225. The output from NAND gate 2225 is passed through inverter 2227 to NAND
Provided as the first input to gate 2228.
Input/output from the 6800 microprocessor (I/
The O) line is provided as the second input to AND gate 2228. The output from AND gate 2228 is NAND gate 2229, NAND gate 223
0 as both first inputs.

The A3 address line from the 6800 microprocessor is provided as the first input to AND gate 2231. The A2 address line from the 6800 microprocessor is provided as the second input to AND gate 2231 via inverter 2232.
The output from AND gate 2231 is provided as the second input to both NAND gates 2229 and 2230.

The φ2 clock from the 6800 microprocessor is connected to NAND via inverters 2234 and 2235.
Sent as the third input of both gate 2229 and NAND gate 2230. The φ2 clock from the 6800 microprocessor is also connected to the inverter 2234,
2235 to the signal 221 illustrated in FIG.
It is also provided as an output signal 2213A forming part of .3.

The read/write (R/) signal from the 6800 microprocessor is routed through inverter 2237.
Provided as the fourth input to NAND gate 2230. (R/) signal is also inverter 2237
and NAND gate 2 via inverter 2238
A fourth input to 229 is also provided. NAND
The output from gate 2229 is applied to the A selection input of decoder 2241. NAND gate 223
The zero output is sent to the Y0 input of decoder 2241.

The A0 address line from the 6800 microprocessor is passed through an inverter 2242 to a decoder 2241.
is sent to the B selection input of and the Y1 output of the decoder 2241. The A0 address line from the 6800 microprocessor is also provided via inverter 2242 as an output signal 2214A forming part of signal 2214 illustrated in FIG.

The A1 address line from the 6800 microprocessor passes through inverter 2243 to decoder 2241.
is sent to the C selection input and the Y2 port. The reset (RST) signal from the 6800 microprocessor is passed through AND gate 224 through 2244 and 2245.
6 as the first input. Inverter 22
The reset signal output from 45 is output signal 221 which forms part of signal 2214 illustrated in FIG.
4D, a signal 2211E forming part of the signal 2211 shown in FIG. 60, and an output signal 2212C forming part of the signal 2212 shown in FIG.
It is also given as

The Y7 output from decoder 2241 is provided as output signal 2211A, which forms part of signal 2211 shown in FIG. 60, and output signal 221A, which forms part of signal 2212 shown in FIG.
Also given as 2A. The Y3 output from decoder 2241 is also provided as output signal 2211B, which forms part of signal 2211 illustrated in FIG. Y5 output from decoder 2241 is
Provided as the first input to AND gate 2248. The Y6 output from decoder 2241 is provided as a second input to AND gate 2246 and as a second input to AND gate 2248. The Y6 output from decoder 2241 is output signal 2214 which forms part of signal 2214 illustrated in FIG.
It is given as B. The output signal from the AND gate 2248 is the three output signals 2211C, 221
2B, 2214C, output signal 2211C
forms part of the signal 2211 shown in FIG. 60, output signal 2212B forms part of the signal 2212 shown in FIG.
forms part of signal 2214 illustrated in FIG. The output signal from AND gate 2246 also provides two output signals 2211D and 2213B. Signal 2211D is signal 2 illustrated in FIG.
211 and signal 2213B forms part of signal 2213 illustrated in FIG.

The counter 2203 shown in FIG.
The figures are shown in more detail.

Signal 2214C, illustrated in FIG.
57 count/load input. The signal 2214A shown in FIG.
3 and the selection input of data selector 2254. The signal 2214B shown in FIG.
Given as input to load input. Signal 2215, illustrated in FIGS. 60 and 64, is provided as an input to the first clock input of counter 2251. The 7-4 data line shown in FIG.
It is applied to the A1-A4 data inputs of the selector 2253. The 3-0 data lines shown in FIG. 60 are applied to the A-D data inputs of counter 2252 and the A1-A4 data inputs of data selector 2254. Reset signal 22 illustrated in FIG.
14D is counter 2251, 2252, 225
6,2257 clear input.

The second clock input of counter 2251 is coupled to the Qa data output of counter 2251. The first clock input of counter 2252 is
51 Qd data output. counter 2
252's second clock input is the second clock input of counter 2252.
Combined with Qa data output. counter 2252
The Qd output of is coupled to the first clock input of counter 2256.

The strobe inputs of both data selector 2253 and data selector 2254 are grounded. Data selector 2253 and data selector 225
Both B1-B4 inputs of 4 are coupled to +5V power supply 2259 via resistor 2261. The Y1-Y4 data outputs from data selector 2253 are coupled to the A-D data inputs of counter 2256. The Y1-Y4 data outputs from data selector 2254 are coupled to the A-D data inputs of counter 2257.

A second clock input of counter 2256 is coupled to the Qa output of counter 2256. counter 2
The first clock input of 257 is the first clock input of counter 2256.
Coupled to Qd output. The second counter 2257
The clock input is coupled to the Qa output of counter 2257. The Qd output of the counter 2257 is the 60th
Inverter 22 as signal 2219 illustrated in the figure.
62.

The D0-D7 data lines from the 6800 microprocessor are used to load counters 2252 and 2251 with the time required for the operation. Data selectors 2253, 2254 and counter 225
6,2257 as well as counters 2251, 225
2 is activated by the output signal from the decoding circuit 2201 shown in FIG. Count circuit 2
A clock signal 203 is provided from counter 2202.

The counter 2202 shown in FIG.
The figures are shown in more detail. Signal 2222A, illustrated in FIG. 64, is applied to both the count-enable parallel (CEP) and count-enable trickle (CET) inputs of counter 2265. Signal 2222A also connects the CEP input of counter 2266 and counter 22
It is also given to the CEP input of 67. The signal 2222B shown in FIG.
66,2267 parallel energized PE inputs.
The signal 2213A shown in FIG.
265, 2266, and 2267 clock inputs. Signal 2213B shown in FIG. 61 is applied to the clear inputs of counters 2265, 2266, and 2267. The terminal count (TC) output from counter 2265 is CET of counter 2266.
given to the input. TC from counter 2266
The output is provided to the CET input of counter 2267. The TC output from counter 2267 is provided as output signal 2215 shown in FIG.

As previously mentioned, the counter illustrated in FIG. 63 is used to generate the 1 mS clock signal 2215 from the 1 μs φ2 clock signal of the 6800 microprocessor. Counter 2265, 2266, 2
The integrated circuit used in the 267 is a 93L10 manufactured by Fairchild Semiconductor.

The energizing circuit 2204 shown in FIG.
The figures are shown in more detail. Signal 2211C shown in FIG. 61 is applied to the set input of flip-flop 2071. flipflop 22
The D input of 71 is grounded. The signal 2219 shown in FIGS. 60 and 62 is connected to flip-flop 22.
71 clock input. Signal 2211B illustrated in FIG. 61 is provided as the first input to AND gate 2272. The signal 2211E, also shown in FIG.
72. The output from AND gate 2272 is the flip-flop 227
1 reset input. The Q output from flip-flop 2271 is output signal 222 which forms part of output signal 2221 illustrated in FIG.
1A and is also provided as output signal 2222A forming part of signal 2222 illustrated in FIG.

The set input of flip-flop 2273 is coupled to +5V power supply 2274 through resistor 2275. +5V power supply 2274 also provides output signal 2222B through resistor 2275. Signal 2222B forms part of output signal 2222 illustrated in FIG. Signal 22 illustrated in FIGS. 60 and 65
20 is applied to the D input of flip-flop 2273. Signal 2211A, shown in FIG. 61, is applied to the clock input of flip-flop 2273. Signal 2211D, shown in FIG. 61, is applied to the reset input of flip-flop 2273. The output from flip-flop 2273 is provided as output signal 2221B, which forms part of signal 2221 illustrated in FIG.

The output circuit 2205 shown in FIG.
The figures are shown in more detail. Signal 2212A, illustrated in FIG. 61, is provided to the enable input of tristate buffer 2287 via inverter 2286. The set input of flip-flop 2281 is coupled to +5V power supply 2280 through resistor 2282. Signal 2221A illustrated in FIG.
is applied to the D input of flip-flop 2281. Signal 2219, shown in FIG. 60, is applied to the clock input of flip-flop 2281.
Signal 2221B shown in FIG. 64 is provided as the first input to AND gate 2283. 6th
The signal 2212C shown in Figure 1 is the AND gate 2
283 as the second input. The output from AND gate 2283 is AND gate 2284
is coupled as the first input to. Signal 2212B, shown in FIG. 61, is provided as the second input to AND gate 2284. AND gate 228
The output from 4 is coupled to the reset input of flip-flop 2281.

The Q output from flip-flop 2281 is used as output signal 2220 and is also a tristate
It is also provided as an output signal 2208 shown in FIG. 60 via a buffer 2287. The output from flip-flop 2281 is provided via tristate buffer 2289 as output signal 2207 shown in FIG. The output from flip-flop 2281 is also connected to inverter 2288.
to the energization input of tristate buffer 2289 via .

Switch and display interface 43 and operator display panel 41 associated with switch and display interface 43, both shown in FIG. 2a.
A portion of this is shown in more detail in FIG. Referring to FIG. 66, address and command lines from the 6800 microprocessor are provided as inputs to address and command decode buffer circuit 2401. In response to addresses and commands from the 6800 microprocessor, the address and command decode buffer circuit 2401 decodes the switch and display interface 43 and the portion of the operator control display panel 41 associated with the switch and display interface 43. Provides a plurality of output signals used to control functions. In response to addresses and commands from the 6800 microprocessor, the address and command decode buffer circuit 2401
Control signals to select inputs of decoders 2402-2404, enable signals to enable inputs of buffers 2406, 2407, peripheral interface adapter 2
409 energization input (E), chip selection 2 input (CS2),
Register selects 0 (RS0) and 1 (RS1) provide multiple output signals to the read/write ((R/) inputs.

Address and command decode/buffer circuit 24
In response to the output signal from 01, the 1-to-8 decoder 2402 provides a plurality of energization outputs to a plurality of thumbwheel switches located on the operator control display panel 41 illustrated in FIG. 2a. Thumbwheel switch 2411 provides one means by which an operator can provide commands and data to the 6800 microprocessor. thumbwheel switch 2
Data from 411 is provided to the input of buffer 2406.

Address and command decode/buffer circuit 24
In response to the output signals from 01, 1-to-8 decoder 2403 provides a plurality of activation signals to rotary switch 2412 located on operator control display panel 41 illustrated in FIG. 2a. A plurality of rotary switches 2412 provide another means by which an operator can direct data and commands to the 6800 microprocessor.
The data from the rotary switch is the rotary switch 241.
2 to the input of buffer 2406.

The output from buffer 2406 is coupled to the D0-D7 data lines of peripheral interface adapter 2409. The output from buffer 2406 is also sent to the input of buffer 2407 and the input of buffer 2414. Buffer 2406 allows thumbwheel switch 2411 and rotary switch 241
2 to the data input of the peripheral interface adapter and the input of the buffer 2407. The output of buffer 2407 is coupled to a 6800 microprocessor. Buffer 2407 now connects the 6800 microprocessor's bidirectional data lines to peripheral interface adapter 2409.
Provides means for coupling to thumbwheel switch 2411 and rotary switch 2412 along with D0-D7 data lines.

Address and Example Decode Buffer Circuit 240
1 to 8 decoder 2 in response to the output signal from 1
404 provides a plurality of energizing signals to the energizing input of the display section 2416. The display section 2416 is composed of a plurality of light emitting diode numeric display sections. Output from buffer 2414 is coupled to data input from display 2416. The buffer 2414 thereby transfers the data from the thumbwheel switch 2411 or rotary switch 2412 to the display section 2416.
provide a means for displaying the information. Data from the 6800 microprocessor can also be displayed on display 2416. Display portion 2416 is located on operator control display panel 41 illustrated in FIG. 2a.

The reset line from the 6800 microprocessor is coupled to the peripheral interface adapter's reset input. The interrupt line from the 6800 microprocessor is coupled to the A, B interrupt inputs of peripheral interface adapter 2409.

peripheral interface adapter 240 from the operator using a plurality of pushbutton switches 2418.
Give data to 9. The data output of switch 2418 is provided to the input of encoder circuit 2419. The 2419 output of the encoder circuit is provided to section A of the peripheral data line of the peripheral interface adapter 2409. The data appearing on the peripheral data line of peripheral interface adapter 2409 is
09 D0-D7 data lines to the 6800 microprocessor. The data appearing on the peripheral data line of peripheral interface adapter 2409 is also displayed on display section 2416 as necessary.

Basically, the circuit shown in Figure 66 allows an operator to input data and commands using multiple switches.
6800 microprocessor. These data and commands are displayed by the operator as needed, as well as data from the 6800 microprocessor. Addresses and commands from the 6800 microprocessor are sent via thumbwheel switch 2411 and rotary switch 24.
12. switch 24
18 is always in an energized state. Accordingly, the circuit illustrated in Figure 66 allows an operator to control the operation of the seismic survey device illustrated in Figures 2a and 2b by means of a plurality of switches available on the operator control display panel 41 illustrated in Figure 2a. provide the means to do so.

The address and command decode buffer circuit 2401 shown in FIG. 66 is shown in more detail in FIG. Referring to FIG. 67, both E1 and E2 energizing inputs of buffer 2421 are grounded.
The φ2 clock signal from the 6800 microprocessor is coupled to the A1 address input of buffer 2421. The read/write (R/) signal from the 6800 microprocessor is coupled to the A2 address input of buffer 2421. The A2 address line from the 6800 microprocessor is coupled to the A3 address input of buffer 2421. The A3 address line from the 6800 microprocessor is coupled to the A4 address input of buffer 2421. The A1 address line from the 6800 microprocessor is coupled to the A5 address input of buffer 2421. The A0 address line from the 6800 microprocessor is A6 of the buffer 2421.
Combined with address input.

The Y1 output from buffer 2421 is provided as the first input to NAND gate 2422 and as the first input to NAND gate 2423. The Y1 output from buffer 2421 is also sent to the energization input of peripheral interface adapter 2409 illustrated in FIG. From Batsuhua 2421
The Y2 data output is sent to the read/write (R/) input of peripheral interface adapter 2409. The Y2 output from buffer 2421 is also the 66th
It is also sent to the decoder 2404 shown in the figure.
It is also sent to the first input to NAND gate 2424. The Y3 output from buffer 2421 is sent as both inputs to decoders 2402 and 2403 illustrated in FIG. 66, and also as the first input to NOR gate 2425. The Y4 output from buffer 2421 is sent as both inputs to decoders 2402 and 2403, and also as the second input to NAND gate 2422. Batsuhua 2421
The Y5 output from is sent to the register select 1 (RS1) input of peripheral interface adapter 2409. The Y6 output from buffer 2421 is coupled to the register select 0 (RS0) input of peripheral interface adapter 2409.

The A4 address line from the 6800 microprocessor is coupled to the input of inverter 2427. The output of the inverter 2427 is the NAND gate 2422
is also sent as a third input to inverter 242.
8 as the second input to NAND gate 2423.

The first input of the NAND gate 2429 is the resistor 24
32 to the +5V power supply 2431.
The A5 address line from the 6800 microprocessor passes through inverter 2433 to NAND gate 24.
29 as the second input. The input/output (I/O) lines from the 6800 microprocessor are
Sent as third input to NAND gate 2429. The A6 address line from the 6800 microprocessor is sent as the first input to NOR gate 2434. The A7 address line from the 6800 microprocessor is provided as the second input to NOR gate 2434. The output from NOR gate 2434 is provided as the fourth input to NAND gate 2429. The output from NAND gate 2429 is passed through inverter 2435 to NAND gate 2
As the fourth input to 422, also NAND gate 2
423 as the third input. NAND
A fourth input of gate 2423 is coupled to +5V power supply 2436 via resistor 2437.

The output of NAND gate 2422 is sent to decoder 2404 illustrated in FIG. 66. The output from NAND gate 2422 is also NAND gate 24
As the first input to 38, also NOR gate 242
It is also provided as a second input to 5. The output from NAND gate 2423 is NAND gate 243
8 and also to decoders 2402 and 2403 shown in FIG.

The output of NAND gate 2438 is provided as a second input to NAND gate 2424.
The output of NAND gate 2424 is provided to buffer 2407 shown in FIG. 66, and is also provided as the first input to NAND gate 2442 via inverter 2441. NOR gate 242
5 output is NAND via inverter 2444
Provided as a second input to gate 2442.
The output of the NOR gate 2425 is also connected to the inverter 24
Peripheral Interface Adapter 2 via 44
It is also coupled to the Chip Select 2 (CS2) input of 409. The output of NAND gate 2442 is provided to buffer 2406 shown in FIG.

The roll-along panel interface 37, both shown in FIG. 2a, and the portion of the operator control display panel 41 associated with the roll-along panel interface 37 are shown in more detail in FIG. 68. be. The operator control display panel provides a visual indication of the programmed propagation profile of the seismic survey system of the present invention. The data lines from the 6800 microprocessor provide the required information.
Used to drive the LED display and alphanumeric display.

Referring to FIG. 68, the D0-D7 data lines from the 6800 microprocessor are fed to the input side of buffer 2451. The buffer data line from the 6800 microprocessor is routed from the output of buffer 2451 to the input of driver 2452. From the output of driver 2452, data lines from the 6800 microprocessor are sent to an alphanumeric display 2453 and a light emitting diode (LED) driver 2454.
From the LED driver 2454, data lines from the 6800 microprocessor are sent to a plurality of light emitting diodes located in the LED display 2455.
Data lines from the 6800 microprocessor are used to drive both the alphanumeric display 2453 and the light emitting diodes located in the LED display 2454.

The A0 address line from the 6800 microprocessor passes through inverter 2457 to register 2458.
is sent to the A0 input of The A1 address line from the 6800 microprocessor is routed through inverter 2459 to the A1 input of register 2458.
The A2 address line from the 6800 microprocessor passes through inverter 2461 to register 2458.
Sent to A2 input. The A3 address line from the 6800 microprocessor is provided as the first enable input of register 2458 through inverter 2462. The A4 address line from the 6800 microprocessor is connected to register 24 via inverter 2463.
58 is provided as a second biasing input to 58.

The φ2 clock signal from the 6800 microprocessor is provided as the first input to NAND gate 2464. Input from 6800 microprocessor/
The output (I/O) line is provided as a second input to NAND gate 2464. The read/write (R/) line from the 6800 microprocessor is provided as the third input to NAND gate 2464.
The A7 address line from the 6800 microprocessor passes through inverter 2465 to NAND gate 24.
64 as the fourth input. The A6 address line from the 6800 microprocessor is sent as the fifth input to NAND gate 2464. The A5 address line from the 6800 microprocessor is provided as the sixth input to NAND gate 2464 through inverter 2466. The reset line from the 6800 microprocessor is connected to NAND gate 246.
It is given as the seventh input to 4. The eighth input of NAND gate 2464 is coupled to +5V power supply 2467.

The output signal from NAND gate 2464 is provided as a third enable signal to register 2458;
It is also applied to both inputs of AND gate 2469.
The output of AND gate 2469 is AND gate 247
1 and is also coupled directly to one input of resistor 2472.
It is also coupled to the second input of the AND gate 2471 via an RC circuit composed of a capacitor 2473 and a capacitor 2473. The output from AND gate 2471 is given as an activation signal to driver 2452. The output from register 2458 is the LED driver 24
54 as an energizing signal.

Operator control display panel 41 shown in FIG. 2a
When it is desired to set up a display on the roll-along status display located in the roll-along panel interface 37 shown in FIG.
Activated by address and command from 6800 microprocessor. In particular, the 6800 shown in Figure 68
The A5-A7 address lines and command lines from the microprocessor are used to energize register 2458 and are also used to energize driver 2452. When driver 2452 is energized,
Data on data lines D0-D7 from the 6800 microprocessor is sent to alphanumeric display 2453.
Data is also sent to LED driver 2454.
When LED driver 2454 is energized in response to the output signal of register 2458, data is output from LED
It is transferred to the display section 2455. In this way,
A status display providing visual identification of the propagation line configuration of the seismic system is provided to the operator at an operator control display panel 41 illustrated in FIG. 2a.

The self-scanning interface 33 shown in FIG. 2a is illustrated in more detail in FIG. 69. The portion of operator control display panel 41 associated with self-scanning interface 33 is also illustrated in FIG. Referring to FIG. 69, the D0-D7 data lines from the 6800 microprocessor are coupled by signal line 2614 through data buffer 2611 to refresh memory 2612. The A8-A15 address lines from the 6800 microprocessor are provided to address decode circuit 2615. 6800
Read/write from microprocessor (R/)
The valid memory address (VMA) line, the φ2 clock line, and the 2φ2 clock line are also sent to the address decode circuit 2615. In response to addresses and commands from the 6800 microprocessor,
The decoding circuit 2615 receives three activation signals 261
Gives 6,2617,2618. energizing signal 26
16 is applied from the address decode circuit 2615 to the refresh memory 2612. signal 2
617 is given as an enable signal to data buffer 2617. Signal 2618 is provided as an enable signal to address multiplexer 2619.

The A0-A7 address lines from the 6800 microprocessor are coupled as inputs to address multiplexer 2619. A0−A7 address lines are
Used to control the locations in refresh memory where data is written to or read from the 6800 microprocessor.

Reference time generator 2621 provides a plurality of clock signals used in the self-scanning interface illustrated in FIG. Reference time generator circuit 26
21 is given 2 clocks, φ2 clock, and 2φ2 clock from the 6800 microprocessor. Reference time generator 2621 is also provided with a reset (RST) line from the 6800 microprocessor. Output signal 2623 from reference time generator 2621 is provided as an input to dot counter circuit 2624. The dot counter circuit is a display device 26.
22 sweeps and is also used to provide part of the address of the character displayed on display 2622. Output signal 2625 from dot counter circuit 2624 is provided as an input to address multiplexer 2619, character generator 2626, character counter 2627, and driver 2628. The output from the driver 2628 and the dot counter 2624 is connected to the signal line 263.
1 to the display device 2622.

Reference time generator 2621 provides one address signal to address multiplexer 2619.
Enable signal 2644 is sent from reference time generator 2621 to register 2636. Reset signal 26
45 is provided from reference time generator 2621 to both master reset (MR) of dot counter 2624 and character counter 2627.

Character counter 2627 is used to provide a portion of the address of the character displayed on display 2622. Output signal 2632 from character counter 2627 is provided as an input to driver 2628 and is also provided as an input to address multiplexer 2619. character counter 2627
An output signal 2632 from is provided to the display device 2622 via a driver 2628 and a signal line 2631.

Output signal 2633 from address multiplexer 2619 is provided as an input to refresh memory 2612. address signal 2633
Either the A0-A7 address lines or signals 2632, 2641, 2625 from the 6800 microprocessor are selected and sent to address multiplexer 2.
619 to the refresh memory 2612, or indicates the location where the data is to be written or read from the display device 2622.
Corresponds to the position to be displayed.

Output signal 2634 from refresh memory 2612 is provided as an input to character generator 2626. The output from the refresh memory 2612 is also passed through the data buffer 2611 to 6800.
coupled to a microprocessor. In this manner, data is read from refresh memory 2612 to the 6800 microprocessor as needed.

Character generator 2626 is used to generate binary addresses that determine which indicators on display 2622 are activated. This binary address is also sent to dot counter 26 in response to output signal 2634 from refresh memory 2612.
is generated in response to an output signal 2625 from 24. The binary address from character counter 2626 is provided to register 2636 by signal line 2635. Output from the register is provided to display device 2622 via signal line 2637.

Signal 2631 is used to sweep display device 2622. While sweeping the display, the character generator 262
Display device 262 in response to the binary address from 6
Each indicator on 2 is activated. In this way,
It is now possible to send data from the 6800 microprocessor to a display device 2622 located on the operator control display panel 41 shown in FIG. becomes.

The reference time generator 2621 shown in FIG. 69 is shown in more detail in FIG. 70. Referring to Figure 70, the 2
The clock is provided as the first input to NAND gate 2651. The φ2 clock from the 6800 microprocessor is sent to the clock input of counter 2652. 2φ2 clock is NOR gate 26
53 as the first input. counter 2
The 652's count-enabled parallel (CEP) input, count-enabled trickle (CET) input, and parallel-enabled (PE) input all connect to the +5V power supply 265 through a resistor 2655.
Combined with a high state of 4.

The reset signal (RST) from the 6800 microprocessor is sent to the master reset (MR) of counter 2652 and counter 2651 via inverters 2657 and 2658. The reset signal (RST) from the 6800 microprocessor is also sent via inverters 2657, 2658, and 2662 to the master reset (MR) of dot counter 2624 and character counter 2627 shown in FIG.

Q0 parallel output from counter 2652 is 1:16
Sent to the A0 input of decoder 2663. The Q0 output from counter 2652 is also the signal 2 to address multiplexer 2619 illustrated in FIG.
Also given as 641A. counter 2652
Q1 parallel output from 1 to 16 decoder 2663
A1 input and also as signal 2641B to address multiplexer 2619. The Q2 output from the counter 2652 is sent to the A2 input of the 1-to-16 decoder 2663, which also provides the signal 26
Address multiplexer 2619 as 41C
It is also given to The Q3 output from counter 2652 is coupled to both inputs of NAND gate 2665;
It is also provided as a second input to NOR gate 2653.

The output from NAND gate 2665 is sent to the clock input (CP) of counter 2661. The count-enable parallel (CEP) input, counter-enable trickle (CET) input, and parallel input (PE) of counter 2661 are all connected to the +5V power supply 266 from resistor 2667.
6. Q0 from counter 2661,
The Q1 outputs are provided as first and second inputs to NOR gate 2669, respectively. The Q2 and Q3 outputs from counter 2661 are coupled as first and second inputs to NOR gate 2671, respectively. counter 266
The Q3 output from 1 is also sent to the clock input of dot counter 2624 shown in FIG.

The output from NOR gate 2669 is passed through inverter 2672 to the first NOR gate 2673.
given as input. The output from NOR gate 2671 is provided as a second input to NOR gate 2673 via inverter 2674.
The output from NOR gate 2673 is coupled as a third input to NAND gate 2651.

Output from NAND gate 2651 is 1:162
663's A3 input. The 0-3 output from the 1-to-16 decoder 2663 is provided as an enable signal 2644 to the register 2636 shown in FIG.

Address decode circuit 2 shown in FIG.
615 is illustrated in more detail in FIG. Referring to FIG. 71, the A11 address line is provided as the first input to NOR gate 2681.
The A10 address line is the second to NOR gate 2681.
given as input. The output from NOR gate 2681 is provided as the first input to NAND gate 2682. The A9 address line is provided as the first input to NOR gate 2683. The A12 address line is coupled as a second input to NOR gate 2683. The output from NOR gate 2683 is coupled as a second input to NAND gate 2682. A8 address line is NAND gate 26
82 is coupled directly as the third input to 82. The A13 address line is coupled as the first input to NOR gate 2684. The A14 address line is coupled as a second input to NOR gate 2684. NOR
The output from gate 2684 is NAND gate 26
82. The A15 address line is coupled directly as the fifth input to NAND gate 2682. The valid memory address (VMA) line is the sixth,
They are combined as the seventh and eighth inputs. The output from NAND gate 2682 is passed through inverter 2685 as the first input to NAND gate 2686.
It is also provided as the first input to NAND gate 2687. The read/write (R/) line is provided as a second input to NAND gate 2687 via inverter 2688 and to NAND gate 26 via inverter 2688 and inverter 2689.
86 as a second input.

The φ2 clock signal is applied via inverter 2689 as signal 2618 shown in FIG. φ2 clock signal is also inverter 2689
and NOR gate 26 via inverter 2690
As the first input to 91, also the NAND gate 26
86 as the third input.

The 2φ2 clock signal is provided as a second input to NOR gate 2691 via inverter 2693. The output from NOR gate 2691 is
Coupled as the third input to NAND gate 2687. The output from NAND gate 2687 is
Refresh memory 261 illustrated in FIG.
69th sent to read/write (R/) input of 2
The signal 2616 illustrated in the figure. signal 2
616 writes data from the 6800 microprocessor to the refresh memory 2612, or writes data from the refresh memory 2612 to the 6800 microprocessor.
Used to control reading to the microprocessor.

The output signal from NAND gate 2686 is illustrated in FIG.
A signal 2617 is sent from 615 to data buffer 2611. Data buffer 2611
is activated by signal 2617 to transfer data from the 6800 microprocessor to refresh memory 2612 or from refresh memory 2612 to the 6800 microprocessor.

Data display control panel 95 shown in FIG. 2a
and data display interface 97 are shown in more detail in FIG. Referring to FIG. 72, all address, command, and data lines shown come from the 2900 microprocessor. The A7 address line is provided as the first input to NAND gate 2701. The A6 address line is provided as the second input to NAND gate 2701. The A5 address line is provided as the third input to NAND gate 2701. The A4 address line is provided as the fourth input to NAND gate 2701. A3
The address line is passed through the inverter 2702.
Provided as the fifth input to NAND gate 2701. The valid memory address (VMA) line is connected to NAND gate 270 via inverter 2703.
It is given as the sixth input to 1. The read/write (R/) line is provided as the seventh input to NAND gate 2701. The display mode (DM) line is
Provided as the eighth input to NAND gate 2701. The output of NAND gate 2701 is provided to the enable input of decoder 2705.

The A0 address line is routed through inverter 2706 to the A0 input of decoder 2705. A1 address line is connected to decoder 2 via inverter 2707.
705 to the A1 input. The A2 address line is connected to the decoder 2705 via the inverter 2708.
Given to A2 input. The A0-A2 address lines are used to energize specific ones of the thumbwheel switches 2709.

The 0-6 output from decoder 2705 is sent to the enable input of thumbwheel switch 2709.
Thumbwheel switch 2709 is located on data display control panel 95 shown in FIG. 2a and is used by the operator to control how data is displayed on data display 93. Thumbwheel switch 2709 is encoded to provide a binary coded decimal (BCD) output signal 2711. The signal 271 actually represents multiple signal lines.
1 is given to buffer 2712.

The rotary switch 2713 is arranged on the data display control panel 95 to transfer data to the data display device 93.
Provide other means for the operator to control how the display is displayed. The output from rotary switch 2713 is also provided to buffer 2712. Batsuhua 2712 is
Coupled to the D0-D7 data lines of the 2900 microprocessor. In this manner, commands set by the operator via thumbwheel switch 2709 and rotary switch 2713 are transferred to the 2900 microprocessor by the 2900 microprocessor data bus. In response to these commands, the 2900 microprocessor controls the manner in which data is displayed on data display 93, illustrated in Figure 2a.

The magnetic tape panel 83 and magnetic tape panel interface 84 shown in FIG. 2a are illustrated in more detail in FIG. 73. Magnetic tape·
Panel 83 and magnetic tape panel interface 84 primarily provide operator control over the recording of seismic data to magnetic tape at the central recording station.
Referring to FIG. 73, the A7 address line from the 6800 microprocessor is provided as the first input to NAND gate 2721. A6 address line is connected to NAND gate 27 via inverter 2722.
21 as the second input. The A5 address line is provided as the third input to NAND gate 2721 via inverter 2723. A4
The address line is provided directly as the fourth input to NAND gate 2721. An input/output (I/O) select line is provided as the fifth input to NAND gate 2721. The remaining inputs of NAND gate 2721 are coupled to the high state of +5V power supply 2724.
The output from NAND gate 2721 is coupled as a first activation input to switch selection circuit 2725 and as a first activation input to output selection circuit 2726. The A4-A7 address lines and input/output (I/O) select lines from the 6800 microprocessor are used primarily to energize either switch select circuit 2725 or output select circuit 2726.

The A0 address line from the 6800 microprocessor is routed through buffer 2728 to switch select circuit 2.
It is sent to the A0 input of 725 and the A0 input of output selection circuit 2726. A1 address line is buffer 272
8 to the A1 input of the switch selection circuit 2725 and the A1 input of the output selection circuit 2726.
The A2 address line is coupled via buffer 2728 to the A2 input of switch selection circuit 2725 and the A2 input of output selection circuit 2726. The A3 address line is connected to the switch selection circuit 2 via the buffer 2728.
725 and as a second energization input to output selection circuit 2726. The read/write (R/) signal line is connected to the switch selection circuit 2 via a buffer 2728.
725 and as a third bias input to output selection circuit 2726.
The A3 address line and the read/write (R/) line are further connected to the switch selection circuit 2725 or the output selection circuit 2.
726.
When switch selection circuit 2725 is activated, either one of the thumbwheel switches 2731 or the rotary switch is activated. When output selection circuit 2726 is energized, either buffer 2734 or buffer 2735 is energized. 6800
The A0-A2 address lines from the microprocessor are used to determine which thumbwheel switch to activate. Rotary switch 2732 also
Energized by A0-A2 address lines. Similarly,
The A0-A2 address lines are used to determine whether buffer 2734 or buffer 2735 is energized. The 0-7 output lines from the switch selection circuit 2725 are connected to the thumbwheel switch 273.
1 and to the ground input of rotary switch 2732. The 0-7 output lines from switch selection circuit 2725 are connected to thumbwheel switch 2.
731 or the rotary switch 2732 by providing a source of current flow at ground.

The information set in the thumbwheel switch 2731 and rotary switch 2732 is stored in the buffer 2738.
The output of buffer 2738 is coupled to the D0-D7 data lines of the 6800 microprocessor. Buffer 2738 receives 0 from switch selection circuit 2725.
It is energized by the -7 output line.

Display driver 274 via D0-D7 data line buffer 2741 from 6800 microprocessor
Sent to 2. D0− from display driver 2742
The D7 data line is sent to the display section 2743. 6800
Data from the microprocessor is displayed on the display section 274.
3 is displayed to the operator.

Pushbutton 2744 is provided to enable the operator to start the tape device, write header information to the magnetic tape, and set the file number in which data from the first explosion is to be stored. The output from pushbutton switch 2744 also interrupts the 6800 microprocessor via buffer 2735.

Rotary switch 2732 is primarily used to allow the operator to command the 6800 microprocessor as to what operations are required to retrieve the magnetic tape. Set the rotary switch 2732 to command the 6800 to automatically position the magnetic tape after recording the final data record;
Flip to position the last record on the tape, flip to search for the file number set on thumbwheel switch 2731, or flip to the thumbwheel switch 2731.
Advance to the file number set in switch 2731 and search.

A pushbutton switch 2744 allows the operator to activate operation of the magnetic tape device. There are three switches labeled "File Setup,""HeaderWrite," and "Start." When you press the "Start" button, the
An interrupt is placed on the 6800 microprocessor.
The 6800 microprocessor energizes buffer 2738 and reads the position of rotary switch 2732 to determine what action is required. "File settings"
When you press the push button switch, the buffer 2738
is activated again, but this time the 6800 microprocessor reads and stores the file number set on thumbwheel switch 2731. This information is also displayed on display section 2743.

Note that thumbwheel switch 2731 is used to set only the first file number for recording seismic data on magnetic tape.
After setting the initial file number, the 6800 microprocessor automatically increments the file number as each explosive charge is ignited. The incremented file number appears on display 2743 and changes after each explosive is ignited.

Activate the "header write" pushbutton switch
Allows the 6800 microprocessor to write header information to magnetic tape.

Thumbwheel switch 2731, rotary switch 2732, and pushbutton switch 2744 are provided to allow operator control of the recording of seismic data to magnetic tape. Thumbwheel switch 2731 is used to set the file number of the first recording started, and rotary switch 2732 is used to set different operations. Push button switch 27
44 to start operating the magnetic tape device, and
Interrupts the 6800 microprocessor to allow it to read the data set on thumbwheel switch 2731 and rotary switch 2732. The A0-A2 address lines from the 6800 microprocessor energize switch selection circuit 2725 and buffer 27.
38 and thumbwheel switch 2731
Or read data from rotary switch 2732.
The position of the pushbutton switch is read by the 6800 microprocessor by energizing output selection circuit 2726 which energizes buffer 2734 or buffer 2735.

The heart of the seismic survey system of the present invention is a computer associated with the central recording station illustrated in FIG. 2a and the remote telemetry device illustrated in FIG. 2b. Second
The computer 51 shown in Figure a is a 6800 microprocessor, and is the master control computer of the seismic exploration device. The second computer 74
The 2900 microprocessor shown in Figure a is a peripheral microprocessor mainly used in the seismic data acquisition procedure. The 2900 microprocessor is under the control of a 6800 microprocessor, shown as computer 51. Computer 111, illustrated in Figure 2b, is also a 6800 microprocessor.
Computer 111 controls the functions of the remote telemetry device illustrated in FIG. 2b, and is also under the control of computer 51.

Many different types of software programs can be written in different languages and formats. The software program is simply the means by which the computer initiates various functions of the seismic system and controls other functions of the seismic system.

[Brief explanation of the drawing]

FIG. 1 is a diagram of a possible physical arrangement of the components of the seismic exploration device of the present invention. FIG. 2a is a block diagram of the central recording station of the present invention. FIG. 2b is a block diagram of the remote telemeter device of the present invention. FIG. 3 is a schematic diagram of the RF interface illustrated in FIG. 2b. FIG. 4 is a schematic diagram of the RF receiver and RF transmitter illustrated in FIGS. 2b and 3.
FIG. 5 is a schematic diagram of the digital phase lock clock shown in FIG. FIG. 6 is a schematic diagram of the transmission data logic control section shown in FIG. 3. FIG. 7 is a schematic diagram of the memory controller shown in FIG. 2b. FIG. 8 is a schematic diagram of the memory location write control section illustrated in FIG. 7. FIG. 9 is a schematic diagram of the write address counter illustrated in FIG. FIG. 10 is a schematic diagram of the read address counter illustrated in FIG. FIG. 11 is a schematic diagram of the state logic shown in FIG. 1st
FIG. 2 is a schematic diagram of the four-set memory clock logic illustrated in FIG. FIG. 13 is a schematic diagram of the memory cycle control logic illustrated in FIG.
FIG. 14 is a schematic diagram of the memory illustrated in FIG. 2b. FIG. 15 is a schematic diagram of the test interface illustrated in FIG. 2b. FIG. 16 is a schematic diagram of the calibration card shown in FIG. 2b. FIG. 17 is a schematic diagram of the voltage divider circuit shown in FIG. 16. FIG. 18 is a schematic diagram of the preamplifier shown in FIG. 2b. FIG. 19 is a schematic diagram of the notch filter and alias filter shown in FIG. 2b. FIG. 20 is a schematic diagram of the gain range amplifier device and A/D conversion device shown in FIG. 2b. FIG. 21 is a block diagram of the power supply regulator shown in FIG. 2b. Figures 22a and 22b are schematic diagrams of the voltage regulator shown in Figure 21. FIG. 23 is a block diagram of an alternative test arrangement for the remote telemeter arrangement shown in FIG. 2b. FIG. 24 is a schematic diagram of the gradient generator illustrated in FIG. 23. FIG. 25 is a schematic diagram of the reference voltage source illustrated in FIG. 23. FIG. 26 is a schematic diagram of the voltage controlled oscillator shown in FIG. 23. 27th
The figure is a schematic diagram of the sine wave shaper illustrated in FIG. 23. FIG. 28 is a schematic diagram of the sawtooth generator shown in FIG. 23. FIG. 29 is a schematic diagram of the output circuit shown in FIG. 23. Figure 30 is 2a
1 is a schematic diagram of the RF transmitter illustrated in the figure; FIG. 31st
The Figure is a schematic diagram of the RF receiver illustrated in Figure 2a. FIG. 32 is a block diagram of the 2900 microprocessor illustrated in FIG. 2a. FIG. 33 is a schematic diagram of the interrupt logic section shown in FIG. 32. Third
FIG. 4 is a schematic diagram of the conditional branch logic section shown in FIG. 32. Figure 35 is a diagram illustrating the locations of random access memory used to develop and test programs for the 2900 microprocessor illustrated in Figure 2a. Figure 36 is illustrated in Figure 35.
FIG. 2 is a schematic diagram of PROM bug RAM. FIG. 37 is a schematic diagram of the decode logic shown in FIG. 36. FIG. 38 is a schematic diagram of the computer-to-computer interface illustrated in FIG. 2a. FIG. 39 is a schematic diagram of the command formatter shown in FIG. 2a. FIG. 40 is a schematic diagram of the decoding device shown in FIG. 39. FIG. 41 is a block diagram of the data formatter illustrated in FIG. 2a. FIG. 42 is a schematic diagram of the clock signal generation circuit shown in FIG. 41. FIG. 43 is a schematic diagram of the decoding circuit shown in FIG. 41. FIG. 44 is a schematic diagram of the parity count circuit shown in FIG. 41. FIG. 45 is a block diagram of the magnetic tape device, magnetic tape controller, and magnetic tape interface illustrated in FIG. 2a. FIG. 46 is a schematic diagram of the first control device shown in FIG. 45. Figures 47a and 4
Figure 7b is a schematic diagram of the second control device shown in Figure 45. FIG. 48 is a schematic diagram of the interface shown in FIG. 45. FIG. 49 is a schematic diagram of the gate shown in FIG. 48. FIG. 50 is a schematic diagram of the decoder shown in FIG. 48. Fifth
FIG. 1 is a block diagram of the data display device shown in FIG. 2a. FIG. 52 is a timing diagram related to the data display device shown in FIG. 51. FIG. 53 is a timing diagram relating to the data display device shown in FIG. 51. FIG. 54 is a schematic diagram of the first-in, first-out memory illustrated in FIG. 51. FIG. 55 is a diagram illustrating how the sample and hold circuit shown in FIG. 51 is addressed. FIG. 56 is a schematic diagram of the control logic shown in FIG. 51. FIG. 57 is a schematic diagram of the data display control section shown in FIG. 51. FIG. 58 is a schematic diagram of the AGC circuit shown in FIG. 57. FIG. 59 is a schematic diagram of the full wave rectifier and integrator shown in FIG. 58. FIG. 60 is a schematic diagram of the central recording station countdown circuit shown in FIG. FIG. 61 is a schematic diagram of the decoding circuit shown in FIG. 60. FIG. 62 is a schematic diagram of the first counter shown in FIG. 60. FIG. 63 is a schematic diagram of the second counter shown in FIG. 60. FIG. 64 is a schematic diagram of the energizing circuit shown in FIG. 60. FIG. 65 is a schematic diagram of the output circuit shown in FIG. 60. Figure 66 is a schematic diagram of the switch and display interface and a portion of the operator display panel associated with the switch and display interface, both shown in Figure 2a. FIG. 67 is a schematic diagram of the address and command decode buffer circuit shown in FIG. 61. Figure 68 is a schematic diagram of the roll-along panel interface and a portion of the operator control display panel associated with the roll-along panel interface, both shown in Figure 2a. Figure 69 is a schematic diagram of the data display control panel and data display control panel interface illustrated in Figure 2a. FIG. 70 is a schematic diagram of the reference time generator shown in FIG. 69. Figure 71 shows the address shown in Figure 69.
FIG. 3 is a schematic diagram of a decoding section. Figure 72 is a schematic diagram of the self-scanning interface illustrated in Figure 2a. Figure 73 is a schematic diagram of the magnetic tape panel and magnetic tape panel interface illustrated in Figure 2a. 11a-f...RTU, 23...CRS, 51...
...Computer, 41...Operator control display panel, 52...Command formatter, 59...RF transmitter, 64...Antenna, 106...RF receiver,
108...RF interface, 111...computer, 201...test interface,
202... Calibration card, 141... A/D converter, 148... Temperature sensor, 171... Gain range amplifier, 65... CRS countdown, 12
4...Memory control unit, 125...Memory device, 1
27...RF transmitter, 68...RF receiver, 71...
...Data formatter, 74...Computer, 58...Computer-to-computer interface, 43...Switch and display interface, 135...Preamplifier, 151...
Notsuchi filter, 161...Elias filter, 78...Magnetic tape interface, 7
9...Magnetic tape device, 88...Magnetic tape controller, 93...Data display device.

Claims (1)

[Scope of Claims] 1. A method for testing seismic exploration equipment, the method comprising: using a central controller to control and obtain data from a plurality of remote geofon monitoring devices; receiving an electrical signal from at least one geoffon device, and generating a first test command representing a command to cause a first of the plurality of remote geoffon monitoring devices to perform a self-test operation; and transmitting the first test command from the central controller to the first of the plurality of remote geofon monitoring devices via a two-way radio frequency link, the first test command In response to said first of said plurality of remote geofone monitoring devices being activated to perform a predetermined self-test operation and to store the results of said predetermined self-test operation. the step of: generating a first command to transmit data after the results of the predetermined self-test operation are stored in the first of the plurality of remote geofon monitoring devices; transmitting a first command for transmitting data from a central controller via the two-way radio frequency link to the first of the plurality of remote geofon monitoring devices; retrieving test data from a storage unit in response to a command from the controller and transmitting the test data from the first of the plurality of remote geofon monitoring devices to the central controller via the two-way radio frequency link; a transmitting step, the test data providing information regarding the operability of the first of the plurality of remote geofon monitoring devices to a central controller. 2. A method of testing a seismic survey device as claimed in claim 1, comprising displaying seismic data on a central control unit, thereby providing immediate information regarding the operability of said first of said plurality of remote geofon monitoring devices. A method of testing a seismic exploration device further comprising the step of displaying. 3. A method of testing a seismic survey device as claimed in claim 1, comprising: detecting errors in the test data provided by the first of the plurality of remote geofon monitoring devices; displaying the test data at the central controller if the number of errors detected in the test data provided from the first of the plurality of remote geofon monitoring devices is less than a predetermined value; and generating a first data retransmission command if the number of errors present in the test data provided by the first of the plurality of remote geofon monitoring devices is greater than the predetermined value. transmitting the first data retransmission command from the central controller via the two-way radio frequency link to the first of the plurality of remote geofon monitoring devices; retransmitting test data from the first of the plurality of remote geofon monitoring devices to the central controller via the two-way radio frequency link in response to a retransmission command of the plurality of remote geofon monitoring devices; a test transmitted from said first of said plurality of remote geofon monitoring devices in response to said test data transmission first command using retransmitted seismic data from said first of said remote geofon monitoring devices; A method for testing a seismic survey device further comprising: correcting errors in the data; 4. A method of testing a seismic survey device according to claim 3, in which retransmitted test data is used to test the plurality of remote geofon monitoring devices in response to the first command to transmit test data. said step of correcting said test data transmitted from said first of said test data in response to said first command of said test data transmission using error-free data blocks in said retransmitted test data. replacing an erroneous data block in test data provided by said first of a plurality of remote geofon monitoring devices, thereby causing said plurality of remote geofon monitoring devices to A method of testing a seismic survey device comprising the step of correcting errors in test data provided from said first of remote geofon monitoring devices. 5. A method of testing a seismic survey device according to claim 4, wherein: (a) after correctly transmitting test data from the first of the remote geofon monitoring devices to the central controller; (b) generating a second test command representing a command to cause a second of the plurality of remote geofon monitoring devices to perform a self-test operation; transmitting the second test command to the second one of the plurality of remote geofion monitoring devices, the step of transmitting the second test command to the second one of the plurality of remote geofion monitoring devices, (c) said transmitting step in which said predetermined self-test operation is activated to perform a predetermined self-test operation and to store the results of said predetermined self-test operation; (d) generating a second command for data transmission after the results of the test operation are stored in the second of the plurality of remote geofon monitoring devices; (e) transmitting a second command for transmitting test data to the second one of the plurality of remote geofon monitoring devices via a link; Responsively retrieving the test data from a storage unit and retrieving the test data from the storage unit,
(f) transmitting the test data from the second one of the plurality of remote geo-on monitoring devices to the central controller via the two-way radio frequency link; (g) if the number of errors detected in the test data provided by the second of the plurality of remote geofon monitoring devices is less than the predetermined value; (h) displaying the test data on the central controller at a time when the number of errors present in the test data provided from the second one of the plurality of remote geofon monitoring devices (i) generating a second data retransmission command of the plurality of remote geofon monitoring devices from the central controller via the two-way radio frequency link; (x) transmitting the second retransmission command to the second one of the plurality of remote geofon monitoring devices in response to the second retransmission command; (l) using the retransmitted test data from the second of the plurality of remote geofon monitoring devices;
(c) correcting errors in data transmitted from the second of the plurality of remote geofon monitoring devices in response to the second command to transmit test data; continuing to test each of the plurality of remote geofon monitoring devices in the manner described in steps (a) to (l) until each of the geofon monitoring devices has been tested; . 6. A method of testing a seismic survey device according to claim 1, wherein the predetermined self-test operation includes: determining the temperature of the remote geofion monitoring device; and supplying power to the remote geofion monitoring device. a method for testing a seismic survey device comprising the steps of: determining whether the at least one geophonic device is operational; 7. A geological seismic survey device, comprising: a plurality of remote geophon monitoring devices, each of which is adapted to receive electrical signals from at least one geophonic device; a central controller that generates an electrical signal to initiate operation of the plurality of remote geofion monitoring devices;
each of the plurality of remote geofon monitoring devices includes: a device for performing a self-test in response to a test command from the central controller and generating test data representing a result of the self-test; a data storage device; a device for providing the test data to the first data storage device to store the test data; and a device for transmitting the stored test data to the central control device in response to a transmission command from the central control device. a first radio frequency transmitter device for transmitting the test data from the first data storage device to the first radio frequency transmitter device; and a device for providing the test data from the first data storage device to the first radio frequency transmitter device; a first radio frequency receiver device receiving the transmission command;
the central controller includes: a device for generating the test commands; a device for generating the transmit commands; and a second radio frequency transmitter device for transmitting commands to the plurality of remote geofon monitoring devices. an apparatus for providing the test command and the transmit command to the second radio frequency transmitter device, thereby providing the test command and the transmit command to at least one of the plurality of remote geofon monitoring devices; a second receiving the test data from at least one of the plurality of remote geofon monitoring devices;
a radio frequency receiver device; a device for displaying data; and providing the test data from the second radio frequency receiver device to a device for displaying the data, thereby providing one of the plurality of remote geofon monitoring devices. A geological seismic survey device comprising: a device for immediately indicating the operability of at least one of; 8. The geological seismic survey device of claim 7, wherein the remote geo-on monitoring device samples electrical signals provided by the at least one geo-on device and converts the sampled electrical signals into digital seismic data. Geological seismic exploration equipment further including equipment for. 9. The geological seismic survey device of claim 8, wherein the device for performing self-testing comprises: a device for determining the temperature of each remote geofion monitoring device; and power available to each remote geofon monitoring device. an apparatus for determining whether the apparatus for sampling an electrical signal provided by at least one geophonic device and for converting the sampled electrical signal into digital seismic data is operational; Including geological seismic exploration equipment. 10. The geological seismic survey device of claim 7, wherein the device for providing the test data from the second radio frequency receiver device to a device for displaying the data comprises: an error detection device; a device for providing the test data from the second radio frequency receiver device to the error detection device; and a device for providing the test data from the error detection device to a device for displaying the data. Seismic exploration equipment. 11. The geological seismic survey device according to claim 10, wherein the error detection device comprises: a device for detecting the location of an error in a block of information; and a device for detecting the location of an error in a block of information. in response to a command from said central controller to said particular remote geo-off-on monitoring device to cause said central controller to retransmit information acknowledged to have been received at least partially in error; a device for replacing corresponding error-free data provided by a monitoring device; and a geological seismic survey device.