JPS6218083B2 - - Google Patents
Info
- Publication number
- JPS6218083B2 JPS6218083B2 JP56177979A JP17797981A JPS6218083B2 JP S6218083 B2 JPS6218083 B2 JP S6218083B2 JP 56177979 A JP56177979 A JP 56177979A JP 17797981 A JP17797981 A JP 17797981A JP S6218083 B2 JPS6218083 B2 JP S6218083B2
- Authority
- JP
- Japan
- Prior art keywords
- line
- resonant
- frequency
- inductor
- lumped constant
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 230000010355 oscillation Effects 0.000 claims description 12
- 238000000059 patterning Methods 0.000 claims 1
- 238000010586 diagram Methods 0.000 description 5
- 230000006866 deterioration Effects 0.000 description 2
- 230000002542 deteriorative effect Effects 0.000 description 2
- 230000001939 inductive effect Effects 0.000 description 2
- 239000000758 substrate Substances 0.000 description 2
- 239000002131 composite material Substances 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 238000010295 mobile communication Methods 0.000 description 1
- 230000035945 sensitivity Effects 0.000 description 1
- 238000005476 soldering Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/18—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance
- H03B5/1841—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance the frequency-determining element being a strip line resonator
- H03B5/1847—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance the frequency-determining element being a strip line resonator the active element in the amplifier being a semiconductor device
Description
【発明の詳細な説明】
本発明は高周波帯で使用される発振回路に関す
る。一般に高周波帯（VHF、UHF帯）で使用さ
れる回路では経済性、使用の面から低損失基板を
用いたストリツプ型分布定数線路が良く用いられ
る。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an oscillation circuit used in a high frequency band. Generally, in circuits used in high frequency bands (VHF, UHF bands), strip-type distributed constant lines using low-loss substrates are often used from the viewpoint of economy and usage.
特に発振回路の主な特性としては、安定性、小
型化の要求がなされ、さらに移動通信関係で周波
数シンセサイザ等に用いられる電圧制御発振器な
どでは雑音特性が重視される。 In particular, stability and miniaturization are required as main characteristics of oscillation circuits, and noise characteristics are important in voltage-controlled oscillators used in frequency synthesizers and the like in mobile communications.
通常発振器の安定性、雑音特性において共振線
路の無負荷Ｑは重要な割合を占める。 The no-load Q of the resonant line usually plays an important role in the stability and noise characteristics of an oscillator.
例えば共振線路の無負荷Ｑを上げるには線路の
特性インピーダンスが小さくなるように設計する
のも一手法ではあるが、この場合小型化という要
求とは相反する。さらに周波数シンセサイザ等に
用いられる電圧制御発振器などには位相同期シス
テム系のループゲインから決定される主制御機能
と製造工程、素子のバラツキによる周波数ズレを
補正するための調整機能とをもたせるため二個の
可変容量素子バラクタを用いており、このバラク
タは一般に所要周波数変化幅を得るために共振線
路に接続されておりバラクタ自身のもつ直列抵抗
ＲSにより共振線路の無負荷Ｑを低下させてい
る。第１図は従来の短縮型λ／２共振回路を示す
もので、１はインダクタ、２，３は容量素子を示
し電圧制御発振器などでは容量素子２，３にバラ
クタを装架し、共振周波数を可変にしているが、
前記したように安定度、雑音特性を満足するには
発振器の寸法自体が大きなものになり、さらに二
個のバラクタによりインダクタ１の無負荷Ｑが劣
化する。本発明は共振線路に分布定数共振線路と
集中定数インダクタを採用し、周波数ズレを補正
する調整機能用バラクタの替りに集中定数部にお
いて調整機能を持たせることにより、特性を劣化
させずに小型化のできる発振回路を提供するもの
である。 For example, one way to increase the no-load Q of a resonant line is to design the line so that its characteristic impedance is small, but this is contrary to the demand for miniaturization. Furthermore, voltage controlled oscillators used in frequency synthesizers, etc. have two main control functions determined from the loop gain of the phase synchronization system and an adjustment function to correct frequency deviations due to manufacturing process and element variations. A variable capacitance element varactor is used, and this varactor is generally connected to a resonant line in order to obtain the required frequency change width, and the no-load Q of the resonant line is lowered by the series resistance R S of the varactor itself. Figure 1 shows a conventional shortened λ/2 resonant circuit, where 1 is an inductor and 2 and 3 are capacitive elements.In voltage controlled oscillators, etc., capacitive elements 2 and 3 are mounted with varactors, and the resonant frequency is adjusted. Although it is made variable,
As described above, in order to satisfy stability and noise characteristics, the size of the oscillator itself must be large, and the two varactors deteriorate the no-load Q of the inductor 1. The present invention adopts a distributed constant resonant line and a lumped constant inductor for the resonant line, and provides an adjustment function in the lumped constant part instead of the adjustment function varactor that corrects frequency deviation, thereby reducing the size without deteriorating the characteristics. The present invention provides an oscillation circuit that can perform the following functions.
以下図面を用いて本発明の一実施例を詳細に説
明する。 An embodiment of the present invention will be described in detail below with reference to the drawings.
第２図は本発明の発振回路に用いる共振回路を
示したもので、分布定数共振線路４とその略中央
に設けた、集中定数インダクタ５をパターン化し
たものでその集中定数部に於いて共振回路の小型
化を計りさらにその部分の細線間をハンダ接続も
しくは切削することにより周波数調整機能をもた
せている。 Figure 2 shows a resonant circuit used in the oscillation circuit of the present invention, in which a distributed constant resonant line 4 and a lumped constant inductor 5 provided approximately in the center are patterned, and resonance occurs in the lumped constant part. The circuit is miniaturized, and the frequency adjustment function is provided by soldering or cutting the thin wires in those areas.
さて、以下に集中定数インダクタ５を分布定数
共振線路４の略中央部に設ける理由について述べ
る。 Now, the reason why the lumped constant inductor 5 is provided approximately at the center of the distributed constant resonant line 4 will be described below.
1/2波長共振線路は第６図ａに示すように、そ
の線路長において線路の中央部で誘導性電流が大
になり、逆に線路の末端部で誘導性電流が小とな
る。すなわちインダクタによつて共振周波数を変
化させようとする場合、中央部の方が線路端より
も感度が高い。本実施例ではこのような性質を利
用して、その中央部に切削可能な集中定数インダ
クタ５を設け、より大きな周波数調整ができるよ
うにしている。 As shown in Figure 6a, in a 1/2 wavelength resonant line, the inductive current is large at the center of the line, and conversely, the inductive current is small at the end of the line. That is, when trying to change the resonant frequency using an inductor, the sensitivity is higher at the center than at the ends of the line. In this embodiment, taking advantage of this property, a cuttable lumped constant inductor 5 is provided in the center of the inductor, thereby enabling greater frequency adjustment.
具体的には６図ｂに示すように分布定数線路の
略中央部に集中定数インダクタンスを設け、その
線路ｂ，ｂを順次切断していつた場合と、第
６図ｃに示すように分布定数線路の端部に集中定
数インダクタンスを設け、その線路ｃ，ｃを
順次切断していつた場合とでは、第６図ｄに示す
ようにその発振周波数の調整幅は0.5〜1.0MHzの
相違があり、より大きな範囲で周波数調整を行な
うには第６図ｂの構成が有利であることは明らか
である。 Specifically, as shown in Figure 6b, a lumped constant inductance is provided approximately at the center of the distributed constant line, and the lines b and b are sequentially cut, and a distributed constant line is installed as shown in Figure 6c. In the case where a lumped inductance is provided at the end of , and the lines c and c are sequentially cut, the adjustment width of the oscillation frequency is different from 0.5 to 1.0 MHz, as shown in Fig. 6 d. It is clear that the configuration shown in FIG. 6b is advantageous for frequency adjustment over a large range.
さらに特性上に於いて集中定数部での周波数調
整機能を持つことから、従来の調整用バラクタの
除去が可能となりバラクタが１個で構成できるこ
とから共振線路の無負荷Ｑが向上し、さらにこの
バラクタは外部雑音に対し変調を受けやすいため
除去されることにより外部雑音に対し強いものと
なる。 Furthermore, since it has a frequency adjustment function in the lumped constant part in terms of characteristics, it is possible to eliminate the conventional adjustment varactor and it can be configured with one varactor, improving the no-load Q of the resonant line. Since it is easily modulated by external noise, by removing it, it becomes resistant to external noise.
又、共振回路のアドミタンスも集中定数を入れ
ることにより高くなり所要電圧に対し周波数可変
範囲も広くとれるためこれは周波数シンセサイザ
等に用いられる場合は好ましいことである。 Further, the admittance of the resonant circuit can be increased by including a lumped constant, and the frequency variable range can be widened with respect to the required voltage, which is preferable when used in a frequency synthesizer or the like.
集中定数インダクタ部５でのＱの劣化はあるが
バラクタを１個除去したことにより、Ｑの劣化は
充分補いむしろ雑音特性では優位性がみられる。 Although there is some deterioration in Q in the lumped constant inductor section 5, by removing one varactor, the deterioration in Q is sufficiently compensated for and, in fact, superiority in noise characteristics can be seen.
第３図はこの共振回路を用いた本発明の一実施
例における発振回路を示し、一般的な負性抵抗を
もつトランジスタ型コルピツク発振回路で、トラ
ンジスタ９のコレクタに第２図に示した共振回路
を結合させている。 FIG. 3 shows an oscillation circuit according to an embodiment of the present invention using this resonant circuit. It is a transistor-type Colpick oscillation circuit with a general negative resistance, and the resonant circuit shown in FIG. 2 is connected to the collector of the transistor 9. are combined.
分布定数共振線路４の一端には容量素子６を介
してバラクタ素子７が設けられており、バラクタ
素子７のカソード側に、端子８が接続され、バラ
クタ電圧ＶFが印加される。 A varactor element 7 is provided at one end of the distributed constant resonant line 4 via a capacitive element 6, and a terminal 8 is connected to the cathode side of the varactor element 7, to which a varactor voltage V F is applied.
第４図は本発明の一実施例の周波数可変範囲特
性を示し、第５図は雑音特性を従来のものと比較
したもので両特性とも本発明の優位性が認められ
る。また雑音特性では離調周波数20kHzに於いて
２〜3dBの向上がみられる。 FIG. 4 shows the frequency variable range characteristics of one embodiment of the present invention, and FIG. 5 compares the noise characteristics with the conventional one, and the superiority of the present invention is recognized in both characteristics. In addition, the noise characteristics are improved by 2 to 3 dB at a detuning frequency of 20 kHz.
また構造上共振線路の曲がり部を生じる場合、
この90゜曲がり部では容量性となり線路の無負荷
Ｑを劣化させる。本発明の場合、たとえば第３図
に示すようにこの曲がり部に集中定数インダクタ
を設置することによりこの欠点を防止できる。あ
るいは両面銅張の誘電体基板を使用し共振線路を
両面に二分割して用いる場合、その接続部に集中
定数を設置するのも有効な手段である。 Also, if the structure causes a bend in the resonant line,
This 90° bend becomes capacitive and degrades the no-load Q of the line. In the case of the present invention, this drawback can be avoided by installing a lumped constant inductor at this bend, as shown in FIG. 3, for example. Alternatively, when a double-sided copper-clad dielectric substrate is used and the resonant line is divided into two on both sides, it is also an effective means to install a lumped constant at the connection part.
以上のように本発明はインダクタ部分を分布定
数線路とその略中央に設けた、集中定数インダク
タとで実現した複合形共振回路を用いることによ
り安定性、雑音特性の劣化を招くことなく小型化
を実現し、かつ共振回路の配置、構成上柔軟性に
富みしかも集中定数部に於いて調整機能を持ち経
済的である等の利点を有する発振回路を提供する
ことができる。 As described above, the present invention achieves miniaturization without deteriorating stability and noise characteristics by using a composite resonant circuit in which the inductor portion is realized by a distributed constant line and a lumped constant inductor provided approximately in the center of the distributed constant line. It is possible to provide an oscillation circuit which has advantages such as being highly flexible in the arrangement and configuration of the resonant circuit, and having an adjustment function in the lumped constant section and being economical.
第１図は従来の短縮型λ／２共振回路の結線
図、第２図は本発明の発振回路に用いる共振回路
の結線図、第３図は本発明の実施例における発振
回路の結線図、第４図および第５図は従来の発振
回路と本発明の発振器との周波数可変範囲特性と
側帯波雑音特性を比較して示す図、第６図ａ〜ｄ
は本発明の一実施例における発振回路の集中定数
インダクタンスを設ける位置を説明するための図
である。
１，４…分布定数線路、２，３…容量素子、５
…集中定数インダクタ、６…容量素子２に等価な
容量値をもつバラクター回路部、９…トランジス
タ。
Fig. 1 is a wiring diagram of a conventional shortened λ/2 resonant circuit, Fig. 2 is a wiring diagram of a resonant circuit used in the oscillation circuit of the present invention, and Fig. 3 is a wiring diagram of an oscillation circuit in an embodiment of the present invention. Figures 4 and 5 are diagrams showing a comparison of the frequency variable range characteristics and sideband noise characteristics of the conventional oscillator circuit and the oscillator of the present invention, and Figures 6 a to d
FIG. 2 is a diagram for explaining the position where a lumped constant inductance is provided in an oscillation circuit according to an embodiment of the present invention. 1, 4...Distributed constant line, 2, 3...Capacitive element, 5
...lumped constant inductor, 6... varactor circuit section having a capacitance value equivalent to the capacitance element 2, 9... transistor.
Claims (1)
し、その部分を切削、または短絡する集中定数イ
ンダクタンスを形成したインダクタンス部と、容
量部とからなる共振回路を具備する発振回路。1. An oscillation circuit comprising a resonant circuit consisting of an inductance section in which a lumped constant inductance is formed by finely patterning approximately the center of a distributed constant line and cutting or short-circuiting that section, and a capacitance section.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17797981A JPS5879306A (en) | 1981-11-05 | 1981-11-05 | Oscillating circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17797981A JPS5879306A (en) | 1981-11-05 | 1981-11-05 | Oscillating circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5879306A JPS5879306A (en) | 1983-05-13 |
| JPS6218083B2 true JPS6218083B2 (en) | 1987-04-21 |
Family
ID=16040411
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP17797981A Granted JPS5879306A (en) | 1981-11-05 | 1981-11-05 | Oscillating circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS5879306A (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP5947110B2 (en) | 2012-05-25 | 2016-07-06 | Dmg森精機株式会社 | Dust collection attachment for cutting, dust collection duct for machine tool, tool holder for machine tool and machine tool |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS54102952A (en) * | 1978-01-31 | 1979-08-13 | Nec Home Electronics Ltd | Local oscillator circuit of uhf tuner |
-
1981
- 1981-11-05 JP JP17797981A patent/JPS5879306A/en active Granted
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS54102952A (en) * | 1978-01-31 | 1979-08-13 | Nec Home Electronics Ltd | Local oscillator circuit of uhf tuner |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS5879306A (en) | 1983-05-13 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US4998077A (en) | VCO having tapered or stepped microstrip resonator | |
| JP2000228602A (en) | Resonance line | |
| EP0532330B1 (en) | Ring resonator device | |
| EP1154560B1 (en) | Voltage controlled oscillator for oscillating signals with high C/N ratio | |
| US4214217A (en) | Electronic tuning circuit having image trapping element | |
| EP0384326B1 (en) | Unitary capacitance trimmer | |
| JPS6218083B2 (en) | ||
| EP1098432B1 (en) | Frequency-switching oscillator and electronic device using the same | |
| JPH1032429A (en) | Voltage controlled resonator and its adjustment method | |
| JPH06314982A (en) | Antenna | |
| JP3205694B2 (en) | Tuner circuit | |
| US4625183A (en) | Low-cost VCO using lumped elements in microwave band | |
| JP2531000B2 (en) | Oscillator | |
| JPH104315A (en) | High frequency oscillation circuit | |
| US6144263A (en) | Voltage-controlled oscillator and method for adjusting frequency shift amount thereof | |
| KR930006654B1 (en) | Frequency control method for microstrip line oscillator | |
| KR100285307B1 (en) | Voltage controlled oscillator device using coaxial resonator | |
| JPS59134904A (en) | Voltage controlled oscillator | |
| JPH1056306A (en) | Resonance circuit and oscillation circuit | |
| JPH0526817Y2 (en) | ||
| JPS6223492B2 (en) | ||
| JPH05145338A (en) | Dielectric oscillation circuit | |
| JPH03131104A (en) | Voltage controlled oscillator | |
| JPS6042481Y2 (en) | UHF tuner resonator device | |
| JPS6113641B2 (en) |