JPS6087668A - Constant-voltage power source - Google Patents

Abstract

PURPOSE:To obtain a stable output DC voltage for the variations in the input and output of wide range by controlling energy amount capable of storing in energy storing means. CONSTITUTION:An input DC power source 30, switching means 31, and input terminals A, B of current limiter 32 and energy storing means 33 are connected in series, a current limiter 34, switching means 35 and a smoothing circuit 36 are connected in series with the output terminal C of the means 33, and a load 37 is connected in parallel with the smoothing circuit 36. The discharged energy amount from the means 33 depends upon the difference between the voltage value between the output terminals C and D showing the energy amount stored in the means 33 and the voltage value of the smoothing circuit 36, and the discharged energy amount is controlled by the switching frequency of the means 35.

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention is directed to a series resonant DC-DC converter that stabilizes the output DC voltage.
This invention relates to a constant voltage power supply using a DCC set.

Conventional Structure and Problems Conventional switching means are generally of the PWM type, which stabilizes the output DC voltage by controlling the duty ratio of the on/off operation of the switching element. However, the disadvantage of the above method is that since there is a period in which both the current and voltage change sharply when the switching element is turned on and off, the switching loss is large and unnecessary width radiation noise is also large. Therefore, if the above switch regulator is considered as a power supply for audio equipment, it is necessary to take noise countermeasures such as inserting a filter in the input/output section to greatly attenuate unnecessary radiation noise, and also applying a completely sealed shield. Therefore, there are problems such as increased cost and decreased reliability. As a means to solve the above drawbacks, a series resonant DC-1 using a series resonant circuit composed of a capacitor coil is proposed.
) C converter has been proposed. This series common gate type □'
In the DC-DC converter, the current waveform when the switching element is turned on is sinusoidal due to the series resonant circuit, and the current and voltage intersect at approximately zero when the switching element E is turned on and off. Therefore, switching loss and unnecessary radiation noise are significantly reduced. However, in the series resonant tMDC-DC converter, it is difficult to perform control to stabilize the output DC voltage without impairing the characteristic described in F with respect to input/output fluctuations.

Based on the above points, the conventionally used series resonant DC
The circuit configuration and operation of the DCC complete set will be explained.

Fig. 1 is a basic circuit configuration diagram of a conventional series resonant DC-DCC set, and Fig. 2 (a), <b), (c)
is its operating waveform diagram. @1 In Figure 1, switching elements (3) (4) (for example, transistors, MOSFETs,
thyristors, etc.) are connected in series, and an E input-resistant DC power supply (1
) (2) and the switching elements (3) (4) The primary winding (
5a) and conden +j (7) are connected. In addition, a rectifier circuit (8) is connected to the secondary winding (5b) of the conversion transformer (5).
and a smoothing capacitor (9), and its output terminal a
, b are connected to a load +11. Here, the effective leakage interface of the conversion transformer (5) functions as a current limiting element, the capacitor (7) functions as an energy storage element, and the effective leakage interface of L and the capacitor (7) form a series resonant circuit. It consists of J: The resonant current flowing through the series resonant circuit is 11. The charging voltage representing the amount of energy stored in the capacitor (7) is Vc.

Figure 2 (a), (b), and (c) show the on/off state of switching elements (3) and (4) and the resonant current i.
1 shows an operation waveform diagram of charging voltage Vc. In Figure 2,
At time t, the switching element (3) is turned on, and the resonant current i is determined by the effective leakage interface and the capacitance of the capacitor (7). flows to During period E,
The charging voltage of the capacitor (7) is the initial charging voltage -Vc+
becomes Vc+ & due to the resonance current i.

Next, at time t2, the switching element (3) is turned off. During time t2 < t (-tL, both the switching elements (3) and (4) are off, so the resonant current iI/i becomes zero, and the charging voltage Vc of the capacitor (7)
+ is also kept at Vc+ since there is no discharge path. In this situation, when the switching element (4) is turned on at time [3], the above-mentioned time t! The operation waveform between t3 and time t3 is repeated in the opposite direction. During this period, the effective leakage interface of the conversion transformer (5) also acts as a current limiting element to determine the peak of the resonant current i.

In addition, the resonant current i is transmitted to the secondary side via the conversion transformer (5), and after rectification and smoothing, a predetermined output DC voltage is generated using the circuit configuration and operation of a conventional series resonant DC-DCC set. be. As means for controlling the series resonant DC-DC converter described in E, a control method for changing the separance value of a capacitor (7) and a switching element <3) are provided.
Two control methods have been proposed in which (4) both increase the off-state period, that is, control the switching frequency. But in both cases, the capacitor (7)
Since the energy storage h1 changes only slightly, that is, the amount of energy f transferred in the entire system changes only slightly, so the amount of energy transmitted to the output does not change either. Therefore, with the two control methods described above, it is difficult to perform control to stabilize the output DC voltage value.

OBJECT OF THE INVENTION The object of the present invention is to stabilize the output DC voltage over a wide range of human output variations without impairing the characteristics of the series resonant DC-DCC, which has extremely low switch loss and unnecessary radiation. The present invention aims to provide a constant voltage power supply and device.

Structure of the Invention In order to achieve the above object, the constant voltage power supply device vt, I'i of the present invention includes at least a first switch means and a first current limiter that operate on and off with respect to the input DC power supply. A series connection circuit including an element and an input terminal of an energy storage means is connected, and an output terminal of the energy storage means is connected to a series connection circuit including a current limiting element, a second switching means, a second current limiting element, and an output terminal of the energy storage means. a constant voltage power supply device configured to connect a smoothing circuit to obtain an output DC voltage;
The energy storage means includes a control transformer for changing the interface of the first winding by at least a signal supplied, and the second winding of the control transformer is arranged such that the second winding of the control transformer is arranged in the energy storage means. a first control means configured to be connected to an output terminal of the bonding means, and for controlling the interface of the first winding of the control transformer as a function of the output DC voltage obtained from the constant voltage power supply device; This allows the output DC voltage to be stabilized over a wide range of input/output fluctuations.

Furthermore, the first switching means is configured to be conductive in only one direction, and furthermore, the first switching means has a structure in which the conduction direction of the switch element built in the first switching means is configured to be conductive in only one direction. A unidirectional element is connected in parallel to the switching means so as to conduct in the opposite direction, thereby reducing switching loss of the first switching means and unnecessary radiation from the constant voltage power supply. This can be significantly reduced.

DESCRIPTION OF EMBODIMENTS An embodiment of the present invention will be described below based on the drawings. First, the operation of the present invention will be described based on the basic circuit configuration diagram of the present invention.

A diagram of one basic circuit configuration of the present invention is shown in FIG.

In FIG. 8, . . . is an input DC power source, 6 (7) is a switching means, (b) is a current limiting element, (to) is an energy f-storage means, and its input terminals are A and B.

The output terminals are shown as C and D. Also, (to) is the smoothing circuit, and (b) is the load. Keep the input DC power supply at tolerable pressure...
, switching means u〃, input terminals A and B of the current limiting element (to) and the energy storage means (to) are connected in series,
Further, a current limiting element (b), a switching means (to), and a smoothing circuit (7) are connected in series to the output terminals C and D of the energy product means F. It is connected in parallel to the circuit (7).

In FIG. 3, when the switching means 6υ is turned on, energy is injected as a current 11 from the input DC power source into the energy f-storage means (g). By providing a resonant circuit in the path through which the current flows, as in the conventional example of the current iuC, a sinusoidal current waveform is obtained. E
The resonant circuit is the current limiting element and the input terminal A of the energy storage means (2).

It is a circuit composed of impedance on the B side, and if
Input terminal A of energy accumulation means 1 in F.

If the impedance on the B side is capacitive, it becomes a current limiting element), and if the impedance E is inductive, it becomes a current limiting element). By doing so, a resonant circuit can be constructed. 'Also, in the E current limiting element) t/'iE sinusoidal current j
Since it is an element that determines the period and peak value of +, the peak value of current 11 can be limited by the magnitude of the value of () in the current limiting element. If it is a circle, the value can be made sufficiently small, and furthermore, the value can be set to zero.

In this way, the input terminal A of
, the current flowing into B. 1. According to vc, the energy F- is accumulated in the energy f- storage means ((3), and the energy F-
The quantity is related to the amount of energy f injected by the current i1 per unit time, that is, the switching frequency of the switching means (b).
It also concerns the storage capacity of the storage means.

Next, when the switching means (2) is turned on, the energy f- stored in the energy crystallizing means is transferred from the output terminals C and D of the energy crystallizing means to the current limiting element. -, the switching means are also supplied with 12 current energies to the smoothing circuit (to) through the lamp. The smoothing circuit (to) smoothes the current i2 and supplies energy as an output DC voltage to the load connected to the output terminals a and bPl of the constant voltage electric device a.

In addition, the L distribution current 12 is the energy storage means (to)
By configuring a resonant circuit with the impedance between the output terminals C and D and the E current limiting element, a sinusoidal current waveform is obtained. Here, the relationship between the impedance between the output terminals C and D of the energy storage means (to) and the current limiting element is as follows.
Since the relationship between the impedance between 11j and the current limiting element Kl is the same, it is possible to make the value of the current limiting element (cJf) sufficiently small, and it is also possible to make it zero.
It is Noh.

Here, the energy released from the energy storage means (1) is the voltage value between output terminals C and D indicating the amount of energy stored in the energy storage means (2), and E It is determined by the differential pressure of the voltage value of the smoothing circuit (7), and its emitted energy level is controlled by the switching means & of the above switching means.

Further, the switch means (7) can be forcibly turned on and off by an active element, but it is also possible to configure it by a passive element such as a one-way element.

With the configuration shown in Figure 3, the output terminal a of the constant voltage power supply
, b has an energy of 1,000 yen from the input DC voltage as the output DC voltage.
However, as a control method for stabilizing the output DC voltage, there is a method described below. the switching means (b) for injecting and releasing the energy f- which can be stored in the energy storage means (b);
By controlling the switching frequency in (7) in accordance with the output DC voltage between the output terminals a and b of the constant voltage power supply device d, a stable output DC voltage can be obtained. Even if such a control method is used, the characteristics of the conventional constant voltage power supply device that utilizes the resonance phenomenon are not impaired.

Next, we will explain an embodiment of the present invention using the circuit configuration and operation described in L. However, before that, we will explain how the interface of the first wax wrapper is changed by the supplied signal, which is used in the present invention. An example of a control lance having a variable interface function will be described. FIG. 4 is a block diagram of the control transformer, FIG. 5 is a characteristic diagram thereof, and FIG. 6 is a diagram showing equivalent symbols. In FIG. 4, AC windings Na, Nb, and Nc are provided on each of the legs of a combination of an E-shaped core and a ■-shaped core, or a combination of two E-shaped cores.

A DC winding Ne is provided on the central leg, and a DC current source I is connected to control terminals E and F of the DC winding Ne. Further, A and B are input terminals, and C2D is an output terminal. The AC windings Na and Nb in L are connected in series to form the first winding, and are wound in such a way that the magnetic flux induced in the center leg by the AC current from input terminals A and B is canceled out. . In other words, the magnetic fluxes iz' induced by the AC windings Na and Nb are equal. Furthermore, AC windings Nc, N
The windings d are connected in series to the output terminals C and D to constitute a second winding, and are formed at a constant turns ratio with respect to the AC windings Na and Nb.

Here, magnetic flux is generated in the DC winding NeK by flowing a DC current from the DC current source (2), and the AC windings Na, Nb
Magnetic flux induced by 12. The balance of j＊' is disrupted,
The interface between input terminals A and B changes. FIG. 5 shows the change in impedance between input terminals A and B due to direct current. Therefore, the direct current applied between the control terminals E, F can reduce the interface between the input terminals A and B. An equivalent symbol of a control transformer having the functions described above is shown in FIG. 6, and an embodiment of the present invention using this will be described below with reference to FIG. 7 and subsequent drawings.

FIG. 7 is a circuit configuration diagram of the first embodiment of the final IJJ, in which parts having the same functions as those already explained in FIG. 1 and 1 are given the same reference numerals. Also, Figure -8 (a),
(b), (c), and (d) are operation waveform diagrams of each part in FIG. 7.

In Fig. 7, (b) a< is a switching means that conducts only in the °-force direction, which is composed of a switch element (3 bars 4) and a unidirectional element aha connected in series thereto, and 4 is a current limiter. A as an element: 7 tactance, uo is the 8th
With the control system as shown in the figure, the condenser +j (7
) constitutes an energy f-storage means qη.

(G) is a DC current control circuit, A is a control circuit for stabilizing the output DC voltage, and @J is an oscillation circuit. The input terminal A of the control transformer H is connected to both ends of the BFi capacitor (7), and also serves as the input terminal for the energy storage unit Q.
This is the output terminal of η. The output terminals C and D of the control transformer are the rectifier circuit*(8)(
For example, control 1 @ child E,
F is connected to the output terminal of the DC current control circuit (G). The control circuit consists of a reference voltage source, an error amplifier, etc., which are already known, and output terminals a, b of the constant voltage 'tit aj device applied to the input terminal of the control circuit.
The voltage difference between the DC voltage and a predetermined reference voltage is compared and amplified using an error amplifier, and the output is sent to the DC current control circuit (To), which is input to the DC current control circuit (To). A direct current corresponding to the input signal is supplied to the control terminals E and F of the control transformer (II) to change the interface value between the control transformer E and the output terminals A and 8. is the switching element (3) (
4) is turned on and off alternately at a certain frequency.

The operation of the constant voltage power supply device of this embodiment constructed as described above will be explained below with reference to the waveform diagram of each part in FIG. 8. In FIG. 8, (a) shows the current i flowing from the switching element (3) (4) to the interface 4, 1, and 1, and (b) shows the input terminal A of the control transformer 01, Current ii+ flowing between B,
(C) is the current io flowing between the output terminals C and D of the control transformer qQ, and (d) is the voltage V across the capacitor (7).
FIG. 3 shows the respective operation waveforms of c, and the horizontal axis is the time axis.

Since this embodiment also utilizes the resonance phenomenon shown in FIG. 1, the explanation that overlaps with the conventional example will be omitted. First, when the switching element (3) is turned on, the current i flows between the interface (to) and the capacitor (
7) and the series resonant circuit of the interface of the primary winding of the control transformer IJQ form a sinusoidal waveform, and the period is determined by each constant of the series resonant circuit. The energy A- due to the current i in E is stored in the energy storage means aη, but since the switching means (to) is unidirectional switching as described above, the energy f- in the energy storage means aη in L is stored in the energy storage means aη. Since there is no path for the energy to move elsewhere, it remains stored, and the amount of stored energy is manifested in the phenomenon of an increase in the voltage value of the voltage Vc across the capacitor (7). The above previous work corresponds to the waveform from time [I to time t3 in FIG. 8. Still in the E period,
The energy A-control m+t-lance O in the storage means θη
The current iL flowing between the input terminals A and B of Q has a current waveform corresponding to the voltage across the capacitor (7).

Here, the time point when the voltage VC across the capacitor (7) becomes higher than the output DC voltage Vo converted to the primary side of the control transformer 4 (time t2 in FIG. 8, and V
C2), the unidirectional element in the rectifier circuit (8) acts as a switching element and changes from an off state to an on state, and the energy f- of the capacitor (7) is transferred to the output terminal C of the control transformer 4, The current is supplied to the negative M (10) from between D through the rectifier circuit (8) and the smoothing capacitor (9).The current at this time is the current type 0 between the output terminals C and D of the control transformer DI. , E current jo has a sinusoidal waveform due to the resonant circuit composed of the effective leakage interface as a current limiting element of the control transformer q and the energy storage means αη, and the period varies depending on each constitution. The following operation is determined by the waveform from time t2 to time [4] in FIG.
The voltage Vc across E decreases due to the current iL flowing between the input terminals A and B of the control transformer σQ, and at time tI' when the switching element (4) is turned on, the voltage Vc across E becomes Vcl. Hereinafter, from time t+' to time tII, from the above-mentioned time to time 1. The phenomenon up to / appears with the polarity reversed, and when the switching element (3) is turned on at time [7], the waveform becomes exactly the same as the waveform from time [1], and the same phenomenon is repeated.

Next, a control method for stabilizing the output DC voltage VO will be described. The basic principle of the control method is that the voltage on the primary side of the control transformer 4 (in FIG. 7, the voltage equal to the voltage Vc across the capacitor (7) +iii) is a constant voltage 11
Utilizing the fact that energy is transmitted to the secondary side of the control transformer when the output DC voltage of the source device kt becomes higher than the primary side conversion value of the control transformer, calculate the amount of energy] The output voltage depends on the input voltage.
It stabilizes 0. Also, the control transformer Q<
The voltage VC on the primary side of 9 is equal to the energy storage means Q″
Since the energy stored in I) indicates -1; t, it is possible to control the energy stored in the energy storage means Uη, that is, the output voltage of E
stabilize.

It turns out.

Hereinafter, a vine control method that implements the above method will be specifically described.

The intertasis value between the input terminals A and B of the hg control transformer IJ (9) determines the amount of energy stored in the energy storage means αη. When the interface value of is increased (decreased), the amount of energy stored in the energy A-I & 4-response αη increases (decreases), and as explained in the operation described in 1fJ, the output energy becomes F Compare the output DC voltage VO between the output terminals a and b of the t4fJ specified voltage power supply α with the reference voltage in the control circuit 0 barrel, using the fact that it increases (decreases) depending on the amount of energy supplied. The lightning current control circuit uses a signal according to the difference.
A direct current flows through the control terminals E and F of the control transformer QQ, and control is performed by changing the intertasis value between the input terminals A and B of the L-order pure transformer OQ.

Therefore, the present invention uses a method of changing the interface value between the input terminals A and B of the control transformer uQ. Furthermore, as can be seen from the operating waveforms in Figure 8, all of the flowing currents are sinusoidal, making it possible to stabilize the output DC voltage without sacrificing any of the characteristics of a constant voltage power supply that utilizes the resonance phenomenon. It is something that can be done.

Fig. 9 shows the second embodiment of the final j, and Fig. 10 shows the fourth embodiment.
Three waveforms are shown. In explaining the second embodiment, we will introduce the same machine as that described in the first embodiment (Fig. 7). J
No particular explanation will be given regarding the case where the same work is done in .

The difference from the first embodiment is the configuration of the switching means tzl@ in FIG. 9.

The switching means 1, 7υ (■c dimension, switching element [3) (4) are connected so as to be electrically conductive in the opposite direction. , that is, the input DC power supply rl
) With respect to (2), reverse bias t′L is applied to the switching elements (3) and (4), and one i51 element (
It has a configuration in which an iH effect (for example, a diode) is connected. The energy stored in the above unidirectional element (1υ1 layer is energy storage means lJ?)! A portion of the energy is supplied to the input DC power source (1) or (2) as regenerative energy via the four unidirectional elements (11).

Next, its operation will be explained with reference to the operation waveform diagram in FIG. 10. Note that (a) and (b) in FIG.
, (c) and (d) are (a), (b),
fc) is an operation waveform diagram of the same location as (d).

Since the basic operation is the same as that of the first embodiment described above, here, the switching means (I)4 has a different configuration from the first embodiment, so that the energy 1,000 - The input DC power supply (sumata Vi(2
) will be described with reference to FIGS. 9 and 10. First, when the switching element (3) is turned on at time [1], the current l flowing through the system is equal to
) and the E and J tuftances between the input terminals A and B of the control transformer O0. At time t3 when the sinusoidal current l has finished flowing, when the voltage Vc across the capacitor (7) becomes higher than the input DC power supply (1), the energy of the energy storage means Uη becomes
It is regenerated as a regenerative current to the input DC power supply (1) via the interface (5), the regenerative element, and the child Oυ (time t
3 to time b). By utilizing the above phenomenon, it is possible to greatly change the amount of energy f stored in the energy storage means (17).Also, as in the first embodiment, the above phenomenon can be applied to the control transformer (11). input terminal A,
It is closely related to the interface value between B.

That is, this is because the amount of regenerated energy is determined by the amount of energy received in the energy storage means Oη. Therefore, the control method for stabilizing the voltage vO at the output terminals a and b of the constant voltage power supply device can be performed in exactly the same manner as in the first embodiment, and since all the flowing currents are sinusoidal, the resonance The output DC voltage can be stabilized without impairing the characteristics of the constant voltage power supply device that utilizes this phenomenon.) Next, an eighth embodiment of the present invention, which is a different configuration of the first embodiment of the present invention, will be described. FIG. 11 shows its operating waveform diagram, and FIG. 12 shows its operating waveform diagram. In FIGS. 11 and 12, parts having the same functions as those described in the first embodiment (FIG. 7) are denoted by the same reference numerals. In this third embodiment, the half abscission configuration of the first embodiment is replaced with a configuration using a single switching element, and the basic operation is almost the same as that of the first embodiment.

' In Fig. 11, an interface Qυ, an energy storage means Oη, and a switching means (2) are connected in series to the input DC power supply (c), and the switching means () is connected in series to the input DC power supply (c). (ii (11)
Similarly, a unidirectional element and a switching element are connected in series.

Hereinafter, the operation of the third embodiment will be explained with reference to FIG. Unlike the first embodiment, since there is only one switching means, the energy to be injected into the energy storage means θη is injected only from one direction. Therefore, compared to the operating waveform diagram of FIG. 8 of the first embodiment and the waveform diagram of FIG. 12 of the third embodiment, only the waveform of the current i flowing through the system differs. Regarding the operation of other parts, please refer to ttr
Since the principle is exactly the same as that of the embodiment t, the operating waveforms are also the same. Therefore, the output DC voltage vO between the output terminals a and b of the constant voltage power supply device can be stabilized using the same control method.

In this way, the first embodiment of the present invention can be configured with just one switching means like the embodiment @8, and can be configured using exactly the same limiting method as the first embodiment. The output IB current voltage can be stabilized without impairing the characteristics of a constant voltage power supply device that utilizes a resonance phenomenon.

Next, FIG. 13 shows a fourth embodiment of the present invention in which the second embodiment of the present invention is realized with a different configuration, and FIG. 14 shows its operating waveform diagram. In FIGS. 13 and 14, J described in the second embodiment
Components having the same functions as those described above are given the same reference numerals. In this fourth embodiment, the hard abscisin configuration of the i$2 embodiment is replaced with a configuration using a single switching element, and the basic operation is almost the same as the second embodiment.

In FIG. 13, an interface (15, energy storage means (17), switching means u7) is connected in series with the input DC power supply (a), and the switch means (b) shown in L is Switching means V in Figure 9! υ(2
) as well as switching confectionery with turning element ＼□□□
are connected in parallel.

The operation of the fourth embodiment will be explained below with reference to FIG. 14, but parts that operate the same as those of the second embodiment will be omitted, and only the different parts will be described. Unlike the second embodiment, since there is only one switching means, the energy injected into the energy storage means a'i) is injected only from one direction. Therefore, compared to FIG. 10 of the operating waveform diagram of the second embodiment, the current i flowing through the system
They differ only in their waveforms. Furthermore, since the operation of other parts is based on exactly the same principle as the second embodiment, the operation waveforms are also the same. Therefore, the control method is exactly the same, and the output DC voltage v between the output terminals a and b of the constant voltage power supply device is
O can be stabilized.

In this way, the second embodiment of the present invention can be configured with one switching means like the fourth embodiment, and the resonance can be controlled by the same control method as the second embodiment. The output DC voltage can be stabilized without impairing the characteristics of the constant voltage power supply device that utilizes this phenomenon.

In addition, as an example of the present invention, the Herabsisin configuration and 1
Although the explanation has been made regarding a circuit composed of stones, the circuit configuration is not limited to the above, and the output DC voltage can be stabilized using a similar control method even in a full bridge configuration using four switching means, for example. I can do it.

In addition, although the switching means has a circuit configuration that combines a switching element and a unidirectional element, it is also possible to use a thyristor or transistor that conducts in only one direction, or a MOSFET that conducts in both directions. It is a Noh play that can also be used in combination.

The energy storage means also has a circuit composed of a capacitor and a control transformer, but the energy storage means is not limited to the circuit configuration described in E, and has the function of storing energy f-. , which exhibits capacitance or i-induction as an impetant, and the output! Any device may be used as long as it can control the amount of energy f- stored according to the voltage value of the a current.

Although a DC power source was used as the input power source in the embodiment of the present invention,
Naturally, the DC voltage obtained from the AC power supply by the rectifier circuit can also be used as the input DC power supply.From the explanation of the effect of this invention, it is clear that the unfired 1=l11
The method is to configure a resonant circuit of a constant voltage power supply using a resonance phenomenon with a current limiting element and an energy storage means, and to control the amount of energy f that can be stored in the energy storage means. Therefore, the output DC voltage of the conventional constant voltage power supply device that utilizes the resonance phenomenon can be obtained as a stable output DC voltage even in a wide range of input/output fluctuations. Furthermore, because it does not lose any of the characteristics of low switching loss and low radiation noise that conventional constant voltage power supplies have, it can be used for acoustic and completely sealed power supplies, which were difficult to use in the past. be.

[Brief explanation of the drawing]

Figure 1 is a circuit diagram of a conventional constant-voltage power supply using resonance phenomenon, Figure 2 is its operating waveform diagram, Figure 8 is an uninvented basic circuit configuration diagram, Figure 4, 5 and 6 are block diagrams, characteristic diagrams, and isometric symbol diagrams of the control transformer used in the present invention, and FIGS. 7 and 8 are circuit block diagrams and their equivalents of the first embodiment of the present invention. The operating waveform diagrams, FIGS. 9 and 10, are the circuit configuration diagram of the second embodiment of the present invention and its operating waveform diagrams, FIGS. 11 and 12.Fi
A circuit configuration diagram and its operating waveform diagram when the switching means of the first embodiment is composed of one, and FIGS. 13 and 14 are circuit diagrams when the switching means of the second embodiment is composed of one. FIG. 2 is a configuration diagram and its operation waveform diagram. (1 bar 2) (e) (7)...Input DC power supply, (3 bar 4
) @... Switching element, (7) (9)... Capacitor, (3)... Rectifier circuit, o1@... Load, Q
υIJ'4e14...unidirectional element, (13(14)
pi)■(A)(B)suυ((9...Switching hand IJLar3-...Interftance, CI!...Control 1 transformer, θη((;Y...Energy 1,000-Storage means,
θ barrel...DC current control circuit, (11...control circuit,
σt...Oscillation circuit, 6th section n-...Current limiting element, (to)
...Smoothing circuit agent Yoshihiro Moriki (Fig. 4, Fig. 7, Fig. 8, 1yo Ct) Fig. 9, W, Fig. 11, False p, Fig. 1/Fig. 13, Fig. 6, Fig. 14 it b lJk tsr , -lx'b'Grsrif
JJct>

Claims (1)

[Claims] 1. A series connection including at least a first switching means that operates on and off with respect to an input DC power supply, a first current limiting element, and an input terminal of an energy f-storage means. A circuit is connected to the output terminal of the energy f-storage means, and a second switching means that operates on and off, a second current limiting element, and a smoothing circuit are connected to obtain an output DC voltage. a constant voltage power supply in said energy f-storage means, comprising a control transformer for changing the interface of the first winding by at least a small amount of the supplied signal pressure; a winding connected to the output terminal of the energy storage means;
A constant voltage power supply device comprising: control means for controlling an intertasis of a first winding of the control transformer as a function of an output DC voltage obtained from the constant voltage power supply device. 2. Claim 1, characterized in that the first switching means is configured to conduct in only one direction.
Constant voltage power supply device as described in section. 3. The first switching means is characterized in that a unidirectional element is connected in parallel to the switching element so as to conduct in a direction opposite to the conduction direction of the built-in switching element. Constant voltage power supply device as described in section.