JPS6069929A - Reception system for eliminating adjacent interference in digital communication system - Google Patents
Reception system for eliminating adjacent interference in digital communication systemInfo
- Publication number
- JPS6069929A JPS6069929A JP17711683A JP17711683A JPS6069929A JP S6069929 A JPS6069929 A JP S6069929A JP 17711683 A JP17711683 A JP 17711683A JP 17711683 A JP17711683 A JP 17711683A JP S6069929 A JPS6069929 A JP S6069929A
- Authority
- JP
- Japan
- Prior art keywords
- wave
- signal
- interference wave
- carrier
- carrier wave
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
- H04B1/12—Neutralising, balancing, or compensation arrangements
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/22—Demodulator circuits; Receiver circuits
- H04L27/227—Demodulator circuits; Receiver circuits using coherent demodulation
- H04L27/2275—Demodulator circuits; Receiver circuits using coherent demodulation wherein the carrier recovery circuit uses the received modulated signals
Abstract
Description
【発明の詳細な説明】
本発明はディジタル通信方式の変調方式のうち、位相ソ
フト・ギーイング(Phase SI+ift Key
iIlg ;以下[P S K Jという。)の2相及
び4相1’ S’ Kにおける隣接干渉波を除去し、周
波数有効利用に寄与する受信方式の改良に関するもので
ある。DETAILED DESCRIPTION OF THE INVENTION The present invention utilizes phase soft steering (Phase SI+ift key) among modulation methods for digital communication systems.
iIlg ;Hereinafter referred to as [PSKJ. This invention relates to an improvement in a reception method that eliminates adjacent interference waves in two-phase and four-phase 1'S' K of 2-phase and 4-phase 1'S' K, contributing to effective frequency utilization.
第1図は、これ捷で採用されてきた周波数割当ての原理
を示す図で、各信号のスペクトルと倣送周波数(Fl、
F2. F3.・・・で示しである。Δlimは、周
波数間隔。)を示したものである。図が示すように、周
波数割当ての原理は隣接信号のスペクトルが互いに重な
シ合わないように、ΔFの周波数間隔を離して割り当て
ることであった。このような場合の受信機構造は第2図
に示すように、自局に送出された信号のみを前置フィル
タ(以下「BPFp」という。)(2)で抽出し、受信
機が飽和動作を起こさないように、前置AGC回路(以
下[AGCpjという。)(3)でレベル制御し、後は
搬送波再生回路(5)で搬送波を再生するか、受信波を
1ビツト遅延させ、その信号を使って検波/判定回路(
4)でマークが送られたのが、スペースが送られたのか
を判定して、データ(6)として出力すればよかった。Figure 1 is a diagram showing the principle of frequency allocation that has been adopted in this system, showing the spectrum of each signal and the transmission frequency (Fl,
F2. F3. ...is shown. Δlim is the frequency interval. ). As shown in the figure, the principle of frequency allocation is to allocate frequencies at intervals of ΔF so that the spectra of adjacent signals do not overlap with each other. As shown in Figure 2, the receiver structure in such a case extracts only the signal sent to its own station using a pre-filter (hereinafter referred to as "BPFp") (2), and the receiver performs saturation operation. To prevent this, the level is controlled by the pre-AGC circuit (hereinafter referred to as AGCpj) (3), and then the carrier wave is regenerated by the carrier wave regeneration circuit (5), or the received wave is delayed by 1 bit, and the signal is Use the detection/judgment circuit (
It would have been better to determine whether a mark or a space was sent in step 4) and output it as data (6).
しかし、このような周波数割当てでは受信機の構造は簡
単で良いが、割り当てる周波数の数が少ないという欠点
がある。However, although this type of frequency allocation allows the receiver to have a simple structure, it has the disadvantage that the number of allocated frequencies is small.
本発明はスペクトルの重畳しあった周波数割当てにおい
て、受信機で隣接干渉波を推定によシ発生させ、その干
渉波を受信信号から引き算により除去することが特徴で
あって、その目的はスペクトル重畳した周波数割当てを
可能にし、周波数有効利用を図る周波数割当てを実現す
ることである本発明の構成及び作用について説明する。The present invention is characterized by estimating and generating adjacent interference waves in a receiver in frequency allocation where spectra are superimposed, and removing the interference waves by subtraction from the received signal. The structure and operation of the present invention, which is to realize frequency allocation that enables efficient frequency allocation and achieves frequency allocation that aims at effective frequency utilization, will be explained.
第3図に、スペクトルが重畳しあった状態の周波数割当
ての様子を示す。スペクトルは隣接波どうしで1部重畳
しあっている。割り当て搬送周波数をt f’+ f2
+ f3+・・・そして周波数間隔をΔfで示しである
。1倍号の占有周波数帯幅が第1図の場合と同じで、Δ
f−ΔF/nなら、第1図の周波数割当てより第3図の
ような割り当てのやりかたの方が0倍よけいに周波数の
数がとれる。しかし、問題点はスペクトル重畳により隣
接干渉波のスペクトルが強大になったとき、通信回線が
破壊されてしまうことである。その様子を第3図に点線
で示した。搬送周波数がf+の信号(以下「fl信号」
という。)を受信している受信機で、帯域フィルタでf
11倍を抽出しても、搬送周波数がf2の信号(以下「
f22倍」という。)のスペクトルが大量に帯域内に落
ち込んでくるため、受信機はf22倍の干渉成分で占有
されf+倍信号受信することは不可能になってしまう。FIG. 3 shows how frequencies are assigned in a state where spectra are superimposed on each other. Adjacent waves in the spectrum partially overlap each other. The allocated carrier frequency is t f'+ f2
+f3+...and the frequency interval is indicated by Δf. The occupied frequency bandwidth of the 1st sign is the same as in Figure 1, and Δ
If f-ΔF/n, the number of frequencies can be increased by a factor of 0 by the allocation method shown in FIG. 3 than by the frequency allocation method shown in FIG. However, the problem is that when the spectrum of adjacent interference waves becomes stronger due to spectrum superposition, the communication line will be destroyed. This situation is shown by the dotted line in Figure 3. A signal with a carrier frequency of f+ (hereinafter referred to as "fl signal")
That's what it means. ) with a bandpass filter.
Even if 11 times the frequency is extracted, the signal whose carrier frequency is f2 (hereinafter referred to as “
f22 times." ) falls within the band, and the receiver is occupied by f22 times the interference component, making it impossible to receive the f+ times signal.
この状態をさけるだめの受信機を第4図に示す。受信信
号がアンテナ(1)、BPI;’p (2)及びAGC
p (3)を通るのは従来の受信機構造と同じである。FIG. 4 shows a receiver that avoids this situation. The received signal is antenna (1), BPI;'p (2) and AGC
The path through p (3) is the same as in the conventional receiver structure.
この後、隣接干渉波に同調した帯域フィルタ(以下[B
PFuJという。After this, a bandpass filter (hereinafter [B
It's called PFuJ.
)(9)でf11倍成分を排除し干渉波のf22倍成分
を抽出し、搬送波再生回路(10)で干渉波の搬送波を
再生する。干渉波発生回路(12)は、 BPFu(9
)から得た干渉波と、搬送波再生回路(10)から得た
同相の搬送波又はそれをπ/2移相器(11)を通して
得た直交搬送波を入力し、干渉波を予測発生する装置で
ある。この装置の構造を第5図に示す。端子(17)に
は搬送波を入力し、端子(18)には干渉波を入力する
。乗算器(19)で干渉波を同期検波しベースバンド信
号を発生させる。この信号は歪んでいるので、リミタ(
20)で矩形パルスに変換し、送信側と全く同じ特性の
低域フィルタ(2J)でスペクトル成形した後、端子(
17)から入力した搬送波と乗算器(22)で掛は算し
被変調波を再び発生させる。一方、乗算器(19)から
出力した信号の平均電力をAGC制御信号発生器(24
)で測定してコヒーレン)AGC制御信号を得、AGC
回路(23)を動作させ、干渉波の振幅を制御して予測
発生して得た干渉波を端子(25)より出力する。2相
P S Kの場合、干渉信号発生回路は(12)■だけ
でよい。4相I) S Kの場合は、(12)■と(1
2)■が必要となる。これらの出力信号を加算器(13
)で合成した後、D P I” p (2)で発生した
歪を帯域フィルタ(14)で再び発生させる。これらの
信号処理にかかわる時間遅れを遅延回路(15)で調節
した後、減算器(16)で受信波から予測干渉波を引き
算し干渉波を除去する。後の受信機構造は従来の受信機
と同じで、検波/判定回路(4)や搬送波再生回路(5
)などがUN <。この受信機における動作は、干渉波
の電力が大きくなればなるほど推定が正しくなり干渉波
除去効果があられれる一方、干渉波が小さくなればAG
C回路(23)により干渉波の振幅を小さくシ、干渉波
の発生を押さえるという働きをする本発明により、ディ
ジタル通信方式における隣接干渉波を除去できるので、
スペクトルを重畳した状態で周波数割当てが可能となり
、周波数有効利用を図ることができる。さらに、本方式
はl) S■(に適用することを目指たものであるが、
原理的には他のティジタル変調方式にも適用可能である) (9) removes the f11 times component and extracts the f22 times component of the interference wave, and the carrier wave regeneration circuit (10) regenerates the carrier wave of the interference wave. The interference wave generation circuit (12) is composed of BPFu (9
) and an in-phase carrier wave obtained from a carrier regeneration circuit (10) or an orthogonal carrier wave obtained by passing it through a π/2 phase shifter (11), and predictably generates an interference wave. . The structure of this device is shown in FIG. A carrier wave is input to the terminal (17), and an interference wave is input to the terminal (18). A multiplier (19) synchronously detects the interference wave and generates a baseband signal. Since this signal is distorted, a limiter (
20) into a rectangular pulse, and after shaping the spectrum with a low-pass filter (2J) with exactly the same characteristics as the transmitting side, the terminal (
The carrier wave input from 17) is multiplied by the multiplier (22) to generate a modulated wave again. On the other hand, the average power of the signal output from the multiplier (19) is converted to the AGC control signal generator (24).
) to obtain the coherence) AGC control signal, and
The circuit (23) is operated to control the amplitude of the interference wave and output the predicted interference wave from the terminal (25). In the case of a two-phase PSK, only the interference signal generating circuit (12) (1) is required. In the case of 4-phase I) S K, (12) ■ and (1
2) ■ is required. These output signals are sent to an adder (13
), the distortion generated in DPI"p (2) is generated again in the bandpass filter (14). After adjusting the time delay involved in these signal processings in the delay circuit (15), the subtracter In (16), the predicted interference wave is subtracted from the received wave to remove the interference wave.The subsequent receiver structure is the same as the conventional receiver, including the detection/judgment circuit (4) and the carrier regeneration circuit (5).
) etc. are UN <. The operation of this receiver is that as the power of the interference wave increases, the estimation becomes more accurate and the interference wave removal effect increases, while as the interference wave becomes smaller, the AG
The present invention, which works by reducing the amplitude of interference waves and suppressing the generation of interference waves by the C circuit (23), can eliminate adjacent interference waves in digital communication systems.
It becomes possible to allocate frequencies in a state where spectra are superimposed, and it is possible to use frequencies effectively. Furthermore, this method aims to be applied to l) S■ (
In principle, it can also be applied to other digital modulation methods.
第1図は従来の周波数割当てを示す図、第2図は一般的
なティジタル通信における受信機ブロック図、第3図は
スペクトル重畳における周波数割当てを示す図、第4図
は本発明における受信機ブロック図、そして第5図は干
渉波発生回路のブロック図である。
1・・・アンテナ、2,9.14・・・帯域フィルタ、
3.23・・・AGC回路、4・・・検波/判定回路、
5,10・・・搬送波再生回路、11・・・π/2移相
器、12・・・干渉波発生回路、 13・・・加算器、
15・・・遅延回路、16・・・減算器、17、18.
25・・・端子、19.22・・・乗算器、20・・・
リミタ、21・・・低域フィルタ、24・・・AGC制
御信号発生器。
特許出願人 郵政省電波研究所長
第 2 口
第 3 図
第 4(!1
7
第 5 図Fig. 1 is a diagram showing conventional frequency allocation, Fig. 2 is a receiver block diagram in general digital communication, Fig. 3 is a diagram showing frequency allocation in spectrum superimposition, and Fig. 4 is a receiver block diagram in the present invention. FIG. 5 is a block diagram of the interference wave generation circuit. 1...Antenna, 2,9.14...Band filter,
3.23...AGC circuit, 4...Detection/judgment circuit,
5, 10... Carrier wave regeneration circuit, 11... π/2 phase shifter, 12... Interference wave generation circuit, 13... Adder,
15...Delay circuit, 16...Subtractor, 17, 18.
25...terminal, 19.22...multiplier, 20...
Limiter, 21...Low pass filter, 24...AGC control signal generator. Patent Applicant: Director, Radio Research Institute, Ministry of Posts and Telecommunications Part 2, Figure 3, Figure 4 (!1 7, Figure 5)
Claims (1)
ムにおいて、隣接干渉波を帯域フィルタ(9)で抽出し
、その信号の搬送波を搬送波再生回路(10)で発生さ
せ、同相搬送波と直交搬送波をそれぞれ異なる干渉波発
生回路(12)に供給し、干渉波発生回路(12)では
、帯域フィルタ(9)の出力信号と入力された搬送波と
を乗算器(19)で掛は算してベースバンド信号を発生
させ、リミタ(20)により矩形パルスに変換したのち
、低域フィルタ(21)で変調信号に変換し、乗算器(
22)で入力されている搬送波と掛は算して再び被変調
波を発生させ、乗算器(19)出力後の信号の平均電力
を測定するAGC制御信号発生器(24)からの制御で
動作するAGC回路(23)で振幅を決定し、搬送波と
同相の干渉波と直交の干渉波をそれぞれ異なる干渉波発
生回路(12)から出力し、それらを加p器(18)で
合成して、受信信号から減算器(16)で引き算するこ
とにより隣接干渉波を除去することを特徴とするディジ
タル通信方式における隣接干渉波除去受信方式。In a communication system in which the modulation method and adjacent frequency interval are determined, adjacent interference waves are extracted by a bandpass filter (9), the carrier wave of the signal is generated by a carrier wave regeneration circuit (10), and the in-phase carrier wave and orthogonal carrier wave are respectively generated. The interference wave generating circuit (12) multiplies the output signal of the bandpass filter (9) and the input carrier wave by a multiplier (19) to generate a baseband signal. is generated, converted into a rectangular pulse by a limiter (20), converted into a modulation signal by a low-pass filter (21), and then sent to a multiplier (
The multiplier is multiplied by the carrier wave input in 22) to generate a modulated wave again, and operates under the control of the AGC control signal generator (24), which measures the average power of the signal after output from the multiplier (19). The amplitude is determined by the AGC circuit (23), and an interference wave in phase with the carrier wave and an interference wave orthogonal to the carrier wave are output from different interference wave generation circuits (12), and they are combined by a p adder (18). An adjacent interference wave removal reception method in a digital communication system, characterized in that adjacent interference waves are removed by subtracting them from a received signal using a subtractor (16).
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP17711683A JPS6069929A (en) | 1983-09-27 | 1983-09-27 | Reception system for eliminating adjacent interference in digital communication system |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP17711683A JPS6069929A (en) | 1983-09-27 | 1983-09-27 | Reception system for eliminating adjacent interference in digital communication system |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS6069929A true JPS6069929A (en) | 1985-04-20 |
Family
ID=16025438
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP17711683A Pending JPS6069929A (en) | 1983-09-27 | 1983-09-27 | Reception system for eliminating adjacent interference in digital communication system |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS6069929A (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2002507361A (en) * | 1997-06-30 | 2002-03-05 | トムソン コンシユーマ エレクトロニクス インコーポレイテツド | Reverse polarization interference cancellation in satellite communications. |
JP2017011577A (en) * | 2015-06-24 | 2017-01-12 | 日本電信電話株式会社 | Crosstalk compensation device and crosstalk removal method |
-
1983
- 1983-09-27 JP JP17711683A patent/JPS6069929A/en active Pending
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2002507361A (en) * | 1997-06-30 | 2002-03-05 | トムソン コンシユーマ エレクトロニクス インコーポレイテツド | Reverse polarization interference cancellation in satellite communications. |
JP2017011577A (en) * | 2015-06-24 | 2017-01-12 | 日本電信電話株式会社 | Crosstalk compensation device and crosstalk removal method |
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