JPS6033708A - Oscillator - Google Patents

Abstract

PURPOSE:To obtain an oscillator whose oscillated frequency is controlled by a digital signal by connecting a voltage variable reactance element to an open terminal of a tuner comprising electrodes provided via a dielectric and controlling the element by a D-A converter. CONSTITUTION:An input terminal 16 of the tuner 17 comprising the dielectric and the electrodes 18, 19 is connected to an input terminal or an output terminal of a feedback amplifier 15 and a voltage variable capacitance diode 20 is connected as the variable reactance element. An analog output voltage of the D-A converter 23 is supplied to the voltage variable capacitance diode 20 via an AC block resistor 22 so as to conduct variable tuning control for a variable tuner 21. The oscillating frequency of the oscillator including the tuner constituted incorporatedly is controlled by a digital signal.

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to a tuned oscillation device that can be used in transmitters and receivers of televisions, radios, stereo tuners, personal radios, and other communication devices in general.

Conventional configurations and their problems In recent years, the number of broadcast waves from televisions and radios and communication waves from communication devices has increased, and the performance of tuned oscillators that oscillate desired signals as the local oscillator of receivers requires high tuning. Accuracy, stability and reliability are required. On the other hand, reducing the manufacturing costs of receivers, transmitters, and communication devices that install tuned oscillators is also a major issue, and the development of fundamental new technology for the components of tuned oscillators in the high frequency section, which is particularly difficult to rationalize. is especially needed.

A conventional oscillation device will be described below with reference to the drawings.

FIG. 1 is a circuit diagram of a conventional oscillation device. 1
is a feedback amplifier, and its input terminal or output terminal 2
was connected to tuner 3. In the tuner 3, 4 is a tuning coil, 6 is a trimmer capacitor, and 6 is a voltage variable capacitance diode. The voltage variable capacitance diode 6 was supplied with the voltage of a DC power source 8 after being divided into voltages by a potentiometer 9 via a resistor 7 for blocking AC signals. By changing the voltage division ratio in the potentiometer 9, the control voltage of the voltage variable capacitance diode 6 is changed, and the tuning frequency in the tuner 3 is variably controlled.

Further, FIG. 2 is a diagram showing a conventional component configuration of the tuner 3 shown in FIG. 1. 1o is a tuning coil, 11 is a trimmer capacitor, and 12 is a voltage variable capacitance diode, each connected by circuit conductors 13 and 14, respectively.

However, in the above configuration, the inductor and capacitor components are larger in size than other high-frequency components, and their height is particularly high, which hinders the miniaturization and thinning of equipment in which the oscillation device is installed. are doing.

- The inductance of an inductor component is subject to deviation due to mechanical vibration, and the ferrite core has a large temperature dependence, so the inductance is unstable, and the tuning frequency of the tuner fluctuates greatly. Therefore, even if an oscillation device is configured, its oscillation frequency will vary greatly depending on the surrounding conditions. ■ Inductor and capacitor components exist as separate components and are connected by long circuit conductors, so lead inductance and stray A large number of capacitors are generated, making the operation of the tuning circuit unstable. As a result, it is not possible to ensure sufficient tuning selection characteristics, and further disadvantages occur such as unnecessary resonance states appearing at uncertain frequency points, making it impossible to realize the oscillation device as designed. . As a result, abnormal oscillation occurs, an increase in harmonic components in the two oscillation signals of the unnecessary signal, an increase in distortion due to this, and a narrowing during change in the variable oscillation frequency.

Furthermore, unnecessary oscillation signals oscillated from the oscillation device itself may cause intermodulation interference or spurious signal radiation interference.

■ Since a tuner is a collection circuit of individual parts with independent minimum unit functions, there are limits to reducing the number of parts and rationalizing manufacturing.

Furthermore, the control voltage for the voltage variable capacitance diode is unstable, and therefore the tuning accuracy of the tuner is significantly degraded. As a result, the required selection characteristics cannot be secured,
A change in the oscillation frequency due to a change in the load condition in the feedback amplifier causes a change in distortion due to a change in the fundamental wave level and harmonic component level in the oscillation signal, and also a change in the intermodulation interference rejection characteristics and spurious interference rejection characteristics.

■ Digitalization, which is a popular trend in the industrial world as a control system configuration technology, cannot be matched with LSI, and it is not possible to realize advanced multifunctional control of oscillators and equipment that uses them. It had some problems.

OBJECTS OF THE INVENTION The purpose of the present invention is to realize an oscillation device equipped with a tuner made of an integrated structure of inductor parts and capacitor parts, and to oscillate the oscillation device including the tuner made of the integrated structure using a digital signal. An object of the present invention is to provide an oscillation device that allows control of the tuning frequency.

Structure of the Invention The oscillation device of the present invention is constructed by setting terminals connected to the ground of electrodes that are arranged opposite to each other via a dielectric material or arranged in parallel on the surface of a dielectric material so that they are on opposite sides of each other. A voltage variable reactance element is connected to an open terminal of one of the electrodes of the tuner, and an input terminal or an output terminal of a feedback amplifier is connected to an open terminal of one of the electrodes of the tuner, and D- The tuning control code is input to the control section consisting of the A converter, and the analog output voltage from the control section is supplied to the variable voltage distribution reactance element. In an electrode, one electrode acts as a distributed inductor, and the electrode acting as a small distributed inductor and the other electrode face each other or are placed in a dish, forming an open-ended distributed constant circuit, thereby generating a negative reactance. By realizing the distributed capacitance of By using the output voltage of the D=A converter as the control voltage of the voltage variable reactance element connected to this tuning circuit, the oscillation frequency can be variably controlled by arbitrarily setting the digital code, which is a tuning control signal. It is something that is made to work.

DESCRIPTION OF EMBODIMENTS Hereinafter, embodiments of the present invention will be described with reference to the drawings.

FIG. 3 shows a circuit configuration diagram of an oscillation device in an embodiment of the present invention. The input or output terminal 16 of the feedback amplifier 15 is connected to a tuner 17 . Tuner 17
In the figure, reference numeral 18 denotes a transmission line electrode having a combined inductance of a distributed inductor and a lumped inductor generated by bending the transmission line. On the other hand, reference numeral 19 is a transmission line electrode that faces or is in a plate with the transmission line electrode 18 via a dielectric (not shown) or on its surface. form a transmission path that generates Here, the ground terminals of the respective transmission line electrodes 18 and 19 are set to be on opposite sides. An input terminal 16 (common with the input terminal or output terminal 16 of the feedback amplifier 16) of the parallel tuner 17 is set to an open terminal of the transmission line electrode 18.

Furthermore, a voltage I variable capacitance diode 20 is connected as a variable reactance element to the input terminal 1e set as an open terminal of the transmission line electrode 18. Tuner 17 and voltage variable capacitance diode 20
The +Tr tuning transformer adjuster 21 is formed by ◎The variable tuning control in the variable tuner 21 depends on the control voltage supplied to the voltage variable capacitance diode 2o via the AC blocking resistor 22. The analog output voltage of the D-A converter 23 is supplied as the control voltage, and the input terminal 24 of the D-A converter 23
A digital signal code for tuning control is input to the unit, and its operating function constitutes a control unit.

FIG. 4 shows a configuration circuit diagram of an oscillation device in another embodiment of the present invention. The configurations and connection configurations of the feedback amplifier 15 and variable tuner 21 are the same as those explained in FIG. 3 above. on the other hand,
As a control unit, the input terminal 24 of the D-A converter 23
A digital signal processor 26 consisting of a latch, RAM, or ROM is connected to and supplied with the digital output signal of the digital signal processor 25.

This digital signal processor 26 functions to store a digital signal code for tuning control inputted to its input terminal 26 and to convert it into another digital signal code.

FIG. 5 shows a configuration circuit diagram of an oscillation device in another embodiment of the present invention. to feedback amplifier 1 and I'T]
The configuration of each modulation tuner 21 and its connection configuration are the same as those explained in FIGS. 3 and 4 above. On the other hand, as a control section ←12, a digital signal processor 26 consisting of a latch, RAM, or ROM is connected to the input/terminal 24 of the D-A converter 23, and a digital signal processor 250 input terminal 26 is installed.
A code converter 27 is connected and installed, and the digital output signal of the code converter 27 is connected to the digital signal processor 25.
supplied to This code converter 27 operates to convert the serial format digital signal code for the synchronization signal inputted to its input terminal 28 into a parallel format digital signal code.

In the embodiments shown in FIGS. 3 to 6 above, each of the terminals set to ground in each tuner 17 is not connected to ground, but is used as a common terminal in each tuning 17, and is connected to each feedback amplifier. The desired purpose can also be achieved by connecting to other circuits including 16. Further, the input terminal 16 of the tuner 17 is not limited to being set at the tip of each transmission line electrode 18, but can be set at any position having the required impedance. Regarding the installation position of the variable voltage capacitance diode 20, the transmission line electrode 1
The connection is not limited to a predetermined position in the transmission path electrode 18, but the desired purpose can be achieved even if the connection is made in any arbitrary position in the transmission line electrode 18.

In the embodiments shown in FIGS. 3 to 5 above, if it is necessary to adjust the tuning frequency in each tuner 17, a required portion of the transmission line electrode 19 is arbitrarily cut out or the transmission line By arbitrarily setting the ground terminal of the electrode 18 or 19 at a required location, the distributed capacitance and inductance can be changed and the purpose can be achieved.

FIGS. 6 to 14 show examples of the structures of the transmission line electrodes and dielectric material in the tuner 1 described in FIGS. 3 to 5. In FIG. 6, (,) shows a front view, (b) shows a side view, and (C) shows a back view. (The same applies to Figures 7 to 13 below) 6th
In the figure, 100 is a dielectric substrate, 101 and 102
are electrodes that form a distributed constant circuit to realize a distributed inductor and a distributed capacitor. The ground terminals of the electrodes 101 and 102 are set so that the opposing electrodes are arranged in opposite directions, as shown in FIG. (Hereafter, Section 7
(Similarly in Figures to Figures 14) ■ As shown in Figure 6(a)
(till, (JMIII and not shown in Figure 6 (C)
The side and ■ side correspond to each other. (Figures 7 to 1 below)
(Similarly in FIG. 3) In FIG. 7, electrodes 104 and 105 each having one bent portion are placed facing each other with a dielectric substrate 103 interposed therebetween.

In FIG. 8, electrodes 107 and 108 having a plurality of bent portions are placed facing each other with a dielectric substrate 106 in between.

In FIG. 9, meander-shaped electrodes 110 and 111 are placed facing each other with a dielectric substrate 109 in between.

In FIG. 10, spiral-shaped electrodes 113 and 114 are placed facing each other with a dielectric substrate 112 in between.

In FIG. 11, an electrode 11 is placed on the surface of a dielectric substrate 116.
6 and 117 are installed laterally facing each other.

In FIG. 12, an electrode 11 is provided inside a dielectric substrate 118.
9 and 120 are installed facing each other.

In FIG. 13, an electrode 12 is provided inside a dielectric substrate 121.
2 is installed, and an electrode 123 is installed on the surface of a dielectric substrate 121, with the electrodes 122 and 123 facing each other.

FIG. 14 shows a configuration diagram of a tuner in another embodiment of the present invention. An electrode 126 is installed on the inner periphery of the cylindrical dielectric 124, and an electrode 126 is placed opposite the electrode 126 on the outer periphery. and,
The ground terminals of the respective electrodes 126 and 126 are set in opposite directions 1H1j. Here, as the dielectric 124, in addition to the cylindrical one, a rectangular cylindrical one can also be used.

In the embodiments shown in FIGS. 6 to 14 above, the electrodes placed opposite each other have the same shape and completely face each other on the entire surface.
Even if one arbitrary electrode has a different equal measurement length from the other electrode, it can be realized even if the other electrodes partially face each other. Dimensions: Shape of each electrode used in the embodiments shown in Figs. 11 to 14 υ Figs. 7 to 10
It can also be realized using the embodiments shown in the figures.

In the embodiments shown in Figures 7 to 10)
Although one curved portion is shown as an arc-shaped pattern having an arbitrary bending angle, the electrode may be formed with an arc-shaped pattern having an arbitrary curvature as a bent portion. Needless to say.

In each of the above embodiments, the ground terminal of each electrode VC is not specially set as a ground terminal, but is generally connected to another circuit section (not shown) as a common terminal to achieve the desired purpose. Something will happen.

- In each of the embodiments described above, the one shown in FIG. 6 can be constructed with a simple electrode pattern, and the electrode pattern can be easily formed at one time. Thereby, it is possible to construct a tuner that precisely matches the design target tuning frequency. What is shown in FIGS. 7 to 10 allows relatively large inductors and capacitors to be formed even if the area occupied by the tuner is small. Therefore, a compact tuner with a relatively low tuning frequency can be realized, and the space factor of the tuner can be improved. In the device shown in FIG. 11, both electrodes can be formed on only one side of the dielectric, so the manufacturing process can be simplified. Furthermore, both electrodes can be formed using the same electrode forming process. This makes it possible to achieve extremely high positioning accuracy between the electrodes.
It is possible to construct a tuner that matches the tuning frequency of the cutting target with extremely high precision. Figures 12 and 13
What is shown in the figure can be introduced into the manufacturing process of multilayer circuit boards. As a result, the electrodes are placed inside the dielectric and are not exposed to the outside, so they are not directly affected by changes in external conditions. Therefore, since it does not affect the tuning frequency of the tuner, it is possible to realize a tuner with extremely stable performance. Even if the S11 device shown in FIG. 14 is made smaller than those shown in FIGS. 0 to 13, it is possible to form a sufficiently large inductor and capacitor. Therefore, an ultra-small tuner having a sufficiently low tuning frequency can be realized. Furthermore, when manufacturing the device shown in FIG. 14, it can be easily manufactured in large quantities by forming electrodes in succession on a continuous cylindrical dielectric material and cutting the electrodes to desired lengths. Is possible.

Note that metal conductors, printed metal foil conductors, thick film printed conductors, thin film conductors, etc. can be used as the transmission line electrodes in each of the above embodiments, and the transmission line electrodes can be formed by combining different types of conductors. may be formed.

On the other hand, as dielectric materials, alumina ceramic, chitavari,
plastic.

Teflon, glass, mica, resin-based printed circuit boards, etc. can be used.

The operation of the tuner of this embodiment configured as described above will be explained below.

, PJ16 are equivalent circuits for explaining the operation of the tuner of the present invention. In FIG. 16(a), a signal source that generates a voltage e for a transmission path formed by transmission path electrodes To and T1 having an electrical length of 2 and having their ground terminals set in opposite directions. , 72 are connected to the transmission line electrode 70 to supply signals. As a result, it is assumed that a traveling wave voltage eA is excited at the open terminal at the tip of the transmission line electrode 70. On the other hand, since the transmission line electrode 71 is disposed close to the above-mentioned transmission line electrode 70, facing each other or in parallel, a voltage is induced by mutual induction. Let eB be the liquid voltage induced at the open terminal at the tip of the transmission line electrode T1.

Since the respective ground terminals of the transmission line electrodes 70 and 71 are set in opposite directions, the induced traveling wave voltage eB has an opposite phase to the excited leading 11 wave voltage eA. Since the respective traveling wave voltages eA and eB are in an open state at the ends of the transmission lines, the voltage standing waves are formed in the form I in the transmission line consisting of the transmitted sound i-electronic circuit 4 and the transmission line 1. Here, the transmission line electrode 70
Let K be the voltage distribution coefficient that indicates the distribution of the voltage standing wave at
The voltage distribution coefficient at the transmission line electrode 71 can be expressed as (1-K).

Therefore, next, if we consider the potential difference V that occurs at arbitrary opposing parts of the transmission line electrodes 7Q and 71, then V=l? It can be expressed as A-(1-K)eB --...--(1). Here, each transmission path electrode 7
If 0 and 71 have the same electrical length 2, then eB-ep, ・・・・・・・・・・・・・・・・・・
...(2), so that the potential difference ■ in the first equation is -V-KeA+(1-IO(II'A-eA
,=--(3). That is, transmission line electrodes 70 and 71
A potential difference V can be generated in all the parts where the two faces each other.

Here, it is assumed that the transmission line electrode 70 and the electrode 1 have an electrode width W and a thin electrode thickness), and are opposed to each other at a distance d via a dielectric material having a dielectric constant εS. . In this case, the capacitance C8 formed per unit length of the transmission line is, and therefore.

Therefore, the transmission path shown in Fig. 16(,) is as shown in Fig. 15(b).
For each unit length as shown in Equation 6, it becomes a path containing the distribution coefficient 73 of round co.

The voltage standing wave distribution (or current standing wave distribution) at each transmission line electrode 70 and transmission line electrode 71 are in an inverse relationship with each other as described above, so this transmission line is It operates as an isometrically balanced mode transmission line. As a result, as shown in FIG. 16(C), S1'iφi signal source 7 with a balanced voltage e'
This is equivalent to a balanced mode transmission line formed by transmission line electrodes 6 and 76 which are excited in a balanced mode by 4. Needless to say, its electrical length is the same as the original electrical length U shown in FIG. 16(a). Furthermore, as shown in FIG. 15(d), this balanced mode transmission line has a total distributed inductance 77 consisting of each of the lumped inductor components generated by the transmission line's inductor component and the bent three shapes of the transmission line. and 78 can be equivalently expressed as a distributed constant circuit consisting of the distributed capacitor 73. Next, the relationship between the formation of the distributed capacitor 73 and the electrical length l of the transmission path will be described. The characteristic impedance Z0 per unit length in the balanced mode transmission line as shown in FIG. 16(a) can be expressed by the equivalent circuit shown in FIG. 16(b). Its characteristic impedance Z0 is generally as follows. Here, if the transmission path is lossless, then This assumption can be applied to many of the embodiments of the tuner of the present invention, and to simplify the explanation, the characteristic impedance shown in equation 8 below is also used. The capacitance C6 in the eighth equation is the same as the capacitance C8 per unit length of the transmission line calculated in the sixth equation. In other words, the characteristic impedance Z is the unit length and I in the transmission path.

is a function of the capacitance C0, which is also a function of the dielectric constant εs1 of the dielectric material involved in the capacitor C0, the width W of the transmission line electrodes, and the installation spacing d of the respective transmission line electrodes.

As mentioned above, the impedance per unit length of the transmission line is Z. Then, the equivalent reactance X generated at the terminal of the transmission line whose electrical length is l and whose tip is open is X--Z. CO1θ ・・・・・・・・・・・・・・・
・・・乍) can be expressed. Here θ−2πf ・・・・・・・・・・・・・・・・・・
...(10) λ, and especially in the case of θ=π・−π, the equivalent reactance X is X≦O・−・・・・・・・・・・・・・・・・・・・・・・
...(12). That is, the equivalent reactance at the terminal of the transmission line can be the capacitive reactance. Therefore, due to the electrical length 4 of the transmission path, θ becomes the first
1, that is, for example, the electrical length l is λ/4
A capacitor can be formed by setting as follows. Then, the capacitance C of the capacitor that can be formed can be realized by changing θ, that is, by setting the electrical length l of the transmission line, as expressed by 0 or above Equations 9 to 13 FIG. 17 is a diagram illustrating the operating mode of the transmission line explained in FIG. FIG. 17 graphically illustrates how the equivalent reactance X generated at the terminal changes in accordance with the change in the electrical length e of a transmission path with the tip in an open state. As is clear from FIG. 17, when the electrical length l of the transmission path is less than λ/4 or between λ/2 and 4λ/3, it is possible to form a negative terminal reactance, i.e. A capacitor can be equivalently formed. Furthermore, under the conditions of generating negative terminal reactance, by arbitrarily setting the electrical length l of the transmission path, it is possible to realize the capacitance C to an arbitrary value.

The capacitor C formed in this way is shown in FIG.
It can be equivalently replaced as the lumped constant capacitor 79 shown in e). Further, an inductor formed by combining the distributed inductor component existing in the transmission line and the lumped inductor component generated by bending the transmission line can be equivalently replaced as the lumped constant inductor 80. If the virtual balanced signal source 74 and the ground in each transmission line are replaced with the same constraints as the original state shown in FIG. 15(a), then the condition shown in FIG. 15(f) is obtained. It becomes as shown in . When the ground terminal is shared in common in FIG. 16(f), it is clear that the final result is a parallel resonant circuit consisting of a lumped constant capacitor 79 and a lumped constant inductor 80, as shown in FIG. 15(q). The feedback amplifier used in the oscillation device described in section 2 can be made of semiconductor devices such as transistors, field effect transistors, and ICs, or vacuum tubes. can.

As is clear from the explanation in Section 2, "Effects of the Invention", the present invention consists of a tuner composed of electrodes that are placed opposite each other through a thin dielectric layer or arranged in parallel on the surface of the dielectric, and that the tuner is fed back. The DC voltage obtained by converting the digital signal coat is used as the control voltage for the voltage variable reactance element, which is configured to be connected to the input terminal or output terminal of the amplifier, and is connected to the tuner. Since the oscillation frequency of the oscillator is variably controlled by setting the code, it is possible to control oscillation tuning using a determinable digital signal code, and has a stable and highly accurate conversion function. By being able to control oscillation tuning using the A converter, the oscillation tuning accuracy of the oscillator is significantly improved. As a result, the oscillation frequency in the oscillator can be maintained stably, the fundamental wave level in the single oscillation signal can be sufficiently raised, and the harmonic component level can be sufficiently lowered, so distortion can be significantly stabilized. Moreover, the intermodulation interference elimination characteristics and the spurious radiation interference elimination characteristics can be significantly and stably improved.

■ It is possible to connect directly to a computer-applied multi-function digital control system. Thereby, advanced multi-functional control of the oscillation device and the equipment installed therein can be achieved simultaneously with highly accurate oscillation tuning control. In other words, it is possible to realize an oscillation device that exhibits a sufficiently stable oscillation tuning function in response to highly accurate control of the multifunctional digital control system.

(Me) In a tuner used in an oscillator, it is possible to configure a resonant circuit and perform the tuning function without installing a connection lead between an inductor and a capacitor.Thereby, the lead inductance and stray capacitor in the tuner can be The occurrence of unexpected resonances other than the resonance at the target tuning frequency does not exist over a wide frequency band.As a result, stable frequency selection is possible. By securing the characteristics, it is possible to sufficiently increase the level of the fundamental wave in the signal that should be oscillated, and it is also possible to sufficiently reduce the level of its harmonic components.Therefore, the distortion in the oscillation signal can be significantly stabilized. Furthermore, by ensuring stable frequency selection characteristics, it is possible to sufficiently reduce the problems of intermodulation interference and spurious radiation interference that occur when a large number of signals are oscillated simultaneously.

- Since an oscillation device with a tuner that can be modularized can be realized, there is no constant variation in inductance and capacitance in the tuner due to mechanical vibration, and the oscillation tuning characteristics are therefore extremely stable.

As a dielectric material that composes a tuner, its dielectric constant is 1.
By using the gain 1 with low temperature dependence, fluctuations in capacitance due to changes in ambient temperature can be made extremely small, thereby making it possible to make the tuning characteristics extremely stable.

Therefore, the oscillation frequency characteristics and unnecessary interference signal rejection characteristics of the oscillator do not depend on changes in ambient conditions.
Furthermore, these characteristics can be stably maintained not only during the initial stage of constructing the oscillation device but also over a very long period of time.

(2) With a simple configuration, it is possible to have an integrated tuner and to realize a very simple oscillation device. Furthermore, it becomes possible to realize an ultra-thin and compact oscillation device.

Therefore, the amount of unnecessary radiation of the oscillation signal radiated from the tuner can be extremely reduced. This not only makes it possible to stabilize the oscillation operation of the oscillation device itself, but also prevents any disturbance from occurring even if 7=J occurs on other oscillation systems.

(2) If the circuit board constituting the feedback amplifier is shared as the dielectric used in the tuner in the oscillation device, the mounting form in the oscillation device can be rationalized. This makes it possible to further reduce the number of parts that make up the tuner, making it possible to create an oscillation device suitable for mass production, and significantly reducing manufacturing costs. .

This excellent effect can be obtained.

[Brief explanation of the drawing]

FIG. 1 is a configuration circuit diagram of a conventional oscillation device, FIG. 2 is a perspective view of a component configuration of a tuner used in the conventional oscillation device, and FIGS. 3 to 5 are of an excavation device according to an embodiment of the present invention. The configuration circuit diagrams shown in FIGS. 6 to 14 are suitable for the embodiment of the present invention.
・This is a configuration diagram of a tuner used in an oscillation device. Figures 15 to 17 are diagrams illustrating the operating principle of the tuner used in the oscillation device in the embodiment of the present invention. 16... Feedback amplifier, 17... Tuner, 21
...Variable tuner, 20...Voltage variable capacitance diode, 23...D-A converter, 2
5... Digital signal processor, 27... Code converter, 18.19, 101.102, 104, 105° 107.108, 110, 111.113, 114° 1
16.117,119,120,122,123゜12
6, 126, 70, 71.75, 76... Transmission line electrode, 100, 103.106, 109° 112.115
, 118, 121.124... Dielectric. Name of agent: Patent attorney Toshio Nakao and 1 other person No. 1
Figure 3 Figure 2 Figure 4/'1 ε;35 Figure 6'I HIS 7 Figure 8 Figure 91! N ・”:'+Ir+1.1 ((L) (die'

Claims (1)

[Claims] (1) The terminals connected to the ground of the electrodes that are placed opposite to each other via a dielectric or arranged in parallel on the surface of the dielectric are set in opposite directions. A voltage variable reactance element is connected to the open terminal of any one electrode of the tuner, and the input terminal or output terminal of the feedback amplifier is connected to the open terminal of any one of the electrodes of the tuner. , an oscillation device characterized in that a tuning control code is input to a control section comprising a DA converter, and an analog output voltage from the control section is supplied to the voltage variable reactance element. (The oscillation device according to claim 1, in which a latch is placed in front of the JD-A converter as a control unit. (3) Claims 1 and 2, in which a RAM or ROM is placed in front of the control unit. The oscillation device according to any of item 2. (4) Parallel output of 7 real input codes (5
5.) The oscillation device according to any one of claims 1 to 4, wherein the electrode has at least one bending part exhibiting an arbitrary bending angle or bending rate and an arbitrary bending direction. (6) The oscillation device according to any one of claims 1 to 4, wherein an electrode having a spiral shape is used. (7) Claims 1 to 6 in which the length of one electrode is arbitrarily set shorter than the length of the other electrode, and the length is set to be opposite to or arranged in parallel at any part.
The oscillation device according to any of paragraphs. (8) The oscillation device according to any one of claims 1 to 7, wherein each electrode or a portion or all of one of the electrodes is provided inside the dielectric. (9) The oscillation device according to any one of claims 1 to 8, wherein the respective electrodes are provided at the inner circumference and/or outer circumference of a cylindrical or prismatic dielectric body. (10) The oscillation device according to any one of claims 1 to 9, wherein the oscillation tuning frequency range is arbitrarily set and controlled by cutting out any desired part of any one electrode or both electrodes. . (11) The oscillation device according to claim 10, wherein the electrode is cut by a non-contact cutting means. (12) Any one of claims 1 to 11, in which the oscillation tuning frequency range is arbitrarily set and controlled by setting any desired part of one or both electrodes as a terminal to be connected to ground. The oscillation device described in . (13) The oscillation device according to any one of claims 1 to 12, wherein the terminal connected to the ground in each electrode is a common terminal without being connected to the ground.