JPS59136090A - Brushless motor - Google Patents

Abstract

PURPOSE:To operate an output transistor always by the constant current amplification factor by inputting an armature current detected value and a torque command to a differential amplifier by a current mirror and controlling a position signal switching circuit by output of the amplifier. CONSTITUTION:The rotating position of a motor which has a permanent magnet rotor 1 and 3-phase armature windings 3 is detected by a detector 2, inputted to switching circuits 5, 7 and connected to output transistors 6, 8 of push-pull configuration. An armature current is detected by a resistor 13, inputted to a differential amplifier 4 by a current mirror together with a torque command 15, the output 19 is applied to the circuit 7, and the other output 18 is applied to the circuit 5 through a differential amplifier 20 and controlled. Accordingly, collector and emitter voltages can be automatically controlled to always operate the output transistors to constant current amplification factor, and the influence of irregular elements is eliminated, thereby operating them stably.

Description

DETAILED DESCRIPTION OF THE INVENTION Field of the Invention The present invention relates to a brushless motor that can be used in tape recorders, record players, video tape recorders, and the like.

Brushless motors, in which the conventional configuration and its problems are controlled by a transistor and controlled by a generated torque command m pressure, are widely used in the above-mentioned sedentary work fields. A conventional example of a typical configuration using a five-phase armature winding is shown in FIG.

・Hiroko Mizuku's magnet, which was swollen in Flood 1 (1)
and the respective % lines L1 to L3 of the electronic winding iIs (3)
The rotational position is detected by the position detector (2) and transmitted to the position signal switching circuits (6) and (7). Each of the position signal switching circuits (587) has a three-differential S configuration, and each collector is connected to the base of each of the transistors Q1 to Q3 and Q4 to Q6 of the corresponding output transistor group (6) t8).

The output transistors (6) and (8) have their emitters connected in common, and their collectors connected to each other in a push-pull configuration. Armature winding (3
) are each connected to one end of the corresponding phase. The common emitters of the output transistor group (6) are connected to the power supply σQ, and the common emitters of the output transistor group (8) are grounded via a resistor @. The voltage at the ungrounded terminal α of the resistor (2) is applied to one input of the current output type differential amplifier circuit (4), and the torque command voltage ( ) is applied, and the output of the differential amplifier circuit (4) is applied in a current mirror format to the position signal switching circuit (7). The other end of the armature winding (3) is commonly connected and connected to one input of the differential amplifier circuit (9), and the other input of the differential amplifier circuit (9) is connected to the divided voltage -54. Therefore, the four voltages of qQ are applied at δ.The output of the differential) 1M circuit (9) is applied to the position signal switching circuit (5) in the form of a current mirror.

Assuming that transistors Q3 and Q4 are in the interrogation state, the operation shown in FIG. 1 will be carried out as best as possible. The armature current flows through the paths of transistor Q5 → winding '1 mL, → winding L3 → transistor Q4 → resistor (14), and the voltage at terminal aih and torque command input '0 are compared, and the shell return circuit (the difference becomes zero) is controlled by VC. As a result, the armature current is controlled by the torque command m-pressure 0→, and therefore the torque generated by the motor is controlled by the torque command m-pressure αG. Ten thousand,
Winding L1. L2. The common connection point of L is a leather amplifier circuit (9
) by the negative feedback circuit of the power supply rolling pressure one [seasoned 7L
Ru. Therefore, the acid level of the armature winding (3) changes around the value of 7 of the E pressure, and the transistor voltage, Q
Since 4Vi operates with the same collector-emitter voltage, the winding 4. When the voltage across L3 is increased, transistors Q3 and Q4 fall into almost the same extreme VCRA sum, improving the utilization rate of the power supply α1.

However, in order to maintain all of the upper common connection points of the Tatsuwishi winding (3), the common connection point is connected to the input (9) of the differential amplifier (9).
6), which requires wiring. As tape recorders, record players, video tape recorders, etc. are becoming smaller and lighter, this has resulted in a disadvantage of having a large number of wires, especially when the dynamic circuit can be integrated into an integrated circuit, leading to an increase in costs. Furthermore, if the output voltage of the voltage divider OcJ deviates from the - supply voltage, either one of the output transistor groups (6) or (8) will saturate first as the current increases. , the current does not increase any further, and it also has the disadvantage that the utilization rate of the power supply voltage deteriorates.

OBJECTS OF THE INVENTION The present invention eliminates the drawbacks of the above-mentioned conventional examples, and provides a brushless motor that reduces the number of wires, is resistant to element variations, and is suitable for integrated circuits of drive circuits.

Structure of the Invention In order to achieve the above-mentioned target sound, the BA of the present invention has a multi-pole magnetized 8n
Detecting the rotational position of the Mizuku Giseki Kaishi, Oi with the - ring connected in common, the several-phase 'Tun Toshiko Ichibachi, the MB seven-time Musashi, and the above-mentioned Aiso Sukan) food. a position detector; a front AC; *a pair of push-pull output transistors connected to each phase of the winding and having a number of m equal to the number of phases; and a first current detection means for detecting the current of the armature winding. , a first amplifier that amplifies the difference between the output signal of the first current detection means and the motor torque command input signal, and an output of the first amplifier that is switched in accordance with the output of the position detector. , first switching means for determining the energized phase of the armature winding by one transistor of the pair of output transistors, and outputting a signal according to the pace current of the one transistor. a second amplifier for amplifying the difference between the respective output signals of the first and second current detecting means; and a second amplifier for amplifying the difference between the output signals of the first and second current detecting means; 1. A second position signal switching circuit that switches in accordance with the output of the 1f position signal detector and determines the energization phase of the electric wire by the other transistor of the output transistor pair; controlling the conduction state of the other transistor with a second amplifier so as to maintain a constant ratio between the pace current of the transistor and the current flowing through the first current detection means;
It is configured to generate torque according to the torque command input, detects the electric current and compares it with the torque command input to control the torque, and also controls the torque corresponding to the pace current of the output transistor. The current is also detected and compared with the armature current, and the push-pull operation is controlled so that the ratio remains constant.This allows the wiring between the common connection point of the armature winding and the sea bream driving circuit to be adjusted. DESCRIPTION OF EMBODIMENTS OF EMBODIMENTS OF THE INVENTION An embodiment of the present invention will be described below with reference to the drawings. Second
The figure shows its configuration. The 0 permanent magnet rotator (1) is magnetized in 8 layers, and the 3-phase Hiroko Ikkatsu (3) is a winding with one end commonly connected. , L2. It is composed of L. Rotor (
The rotational positions of
2), and the position signal switching circuit (5
) (7) is printed. The position signal switching circuit (5) has a three-running configuration of NPN l-transistors and drives the output transistor group (b). Location No. 100 Kirihou Circuit (7
) has a three-differential excitation configuration using PNP transistors and drives the output transistor P (8). Output transistor group (
6 have a common emitter (PIJP connected to Amogen)
The transistor also has Q2. The output transistor group (8) consists of an NPN transistor Q4.Q3 whose emitter is connected to the current detection resistor α. q5. Q. Consists of 6. Q4 to the transistor. Q2 and Q5°, Q3 and Q6 have a push-pull configuration, and their respective collectors have a common winding L3. L2. Connected to L1. Torque command '
It is connected so that the voltage at the terminal (14) of the resistor (fi) is applied to the inversion side human power (-).The output terminal α9 is connected to the position 1 switching circuit (7). It is connected to the common emitter, and the output terminal 0 is connected to the non-inverting side input of the differential amplifier (A) together with the connected resistor (17+).The inverting side input of the differential amplifier (A) is connected to the non-grounded side of the resistor port, and the output is connected to the emitter of the position signal switching circuit (5) via the low-pass filter υ.

Next, the circuit operation will be explained. 1 twin turtle flow flows in the output path of output transistor group (6) → winding its (3) → output transistor group (8) → resistor port, running J so I corner pjl path (4), position 1g switching circuit (7 ), an output transistor group (8), and a negative feedback loop consisting of a resistor (n) is controlled so that the torque command voltage and the voltage across the resistor u3 are equal to each other. Therefore, it is determined by the thickness Q of the armature current (torque command voltage/resistance value of resistance α■).

Now, it is assumed that only transistors Q and Q of the output transistors Q1 to Q6 are in a conductive state because of the phase relation t between the rotor (1) and the armature winding section (3). Resistance Q:
14 is the emitter current of transistor Q4 or m11-.

The pace current of transistor Q4 increases by the difference wJ in the first corner circuit (4
) Current output terminal (
G) Force) When the same thick current is supplied to the resistor u7+, the value of the resistor port and the current value 7 that flows to V.
So f(.

If each is ``S51R+7 and the sum, , , 7, then the input voltage V2o of the difference a amplifier is v20 ``'R17' 17- R13' ``13
``' (1). - If the current amplification factor of the caton non-star q4 is □, then hF, 3 = (fH + hFK) · tag, ...(2), so equation (1) is Since hFlli of the transistor Q4 changes with the collector-emitter voltage vcBVc as shown in Fig. 3, the differential amplifier wire, low-pass filter Qυ, position signal switching circuit (5), output transistor Q3, and winding L1 When the loop gain of the negative feedback loop consisting of L3, output transistor Q4, and resistor is sufficiently high, the input voltage increases ■2.
The collector of transistor Q4 is connected so that ofi is zero.
Eminter operating voltage is automatically determined. Therefore, it follows from equation (3). Since the right side of equation (4) is constant, hFK of transistors Q and 4 is constant. When the torque command voltage changes, the emitter current of the transistor Q also changes, and from FIG. 3, the collector-emitter' voltage of the transistor Q4 also changes automatically. In other words, since the collector-emitter' voltage is controlled δ according to the emitter current so that the current amplification factor of transistor Q4td is kept constant, the winding L
1. The 4th position at both ends of L3 also corresponds to the electric current, and
Operates stably.

As the motor rotates, the rotor (1) and armature winding (3)
Even if the rotational position of the transistors Q1 to Q6 changes and which one of the transistors Q1 to Q6 becomes conductive changes, the windings Xr, , L2 . The operating position of L6 changes stably in response to the winding current.

FIG. 4 shows another embodiment of the invention. transistor Q,
, Q8. Q, has an emitter of Q4. Q5. Q6
transistor Q, whose collectors are connected in common. is connected to the collector of Transistor Q, oi is diode-connected and transistor "1"
Together with 1, it constitutes a current mirror. The collector of the transistor Q11 is connected as a current mirror output to the resistor q and the non-inverting input of the differential amplifier (7). The bases of the transistors Q7-Q are connected to the corresponding phase of the phase switching circuit (7). The configuration of FIG. 4 other than the above is the same as that of FIG. 2, so a description thereof will be omitted.

The base currents of transistors Q4 to Q6 are emitter currents of transistors Q7 to Q, respectively, but since transistors Q7 to Q are emitter followers, their current amplification factors are sufficiently large and can be regarded as collector currents.

These collector currents are integrated into transistor Q1o
, Q++ current mirror reverses the current direction and applies it to the resistor ση. As a result, both ends l of the resistor (17)
This corresponds to the pace current of transistors Q4 to Q6.
A voltage is generated, similar to that in the first embodiment described above (/J
@Feedback loop determines the collector operating voltage of transistors Q4 to Q and 6.

As described in detail, the brushless motor of the present invention automatically controls the collector-emitter voltage by operating the output transistor so that the current amplification factor is always constant, which can be determined by the resistance ratio. Since the operating potential can be maintained stably according to the current, the wiring between the common connection point of the armature winding and the drive (b) path becomes small, and the output stage voltage is effective regardless of element variations. The VC canopy is effective when integrating the V-drive circuit or when reducing the size and weight of a brushless morph application device.

[Brief explanation of the drawing]

Fig. 1 is a block diagram of a conventional example of a brushless motor, Fig. 2 is a block diagram of an embodiment of the present invention, Fig. 3 is a graph showing the relationship between collector-emitter voltage and current amplification factor of a transistor, and Fig. 4 FIG. 2 is a configuration diagram of a second embodiment of the present invention. (1)...Permanent magnet coil, (2)...Position detector, (3)...Meigame Shinshi winding, (4)...Differential amplifier circuit,
(5) (7)...Position signal switching circuit, (6) (8)
...Output transistor liver, 0qη...Resistance, (1
G-) Luc command human power'voltage, μsu...'source, (4)
...Differential multiplier, 3υ...Filter agent Yoshihiro Asamoto

Claims (1)

[Claims] 1. The rotational position of the multi-pole magnetized permanent shingle coil, the mantissa phase armature winding whose one end is commonly connected, and the rotor and the front ml armature winding. a position detector for detecting, a pair of output transistors connected to each phase of the armature winding and having a number equal to the number of phases, and a first current for detecting the current of the papier-mache winding. a detection means, a first amplifier for increasing the distance between the output signal of the first current detection means and the motor torque command manual power signal; a first position signal switching means for switching the output VC ratio of the detector and determining the trace of the front Tadagame winding by the 10,000 transistors of the output transistor pair; a second current detection means for outputting a signal according to the base current of the transistor; and a second amplifier for controlling the output 1g of each of the first and second current detection means. and RlJ rje, the output tray of the second amplifier is switched in accordance with the output of the position 4 extractor, and the energizing phase of the M'+J A pin winding by the other transistor of the output transistor pair is determined. !
2 position signal switching means, and the conduction state of the other transistor is controlled by the second position signal switching means so as to maintain a constant ratio between the base current of the one transistor and the current flowing through the first A brushless motor controlled by an amplifier to generate torque according to the torque command input. 2. A current mirror and a resistor are used as the second current detection means, a differential amplifier with a current output value is used as the first amplifier, and the current output of the differential amplifier is transferred to the first position No. 16 by the current mirror. a switching means and the resistor;
2. The brushless motor according to claim 1, wherein the voltage across the front ml resistor is the output of the second current detection means. 3. The stage where the ICD position is to be cut is τ current double force type,
An emitter follower transistor is inserted between the first position signal switching circuit and the base of the output transistor, a resistor is inserted as a second current detection means in the collector circuit of the emitter follower transistor, and the voltage across the resistor is set to the A brushless motor according to Patent No. 1, characterized in that the output of the second return current detection means is used as the output of the second return flow detection means.