JPS59103575A - Dc/dc converter - Google Patents
Dc/dc converterInfo
- Publication number
- JPS59103575A JPS59103575A JP21353682A JP21353682A JPS59103575A JP S59103575 A JPS59103575 A JP S59103575A JP 21353682 A JP21353682 A JP 21353682A JP 21353682 A JP21353682 A JP 21353682A JP S59103575 A JPS59103575 A JP S59103575A
- Authority
- JP
- Japan
- Prior art keywords
- voltage
- primary winding
- capacitor
- transistor
- diode
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33538—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Description
【発明の詳細な説明】
発明の属する技術分野
本発明はスイッチング動作にともなう導電雑音の吸収回
路における損失を削減するＤＣ−ＤＣコンバータに関す
る。DETAILED DESCRIPTION OF THE INVENTION Field of the Invention The present invention relates to a DC-DC converter that reduces loss in a conduction noise absorption circuit associated with switching operations.
従来技術
従来ノゾングルエンドＷＤＣ−ＤＣコンバータのうち外
部駆動型に分類されるものは第１図に示される回路構成
が一般に用いられている。BACKGROUND OF THE INVENTION Among conventional GLE-END WDC-DC converters, those classified as external drive type generally have a circuit configuration shown in FIG.
第１図を参照すると、端子５１からは図に示さッチング
素子としてのトランジスタＱ１が導通状態となる埃合に
は電流ｉ１はトランスＴ１の一次巻飼（の内の巻祢Ｔ
１ （ＡＪおよびトランジスタＱｔを通電して直流入力
電源の負側に流入する。この時点において、トランス１
゛ｌの一次巻線の中の巻鞄’ｒｌ（）３）に起電力が誘
起される。この起電力によりダイオードＤ１のカソード
とアノードとの間に加わる電圧■２は、−次巻線Ｔｌ（
Ａ）と’Ｉ”１３］との巻徐が等しければ、大略２倍の
電圧となる。前記パルス電圧ｖ１が終止すると、トラン
ジスタＱ１を流れる電流１１は零となる。このトランス
ＴＩの一次巻線の励磁電流が零となるまでの時間ダイオ
ードＤ１が導通状態となる。トランスＴ１の一次巻線Ｔ
ｌ（Ａｌおよび’ｌ’ １（Ｂｌにおける誘起起電力に
よシ、トランジスタＱｌのコレクタとエミッタとの間に
加わる電圧Ｖｌは零から大略２ＥｉＯ値に上昇する。こ
の状態は、トランジスタＱ１の導通時間を若干下廻る程
度の時間継続する。しかる後初期の状態、すなわち、前
記電圧■１および■２が直流入力電圧Ｅｉに等しい状態
に復帰する。以下外部駆動パルス電圧ｖ１によシ、端子
５５が励振されて、前述の動作経過が繰返される。この
ような動作経過における外部駆動のパルス電圧ｖ１゜ト
ランジスタＱ１を流れる電流ｉｌ、トランジスタＱｌの
コレクタとエミッタ間の電圧■１およびダイオードＤ１
のカソードとアノードとの間の市：圧Ｖ２＃の動作波形
を第３図に示す。Referring to FIG. 1, when the transistor Q1 as a switching element shown in the figure becomes conductive, a current i1 flows from the terminal 51 to the primary winding T of the transformer T1.
1 (AJ and transistor Qt are energized to flow into the negative side of the DC input power supply. At this point, transformer 1
An electromotive force is induced in the winding bag 'rl()3) in the primary winding of 'l. The voltage ■2 applied between the cathode and anode of the diode D1 due to this electromotive force is
If the winding ratios of A) and 'I'13] are equal, the voltage will be approximately twice as high.When the pulse voltage v1 ends, the current 11 flowing through the transistor Q1 becomes zero.The primary winding of this transformer TI The diode D1 becomes conductive until the excitation current becomes zero.The primary winding T of the transformer T1
Due to the induced electromotive force in l(Al and 'l' 1(Bl), the voltage Vl applied between the collector and emitter of transistor Ql increases from zero to a value of approximately 2EiO. continues for a period of time that is slightly lower than .Thereafter, the initial state is restored, that is, the state where the voltages (1) and (2) are equal to the DC input voltage Ei.Hereafter, due to the external drive pulse voltage v1, the terminal 55 is Excited, the above-mentioned operating sequence is repeated.In such an operating sequence, the externally driven pulse voltage v1, the current il flowing through the transistor Q1, the voltage between the collector and emitter of the transistor Q1, and the diode D1
FIG. 3 shows the operating waveform of the voltage V2# between the cathode and anode.
第３図を参照すると、トランジスタＱｉのコレクタとエ
ミッタとの間の電圧■１およびダイオードＤＩのカソー
ドとアノードとの間の電圧■２について見ると、１１が
終止する時点およびｉｌが始動する時点において電圧２
Ｅｉ をオーバーするスパイク状電圧を生じる。この
スパイク状電圧は主にトランスＴ１の一次巻線のＴ１（
５）とＴ Ｉ （Ｂ）の漏れインダクタンスにより、ス
イッチング時に生じる導電雑音に起因する。この４矩、
雑音のレベルは電圧Ｅｉに比し極めて大きなレベルとな
り、スイッチング素子としてのトランジスタＱ １ 全
電圧破壊する恐れがある。この防止策として前記導電雑
音の吸収回路が構成されている。この回路は第１図に示
されるように抵抗ＫｌとコンデンサＣ１の直列素子をト
ランジスタＱ１に並列に接続して構成されている０第３
図（Ｃ）の電圧■ｌの波形図に示される前記スパイク状
電圧は、前記吸収回路を用いて前記導電雑音を抑制した
結果において生じている残留電圧である。この導電雑音
の吸収回路を形成する抵％’ｉ’、Ｒ１とコンデンサＣ
１には、スイッチング動作時相当のパルス電流が流入し
、抵抗Ｒ１において熱損失を生じる。ＤＣ−ＤＣコンノ
（−タの動作周波数が高い場合には、この吸収回路にお
ける損失の比重は増大しＤＣ−ＤＣコンノく一夕の効率
を著しく劣化させる。Referring to FIG. 3, looking at the voltage 1 between the collector and emitter of the transistor Qi and the voltage 2 between the cathode and anode of the diode DI, at the point when 11 ends and when il starts, Voltage 2
This produces a spike-like voltage that exceeds Ei. This spike voltage is mainly caused by T1(
5) and T I (B) due to the conduction noise generated during switching. These four rectangles,
The noise level becomes extremely large compared to the voltage Ei, and there is a risk that the entire voltage of the transistor Q 1 as a switching element will be destroyed. As a measure to prevent this, the conduction noise absorption circuit is constructed. As shown in FIG. 1, this circuit is constructed by connecting a series element of a resistor Kl and a capacitor C1 in parallel to a transistor Q1.
The spike-like voltage shown in the waveform diagram of the voltage 1 in Figure (C) is the residual voltage generated as a result of suppressing the conduction noise using the absorption circuit. Resistor 'i', R1 and capacitor C that form this conduction noise absorption circuit
A pulse current corresponding to the switching operation flows into the resistor R1, causing heat loss in the resistor R1. When the operating frequency of the DC-DC converter is high, the specific weight of loss in this absorption circuit increases, significantly degrading the overnight efficiency of the DC-DC converter.
なお、トランジスタＱ１によるスイッチング動作により
、トランスＴＩ’ｒ介して交流電圧が発生され、ダイオ
ードＤ２．Ｄ３．チョークコイルＬｌおよびコンデンサ
Ｃ２とから成る整流回路１によシ端子５２を介して直流
出力電圧を出力することは良く知られている。Note that due to the switching operation of the transistor Q1, an alternating current voltage is generated through the transformer TI'r, and the diodes D2. D3. It is well known that the rectifier circuit 1 comprising the choke coil Ll and the capacitor C2 outputs a DC output voltage via the terminal 52.
すなわち、従来のシングルエンド型ＤＣ−ＤＣコンバー
タにおいては、スイッチング動作時に発生する導伝雑音
によるスイッチング素子の電圧破壊防止用として、抵抗
とコンデンサとを含む吸収回路を用いているため、吸収
回路における損失が増大しＤＣ−ＤＣコンバータの効率
を劣化させるという欠点がある０
発明の目的
本発明の目的は上記欠点を除去し、抵Ｕ［素子を含まな
い導電雑音吸収機能を付与してスイッチング素子の電圧
破壊を防止し、外部への伝導及び４君射ノイズを低減し
かつ効率の良いＤＣ−ＤＣニア ７ ／＜−タを提供す
ることにある。In other words, in conventional single-ended DC-DC converters, an absorption circuit including a resistor and a capacitor is used to prevent voltage breakdown of the switching element due to conduction noise generated during switching operation, so the loss in the absorption circuit is reduced. OBJECT OF THE INVENTION The object of the present invention is to eliminate the above-mentioned drawbacks and increase the voltage of the switching element by providing a conductive noise absorbing function that does not include the resistor U [element]. It is an object of the present invention to provide an efficient DC-DC near 7/<- data that prevents destruction, reduces external conduction and radiation noise, and has high efficiency.
発明の構成
本発明のＤＣ−ＤＣコンノ（−夕は、直流出力電圧の正
側端子と、
この正側端子に一端を接続したトランスの第１の１次巻
線と、
この第１の一次巻線の他端に一端を＆絖したトランジス
タ回路と、
前記第１の一次巻線の他端に一ηけ接続したコンデンサ
と、
このコンデンサの他端にアノ−ドラ前配置流入カー、源
の正端子にカソードをそれぞれ接続した夕。Structure of the Invention The DC-DC converter of the present invention (-) is a positive terminal of a DC output voltage, a first primary winding of a transformer having one end connected to this positive terminal, and a first primary winding of a transformer. A transistor circuit with one end connected to the other end of the wire, a capacitor connected to the other end of the first primary winding, and an inflow car placed in front of the anode at the other end of the capacitor, and a After connecting the cathode to each terminal.
イオードと、
前記コンデンサの他端に一端を接続し前記直流入力電源
の負側端子および６り記トランジスタ回路の他端に他端
を接続した前記トランスの第２の−次巻線とを備えたこ
と″ｆ特徴とする。a second secondary winding of the transformer, one end of which is connected to the other end of the capacitor, and the other end of which is connected to the negative terminal of the DC input power supply and the other end of the transistor circuit set forth in item 6. It is characterized by "f".
発明の実施例
次に本発明について図面を参照して詳細に説明する。第
２図を参照すると、本発明の一実施例は、第１の一次巻
線Ｔ２囚、および第２の一次巻線Ｔ２ （Ｂ） ’ｆ：
含むトランスＴ２、スイッチング素子として作用する
トランジスタＱ２、コンデンサＣ３、ダイオードＤ４、
およびダイオードＤ５およびＤＣとチョークコイルＬ１
とコンデンサＣ４とを有する整流回路２ｊを備えている
。Embodiments of the Invention Next, the present invention will be described in detail with reference to the drawings. Referring to FIG. 2, one embodiment of the present invention includes a first primary winding T2 and a second primary winding T2 (B)'f:
including a transformer T2, a transistor Q2 acting as a switching element, a capacitor C3, a diode D4,
and diode D5 and DC and choke coil L1
and a capacitor C4.
次にこの実施例の動作について詳細に説明する。Next, the operation of this embodiment will be explained in detail.
端子５３から図に示される極性で直流電圧Ｅ１が入力さ
れる。また、端子５６が外部駆、動のパルス電圧ｖ２に
より励振される。この励振によりスイッチング素子とし
てのトランジスタＱ２が導通状態になる場合には、直流
１２はトランスＴ２の一次巻線の内の巻＆Ｔ２（５）お
よびトランジスタＱ２を通電して直流入力電源の負側に
流入する。この時点において、トランスＴ２の一次巻線
の中の巻線Ｔ２（Ｂｌに紡起される起電力により、−次
巻線Ｔ１（５）とＴ １ （Ｂ）の巻線が等しけれはダ
イオードＤ４のカソードとアノードとの間に加わる電圧
■４は、前記電圧Ｅｉの大略２倍の電圧となる。前記パ
ルス電圧ｖ２が終止するとトランジスタＱ２を流れる電
流１２は零となる。しかし、トランスＴ２の一次巻線の
励磁電流が零となる迄の時間、巻線１゛２（５）および
Ｔ２（Ｂ）における訪起起電力によりトランジスタＱ２
のコレクタとエミッタとの間に加わる電圧Ｖ３は零から
大略２Ｅｉ の電圧値に上昇する。A DC voltage E1 is input from the terminal 53 with the polarity shown in the figure. Further, the terminal 56 is excited by an externally driven pulse voltage v2. When the transistor Q2 as a switching element becomes conductive due to this excitation, the DC 12 flows into the negative side of the DC input power supply by energizing the primary winding of the transformer T2 &T2 (5) and the transistor Q2. do. At this point, due to the electromotive force generated in the winding T2 (Bl) in the primary winding of the transformer T2, if the windings of the -order winding T1 (5) and T1 (B) are equal, the diode D4 The voltage 4 applied between the cathode and the anode is approximately twice the voltage Ei. When the pulse voltage v2 ends, the current 12 flowing through the transistor Q2 becomes zero. However, the primary winding of the transformer T2 During the time until the excitation current of the wire becomes zero, the induced electromotive force in the winding 1゛2 (5) and T2 (B) causes the transistor Q2 to
The voltage V3 applied between the collector and emitter of is increased from zero to a voltage value of approximately 2Ei.
また、ダイオードＤ４のカソードとアノードとの間に加
わる電圧■４は電圧値２Ｅｉ から零に低下する。この
状態が特定の時間継続した後、初期の状態、すなわち、
前記電圧Ｖ３および■４が電圧Ｅｉに等しい状態に復帰
する。以下外部駆動のパルス電圧ｖ２により、端子５６
が周期的に励振されて、前述の動作経過が繰シ返される
。このような動作経過における外部駆動のパルス電圧ｖ
２、トランジスタＱ２’を流れる電流１２、トランジス
タＱ２のコレクタとエミッタとの間の電圧■３とダイオ
ードＤ４のカソードとアノードとの間の電圧■４の動作
波形図を第４図に示す。この波形図において、トランジ
スタＱ２のコレクタとエミッタとの間の電圧■３につい
て見ると、電流１２が終止する時点において前記従来例
の場合と同様に導電雑音が発生する条件が介在する。し
かしながら本発明の一実施例においては、−次巻Ｆｊｔ
Ｔ ２ （ＡＪとトランジスタＱ２のコレクタとの接
続点と、−次巻線Ｔ ２ （ＢｌとダイオードＤ４のア
ノードとの接続点との間に所定容量のコンデンサＣ３が
接続されている。このコンデンサＣ３により前記スイッ
チング動作時に発生する導電雑音はすべて吸収されてし
まい、第４図に示されるようにスパイク状電圧は一切生
じない。しかもコンデンサｃ３からなる吸収回路には抵
抗素子が含まれていないためｉｊＪ記従来例のＤＣ−Ｄ
Ｃコンバータに見られるような抵抗損失は全く存在しな
い。なお、前述のように一次側における外部駆動パルス
電圧によるスイッチング動作にょ勺、トランスＴ２を介
して２次側に交流電圧が発生し、整流回路２にょシ所定
の直流電圧が端子５４を介して出力されることは従来例
と同様である。Further, the voltage 4 applied between the cathode and the anode of the diode D4 decreases from the voltage value 2Ei to zero. After this state lasts for a certain time, the initial state, i.e.
The voltages V3 and 4 return to a state equal to the voltage Ei. Below, by the externally driven pulse voltage v2, the terminal 56
is excited periodically and the above-described operating sequence is repeated. The pulse voltage v of the external drive during such an operation process
2. The operating waveform diagram of the current 12 flowing through the transistor Q2', the voltage (3) between the collector and emitter of the transistor Q2, and the voltage (4) between the cathode and anode of the diode D4 is shown in FIG. In this waveform diagram, when looking at the voltage (3) between the collector and emitter of the transistor Q2, there is a condition in which conduction noise occurs at the time when the current 12 ends, as in the case of the conventional example. However, in one embodiment of the invention - next volume Fjt
A capacitor C3 of a predetermined capacity is connected between the connection point between T 2 (AJ and the collector of the transistor Q2) and the connection point between the -order winding T 2 (Bl and the anode of the diode D4. Therefore, all the conductive noise generated during the switching operation is absorbed, and no spike voltage is generated as shown in Fig. 4.Moreover, since the absorption circuit consisting of capacitor c3 does not include a resistive element, ijJ Conventional DC-D
There are no resistive losses as seen in C converters. As mentioned above, during the switching operation by the external drive pulse voltage on the primary side, an AC voltage is generated on the secondary side via the transformer T2, and a predetermined DC voltage is output from the rectifier circuit 2 via the terminal 54. What is done is the same as in the conventional example.
発明の効果
本発明には、−次側におけるスイッチング動作を通じて
発生する供給直流重圧の２倍を越える導電雑音を抵抗素
子を用いることなく完全に吸収してスイッチング素子の
電圧破壊を防止し、外部への伝導及び輻射ノイズを低減
するとともに、前記導電雑音吸収回路におりる損失を全
く除去して変換効率を向上できるという効果がある。Effects of the Invention The present invention is capable of completely absorbing conduction noise, which is more than twice the supply DC pressure generated through the switching operation on the negative side, without using a resistive element to prevent voltage breakdown of the switching element, and transmitting it to the outside. This has the effect of reducing the conduction and radiation noise of the conductive noise absorbing circuit, and completely eliminating the loss that occurs in the conductive noise absorbing circuit, thereby improving the conversion efficiency.
第１図および第３図は従来例を示す回路図、および第２
図および第４図は本発明の一実施例を示す回路図である
。
図において、１，２・・・・・・整流回路、５１〜５６
・・・・・・端子、Ｑｌ、Ｑ２・・・・・・トランジス
タ、Ｄｉ−ＤＣ・・・・・・ダイオード、Ｔｌ、Ｔ２・
・・・・・トランス、Ｌｌ、Ｌ２・・・・・・チョーク
コイル Ｃ１〜Ｃ４・・・・・・コンデンサ、め４図Figures 1 and 3 are circuit diagrams showing a conventional example, and a second
4 and 4 are circuit diagrams showing one embodiment of the present invention. In the figure, 1, 2... Rectifier circuit, 51 to 56
...Terminal, Ql, Q2...Transistor, Di-DC...Diode, Tl, T2...
...Transformer, Ll, L2...Choke coil C1-C4...Capacitor, Figure 4
Claims (1)
次巻魅１と、 この第１の一次巻線の他端に一端を接続したトランジス
タ回路と、 前記第１の一次巻線の他端に一端を接続したコンデンサ
と、 このコンデンサの他端にアノードを前記直流入力電源の
正端子にカンードをそれぞれ接続したダイオードと、 前記コンデンサの他端に一端を接続し前記直流入力電源
の負側端子および前記トランジスタ回路の他端に他端を
接続した前記トランスの第２の一次巻線とを備えたこと
を特徴とするＤＣ−ＤＣコンバータ。[Claims] A positive terminal of a DC input power supply, a first primary winding 1 of a transistor having one end connected to the positive terminal, and a first primary winding having one end connected to the other end of the first primary winding. a transistor circuit; a capacitor having one end connected to the other end of the first primary winding; a diode having an anode connected to the other end of the capacitor and a cand connected to the positive terminal of the DC input power source; and the other end of the capacitor. A DC-DC converter comprising: a negative terminal of the DC input power supply having one end connected thereto; and a second primary winding of the transformer having the other end connected to the other end of the transistor circuit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP21353682A JPS59103575A (en) | 1982-12-06 | 1982-12-06 | Dc/dc converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP21353682A JPS59103575A (en) | 1982-12-06 | 1982-12-06 | Dc/dc converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS59103575A true JPS59103575A (en) | 1984-06-15 |
| JPS6361869B2 JPS6361869B2 (en) | 1988-11-30 |
Family
ID=16640809
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP21353682A Granted JPS59103575A (en) | 1982-12-06 | 1982-12-06 | Dc/dc converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS59103575A (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6146173A (en) * | 1984-08-10 | 1986-03-06 | Nec Corp | Flyback type dc/dc converter |
| JPH0284063A (en) * | 1988-09-19 | 1990-03-26 | Fujitsu Ltd | Dc/dc converter |
| JPH03178569A (en) * | 1989-12-07 | 1991-08-02 | Sanken Electric Co Ltd | Switching power supply |
| US5103386A (en) * | 1990-01-18 | 1992-04-07 | U.S. Philips Corporation | Flyback converter with energy feedback circuit and demagnetization circuit |
-
1982
- 1982-12-06 JP JP21353682A patent/JPS59103575A/en active Granted
Non-Patent Citations (2)
| Title |
|---|
| ELECTRONICS COMPONENTS=1981 * |
| HONG KONG GOVERMENT GAZETTE=1983 * |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6146173A (en) * | 1984-08-10 | 1986-03-06 | Nec Corp | Flyback type dc/dc converter |
| JPH0284063A (en) * | 1988-09-19 | 1990-03-26 | Fujitsu Ltd | Dc/dc converter |
| JPH03178569A (en) * | 1989-12-07 | 1991-08-02 | Sanken Electric Co Ltd | Switching power supply |
| US5103386A (en) * | 1990-01-18 | 1992-04-07 | U.S. Philips Corporation | Flyback converter with energy feedback circuit and demagnetization circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS6361869B2 (en) | 1988-11-30 |
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