JPS58212384A - Operating method for brushless motor - Google Patents
Operating method for brushless motorInfo
- Publication number
- JPS58212384A JPS58212384A JP57094904A JP9490482A JPS58212384A JP S58212384 A JPS58212384 A JP S58212384A JP 57094904 A JP57094904 A JP 57094904A JP 9490482 A JP9490482 A JP 9490482A JP S58212384 A JPS58212384 A JP S58212384A
- Authority
- JP
- Japan
- Prior art keywords
- circuit
- inverter
- reference voltage
- motor
- output
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/10—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation using bang-bang controllers
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/28—Arrangements for controlling current
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
Description
【発明の詳細な説明】
本発明はブラシレスモータの運転法に係り、特に巻線電
流が断続するブラシレスモータに好適な運転法に関する
。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a method of operating a brushless motor, and particularly to a method of operating a brushless motor in which winding current is intermittent.
第１図は従来のブラシレスモータに、インバータ回路の
小形化、ひいてはシリコンワンチップ化を図るためにコ
ンデンサレスタイツのインバータを接続した回路図であ
り、第２図はこのブラシレスモータの動作時の直流電圧
波形、巻線電流波形及び誘起電圧波形を示したものであ
る。交流電源ＡＣはダイオードＤ１〜Ｄ４で構成された
全波整流回路１の入力側に接続され、この全波整流回路
１の出力側は次段のインバータ回路２０入力側に接続さ
れている。インバータ回路２はＰＮＰ）う／ジスタＴ１
〜Ｔ３及びＮＰＮ トランジスタＴ４〜Ｔ５を三相ブリ
ッヂ回路に組み、各トランジスタのコレクタとエミッタ
側にはフライホイールダイオードＤ５〜ＤＩＯが接続さ
れている。このインバータ回路２０入力側は前述したよ
うに整流回路１の出力側に接続され、このインバータ回
路２の出力（ＩｌＩＩＶｉモータ（ブラシレスモータ）
ＭＯ固定子巻線に接続されている。モータＭＫは回転位
置を検出する位置検出素子Ｓが設置されており、この位
置検出素子Ｓの検出信号は位置検出回路３に入力されて
いる。この位置検出回路３は分配回路４に接続されてお
り、この分配回路４は前記位置検出回路３の出力からド
ライブ信号を作り出し、ドライブ回路５にその信号を出
力する。ドライブ回路５の出力側は前述したインバータ
回路２の各トランジスタのベースに接続されて、インバ
ータ回路２をドライブする。Figure 1 is a circuit diagram in which a capacitorless inverter is connected to a conventional brushless motor in order to miniaturize the inverter circuit and eventually integrate it into a single silicon chip. Figure 2 shows the direct current during operation of this brushless motor. It shows a voltage waveform, a winding current waveform, and an induced voltage waveform. An alternating current power supply AC is connected to the input side of a full-wave rectifier circuit 1 composed of diodes D1 to D4, and the output side of this full-wave rectifier circuit 1 is connected to the input side of an inverter circuit 20 at the next stage. Inverter circuit 2 is PNP)
~T3 and NPN transistors T4 to T5 are assembled into a three-phase bridge circuit, and flywheel diodes D5 to DIO are connected to the collector and emitter sides of each transistor. The input side of this inverter circuit 20 is connected to the output side of the rectifier circuit 1 as described above, and the output side of this inverter circuit 2 (IlIIVi motor (brushless motor)
Connected to MO stator winding. The motor MK is provided with a position detection element S for detecting the rotational position, and a detection signal from the position detection element S is input to the position detection circuit 3. This position detection circuit 3 is connected to a distribution circuit 4, which generates a drive signal from the output of the position detection circuit 3 and outputs the signal to a drive circuit 5. The output side of the drive circuit 5 is connected to the base of each transistor of the inverter circuit 2 described above, and drives the inverter circuit 2.
上記のような構成のインバータ回路２は整流回路１の直
流出力側に平滑用コンデンサを有してい、：１・↓
ない几め小形且つ軽量とな′ｉｌ＋％□１また、ダイオ
ードやトランジスタを１つの集積回路で実現できる利点
を有している。しかし、前記インバータ回路２の動作時
【は上記の如くコンデンサによる平滑がなされていない
九め、整流回路１の出力である直流電圧の脈動が大きく
、このためモータＭの巻線電流の脈動も大趣くなって巻
線電流が遮断される期間が長くなる。この結果、インバ
ータ回路２及びモータＭの効率が低くなるという欠点が
ある。The inverter circuit 2 configured as above has a smoothing capacitor on the DC output side of the rectifier circuit 1, and is compact and lightweight. It has the advantage that it can be realized with a single integrated circuit. However, when the inverter circuit 2 is in operation, the DC voltage that is the output of the rectifier circuit 1 is not smoothed as described above, and the DC voltage that is the output of the rectifier circuit 1 has large pulsations, and therefore the winding current of the motor M also has large pulsations. The winding current is interrupted and the period during which the winding current is interrupted becomes longer. As a result, there is a drawback that the efficiency of the inverter circuit 2 and the motor M becomes low.
上記の様子を第２図に従って説明すると、全波整流電圧
波形Ｖ−がインバータ回路２を介してモータＭに印加さ
れる。すると、このモータＭの巻線には負荷に見合った
巻線電流工、が流れ、誘起電圧Ｅ、で一定速度で回転す
る。しかし、誘起電圧Ｅ０が全波整流電圧Ｖａより高い
期間は巻線電流１．は流れず、巻線電流１．の変動は極
めて大きくな９モ一タＭの効率が低下する。The above situation will be explained with reference to FIG. 2. A full-wave rectified voltage waveform V- is applied to the motor M via the inverter circuit 2. Then, a winding current commensurate with the load flows through the windings of this motor M, and the motor M rotates at a constant speed with an induced voltage E. However, during the period when the induced voltage E0 is higher than the full-wave rectified voltage Va, the winding current 1. does not flow, and the winding current 1. The fluctuation of 9 is extremely large, and the efficiency of the motor M decreases.
本発明の目的は、上記の欠点を解消し、コンデンサレス
タイプのインバータｔ−［用し几場合にもす
高効率を維曇神ことができるブラシレスモータの：１゛
ｌ
運転法を提供するにあ、る。The purpose of the present invention is to eliminate the above-mentioned drawbacks and provide a method of operating a brushless motor that can achieve high efficiency even when using a capacitorless type inverter. be.
本発αは、先ず、モータの持つ誘起電圧定数を小さく選
定して誘起電圧を低くすることにより、巻線電流の遮断
される期間を短くすると共に、更に、巻線電流を検出し
て巻線電流のピーク値を一定値で抑えるようにインバー
タをチゴツピングすることにより、巻線電流のピーク値
を平坦にし、巻線電流の脈動を小さくして上記目的を達
成する。This α first reduces the period during which the winding current is cut off by selecting a small induced voltage constant of the motor to lower the induced voltage, and also detects the winding current and By dynamically pumping the inverter so as to suppress the peak value of the current to a constant value, the peak value of the winding current is flattened, and the pulsation of the winding current is reduced, thereby achieving the above object.
以下本発明の実施例を従来例と同部品は同符号を用いて
第３図乃至第６図に従って説明する。Embodiments of the present invention will be described below with reference to FIGS. 3 to 6, using the same reference numerals for the same parts as those of the conventional example.
第３図は本発明のブラシレスモータの運転法の一実施例
を適応したインバータの構成例を示した回路図である。FIG. 3 is a circuit diagram showing an example of the configuration of an inverter to which an embodiment of the brushless motor operating method of the present invention is applied.
電源Ａ（ＪｔダイオードＤ１〜Ｄ４より構成された整流
回路１の入力側に接続され、この整流回路ｌの出力側は
インバータ回路２の入力側に接続されている。インバー
タ回路２はダイオードＴ１〜Ｔ３とダイオードＴ４〜Ｔ
６とから成り、ダイオードＴ１〜Ｔ３のコレクタエミッ
タ間にはフライホイールダイオードＤ５〜Ｄ７が接続さ
れており、トランジスタＴ４〜Ｔ６のコレクタ側と前記
整流回路１の負極との間にフライホイールダイオードＤ
８〜ＤＩＯが接続されている。Power supply A (connected to the input side of a rectifier circuit 1 composed of Jt diodes D1 to D4, and the output side of this rectifier circuit I is connected to the input side of an inverter circuit 2. and diode T4~T
6, flywheel diodes D5 to D7 are connected between the collectors and emitters of the diodes T1 to T3, and flywheel diodes D are connected between the collector sides of the transistors T4 to T6 and the negative electrode of the rectifier circuit 1.
8 to DIO are connected.
なお存整流回路ｌとインバータ回路２との接続部におい
て、負極側にはシャント抵抗比が挿介されており、前記
フライホイールダイオードＤ８〜ＤＩＯのアノード側が
前記シャント抵抗比の整流回路１側に接続されている。Note that at the connection between the existing rectifier circuit 1 and the inverter circuit 2, a shunt resistance ratio is inserted on the negative electrode side, and the anode sides of the flywheel diodes D8 to DIO are connected to the rectifier circuit 1 side of the shunt resistance ratio. has been done.
前記シャント抵抗Ｒの両端子は電流検出回路６に接続さ
れ、この電流検出回路６の出力は比較回路７に入力され
ている。Both terminals of the shunt resistor R are connected to a current detection circuit 6, and the output of this current detection circuit 6 is input to a comparison circuit 7.
この比較回路７には基準電圧Ｖｍが入力されており、そ
の出力はドライバ回路５に入力されている。A reference voltage Vm is input to this comparison circuit 7, and its output is input to the driver circuit 5.
このドライバ回路５の出力は図示されていないがトラン
ジスタＴ１〜Ｔ６のベースに入力されている。前記電流
検出回路７はシャント抵抗比の両端間の電圧を検出して
巻線電流を検出するものである。比較回路７は電流検出
回路６の出力電圧と基準電圧７票とを比較し、ドライバ
回路５はこの比較回路７の出力に基づいてインバータを
構成するトランジスタへ印加するベース信号を出力する
。Although not shown, the output of this driver circuit 5 is input to the bases of transistors T1 to T6. The current detection circuit 7 detects the voltage across the shunt resistance ratio to detect the winding current. The comparison circuit 7 compares the output voltage of the current detection circuit 6 and the reference voltage 7, and the driver circuit 5 outputs a base signal to be applied to the transistors forming the inverter based on the output of the comparison circuit 7.
第４図は第３図に示した電流検出回路６、比較回路７及
びドライバ回路５の部分をより詳細に説明する回路図で
あり、第５図はこの回路による動作波形を示す図である
。電流検出回路６は、シャント抵抗凡の電圧降下を、内
蔵しているオペアンプＡ１で増幅し、巻線電流工、に比
例した巻線電流検出電圧■、を出力する。比較回路７は
巻線電流検出電圧Ｖ、と基準電圧ｖ真とを比較するヒス
テリシス付のコンパレータＡ２で構成されている。FIG. 4 is a circuit diagram illustrating in more detail the current detection circuit 6, comparison circuit 7, and driver circuit 5 shown in FIG. 3, and FIG. 5 is a diagram showing operating waveforms of this circuit. The current detection circuit 6 amplifies the voltage drop across the shunt resistor using a built-in operational amplifier A1, and outputs a winding current detection voltage proportional to the winding current. The comparison circuit 7 includes a comparator A2 with hysteresis that compares the winding current detection voltage V and the reference voltage v true.
この比較回路７の出力電圧Ｖｃは第５図１に示すように
、巻線電流検出電圧■、が前記基準電圧 ■暑よりも
高い基準電圧Ｖｉａ及び低い基準電圧ＶＲＬに等しくな
る時点において、それぞれ、ローレベル、ハイレベルと
なる信号電圧である。ドライバ回路５には、モータＭの
回転子角位置に応じた分配回路４の出力が入力される。As shown in FIG. 5, the output voltage Vc of the comparator circuit 7 is as shown in FIG. This is a signal voltage that becomes low level and high level. The output of the distribution circuit 4 corresponding to the rotor angular position of the motor M is input to the driver circuit 5 .
更に、前記ドライバ回路５の正アーム側のトランジスタ
Ｔ１〜Ｔ３に対する信号は、ベース信号停止回路８を構
成するアンド素子によって前記比較回路７の出力とアン
ドがとられ、前記比較回路７の出力■。がローレベルの
時には、正アームのトランジスタＴ１〜Ｔ３がドライブ
されない構成となっている。Furthermore, the signals to the transistors T1 to T3 on the positive arm side of the driver circuit 5 are ANDed with the output of the comparison circuit 7 by an AND element constituting the base signal stop circuit 8, so that the output of the comparison circuit 7 is obtained. When is at a low level, the transistors T1 to T3 in the positive arm are not driven.
次に本実施例の動作について第５図を主に用いて説明す
る０本実施例で使用されているモータＭの誹起電圧Ｅｏ
ｔｉ従来例に比べて小さくなるように設定されている。Next, the operation of this embodiment will be explained using mainly FIG. 5.
ti is set to be smaller than that of the conventional example.
この丸め、速い位相で整流回路１の全波整流電圧Ｖａが
Ｅｏより高くなり、巻線電流１．は速く流れ始め、この
巻線電流１．の流れない期間ｔ、＃′ｉ極めて短くなっ
ている。′を几、この巻線電流工、の立上りは前記誘起
電圧Ｅｏが小さいために急峻であり、巻線電流検出電圧
■。With this rounding and fast phase, the full-wave rectified voltage Va of the rectifier circuit 1 becomes higher than Eo, and the winding current 1. begins to flow quickly, and this winding current 1. The period t, #'i during which no flow occurs is extremely short. The rise of this winding current is steep because the induced voltage Eo is small, and the winding current detection voltage .
は基準電圧ＶＲに短時間で達する。しかし、比較回路７
にはヒステリシスがあるため、前記巻線電流検出電圧Ｖ
、が高基準電圧■■に達するまでは、前記比較回路７の
出力Ｖｃは・・イレベルを維持し、巻線電流１．ｉｊ上
昇し続ける。reaches the reference voltage VR in a short time. However, comparison circuit 7
Since there is hysteresis, the winding current detection voltage V
Until , reaches the high reference voltage ■■, the output Vc of the comparator circuit 7 maintains the ... level, and the winding current 1. ij continues to rise.
前記巻線電流検出電圧Ｖ、が高基準電圧Ｖ■に達すると
、前記比較回路７の出力ＶｃＦｉローレベルに移行する
。このためベース信号停止回路８の出力は分配回路４の
出力にかかわらずローレベルとなり、ドライバ回路５の
卯アームトランジスタ、・１
Ｔ１〜Ｔ３のドライブ信号は零となり、正アーム側のト
ランジスタはオフし、この結果、巻線電流１、ｔｉ減少
し始める。この巻線電流工、の減少に伴い、巻線電流検
出電圧Ｖ、は減少するが、比較回路８のヒステリシスに
より、低基準電圧■真に達するまで前記比較回路７の出
力はハイレベルに復帰しない。比較回路７の出力がハイ
レベルになると、再び正アーム側のトランジスタＴ１〜
Ｔ３はオンジ、巻線電流１．は増加し始める。このよう
に、巻線電流検出電圧Ｖ、にょって正アーム側のトラン
ジスタＴ１〜Ｔ３をチョッピングすることにより、巻線
電流１．は基準電圧ｖ覧に応じて略一定となる。When the winding current detection voltage V reaches the high reference voltage V■, the output VcFi of the comparison circuit 7 shifts to a low level. Therefore, the output of the base signal stop circuit 8 becomes a low level regardless of the output of the distribution circuit 4, and the drive signals of the U-arm transistors of the driver circuit 5, T1 to T3 become zero, and the transistors on the positive arm side are turned off. , As a result, the winding current 1,ti begins to decrease. As the winding current V decreases, the winding current detection voltage V decreases, but due to the hysteresis of the comparator circuit 8, the output of the comparator circuit 7 does not return to the high level until the low reference voltage reaches true. . When the output of the comparator circuit 7 becomes high level, the positive arm side transistors T1~
T3 is on-state, winding current 1. starts to increase. In this way, by chopping the transistors T1 to T3 on the positive arm side according to the winding current detection voltage V, the winding current 1. is approximately constant depending on the reference voltage v.
本実施例によれば、誘起電圧Ｅｏの小さいモータＭを用
い、且つ、巻線電流Ｉ、に対応した巻線電流検出電圧■
、が所定の基準電圧ＶＲに略等しくなるように、インバ
ータ回路２の正アーム側トランジスタＴ１〜Ｔ３をチョ
ッピングすることにより、前記巻線電流工、の遮断され
る期間が短く、且つ、この巻線電流１．のピークが平坦
となるため、巻線電流１．の脈動が小さくなり、インバ
ータ回路２の効率（ひいてはモータＭの効率）が向上す
るという効果がある。このため、効率を落とすことなく
ブラシレスモータを駆動するインバータから平滑コンデ
ンサをなくして、これを小形軽量化し得る効果があり、
また、インバータを構成するダイオードやトランジスタ
を１つの集積回路とし得る効果がある。According to this embodiment, a motor M with a small induced voltage Eo is used, and the winding current detection voltage .
By chopping the positive arm side transistors T1 to T3 of the inverter circuit 2 so that , becomes substantially equal to a predetermined reference voltage VR, the period during which the winding current is cut off is shortened, and the winding current Current 1. Since the peak of the winding current becomes flat, the winding current 1. This has the effect that the pulsation of is reduced, and the efficiency of the inverter circuit 2 (and thus the efficiency of the motor M) is improved. This has the effect of eliminating the smoothing capacitor from the inverter that drives the brushless motor and making it smaller and lighter without reducing efficiency.
Further, there is an effect that the diodes and transistors that constitute the inverter can be integrated into one integrated circuit.
第６図は本発明の他の実施例の要部を示したものである
０位置検出回路３の出力は分配回路４を介して基準電圧
発生回路９に入力される。この基準電圧発生回路９はＥ
Ｏ几（）：ｘｃｌｕｓｉｖｅ Ｑｌｌ）素子９１及びワ
ンショットマルチバイブレータ９２から主に構成され、
位置検出回路の出力はこの基準電圧発生回路９のＥＯＲ
素子９１を経てワンショットマυチバイプレータ９２に
入り、このワンショットマルチバイブレータ９２は回転
数信号ＶＦを出力する。回転数検出回路９の出力である
前記回転数信号Ｖｒｔｉ第２の比較回路１０に入力され
る。この第２の比較回路１０はオペアンプ１０１で主に
構成され、前記回転数信号ＶＦと別に入力される回転数
指令信号ｖ罠ｒとを比較して基準電圧■１１を比較回路
７に出力する。なお、前記回転数検出回路９及び第２の
比較回路１０により基準電圧発生回路１１が構成されて
いる。他の構成は前実施例と同様である九め図示及び説
明は省略する。FIG. 6 shows the main part of another embodiment of the present invention. The output of the 0 position detection circuit 3 is inputted to the reference voltage generation circuit 9 via the distribution circuit 4. This reference voltage generation circuit 9 is
It mainly consists of an O(): x exclusive Qll) element 91 and a one-shot multivibrator 92,
The output of the position detection circuit is the EOR of this reference voltage generation circuit 9.
It enters a one-shot multivibrator 92 via an element 91, and this one-shot multivibrator 92 outputs a rotational speed signal VF. The rotation speed signal Vrti, which is the output of the rotation speed detection circuit 9, is input to a second comparison circuit 10. The second comparator circuit 10 is mainly composed of an operational amplifier 101, and compares the rotation speed signal VF with a separately input rotation speed command signal vtrapr, and outputs a reference voltage 11 to the comparison circuit 7. Note that the rotation speed detection circuit 9 and the second comparison circuit 10 constitute a reference voltage generation circuit 11. The other configurations are the same as those of the previous embodiment, so illustration and description will be omitted.
本実施例では、位置検出回路３の出力を回転数信号Ｖν
に変換し、この回転数信号Ｖｙを考慮して基準電圧■寞
を発生するため、モータの回転数に応じて基準電圧Ｖｍ
を変化させるという回転数フィードバックが行なわれて
おり、回転数指令信号ｖ＊ｖに応じて図示されないモー
タの巻線電流を前実施例のそれよりも一層安定に制御し
得る効果がある。このため、巻線電流の脈動が前実施例
より一層小さくなり、インバータ及びモータの効率を一
層向上させる効果がある。In this embodiment, the output of the position detection circuit 3 is used as the rotational speed signal Vν
In order to generate the reference voltage Vm in consideration of this rotational speed signal Vy, the reference voltage Vm is changed according to the rotational speed of the motor.
Since the rotation speed feedback is performed by changing the rotation speed command signal v*v, the winding current of the motor (not shown) can be controlled more stably than in the previous embodiment in accordance with the rotation speed command signal v*v. Therefore, the pulsation of the winding current becomes even smaller than in the previous embodiment, which has the effect of further improving the efficiency of the inverter and motor.
以上記述した如く本発明のブラシレスモータの運転法に
よれば、コンデンサレスタイプのインバータを使用した
場合にもＰ？率を維持することができる。As described above, according to the brushless motor operating method of the present invention, P? rate can be maintained.
第１図はブラシレスモータを駆動する従来のインバータ
の構成を示した回路図、第２図は第１図で示した回路の
動作波形線図、第３図は本発明のブラシレスモータの運
転法の一実施例を適用し次インバータの構成例を示した
回路図、第４図は第３図に示した電流検出回路及び比較
回路部の詳細例を示した回路図、第５図は第４図で示し
た回路によるモータ運転時の各部の動作波形線図、第６
図は本発明のブラシレスモータの運転法の一実施例を適
用したインバータ回路の他の構成例の要部を示した回路
図である。
１・・・整流回路、２・・・インバータ回路、３・・・
位置検出回路、４・・・分配回路、５・・・ドライブ回
路、６・・・電流検出回路、７・・・比較回路、１１・
・・基準電圧発第３ 図
５Fig. 1 is a circuit diagram showing the configuration of a conventional inverter that drives a brushless motor, Fig. 2 is an operating waveform diagram of the circuit shown in Fig. 1, and Fig. 3 is a method of operating the brushless motor of the present invention. FIG. 4 is a circuit diagram showing a detailed example of the current detection circuit and comparison circuit section shown in FIG. 3, and FIG. Operation waveform diagram of each part during motor operation using the circuit shown in Figure 6
The figure is a circuit diagram showing a main part of another configuration example of an inverter circuit to which an embodiment of the brushless motor operating method of the present invention is applied. 1... Rectifier circuit, 2... Inverter circuit, 3...
Position detection circuit, 4... Distribution circuit, 5... Drive circuit, 6... Current detection circuit, 7... Comparison circuit, 11.
...Reference voltage generation Figure 3
Claims (1)
である直流を任意の同波数の交流に変換するインバータ
と、このインバータの出力を固定子巻線に通流して回転
子を回転させるブラシレスモータとを備え、前記巻線に
流れる巻線電流が少なくとも前記交流の極性が切替わる
時点を含む期間に断続する前記ブラシレスモータの運転
法において、前記インバータに流れる電流を検出する電
流検出回路と、所定の基準電圧を発生する基準電圧発生
回路と、前記電流検出回路の出力信号と、前記基準電圧
とを比較する比較回路とを設け、この比較回路の出力信
号に基づいて前記整流器からインバータへ流れる直流を
オン、オフすることを特徴とするブラシレスモータの運
転法。 ２ 前記基準電圧発生回路は、前記ブラシレスモータの
回転数を検出する回転数検出回路と、この回転数検出回
路の出力信号と所定の回転数指令信号とを比較する比較
回路とを有し、ブラシレスモータの回転数に応じ次基準
電圧を発生することを特徴とする特許請求の範囲第１項
記載のブラシレスモータの運転法。[Claims] 1. A rectifier that converts alternating current into direct current, an inverter that converts the direct current that is the output of this rectifier into alternating current of the same arbitrary wave number, and the output of this inverter is passed through a stator winding. A brushless motor that rotates a rotor is provided, and a current flowing through the inverter is detected in a method of operating the brushless motor in which a winding current flowing through the windings is intermittent during a period including at least a time point when the polarity of the alternating current is switched. A current detection circuit that generates a predetermined reference voltage, a reference voltage generation circuit that generates a predetermined reference voltage, and a comparison circuit that compares the output signal of the current detection circuit with the reference voltage, and A method of operating a brushless motor characterized by turning on and off a direct current flowing from the rectifier to an inverter. 2. The reference voltage generation circuit includes a rotation speed detection circuit that detects the rotation speed of the brushless motor, and a comparison circuit that compares an output signal of the rotation speed detection circuit with a predetermined rotation speed command signal. A method of operating a brushless motor according to claim 1, characterized in that the following reference voltage is generated in accordance with the rotational speed of the motor.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57094904A JPS58212384A (en) | 1982-06-04 | 1982-06-04 | Operating method for brushless motor |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57094904A JPS58212384A (en) | 1982-06-04 | 1982-06-04 | Operating method for brushless motor |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS58212384A true JPS58212384A (en) | 1983-12-10 |
| JPH0159839B2 JPH0159839B2 (en) | 1989-12-19 |
Family
ID=14123003
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP57094904A Granted JPS58212384A (en) | 1982-06-04 | 1982-06-04 | Operating method for brushless motor |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS58212384A (en) |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6192194A (en) * | 1984-10-11 | 1986-05-10 | Hitachi Ltd | Operation controlling method of air conditioner |
| WO1987000705A1 (en) * | 1985-07-16 | 1987-01-29 | Matsushita Electric Industrial Co., Ltd. | Motor controller |
| EP0387358A1 (en) * | 1988-09-12 | 1990-09-19 | Kabushikigaisha Sekogiken | Dc motor |
| JPH06113587A (en) * | 1990-08-21 | 1994-04-22 | Heidelberger Druckmas Ag | Adjusting method of motor current of brushless dc current |
| JP2002027785A (en) * | 2000-07-05 | 2002-01-25 | Matsushita Electric Ind Co Ltd | Inverter and washing machine or cleaner utilizing the same |
-
1982
- 1982-06-04 JP JP57094904A patent/JPS58212384A/en active Granted
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6192194A (en) * | 1984-10-11 | 1986-05-10 | Hitachi Ltd | Operation controlling method of air conditioner |
| WO1987000705A1 (en) * | 1985-07-16 | 1987-01-29 | Matsushita Electric Industrial Co., Ltd. | Motor controller |
| EP0387358A1 (en) * | 1988-09-12 | 1990-09-19 | Kabushikigaisha Sekogiken | Dc motor |
| JPH06113587A (en) * | 1990-08-21 | 1994-04-22 | Heidelberger Druckmas Ag | Adjusting method of motor current of brushless dc current |
| JP2002027785A (en) * | 2000-07-05 | 2002-01-25 | Matsushita Electric Ind Co Ltd | Inverter and washing machine or cleaner utilizing the same |
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0159839B2 (en) | 1989-12-19 |
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