JPS58111587A - Automatic gain controlling circuit - Google Patents
Automatic gain controlling circuitInfo
- Publication number
- JPS58111587A JPS58111587A JP56209394A JP20939481A JPS58111587A JP S58111587 A JPS58111587 A JP S58111587A JP 56209394 A JP56209394 A JP 56209394A JP 20939481 A JP20939481 A JP 20939481A JP S58111587 A JPS58111587 A JP S58111587A
- Authority
- JP
- Japan
- Prior art keywords
- circuit
- output
- pulse
- signal
- synchronizing signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/76—Television signal recording
- H04N5/91—Television signal processing therefor
Landscapes
- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
- Television Receiver Circuits (AREA)
- Television Signal Processing For Recording (AREA)
Abstract
Description
【発明の詳細な説明】
本発明は、ビデオ信号の自鯛利4i1tll(il (
以F、t;Cと略す)1gi路に好適な集積回路に関す
るものである。DETAILED DESCRIPTION OF THE INVENTION The present invention provides a method for controlling video signal
This invention relates to an integrated circuit suitable for a 1gi circuit (hereinafter abbreviated as F, t; C).
通常、VTR等で用いられているビデオ信号の記鍮用A
GC回路においては、同期信号のバックポーチに白パル
スを付加したビデオ信号を被検波信号として発生させ℃
、AGC制#僅号消号、ビデ第1g号のシンクチップか
ら白レベルまでの振幅が一定になるようにmat、てい
る。A for recording video signals usually used in VTRs, etc.
In the GC circuit, a video signal with a white pulse added to the back porch of the synchronization signal is generated as the test wave signal.
, AGC system No. 1 g is set so that the amplitude from the sync tip to the white level of the bidet No. 1g is constant.
従来上記白パルスをビデオ信号に付加する几めの牛−パ
ルスな得る集積回路としては、第1図に示すように、ピ
ーク横波回路1と砿小定′IEflL放電回路2と比較
器3からlllgL、等価的に入力された同期信号の後
縁なi4延させたパルスな得てい几。ピークIlt波用
コンアン?4としてモノリシックICに内斌町馳な厘は
IQpFg度であり、その時の放電電流は10 、an
ii度になるが、抵抗バイアス法電流吸込み回路で比軟
的容易に得られ、集積化を実現している。第2図の動作
説明図を用いてさらKi#側に説明する。第2図(α)
に示した可変有得回路5の出力であるビデオ信号から、
P4期分jIliIm路6を介して得られ危第2図(j
)に示した同期信号が、ピーク検波回路1に供給され、
同期信号のピークがサンプルされる。サンプルされへ電
位は、微小定電流放電回路2において、非テンプルM間
に放@降下して、放電回路2の出力は82図(c)に示
すようになる。第2図C)の信号は、基準電圧源7で与
えられた比較電位(イ)〔第2図(c)に破線で図示〕
を有する比較器3に供給され、比較器3からは、鴫2図
(C) K示した信号が比較電位(イ)より高い場合高
電位を、低い場合低電位を有する第2図(d) K示す
ようなパルスを發生じ、被検波信号発生回路8にキーパ
ルスとして入力される。Conventionally, as shown in FIG. 1, an integrated circuit for adding the white pulse to a video signal in a refined manner is composed of a peak transverse wave circuit 1, an IEflL discharge circuit 2 and a comparator 3. , equivalently the trailing edge of the input synchronization signal i4 is the extended pulse. Conan for peak Ilt wave? 4, the power of monolithic IC is IQpFg, and the discharge current at that time is 10, an
2 degrees, but it can be obtained relatively easily with a resistance bias method current sink circuit, and integration has been realized. The Ki# side will be further explained using the operation explanatory diagram of FIG. Figure 2 (α)
From the video signal that is the output of the variable gain circuit 5 shown in
P4 period jIliIm path 6 obtained through the crisis Figure 2 (j
) is supplied to the peak detection circuit 1,
The peak of the sync signal is sampled. The sampled potential drops across the non-temple M in the minute constant current discharge circuit 2, and the output of the discharge circuit 2 becomes as shown in FIG. 82(c). The signal in Figure 2C) is the comparison potential (A) given by the reference voltage source 7 [shown by the broken line in Figure 2C].
If the signal shown in Figure 2 (C) is higher than the comparison potential (A), a high potential is given, and if it is lower than the comparison potential (A), a low potential is supplied from the comparator 3. A pulse as indicated by K is generated and inputted to the test wave signal generation circuit 8 as a key pulse.
被検波信号発生回路8では、上記キーパルス期間だけ、
他方から入力されたビデオ信号とシンフチラグとの電位
差を足数情して自パルスを発生させ、ビデオ信号忙付加
し、7s2図(#)に示すような被横波信号を得て、検
波回路9を介して町変利41al略5を制御していた。In the test wave signal generation circuit 8, only during the above key pulse period,
A self-pulse is generated by calculating the potential difference between the video signal inputted from the other side and the syn-edge lag, and the video signal is added to the signal to obtain a transverse wave signal as shown in Figure 7s2 (#), and the detection circuit 9 is Through this, he controlled approximately 5 of the town's Henri stations.
しかし上述の従来技術においては、AGC回#F前段の
膚波毅特性の影−等により、第5図(glに示すような
バンクポーチ前縁がもチ上カっ九ビデオ信号がAGC回
路に入力されると、キーパルス期間中のペデスタルレベ
ルに上記もち上がりがある虎め、付加される白パルスは
第3図(6)K示すようになる。このため被検波信号は
第5図(−)に示すような波形になり、検波回路9の出
力はもち上がった分だけ高くなり、可変有得回路の利得
が小さくなり、ビデオ信号の振幅がFTrjiIのレベ
ルより小さくなるという欠点があつ次。However, in the above-mentioned conventional technology, due to the influence of the characteristic of Takeshi Hadami in the front stage of the AGC circuit #F, the leading edge of the bank pouch as shown in FIG. When input, if the pedestal level during the key pulse period has the above-mentioned rise, the added white pulse becomes as shown in Fig. 3 (6) K. Therefore, the test wave signal becomes as shown in Fig. 5 (-). The waveform becomes as shown in , the output of the detection circuit 9 increases by the amount of increase, the gain of the variable gain circuit decreases, and the amplitude of the video signal becomes smaller than the level of FTrjiI.
本WA@の目的は上記し友従来技術の欠点をなくし、A
GC回路に人力されたビデオ信号のバンクポーチ前縁の
波形歪にかかわらずAGC性能の良好なAGC用#&積
回路を提供することにある。The purpose of this WA@ is to eliminate the drawbacks of the prior art and to
An object of the present invention is to provide an #& product circuit for AGC which has good AGC performance regardless of waveform distortion at the leading edge of a bank pouch of a video signal inputted to a GC circuit.
上記目的な達成するために、本発明では、キーパルスJ
k4る集積回路として、集積化可能なピーク検ma路と
微小定電流放電回路により同期信号の後縁の立ち下りに
傾斜をもりた傾斜パルスt−発生させるとともに、上記
傾斜パルスを横切る21C)比較電位な設けて、上記傾
斜パルスの電位が211の比較電位の閾にあると−きの
み高電位のパルスt−発生させ、キーパルスとするもの
である。即ち第1の比較電位により同期イg号のバック
ポーチIi1鑞部をキーパルス期間から除き、第2の比
較電位によりキーパルス終瑞を決定して、上記前緻澤に
生じた波形歪の影響を解消するものである。In order to achieve the above object, the present invention provides a key pulse J
As an integrated circuit, a slope pulse t with a slope is generated at the trailing edge of the synchronization signal using an integrated peak detection path and a minute constant current discharge circuit, and a comparison potential across the slope pulse is generated. Moreover, only when the potential of the gradient pulse is at the threshold of the comparison potential 211, a high potential pulse t is generated and used as a key pulse. That is, the first comparison potential removes the back porch Ii1 part of the synchronous Ig from the key pulse period, and the second comparison potential determines the end of the key pulse, thereby eliminating the influence of waveform distortion occurring in the front part. It is something to do.
以下本発明を実施fIt−用いて説明する。第4図は本
発明のAGC用集横d路の一実施例を示す図で、第5囚
は本発明の詳細な説明する図である。第4#!Jにおい
て、第1図に示し迄従来例と同等あるいは同一部分は同
−書号が付しである。今、従来例ではA’GC特性を劣
化させる第5図(α)に示すようなビデオ信号がAGC
回路に人力されると、7q変利4−路5、同期信号分層
回踏6を介して、第5図(6)り示すような同期信号が
優られ、次段のピーク検波回路1に供給される。ピーク
検波回路1及び微小定lic流放電回Ms2では、同期
信号のピーク域値をサンプルするとともに、非サンプル
期間には放IIc降下し、第5図CC)に示すような信
号が得られる。The present invention will be explained below using an example. FIG. 4 is a diagram showing an embodiment of the AGC collection lateral d path of the present invention, and the fifth figure is a diagram illustrating the present invention in detail. 4th #! In J, parts that are equivalent or identical to those of the conventional example up to the point shown in FIG. 1 are given the same numbers. Now, in the conventional example, a video signal as shown in FIG. 5 (α) that deteriorates the A'GC characteristic is
When inputted to the circuit, a synchronizing signal as shown in FIG. Supplied. The peak detection circuit 1 and the minute constant LIC current discharge circuit Ms2 sample the peak threshold value of the synchronizing signal, and during the non-sampling period, the signal IIc drops, resulting in a signal as shown in FIG. 5 (CC).
第5図(C)−の信号は、基準電圧源1oで与えられ次
比較1位(C1) (第5図CC)t/C破線で図示〕
を有する比較器11、および基準電圧源12で与えら。The signal in Fig. 5 (C) is given by the reference voltage source 1o and is shown as the first comparison (C1) (Fig. 5 CC) by the t/C broken line]
and a reference voltage source 12.
れた比較電位(ハ)〔第5図(d)に一点@−で図示〕
を有する比較器13に供給され、比較器11の出力とし
て第5図Cd)、ま危比42蕃15の出方として第5図
(1)に示すような信号が得られる。Comparison potential (c) [shown in Figure 5(d) with a single point @-]
The output of the comparator 11 is Cd) in FIG. 5, and the output of the ratio 42 and the output signal 15 is as shown in FIG.
次にAND回路14で、上記比軟器11 、13の両出
力のANDをとると、第5図げ)K示すようなビデオ信
号のバックポーチの前縁を含ま、ないパルスが得られ、
キーパルスとして被検波信号発生回路!3に供給される
。而して′、門構波信号としては、°第5、図(!i)
に示すよう忙、パックボない白パルスが付加されること
となり、AGC性艷の劣化を解消できる。またピーク検
波用コンデンサ4としては、従来例で前に説明し友よう
に、モノリシックICfCP3蔵可能な1直(10pF
−程度)で、十分jg5s(C)K示すような信号が得
られ、本発明の全構成の集積化が容易に可能となる。Next, when the AND circuit 14 performs an AND operation on the outputs of the softeners 11 and 13, a pulse is obtained that does not include the leading edge of the back porch of the video signal, as shown in Figure 5).
Test wave signal generation circuit as key pulse! 3. Therefore, the gate configuration signal is shown in Figure 5 (!i).
As shown in the figure, a white pulse with no busy or back-up is added, and the deterioration of the AGC characteristic can be eliminated. In addition, as the peak detection capacitor 4, as explained earlier in the conventional example, a single direct current (10 pF
- degree), a signal such as jg5s(C)K can be sufficiently obtained, and the entire structure of the present invention can be easily integrated.
第6図に本発明の一具体的集積回路例を示す。FIG. 6 shows a specific example of an integrated circuit according to the present invention.
N6図においても、N1図、第4図と同等あるいは同一
部分は同−誉号を付している。トランジスタ15とコン
デンt4でピーク横波flatを、トランジスタ16.
17%抵抗18.19.20で抵抗バイアス法電流吸込
み回路による徽小定域流放電回路2を構成している。ト
ランジスタ21、抵抗22は、上記ビーク検波回路1及
び微小定電流放(Igl路2からの信号を高インピーダ
ンスでうけ、トランジスタ25 、24、定電流源25
%抵抗26゜基準電圧l112からなる比較a15およ
びトランジスタ27 、28、定電流源29、抵抗50
、基準電圧源10からなる比較器11に供給している。In Figure N6, parts that are equivalent or identical to those in Figures N1 and 4 are given the same honor symbol. The peak transverse wave flat is generated by transistor 15 and capacitor t4, and transistor 16.
The 17% resistors 18, 19, and 20 constitute a small constant current discharge circuit 2 using a resistance bias method current sink circuit. The transistor 21 and the resistor 22 receive the signal from the peak detection circuit 1 and the minute constant current discharge (Igl path 2) at high impedance, and the transistors 25 and 24 and the constant current source 25
Comparison a15 consisting of % resistance 26° reference voltage l112, transistors 27, 28, constant current source 29, resistor 50
, is supplied to a comparator 11 consisting of a reference voltage source 10.
抵抗51では、上記両比較器11 、15からの出力の
AND信号を得、トランジスタ32、抵抗55からなる
高入力拳低出力インピーダンス回路に供給している。而
してトランジスタ23のエミッタからはバックポーチ前
縁を含まないキーパルスが次段の被検波信号発生回路8
に供給されることとなり、比較的簡単な回路で集積化が
実現できる。The resistor 51 obtains an AND signal of the outputs from both the comparators 11 and 15, and supplies it to a high-input, low-output impedance circuit consisting of a transistor 32 and a resistor 55. Then, a key pulse that does not include the front edge of the back porch is output from the emitter of the transistor 23 to the test wave signal generation circuit 8 in the next stage.
This means that integration can be achieved with a relatively simple circuit.
以上述べたように本発明によれば、AGC1路に入力さ
れるビデオ信号の波形歪処かかわらすAGC性能が良好
で、集積化に適したAGC用集積回路を実現できる。As described above, according to the present invention, it is possible to realize an AGC integrated circuit that has good AGC performance regardless of the waveform distortion of the video signal input to the AGC 1 path and is suitable for integration.
第1図は、従来のAG、CMQ積回路を示す図。
82図、#I3図は従来例の説明図、第4図は本発明の
一実施例を示す図、N5図は本発明の詳細な説明する図
、第6図は本発明の一具体的回路例を示す図である。
図において、
1・・・ピーク検波回路
2・−・倣小定電流款電回路
! 、 11 、13−比較器
6・−同期分離回路
8−被検波信号発生回路
14・−ANI)回路
である。
i3図
!+rfU
も5図
】−〇 匹口FIG. 1 is a diagram showing a conventional AG/CMQ product circuit. Figure 82 and #I3 are explanatory diagrams of the conventional example, Figure 4 is a diagram illustrating an embodiment of the present invention, Figure N5 is a diagram illustrating details of the present invention, and Figure 6 is a specific circuit of the present invention. It is a figure which shows an example. In the diagram, 1...Peak detection circuit 2...Imitation small constant current power circuit! , 11, 13 - Comparator 6 - Synchronization separation circuit 8 - Test wave signal generation circuit 14 - ANI) circuit. i3 figure! +rfU Figure 5】-〇 Fish mouth
Claims (1)
ーク検波回路の出力に接続された放電回路と、該放電回
路の出力が供給される第1、第2の比較器と%該両比較
器の出力が供給されるmaw路とを少なくとも具備し、
該鹸埋崗路の出力をn1m利得ia制御回路用キーパル
スとして利用することを特徴とする自励利得制御用回路
。 2、 上記両比較器を各々トランゾスタ対からなる差励
増a器で構成し、上記放1IC1[2I14出力に一対
し工、上記j11の比較器の4準屯圧が高い場合に、お
よび上記$2の比較器の4準鑞圧が低い場合に、各々該
トランジスタ対の内コレクタ電流がし中断される方のト
ランジスタのコレクタに接続された抵抗を共通にして、
上記輪環回路を構成したことを特徴とする特許m求のI
[踊箒1項紀或の自励利得制御用回路。[Claims] 1. A peak detection circuit into which the split layer synchronization No. 1 is input, a discharge circuit connected to the output of the peak detection circuit, and a first and second circuit to which the output of the discharge circuit is supplied. comprising at least a comparator and a maw path to which the outputs of both comparators are supplied;
A circuit for self-excitation gain control, characterized in that the output of the oscilloscope is used as a key pulse for an N1M gain IA control circuit. 2. Both of the above comparators are each configured with a differential excitation amplifier a consisting of a pair of transistors, and one pair is connected to the above output 1 IC1 [2 When the quasi-voltage voltage of the comparators 2 and 4 is low, the collector current of each of the transistors in the pair is interrupted by using a common resistor connected to the collector of the transistor,
I of the patent m characterized by configuring the above-mentioned ring circuit
[Circuit for self-excitation gain control of Orihoki 1st term.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP56209394A JPS58111587A (en) | 1981-12-25 | 1981-12-25 | Automatic gain controlling circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP56209394A JPS58111587A (en) | 1981-12-25 | 1981-12-25 | Automatic gain controlling circuit |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS58111587A true JPS58111587A (en) | 1983-07-02 |
JPH0559634B2 JPH0559634B2 (en) | 1993-08-31 |
Family
ID=16572167
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP56209394A Granted JPS58111587A (en) | 1981-12-25 | 1981-12-25 | Automatic gain controlling circuit |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS58111587A (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
FR2611337A1 (en) * | 1987-02-20 | 1988-08-26 | Thomson Semiconducteurs | DEVICE FOR AUTOMATIC CONTROL OF VIDEO SIGNAL GAIN |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5062725A (en) * | 1973-10-05 | 1975-05-28 | ||
JPS554747A (en) * | 1978-06-28 | 1980-01-14 | Hitachi Ltd | Video signal recording circuit |
-
1981
- 1981-12-25 JP JP56209394A patent/JPS58111587A/en active Granted
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5062725A (en) * | 1973-10-05 | 1975-05-28 | ||
JPS554747A (en) * | 1978-06-28 | 1980-01-14 | Hitachi Ltd | Video signal recording circuit |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
FR2611337A1 (en) * | 1987-02-20 | 1988-08-26 | Thomson Semiconducteurs | DEVICE FOR AUTOMATIC CONTROL OF VIDEO SIGNAL GAIN |
Also Published As
Publication number | Publication date |
---|---|
JPH0559634B2 (en) | 1993-08-31 |
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