JPH08288838A - Phase locked loop circuit - Google Patents
Phase locked loop circuitInfo
- Publication number
- JPH08288838A JPH08288838A JP7085839A JP8583995A JPH08288838A JP H08288838 A JPH08288838 A JP H08288838A JP 7085839 A JP7085839 A JP 7085839A JP 8583995 A JP8583995 A JP 8583995A JP H08288838 A JPH08288838 A JP H08288838A
- Authority
- JP
- Japan
- Prior art keywords
- phase
- voltage
- resistor
- phase difference
- voltage division
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Abstract
Description
【0001】[0001]
【産業上の利用分野】本発明は位相同期回路に関し、特
に周波数シンセサイザ等の位相同期方式の発振回路の改
良に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a phase locked loop circuit, and more particularly to improvement of a phase locked loop oscillator such as a frequency synthesizer.
【0002】[0002]
【従来の技術】図4はこの種の位相同期方式の発振回路
の一例を示すブロック図であり、VCO(電圧制御発振
器)3の出力は分周回路4により分周(fp )されて基
準入力信号の周波数fr と周波数位相比較器1にて周波
数差及び位相差がディジタル的に検出される。2. Description of the Related Art FIG. 4 is a block diagram showing an example of an oscillation circuit of this type of phase-locking system, in which an output of a VCO (voltage controlled oscillator) 3 is frequency-divided (fp) by a frequency dividing circuit 4 and a reference input. The frequency fr and the frequency phase comparator 1 digitally detect the frequency difference and the phase difference.
【0003】すなわち、基準入力信号(fr )に対して
分周信号(fp )の位相が進んでいれば、その進み量に
応じたパルス幅の第1の位相差出力Pd が生成される。
逆に基準入力信号に対して分周信号の位相が遅れていれ
ば、その遅れ量に応じたパルス幅の第2の位相差出力P
u が生成される。That is, if the phase of the divided signal (fp) is advanced with respect to the reference input signal (fr), the first phase difference output Pd having a pulse width corresponding to the amount of advance is generated.
On the contrary, if the phase of the divided signal is delayed with respect to the reference input signal, the second phase difference output P having a pulse width corresponding to the delay amount is output.
u is generated.
【0004】この様なディジタル周波数位相比較器は周
知の回路であり、例えば特開平3−295316号公報
や特開平5−206845号公報等に開示されたものを
用いることができる。Such a digital frequency phase comparator is a well-known circuit, and for example, those disclosed in Japanese Patent Laid-Open Nos. 3-295316 and 5-206845 can be used.
【0005】これ等第1及び第2の位相差出力Pd ,P
u は抵抗R1,R2及びコンデンサ6a,6bからなる
平滑化用フィルタを介して高域成分が除去され、そして
差動入力型のループフィルタ2の差動入力となる。この
差動入力ループフィルタ2の出力がVCO3の制御電圧
となり、このVCO3の出力Oに基準入力信号(fr)
に位相同期した信号が得られるものである。These first and second phase difference outputs Pd, P
The high frequency component of u is removed through a smoothing filter composed of resistors R1 and R2 and capacitors 6a and 6b, and becomes a differential input of a differential input type loop filter 2. The output of the differential input loop filter 2 becomes the control voltage of the VCO 3, and the reference input signal (fr) is output to the output O of the VCO 3.
A signal that is phase-synchronized with is obtained.
【0006】この様な構成の位相同期方式発振回路にお
いて、位相同期が確立している状態では周波数位相比較
器1の2入力である基準入力信号(fr )と分周回路4
の分周信号(fp )とは、図5の下側に示す如く完全に
位相同期しており、両者の位相差は零となっている。従
って、比較器1の2つのディジタル出力Pd ,Pu は共
にハイレベル(VH )を維持し、これ等両ディジタル出
力Pd ,Pu の直流成分の電位差は零となっている。In the phase locked oscillator circuit having such a structure, the reference input signal (fr), which is the two inputs of the frequency phase comparator 1, and the frequency divider circuit 4 when the phase lock is established.
The frequency-divided signal (fp) is completely phase-synchronized as shown in the lower side of FIG. 5, and the phase difference between the two is zero. Therefore, the two digital outputs Pd and Pu of the comparator 1 both maintain a high level (VH), and the potential difference between the DC components of these two digital outputs Pd and Pu is zero.
【0007】但し、位相同期状態において、基準入力信
号に対して分周出力信号(fp )の位相は種々の要因に
より瞬間的にずれるために、このずれに応じた誤差信号
が比較器1から出力され、この誤差信号によりVCO3
が制御されて基準入力信号(fr )と分周出力信号(f
p )との位相が一致する様に制御がなされる。よって、
常に基準入力信号に位相同期した出力信号OがVCO3
から生成されるのである。However, in the phase-locked state, the phase of the frequency-divided output signal (fp) with respect to the reference input signal instantaneously shifts due to various factors. Therefore, an error signal corresponding to this shift is output from the comparator 1. This error signal causes VCO3
Are controlled so that the reference input signal (fr) and the divided output signal (f
The control is performed so that the phase of (p) coincides with that of p). Therefore,
The output signal O that is always in phase with the reference input signal is VCO3.
Is generated from.
【0008】ここで、周波数位相比較器1の入出力特性
を示す入力位相差に対する出力信号Pd とPu との差の
直流成分の関係は、一般に線形であると考えられる。し
かしながら、実際には、当該比較器1の内部伝搬遅延等
の要因により、完全な線形ではなく、図6に示す様な不
感帯を有する特性を呈するものである。この不感帯は入
力信号位相差が零付近において出力信号(Pd とPu と
の差直流電圧)が変化しないものである。Here, the relationship of the DC component of the difference between the output signals Pd and Pu with respect to the input phase difference showing the input / output characteristic of the frequency phase comparator 1 is generally considered to be linear. However, in reality, due to factors such as the internal propagation delay of the comparator 1, it is not perfectly linear and exhibits a characteristic having a dead zone as shown in FIG. This dead zone is such that the output signal (DC voltage difference between Pd and Pu) does not change when the input signal phase difference is near zero.
【0009】[0009]
【発明が解決しようとする課題】この様な図4に示した
従来の位相同期方式の発振回路では、図6に示す如く周
波数位相比較器の入出力特性に不感帯を有しているため
に、基準入力信号に対する分周回路出力の位相が一致し
て同期確立している状態で、基準入力信号に対する分周
出力の微小な位相ずれを検出することができず、制御が
かからず、よって出力信号の位相雑音の劣化を招来する
という欠点がある。The conventional phase-locking oscillator circuit shown in FIG. 4 has a dead zone in the input / output characteristics of the frequency phase comparator as shown in FIG. When the phase of the frequency divider circuit output with respect to the reference input signal matches and the synchronization is established, a minute phase shift of the frequency division output with respect to the reference input signal cannot be detected, and control is not applied, so the output There is a drawback in that the phase noise of the signal is deteriorated.
【0010】尚、この様な周波数位相比較器の入出力特
性における不感帯を避ける技術が、先に掲げた特開平3
−295316号公報や特開平5−206845号公報
等に提案されているが、これ等の技術では、位相比較器
とフィルタとの間にチャージポンプ回路を設けた位相同
期回路を前提としており、このチャージポンプ回路を有
さない図4に示した差動入力ループフィルタ2を有する
形式の位相同期方式の発振回路には、前記各公報の技術
をそのまま適用することはできない。A technique for avoiding the dead zone in the input / output characteristics of such a frequency phase comparator is disclosed in the above-mentioned Japanese Patent Laid-Open No.
Although proposed in Japanese Patent Application Laid-Open No. 295316/1993 and Japanese Patent Application Laid-Open No. 5-206845, these techniques are premised on a phase locked loop circuit provided with a charge pump circuit between a phase comparator and a filter. The techniques of the above publications cannot be applied as they are to the phase-locked oscillation circuit having the differential input loop filter 2 shown in FIG. 4 that does not have a charge pump circuit.
【0011】本発明の目的は、差動入力ループフィルタ
を有する形式の回路に対して簡単な回路を追加するのみ
で不感帯を避けて動作可能とした位相同期回路を提供す
ることである。An object of the present invention is to provide a phase locked loop circuit which is operable by avoiding a dead zone by simply adding a simple circuit to a circuit having a differential input loop filter.
【0012】[0012]
【課題を解決するための手段】本発明によれば、電圧制
御発振手段と、この発振信号と基準入力信号との位相比
較を行い前記基準信号に対して前記発振信号が位相進み
状態の時にこの位相進み量に応じた第1の位相差出力を
生成し、位相遅れ状態の時にこの位相遅れ量に応じた第
2の位相差出力を生成する位相比較手段と、前記第1及
び第2の位相差出力に夫々対応して設けられ対応位相差
出力を互いに異なる分圧比で夫々分圧する第1及び第2
の分圧手段と、前記第1及び第2の分圧手段の両分圧出
力を差動入力とし前記電圧制御発振手段の制御電圧を生
成するフィルタ手段とを含むことを特徴とする位相同期
回路が得られる。According to the present invention, the voltage-controlled oscillation means compares the phase of this oscillation signal with the reference input signal, and when the oscillation signal is in a phase lead state with respect to the reference signal, Phase comparing means for generating a first phase difference output according to the phase lead amount and for generating a second phase difference output according to the phase delay amount in the phase delay state, and the first and second positions. First and second parts provided corresponding to the phase difference outputs and respectively dividing the corresponding phase difference outputs with different voltage division ratios.
And a filter means for generating a control voltage for the voltage controlled oscillation means by using both the divided voltage outputs of the first and second voltage dividing means as differential inputs. Is obtained.
【0013】[0013]
【作用】周波数位相比較器の2つの位相差出力の各々に
対する分圧回路を設け、これ等分圧回路の分圧比をわず
かに異なる様に設定しておく。これ等分圧出力を差動入
力ループフィルタへ供給してVCOの制御電圧とするこ
とで、不感帯を避けて、周波数位相比較器を安定動作さ
せるようにするものである。The voltage dividing circuit is provided for each of the two phase difference outputs of the frequency phase comparator, and the voltage dividing ratios of these voltage dividing circuits are set to be slightly different. By supplying this divided voltage output to the differential input loop filter and using it as the control voltage of the VCO, the dead zone is avoided and the frequency phase comparator is operated stably.
【0014】[0014]
【実施例】以下、図面を用いて本発明の実施例について
説明する。Embodiments of the present invention will be described below with reference to the drawings.
【0015】図1は本発明の実施例の回路図であり、図
4と同等部分は同一符号にて示されている。図1におい
て、図4と異なる部分について述べると、周波数位相比
較器1の2つの位相差出力Pd とPu とに夫々対応して
設けられ、これ等対応位相差出力を夫々分圧する分圧回
路5が設けられており、各分圧出力Pd ′とPu ′とは
平滑用コンデンサ6a,6bにより夫々平滑化されて差
動入力ループフィルタ2の差動入力となる。FIG. 1 is a circuit diagram of an embodiment of the present invention, and the same parts as those in FIG. 4 are designated by the same reference numerals. In FIG. 1, a portion different from FIG. 4 will be described. The voltage dividing circuit 5 is provided corresponding to each of the two phase difference outputs Pd and Pu of the frequency phase comparator 1, and divides the corresponding phase difference outputs respectively. Are provided, and the divided outputs Pd 'and Pu' are smoothed by smoothing capacitors 6a and 6b, respectively, and become the differential inputs of the differential input loop filter 2.
【0016】分圧回路5は抵抗分圧回路構成であり、位
相差出力Pd の信号ラインに直列に挿入された抵抗R1
と並列に挿入された抵抗Raとからなる。また、位相差
出力Pu の信号ラインに直列に挿入された抵抗R2と並
列に挿入された抵抗Rbとからなる。The voltage dividing circuit 5 has a resistance voltage dividing circuit configuration, and a resistor R1 is inserted in series with the signal line of the phase difference output Pd.
And a resistor Ra inserted in parallel therewith. Further, it comprises a resistor R2 inserted in series and a resistor Rb inserted in parallel to the signal line of the phase difference output Pu.
【0017】そして、抵抗R1とR2とは同一の抵抗値
Rとされ、抵抗RaとRbとは互いに若干異なる抵抗値
が夫々選定されているものとする。The resistors R1 and R2 have the same resistance value R, and the resistors Ra and Rb are selected to have slightly different resistance values.
【0018】他の構成は図4の回路のそれと同一であ
り、その説明は省略する。The other structure is the same as that of the circuit of FIG. 4, and the description thereof is omitted.
【0019】かかる構成において、上述した如くR1=
R2=Rであり、RaとRbとはわずかな差が設けられ
ているので、両分圧回路部分の分圧比はわずかな差があ
ることになる。In such a configuration, R1 =
Since R2 = R and there is a slight difference between Ra and Rb, there is a slight difference in the voltage division ratio of both voltage dividing circuit portions.
【0020】ここで、位相同期状態では、差動入力ルー
プフィルタ2の入力電圧Pd′とPu ′とは一致する様
に、位相帰還ループの作用により制御が働く。しかし、
2つの抵抗分圧比に差があることから、上記の如く分圧
後の電圧Pd ′とPu ′との差が等しくなるには、比較
器1の2つの出力信号Pd とPu との直流電圧に差が生
じている必要がある。Here, in the phase locked state, control is performed by the action of the phase feedback loop so that the input voltages Pd 'and Pu' of the differential input loop filter 2 match. But,
Since there is a difference between the two resistance voltage division ratios, in order to equalize the difference between the divided voltages Pd 'and Pu' as described above, there is a difference in the DC voltage between the two output signals Pd and Pu of the comparator 1. Must have happened.
【0021】図2は上述した位相同期状態での各部信号
の波形例を示しており、RaをRbよりやや大きめに設
定した場合の例である。この場合には、Pd ,Pd ′間
の分圧比Ra/(R+Ra)がPu ,Pu ′間の分圧比
Rb/(R+Rb)よりやや大となり、従って位相同期
状態では、Pd ′とPu ′との電圧が一致するために
は、Pd の直流成分がPu のそれに比し小さいことが必
要である。FIG. 2 shows an example of the waveform of each signal in the above-mentioned phase locked state, and is an example in the case where Ra is set slightly larger than Rb. In this case, the voltage division ratio Ra / (R + Ra) between Pd and Pd 'is slightly larger than the voltage division ratio Rb / (R + Rb) between Pu and Pu', and therefore in the phase locked state, Pd 'and Pu' In order for the voltages to match, the DC component of Pd must be smaller than that of Pu.
【0022】図2のPd とPu の波形は正にその状態を
示しており、結果的にfr とfp との間には定常位相差
φを有する状態で位相同期ループがロック(位相同期確
立)していることになる。The waveforms of Pd and Pu in FIG. 2 show exactly that state, and as a result, the phase-locked loop is locked (phase synchronization is established) with a steady phase difference φ between fr and fp. You are doing it.
【0023】このことは、取りも直さず図3に示す如く
入出力特性の不感帯を避けた直線部分において動作点を
定めたことに等しくなり、従って、不感帯外にて動作さ
せることが可能となって出力信号の位相変化に対して感
度が良くなり、位相雑音特性が良好となるのである。This is equivalent to setting the operating point in a straight line portion avoiding the dead zone of the input / output characteristic without repairing it, and therefore, it becomes possible to operate outside the dead zone. As a result, the sensitivity to the phase change of the output signal is improved, and the phase noise characteristic is improved.
【0024】[0024]
【発明の効果】この様に、本発明によれば、単に位相比
較器の出力に分圧回路を追加するのみの簡単な構成で、
差動入力ループフィルタを用いた形式の位相同期方式発
振回路に、位相比較器の不感帯を回避させて動作させる
回路を適用することができ、良好な位相雑音特性が得ら
れるという効果がある。As described above, according to the present invention, with a simple configuration in which a voltage divider circuit is simply added to the output of the phase comparator,
A circuit that operates by avoiding the dead zone of the phase comparator can be applied to the phase-locked oscillator circuit that uses the differential input loop filter, and an excellent phase noise characteristic can be obtained.
【図1】本発明の実施例の回路図である。FIG. 1 is a circuit diagram of an embodiment of the present invention.
【図2】本発明の実施例の回路の動作例を示す各部信号
波形図である。FIG. 2 is a signal waveform diagram of each part showing an operation example of the circuit of the embodiment of the present invention.
【図3】本発明の実施例回路の周波数位相比較器の動作
点を示す図である。FIG. 3 is a diagram showing operating points of the frequency phase comparator of the embodiment circuit of the present invention.
【図4】従来の位相同期回路の例を示す図である。FIG. 4 is a diagram showing an example of a conventional phase locked loop circuit.
【図5】図4の従来例の動作例を示す各部信号波形図で
ある。FIG. 5 is a signal waveform diagram of each part showing an operation example of the conventional example of FIG.
【図6】周波数位相比較器の入出力特性図である。FIG. 6 is an input / output characteristic diagram of the frequency phase comparator.
1 周波数位相比較器 2 差動入力フィルタ 3 VCO 4 分周回路 5 分圧回路 6a,6b 平滑化コンデンサ 1 frequency phase comparator 2 differential input filter 3 VCO 4 frequency divider circuit 5 voltage divider circuit 6a, 6b smoothing capacitor
Claims (3)
準入力信号との位相比較を行い前記基準信号に対して前
記発振信号が位相進み状態の時にこの位相進み量に応じ
た第1の位相差出力を生成し、位相遅れ状態の時にこの
位相遅れ量に応じた第2の位相差出力を生成する位相比
較手段と、前記第1及び第2の位相差出力に夫々対応し
て設けられ対応位相差出力を互いに異なる分圧比で夫々
分圧する第1及び第2の分圧手段と、前記第1及び第2
の分圧手段の両分圧出力を差動入力とし前記電圧制御発
振手段の制御電圧を生成するフィルタ手段とを含むこと
を特徴とする位相同期回路。1. A voltage-controlled oscillating means, and a phase comparison between the oscillated signal and a reference input signal, and when the oscillated signal is in a phase lead state with respect to the reference signal, a first position corresponding to the phase lead amount. Phase comparison means for generating a phase difference output and for generating a second phase difference output according to the phase delay amount when in the phase delay state, and provided corresponding to the first and second phase difference outputs, respectively. First and second voltage dividing means for dividing the phase difference output into different voltage division ratios, respectively, and the first and second voltage dividing means.
And a filter means for generating a control voltage of the voltage controlled oscillation means by using both voltage division outputs of the voltage division means as differential inputs.
の分圧手段の各分圧出力を夫々平滑化する平滑用コンデ
ンサと、これ等平滑出力を差動入力とする差動入力ルー
プフィルタとを有することを特徴とする請求項1記載の
位相同期回路。2. The filter means includes the first and second filters.
2. The phase-locked loop circuit according to claim 1, further comprising a smoothing capacitor for smoothing each divided output of the voltage dividing means, and a differential input loop filter using these smoothed outputs as differential inputs. .
差出力の信号ラインに直列挿入された第1の抵抗と、前
記第1の位相差出力の信号ラインに並列に挿入された第
2の抵抗とを有し、前記第2の分圧手段は、前記第2の
位相差出力の信号ラインに直列挿入された第3の抵抗
と、前記第2の位相差出力の信号ラインに並列に挿入さ
れた第4の抵抗とを有し、前記第1及び第3の抵抗は等
しい抵抗値を有し、前記第2及び第4の抵抗は互いに異
なる抵抗値を有するように設定されていることを特徴と
する請求項1または2記載の位相同期回路。3. The first voltage dividing means is inserted in parallel with a first resistor serially inserted in the signal line of the first phase difference output and a signal line of the first phase difference output. And a second resistor, the second voltage dividing means includes a third resistor serially inserted in the signal line of the second phase difference output, and the signal line of the second phase difference output. And a fourth resistor inserted in parallel with the first resistor, the first resistor and the third resistor having the same resistance value, and the second resistor and the fourth resistor having different resistance values. The phase locked loop circuit according to claim 1 or 2, wherein
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7085839A JPH08288838A (en) | 1995-04-12 | 1995-04-12 | Phase locked loop circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7085839A JPH08288838A (en) | 1995-04-12 | 1995-04-12 | Phase locked loop circuit |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH08288838A true JPH08288838A (en) | 1996-11-01 |
Family
ID=13870036
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP7085839A Pending JPH08288838A (en) | 1995-04-12 | 1995-04-12 | Phase locked loop circuit |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH08288838A (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2007274081A (en) * | 2006-03-30 | 2007-10-18 | Mitsubishi Electric Corp | Phase locked loop type frequency synthesizer |
JP2010226327A (en) * | 2009-03-23 | 2010-10-07 | Hioki Ee Corp | Phase-locked loop |
Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0477140A (en) * | 1990-07-17 | 1992-03-11 | Fujitsu Ltd | Phase locked loop circuit |
-
1995
- 1995-04-12 JP JP7085839A patent/JPH08288838A/en active Pending
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0477140A (en) * | 1990-07-17 | 1992-03-11 | Fujitsu Ltd | Phase locked loop circuit |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2007274081A (en) * | 2006-03-30 | 2007-10-18 | Mitsubishi Electric Corp | Phase locked loop type frequency synthesizer |
JP2010226327A (en) * | 2009-03-23 | 2010-10-07 | Hioki Ee Corp | Phase-locked loop |
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