JP6176547B2 - Non-contact power feeding device and starting method of non-contact power feeding device - Google Patents

Description

  The present invention relates to a contactless power supply device and a method for starting the contactless power supply device.

  Conventionally, various non-contact power feeding apparatuses that perform non-contact power feeding by mutual induction from the primary coil of the power feeding apparatus to the secondary coil of the power receiving apparatus have been proposed (for example, Patent Document 1). With the spread of electric vehicles, this type of contactless power supply apparatus has been increasingly attracting attention in recent years for application to electric vehicle contactless charging systems.

  By the way, when the non-contact power supply device is applied to an electric vehicle non-contact charging system, the power supply device is provided in the charging station and the power receiving device is mounted on the electric vehicle. Incidentally, the primary coil of the power feeding device is installed on the ground at the designated place of the charging station, and the secondary coil of the power receiving device is provided on the lower surface of the vehicle body, for example. As a result, when the electric vehicle stops at the designated place of the charging station, the primary coil and the secondary coil are opposed to each other, and the primary coil and the secondary coil are in contact with each other by non-contact power feeding from the power feeding device to the power receiving device. Is made. The induced electromotive force generated in the secondary coil is rectified and charged in a secondary battery such as a lithium battery of an electric vehicle.

JP 2003-204637 A

  By the way, when applied to an electric vehicle non-contact charging system, there is a large variation in the gap between the primary coil of the charging station and the secondary coil of the electric vehicle. In addition, it is difficult for the electric vehicle to stop at the designated location of the charging station accurately, and it stops at a position shifted from the designated location. Therefore, the relative position of the primary coil L1 and the secondary coil L2 for each electric vehicle to be charged. May be different.

  Therefore, when the relative position between the primary coil L1 and the secondary coil L2 changes each time, the leakage magnetic flux also changes and the coupling coefficient changes. The resonance characteristic (resonance frequency) of the power feeding device also varies each time due to the variation of the coupling coefficient. As a result, efficient non-contact power feeding of power was difficult.

  Further, when a high-frequency current having a driving frequency to be passed through the primary coil is generated in the high-frequency inverter by the fluctuation of the resonance characteristic (resonance frequency) of the power feeding device, the fast-advance mode in which the driving frequency is the resonance characteristic (resonance frequency). There is a risk of being located in the range. If this drive frequency is in the phase advance mode range of the resonance characteristics (resonance frequency) and the high-frequency inverter generates a high-frequency current, the switching element of the high-frequency inverter becomes hard switching and current loss increases, and the switching element is damaged. There was a problem that led to

  The present invention has been made in order to solve the above-described problem, and an object of the present invention is to generate a high-frequency current in the range of the slow-phase mode in which the drive frequency is a resonance characteristic even if the coupling coefficient varies. It is in providing the starting method of a contact electric power feeder and a non-contact electric power feeder.

One aspect of the present invention is a contactless power supply device, which includes an inverter, a primary coil, and a power supply side resonance circuit provided between the inverter and the primary coil; A power receiving device that includes a secondary coil that is magnetically coupled to a secondary coil and acquires energy from the primary coil, and that converts the energy acquired by the secondary coil to generate output power; and the inverter A mode determination circuit that determines whether the operation mode is a phase advance mode or a phase delay mode, and a control circuit that controls a resonance parameter of the power supply side resonance circuit so that the operation mode becomes a phase lag mode. The resonance characteristic in the coupled state of the primary coil and the secondary coil is a bimodal characteristic having two series resonance frequencies, and the power receiving device has a secondary current flowing through the power receiving device. A secondary current detecting device to detect, and a power receiving side communication circuit for transmitting information including a current value of a secondary current detected by the secondary current detecting device to the power feeding device, wherein the power feeding device includes the power receiving device A power supply side communication circuit that receives the information transmitted from the side communication circuit, and the control circuit is configured such that an operating frequency of the power supply device is close to a low series resonance frequency of the two series resonance frequencies. The resonance parameter of the power supply side resonance circuit is controlled to obtain a phase difference between the primary current and the secondary current based on the information supplied from the power supply side communication circuit, and the acquired primary current in accordance with the phase difference between said second current, that controls the resonance parameters of the power supply-side resonant circuit.
One aspect of the present invention is a contactless power supply device, which includes an inverter, a primary coil, and a power supply side resonance circuit provided between the inverter and the primary coil; A power receiving device that includes a secondary coil that is magnetically coupled to a secondary coil and acquires energy from the primary coil, and that converts the energy acquired by the secondary coil to generate output power; and the inverter A mode determination circuit that determines whether the operation mode is a phase advance mode or a phase delay mode, and a control circuit that controls a resonance parameter of the power supply side resonance circuit so that the operation mode becomes a phase lag mode. The resonance characteristic in the coupled state of the primary coil and the secondary coil is a bimodal characteristic having two series resonance frequencies, and the power receiving device has a secondary current flowing through the power receiving device. A secondary current detecting device to detect, and a power receiving side communication circuit for transmitting information including a current value of a secondary current detected by the secondary current detecting device to the power feeding device, wherein the power feeding device includes the power receiving device A power supply side communication circuit that receives the information transmitted from the side communication circuit, and the control circuit is configured such that an operating frequency of the power supply apparatus is close to a high series resonance frequency of the two series resonance frequencies. The resonance parameter of the power supply side resonance circuit is controlled to obtain a phase difference between the primary current and the secondary current based on the information supplied from the power supply side communication circuit, and the acquired primary current The resonance parameter of the power supply side resonance circuit is controlled in accordance with the phase difference between the current and the secondary current.

  In the above configuration, the mode determination circuit includes a primary current detection device that detects a primary current flowing in the power feeding device, and the mode determination circuit is configured to detect the primary current detected by the primary current detection device. Accordingly, it is preferable to determine whether the operation mode of the inverter is a phase advance mode or a phase delay mode.

  In the above configuration, the power feeding device includes a detection coil that is provided in the vicinity of the primary coil and detects a magnetic flux, and the control circuit includes the power feeding side resonance circuit according to the magnetic flux detected by the detection coil. It is preferable to control the resonance parameter.

  In the above configuration, it is preferable that the power supply side resonance circuit includes a variable capacitor connected in series to the primary coil, and the resonance parameter includes a capacitor capacity of the variable capacitor.

  In the above-described configuration, the variable capacitor includes a plurality of series circuits, each of the plurality of series circuits including the plurality of series circuits including a switching element and a capacitor connected in series. The circuits are preferably connected in parallel.

  In the above configuration, the variable capacitor preferably includes a series circuit including a bidirectional switching element and a capacitor connected in series, and a bidirectional switching element connected in parallel to the series circuit.

  In the above configuration, the variable capacitor preferably includes a parallel circuit including a bidirectional switching element and a capacitor connected in parallel, and a bidirectional switching element connected in series to the parallel circuit.

  In the above configuration, it is preferable that the power supply side resonance circuit includes a variable coil connected in series to the primary coil, and the resonance parameter includes an inductance of the variable coil.

  In the above configuration, the variable coil is a plurality of series circuits, and each of the plurality of series circuits includes the plurality of series circuits including a switching element and a coil connected in series, and the plurality of series circuits The series circuits are preferably connected in parallel.

  In the above configuration, the power feeding device includes a power feeding side communication circuit that transmits determination information by the mode determination circuit to the power receiving device, and the power receiving device includes a power receiving side resonance circuit connected in series to the secondary coil; A power-receiving-side communication circuit that receives determination information by the mode-determining circuit transmitted from the power-feeding-side communication circuit; and the power-receiving-side resonance according to the determination information by the mode-determining circuit that is supplied from the power-receiving-side communication circuit And a power receiving side control circuit for controlling a resonance parameter of the circuit.

  In the above configuration, it is preferable that the power receiving side resonance circuit includes a variable capacitor connected in series to the secondary coil, and the resonance parameter includes a capacitor capacity of the variable capacitor.

  In the above configuration, the variable capacitor is a plurality of series circuits, each of the plurality of series circuits including the plurality of series circuits including a switching element and a capacitor connected in series, and a plurality of series circuits. The circuits are preferably connected in parallel.

  In the above configuration, the variable capacitor preferably includes a series circuit including a bidirectional switching element and a capacitor connected in series, and a bidirectional switching element connected in parallel to the series circuit.

  In the above configuration, the variable capacitor preferably includes a parallel circuit including a bidirectional switching element and a capacitor connected in parallel, and a bidirectional switching element connected in series to the parallel circuit.

  In the above configuration, it is preferable that the power receiving side resonance circuit includes a variable coil connected in series to the secondary coil, and the resonance parameter includes an inductance of the variable coil.

  In the above configuration, the variable coil is a plurality of series circuits, and each of the plurality of series circuits includes the plurality of series circuits including a switching element and a coil connected in series, and the plurality of series circuits. The circuits are preferably connected in parallel.

  In the above configuration, the power reception device includes an output power detection circuit that detects the output power, and the power reception side control circuit is configured to output the power reception side resonance circuit based on the output power detected by the output power detection circuit. It is preferable to control the resonance parameters.

The said structure WHEREIN: It is preferable that the drive frequency of the said inverter does not change.
One aspect of the present invention, there is provided a method of starting the non-contact power feeding device configured as described above, by setting the resonance parameters of the feeding-side resonant circuits to a predetermined value, and starting the feeding device, said feeding device according to the start time elapses after, smaller than said predetermined value the resonance parameters of the power supply-side resonant circuit.

  According to the present invention, it is possible to generate a high-frequency current in a state where the drive frequency is in the range of the slow phase of the resonance characteristics.

The electric block diagram of the electric power feeder and power receiving device of a non-contact electric power feeder for demonstrating 1st Embodiment. The electric circuit diagram of the high frequency inverter of the electric power feeder for demonstrating 1st Embodiment. The electric circuit diagram of the electric power feeding side resonance circuit for demonstrating 1st Embodiment. (A) for explaining the first embodiment is a resonance characteristic diagram showing an output with respect to the frequency for explaining the phase advance mode and the phase lag mode, and (b) shows a state where the drive frequency is in the range of the phase advance mode. FIG. 4C is a diagram showing a state where the drive frequency is in the slow-phase mode range and is in an optimum position. The resonance characteristic figure which shows the output with respect to the frequency for demonstrating the phase advance mode and slow phase mode in the resonance characteristic of the bimodal characteristic for describing 1st Embodiment. The electric block diagram of the electric power feeder and power receiving device of a non-contact electric power feeder for demonstrating 2nd Embodiment. The electric circuit diagram of the receiving side resonance circuit for demonstrating 2nd Embodiment. The electric circuit diagram explaining another example of the electric power feeding side resonance circuit. The electric circuit diagram explaining another example of the electric power feeding side resonance circuit. The electric circuit diagram explaining another example of the electric power feeding side resonance circuit. The electric circuit diagram explaining another example of a receiving side resonance circuit.

(First embodiment)
Hereinafter, a non-contact power feeding apparatus according to a first embodiment embodying the present invention will be described with reference to the drawings.
FIG. 1 is an electric block circuit diagram for explaining the electrical configuration of the non-contact power feeding apparatus. In FIG. 1, the non-contact power feeding device includes a power feeding device 1 including a primary coil L <b> 1 and a power receiving device 2 including a secondary coil L <b> 2 that receives non-contact power feeding from the power feeding device 1.

(Power supply device 1)
As shown in FIG. 1, the power supply device 1 including the primary coil L1 includes a power supply circuit 10, a high-frequency inverter 11, a power supply side resonance circuit 12, a drive circuit 13, a primary current detection circuit 14, and a power supply side control unit 15. I have.

(Power supply circuit 10)
The power supply circuit 10 includes a rectifier circuit and a DC / DC converter. The power supply circuit 10 is supplied with AC power from an external commercial AC power supply G. The rectifier circuit rectifies the supplied AC power. The DC / DC converter converts the DC voltage supplied from the rectifier circuit into a desired voltage and outputs the DC voltage Vdd to the high frequency inverter 11 as drive power. Further, the power supply circuit 10 is configured to generate and supply an operating voltage to the drive circuit 13 and the power supply side control unit 15.

(High frequency inverter 11)
As shown in FIG. 2, the high-frequency inverter 11 is a known full bridge circuit, and has four MOS transistors Qa, Qb, Qc, and Qd. The four MOS transistors Qa, Qb, Qc, and Qd are MOS transistors Qa connected in a hanging manner with a primary circuit of the power feeding device 1 including a series circuit of the primary coil L1 and the power feeding side resonance circuit 12 interposed therebetween. , Qd and MOS transistors Qb, Qc. Then, by alternately turning on and off the two sets, a high-frequency current having a predetermined drive frequency fz that energizes the primary coil L1 is generated. The high frequency inverter 11 has an operation mode including a phase advance mode and a phase delay mode. For example, in the phase advance mode, the high frequency inverter 11 operates in a state where the drive frequency fz is located in a frequency region lower than the resonance frequency of the resonance characteristic in the coupled state between the primary coil L1 and the secondary coil L2. In the slow phase mode, the high frequency inverter 11 operates in a state where the drive frequency fz is located in a frequency region higher than the resonance frequency of the resonance characteristic in the coupled state between the primary coil L1 and the secondary coil L2. In addition, although the high frequency inverter 11 was comprised by the MOS transistor, you may comprise by IGBT and another transistor. A bidirectional switch may be used for the MOS transistor and the diode connected in antiparallel.

(Power feeding side resonance circuit 12)
As shown in FIG. 3, in the power supply side resonance circuit 12, bidirectional switching elements Q1 to Q5 are connected in series to five capacitors C1 to C5 having different capacities, and the five series circuits are connected in parallel. Connected to. In the power supply side resonance circuit 12, a reference capacitor C0 is connected in series to the parallel circuit. Although five series circuits of capacitors and switching elements are connected in parallel, the present invention is not limited, and a plurality of other series circuits may be connected in parallel. Further, the reference capacitor C0 may not be provided.

  Each of the switching elements Q1 to Q5 is configured to be on / off controlled based on selection control signals SLS1 to SLS5 from the power supply side control unit 15. When one of the switching elements Q1 to Q5 is turned on, a capacitor connected in series with the turned on switching element is connected in series with the primary coil L1 via the reference capacitor C0. That is, the power supply side resonance circuit 12 includes a variable capacitor connected in series to the primary coil L1. Thereby, the resonance characteristic F1 (resonance frequency fr) of the primary side circuit of the electric power feeder 1 can be adjusted.

  More specifically, the resonance characteristic F1 shown in FIG. 4A is changed in the arrow direction by changing the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 connected in series with the primary coil L1. (Resonance frequency fr) can be biased. In addition, in FIG. 4A, generally known phase advance mode regions and phase delay mode regions are described, but the boundaries are not limited to those illustrated.

(Drive circuit 13)
The drive circuit 13 receives the excitation control signal CTS from the power supply side control unit 15 and generates drive signals PSa, PSb, PSc, and PSd for outputting to the gate terminals of the MOS transistors Qa to Qd, respectively. That is, based on the excitation control signal CTS from the power supply side control unit 15, the drive circuit 13 generates drive signals PSa to PSd that alternately turn on and off each group.

  At this time, the drive circuit 13 generates drive signals PSa to PSd based on the excitation control signal CTS from the power supply side control unit 15 so that the primary coil L1 is excited and driven with a high-frequency current having a predetermined drive frequency fz. To do.

(Primary current detection circuit 14)
A primary current detection circuit 14 is provided between the power supply side resonance circuit 12 and the drive circuit 13. The primary current detection circuit 14 detects a primary current i that flows when one pair of MOS transistors Qa and Qd is turned off from on, and outputs the detected value of the primary current i to the power supply side control unit 15. To do.

(Power supply side control unit 15)
The power supply side control unit 15 includes a microcomputer and outputs an excitation control signal CTS to the drive circuit 13 so that the primary coil L1 is excited at a predetermined drive frequency fz.

Further, the power supply side control unit 15 receives the value of the primary current i detected by the primary current detection circuit 14 and determines whether or not it is operating in the slow phase mode.
That is, as shown in FIG. 4B, when operating in the phase advance mode, the MOS transistors Qa to Qd of the high-frequency inverter 11 are hard-switched. Hard switching increases current loss and damages the switching element. Therefore, we want to avoid operation in the phase advance mode range.

  On the other hand, as shown in FIG. 4A, hard switching of the MOS transistors Qa to Qd of the high-frequency inverter 11 is suppressed when operating in the slow phase mode. As a result, a problem like the phase advance mode does not occur.

Therefore, it is preferable to operate in the slow phase mode.
This determination can be made based on the value of the primary current i detected by the primary current detection circuit 14 when the MOS transistors Qa and Qd are turned off from on.

  That is, it can be seen that the operation in the phase advance mode is performed when the value of the primary current i detected by the primary current detection circuit 14 when the MOS transistors Qa and Qd are turned off is smaller than 0. It can also be seen that when the value of the primary current i is larger than 0, the operation in the slow phase mode is performed.

  Therefore, when the power supply side control unit 15 determines that the operation in the advanced phase mode is performed when the value of the primary current i is negative, the power supply side control unit 15 outputs selection control signals SLS1 to SLS5 to the power supply side resonance circuit 12. Change the capacitor capacity (resonance parameter). And the electric power feeding side control part 15 is controlling the electric power feeding side resonance circuit 12 so that the resonance characteristic F1 (resonance frequency fr) at that time may be deviated.

  In addition, when it is determined that the power supply side control unit 15 is operating in the slow phase mode, the power supply side is within the range in the slow phase mode as shown in FIG. The capacitor capacity (resonance parameter) of the resonance circuit 12 is adjusted by the same method to adjust the resonance characteristic F1.

(Power receiving device 2)
Next, the power receiving device 2 including the secondary coil L2 will be described. In the power receiving device 2, the secondary coil L2 is linked to an alternating magnetic field generated based on the excitation drive of the primary coil L1 of the power feeding device 1, and an induced electromotive force induced in the secondary coil L2 by mutual induction is generated. The power is received and converted into a direct current, supplied to the secondary battery 20 as a load, and the secondary battery 20 is charged.

As illustrated in FIG. 1, the power receiving device 2 includes a secondary battery 20, a power receiving resonance circuit 21, a rectifier circuit 22, and a smoothing circuit 23.
Note that the power feeding means to the secondary coil L2 is not limited to the electromagnetic induction method by mutual induction, but may be another method such as a magnetic resonance method using a resonance phenomenon.

(Receiving side resonance circuit 21)
The power receiving device 2 includes a power receiving resonance circuit 21 connected in series with the secondary coil L2. In the first embodiment, the power reception side resonance circuit 21 includes a resonance capacitor Cx and is connected in series with the secondary coil L2 to configure a secondary circuit of the power reception device 2.

(Rectifier circuit 22)
The power receiving device 2 includes a rectifier circuit 22 and is connected to a secondary side circuit including a series circuit of a secondary coil L2 and a resonance capacitor Cx. The rectifier circuit 22 performs full-wave rectification on the induced electromotive force induced in the secondary coil L2 by mutual induction by excitation of the primary coil L1 of the power feeding apparatus 1, and outputs the rectified circuit to a smoothing circuit 23 including a capacitor provided in the next stage. And convert it to a DC power supply without ripples. Then, the DC power source without ripple is supplied to the secondary battery 20.

(Secondary battery 20)
For example, the secondary battery 20 is a secondary battery such as a lithium battery. The secondary battery 20 is charged by the above-described DC power source without ripples.

Next, the operation of the non-contact power feeding device configured as described above will be described.
In the description of the operation, the non-contact power supply device will be described specifically as an electric vehicle non-contact charging system in which the power supply device 1 is provided in the charging station and the power receiving device 2 is mounted on the electric vehicle.

  Therefore, the primary coil L1 of the power feeding device 1 provided in the charging station is assumed to be installed on the ground of a designated place where the electric vehicle receives power. On the other hand, the secondary coil L2 of the power receiving device 2 mounted on the electric vehicle is provided on the lower surface of the vehicle body, for example, and is positioned above the primary coil L1 when the electric vehicle is stopped at a designated place of the charging station. It is assumed that it is opposite to the next coil L1.

  Now, when the electric vehicle is stopped at the designated place of the charging station and the power feeding by the power feeding device 1 provided in the charging station is started, the power feeding side control unit 15 excites the primary coil L1 at a predetermined driving frequency fz. As described above, the excitation control signal CTS is output to the drive circuit 13. The drive circuit 13 outputs drive signals PSa to PSd to the high frequency inverter 11 in response to the excitation control signal CTS. The high frequency inverter 11 generates a high frequency current having a predetermined drive frequency fz in response to the drive signals PSa to PSd, and energizes the primary coil L1 with the generated high frequency current. When the primary coil L1 is energized with a high-frequency current having a drive frequency fz, the primary coil L1 generates an alternating magnetic field having the drive frequency fz.

  The secondary coil L2 located above the primary coil L1 induces an induced electromotive force having a drive frequency fz by the action of mutual induction. The rectifier circuit 22 of the power receiving device 2 rectifies the induced electromotive force induced in the secondary coil L2, and the smoothing circuit 23 smoothes the DC voltage supplied from the rectifier circuit 22. As a result, the smoothed DC voltage is supplied to the secondary battery 20. Thereby, the secondary battery 20 of the electric vehicle is charged.

  On the other hand, from the start of the power feeding operation, the primary current detection circuit 14 of the power feeding apparatus 1 detects the primary current i when the MOS transistors Qa and Qd flowing through the primary coil L1 are turned off from the on-state and detects the primary current i. The value of the primary current i as a signal is output to the power supply side control unit 15.

  When the electric vehicle cannot be stopped at the designated place but is shifted and stopped, the leakage magnetic flux between the primary coil L1 and the secondary coil L2 varies and the coupling coefficient varies. In this case, the resonance characteristic F1 varies.

  For this reason, the power supply side control unit 15 determines whether the predetermined drive frequency fz is in the phase advance mode range, the phase delay mode range, or the delay mode based on the value of the primary current i. If it is in the range of the phase mode, it is determined whether there is an optimum position.

  Then, the power supply side control unit 15 outputs the selection control signals SLS1 to SLS5 to the power supply side resonance circuit 12 so that the predetermined drive frequency fz is located in the range of the slow phase mode, thereby reducing the capacitor capacitance. change. As the capacitance of the capacitor is reduced, the resonance characteristic F1 (resonance frequency fr) is biased in the direction of lowering, and the predetermined drive frequency fz is positioned in the slow phase range. Here, based on the value of the primary current i, the power supply side control unit 15 determines whether the operating frequency of the power supply device 1 is in the phase advance mode range, the phase delay mode range, When it is in the range of the slow phase mode, it may be determined whether there is an optimum position. The power supply side control unit 15 outputs the selection control signals SLS1 to SLS5 to the power supply side resonance circuit 12 so that the operating frequency of the power supply device 1 is in the range of the slow phase mode, and changes the capacitor capacitance to a small value. May be.

  In addition, when the predetermined drive frequency fz is in the slow-phase mode range and is not in the optimum position, the power feeding side control unit 15 determines that the predetermined drive frequency fz is in the slow-phase mode range. The power supply side resonance circuit 12 is controlled so as to be in an optimum position. That is, the power supply side control unit 15 finely adjusts the capacitor capacity (resonance parameter) by outputting the selection control signals SLS1 to SLS5 to the power supply side resonance circuit 12. By finely adjusting the capacitance of the capacitor, the frequency characteristic (resonance frequency) is finely moved in the direction of increasing or decreasing, and the predetermined driving frequency fz converges to the optimum position within the slow phase range. As a result, the MOS transistors Qa to Qd of the high-frequency inverter 11 quickly shift to an optimum state in which operation is performed in the slow phase mode and high output is obtained.

  Further, when the predetermined drive frequency fz is within the range of the slow mode and is in the optimum position, the power supply side control unit 15 maintains the resonance characteristic F1 (resonance frequency fr) at that time. The power supply side control unit 15 maintains the capacitor capacity at that time without outputting the selection control signals SLS1 to SLS5 for adjustment to the power supply side resonance circuit 12.

In other words, the MOS transistors Qa to Qd of the high-frequency inverter 11 generate a high-frequency current having a predetermined drive frequency fz while maintaining a state in which a high output is obtained in the slow phase mode.
In particular, in the case of an electric vehicle non-contact charging system, it is difficult for the electric vehicle to accurately stop at a specified location of the charging station, and there is a possibility that the electric vehicle always stops at a position shifted from the specified location. In other words, the relative position of the primary coil L1 and the secondary coil L2 may be different each time the electric vehicle is charged. Therefore, depending on the relative position of the primary coil L1 and the secondary coil L2, the leakage magnetic flux is different and the coupling coefficient is also changed. The resonance characteristic F1 (resonance frequency fr) of the power feeding device 1 also varies due to the variation of the coupling coefficient.

  However, even if the resonance characteristic F1 fluctuates every time the electric vehicle is charged, the power supply side control unit 15 controls the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 and adjusts the resonance characteristic F1 (resonance frequency fr). To do. Therefore, the power feeding side control unit 15 can control the predetermined drive frequency fz of the high-frequency inverter 11 so as to be located in the range of the slow phase mode.

  Therefore, when embodied in an electric vehicle non-contact charging system, current loss can be prevented and the switching element can be prevented from being damaged, and stable in a lagging mode without changing the driving frequency fz. It can be realized to operate.

  Incidentally, when the electric vehicle non-contact charging system is started, the power supply side control unit 15 starts the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 with a large value as an initial value. Then, the power supply side control unit 15 gradually decreases the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12. As a result, a soft start operation for gradually increasing the output can be realized.

  By controlling the resonance parameter as described above, the drive frequency fz can be positioned in the slow phase range. That is, stable operation of the electric vehicle non-contact charging system can be realized without changing the driving frequency fz.

By the way, in the case of a non-contact power supply device such as an electric vehicle non-contact charging system, it is conceivable that the coupling coefficient between the primary coil L1 and the secondary coil L2 is small.
When the coupling coefficient is small, the resonance characteristic F1 shown in FIG. 4 becomes the resonance characteristic F2 shown in FIG. In other words, the resonance characteristic F1 shown in FIG. 4 has a single peak, whereas the resonance characteristic F2 when the coupling coefficient shown in FIG. 5 is small has two series resonance points (peaks) and one parallel resonance point ( Valley), that is, it has bimodality.

In the resonance characteristic F1 having a single peak characteristic shown in FIG. 4, since there is a single resonance frequency fr, there is a single fast mode range and a single slow mode range.
On the other hand, the bimodal resonance characteristic F2 shown in FIG. 5 has two series resonance frequencies fr1 and fr2, and therefore generally has two fast-phase modes and two slow-modes. It has been said. However, the boundary between the phase advance mode and the phase delay mode is not limited to the illustrated one.

  Thus, in the case of an electric vehicle non-contact charging system with a small coupling coefficient, it is necessary to assume the bimodal resonance characteristic F2 shown in FIG. In other words, there are a phase advance mode range and a slow mode range with the lower series resonance frequency fr1 as a boundary, and a phase advance mode range and a slow mode range with the higher series resonance frequency fr2 as a boundary. A range exists.

In this case, there is the following method as one method for positioning the drive frequency fz in the range of any one of the slow phase modes.
For example, the secondary current detection device detects a secondary current flowing through the power receiving device 2, and the power receiving side communication circuit transmits the information to the power feeding side communication circuit of the power feeding device 1. The power supply side control unit 15 acquires the phase difference between the primary current and the secondary current based on the information received by the power supply side communication circuit, and is driven according to the acquired phase difference between the primary current and the secondary current. Whether the frequency fz is located in the vicinity of the lower series resonance frequency fr1 or the higher series resonance frequency fr2 can be determined. The power supply side control part 15 should just change the capacitor | condenser capacity (resonance parameter) of the power supply side resonance circuit 12 based on the information.

  For example, a magnetic detection coil is provided in the vicinity of the primary coil. Then, depending on the magnetic flux of the primary coil L1 of the power feeding device 1 detected by the magnetic detection coil, the power feeding side control unit 15 is positioned in the vicinity of the lower series resonance frequency fr1 with the lower driving frequency fz. It is also possible to determine whether it is in the vicinity of the series resonance frequency fr2. Based on the information, the power supply side control unit 15 can change the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 to position the drive frequency fz in one of the slow-phase modes.

  That is, the power supply control circuit 15 controls the resonance parameter of the power supply side resonance circuit 12 so that the drive frequency of the high frequency inverter 11 is located at a frequency close to the low series resonance frequency of the two series resonance frequencies. On the other hand, the power supply control circuit 15 controls the resonance parameter of the power supply side resonance circuit 12 so that the drive frequency of the high frequency inverter 1 is located at a frequency close to a higher frequency of the two series resonance frequencies.

  When the switching operation is performed with the drive frequency fz positioned in the slow mode range of the lower series resonance frequency fr1, the drive frequency fz is positioned in the slow mode range of the higher series resonance frequency fr2. Compared to switching operation, noise reduction is excellent.

Next, the effect of 1st Embodiment comprised as mentioned above is described below.
(1) According to the first embodiment, the power feeding device 1 can control the capacitor capacity (resonance parameter) of the power feeding side resonance circuit 12 by the selection control signals SLS1 to SLS5 from the power feeding side control unit 15. In the power supply device 1, the power supply side control unit 15 controls the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12. Thus, the resonance characteristic F1 (F2) is biased, and the predetermined drive frequency fz that is driven by the high-frequency inverter 11 is controlled so as to be located in the range of the slow phase mode.

  Therefore, the power feeding apparatus 1 can drive the high-frequency inverter 11 so that the predetermined drive frequency fz is located in the range of the slow-phase mode, and the MOS transistors Qa, Qb, Qc, Qd constituting the high-frequency inverter 11 are driven. Hard switching can be avoided. As a result, current loss can be prevented and damage to the switching element can be prevented.

  (2) According to the first embodiment, when the resonance characteristic of the power feeding device 1 fluctuates every time the usage conditions change, as in an electric vehicle non-contact charging system, a predetermined driving frequency of the high-frequency inverter 11 fz can be controlled to be in the range of the slow phase mode.

  (3) According to the first embodiment, the power supply side resonance circuit 12 connects a plurality of capacitors C1 to C5 in parallel, and appropriately turns on the switching elements Q1 to Q5, whereby a plurality of capacitor capacities (resonance parameters). ) Can be set. For this reason, the predetermined drive frequency fz can be set to an optimum position within the slow phase range and high output can be obtained.

  (4) According to the first embodiment, when the power supply device 1 is started, the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 is started with a large value, and the capacitor capacity is gradually decreased. I made it. This enables a soft start operation that gradually increases the output.

(Second Embodiment)
A non-contact power feeding apparatus according to the second embodiment will be described.
The second embodiment is characterized in that, in addition to controlling the resonance parameter of the power supply side resonance circuit 12 of the first embodiment, the resonance parameter of the power reception side resonance circuit 21 provided in the power receiving device 2 is controlled.

Further, the second embodiment is characterized in that data can be exchanged between the power feeding device 1 and the power receiving device 2 by wireless communication.
Therefore, in the second embodiment, portions common to the first embodiment are omitted for convenience of explanation, and different characteristic portions will be described in detail.

(Power supply device 1)
As shown in FIG. 6, the power feeding apparatus 1 includes a power feeding side communication circuit 17 and a power feeding side antenna AT1.

(Power supply side communication circuit 17)
The power feeding side communication circuit 17 sends mode determination information indicating whether the drive frequency fz determined by the power feeding side control unit 15 is in the fast phase range or the slow phase mode via the power feeding antenna AT1. It transmits to the power receiving apparatus 2.

(Power receiving device 2)
The power receiving device 2 includes a power receiving side resonance circuit 21 having a resonance parameter that can be adjusted unlike the power receiving side resonance circuit 21 of the first embodiment.

The power receiving apparatus 2 includes a power receiving side communication circuit 24, a power receiving side control unit 25, a power receiving side antenna AT2, and an output power detection circuit 26.
(Receiving side resonance circuit 21)
As shown in FIG. 7, in the power receiving side resonance circuit 21 of the second embodiment, bidirectional switching elements Qx1 to Qx5 are connected in series to five capacitors Cx1 to Cx5 having different capacities, respectively. Are connected in parallel. In the power receiving side resonance circuit 21, a reference capacitor Cx0 is connected in series with the parallel circuit. In addition, although the five series circuits of the capacitor and the switching element are connected in parallel, the present invention is not limited, and a plurality of other series circuits may be connected in parallel. Further, the reference capacitor Cx0 may not be provided.

  The switching elements Qx1 to Qx5 are on / off controlled based on selection control signals SLSx1 to SLSx5 from the power receiving side control unit 25. When one of the switching elements Qx1 to Qx5 is turned on, the capacitor connected in series with the turned on switching element is connected in series with the secondary coil L2 via the reference capacitor Cx0.

  That is, the power reception side resonance circuit 21 includes a variable capacitor connected in series to the secondary coil L2. The power receiving side control unit 25 changes the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21 connected in series with the secondary coil L2. Thereby, the power receiving side control unit 25 can adjust the resonance characteristic (resonance frequency) of the secondary side circuit of the power receiving apparatus 2 and also bias the resonance characteristic F1 (F2) of the primary circuit of the power feeding apparatus 1. .

(Power-receiving-side communication circuit 24)
The power reception side communication circuit 24 receives the mode determination information of the power supply side control unit 15 transmitted from the power supply side communication circuit 17 of the power supply apparatus 1 via the power reception side antenna AT2. Then, the power receiving side communication circuit 24 outputs the received mode determination information to the power receiving side control unit 25.

(Power-receiving-side control unit 25)
The power receiving side control unit 25 includes a microcomputer and generates selection control signals SLSx1 to SLSx5 for controlling the resonance parameters of the power receiving side resonance circuit 21 based on the mode determination information from the power receiving side communication circuit 24. To the side resonance circuit 21.

  That is, the power receiving side control unit 25 controls the resonance parameter of the power receiving side resonance circuit 21, thereby biasing the resonance characteristic F1 (F2) of the power feeding device 1, and setting the predetermined drive frequency fz that the high frequency inverter 11 drives. Control to be in the range of the slow phase mode.

(Output power detection circuit 26)
The output power detection circuit 26 is provided between the smoothing circuit 23 and the secondary battery 20 and detects the output power P at that time supplied to the secondary battery 20. The output power detection circuit 26 outputs a detection signal of the detected output power P to the power receiving side control unit 25.

  The power receiving side control unit 25 determines a case where the output power P at that time from the output power detection circuit 26 is larger than a predetermined reference value or smaller than a predetermined reference value. Then, when the output power P is larger than the reference value or smaller than the reference value, the power receiving side control unit 25 sets the capacitor capacity of the power receiving side resonance circuit 21 so that the output power P is within the reference value. (Resonance parameter) is controlled. That is, the power receiving side control unit 25 is configured to generate selection control signals SLSx1 to SLSx5 for adjusting the output power P to be within a reference value and output the selection control signals SLSx1 to SLSx5 to the power receiving side resonance circuit 21.

Next, the operation of the non-contact power feeding device configured as described above will be described.
In addition to the operation of the first embodiment, the primary coil L1 of the power feeding device 1 is energized, and induced electromotive force is induced in the secondary coil L2 of the power receiving device 2 by mutual induction.

The power receiving side communication circuit 24 receives the mode determination information at that time. The power receiving side control unit 25 controls the capacitor capacity of the power receiving side resonance circuit 21 based on the mode determination information.
That is, when the mode determination information is the phase advance mode, the power reception side control unit 25 sets the capacitor capacity of the power reception side resonance circuit 21 so that the predetermined drive frequency fz driven by the high frequency inverter 11 falls within the range of the slow phase mode. Adjust.

  When the mode determination information is the slow phase mode, the power receiving side control unit 25 sets the predetermined drive frequency fz that is driven by the high frequency inverter 11 to the optimum position within the range of the slow phase mode. The capacitor capacity of the resonance circuit 21 is adjusted.

Furthermore, when the mode determination information is the slow phase mode and the optimum position, the power receiving side control unit 25 maintains the capacitor capacity of the power receiving side resonance circuit 21 in that state.
Therefore, in order to set the predetermined drive frequency fz to the optimum position within the range of the slow phase mode, the capacitor capacities (resonance parameters) of both the power supply side resonance circuit 12 and the power reception side resonance circuit 21 can be adjusted simultaneously. . As a result, the predetermined drive frequency fz is controlled to an optimum position in the slow phase range.

The second embodiment has the following effects in addition to the first embodiment.
(1) According to the second embodiment, the power receiving device 2 can control the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21 with the selection control signals SLSx1 to SLSx5 from the power receiving side control unit 25. Based on the mode determination information, the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21 is varied.

  Therefore, the power reception side resonance circuit 21 cooperates with the power supply side resonance circuit 12, that is, the power supply side control unit 15 and the power reception side control unit 25 have the capacitor capacities of both the power supply side resonance circuit 12 and the power reception side resonance circuit 21. (Resonance parameter) can be adjusted simultaneously, and the predetermined drive frequency fz is controlled earlier by an optimum position within the range of the slow phase mode.

  (2) According to the second embodiment, the output power P supplied to the secondary battery 20 detected by the output power detection circuit 26 is larger than a predetermined reference value or smaller than a predetermined reference value. In this case, the power reception side control unit 25 controls the capacitor capacity of the power reception side resonance circuit 21. Then, the output power P can be converged within the reference value. Therefore, the secondary battery 20 can be charged in a stable state.

The first and second embodiments may be modified as follows.
In each of the above embodiments, when controlling the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12, one of the plurality of capacitors C1 to C5 is selected. On the other hand, the power supply side control unit 15 may select a plurality of capacitors at the same time and control the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12.

  In each of the above embodiments, the capacitors C1 to C5 of the power supply side resonance circuit 12 have different capacitor capacities, but may have the same value. In this case, the power supply side control unit 15 outputs selection control signals SLS1 to SLS5 to the power supply side resonance circuit 12 so that a plurality of capacitors can be simultaneously selected and the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 can be controlled. You may make it do.

In each of the above embodiments, the power supply side resonance circuit 12 is configured by connecting a plurality of capacitors C1 to C5 in parallel and connecting the parallel circuit in series to the reference capacitor C0.
As shown in FIG. 8, in the power supply side resonance circuit 12, a plurality of resonance coils Lr1 to Lr5 are connected in parallel, and a reference capacitor C0 is connected in series to the parallel circuit. That is, the power supply side resonance circuit 12 includes a variable coil connected in series with the primary coil L1. The power supply side control unit 15 appropriately turns on / off the switching elements Q1 to Q5 to adjust the inductance (resonance parameter) of the power supply side resonance circuit 12 so that the predetermined drive frequency fz is positioned in the slow phase mode. You may control.

Of course, also in this case, the power supply side control unit 15 may select a plurality of coils at the same time and control the inductance (resonance parameter) of the power supply side resonance circuit 12.
Furthermore, you may set the some coils Lr1-Lr5 to the inductance of the same value. In this case, the power supply side control unit 15 may select a plurality of coils simultaneously and control the inductance (resonance parameter) of the power supply side resonance circuit 12.

The power supply side resonance circuit 12 of each of the above embodiments may be configured by a series circuit of a capacitor and a coil.
○ The range of the slow mode in the frequency range of the high series resonance frequency of the two series resonance frequencies of the resonance characteristic F2 having the bimodal resonance characteristic (drive frequency fz) (the resonance frequency shown in FIG. 5). In the slow phase mode corresponding to fr2, the phase of the current flowing through the primary coil L1 and the phase of the current flowing through the secondary coil L2 are in phase. On the other hand, the operating frequency (driving frequency fz) of the power feeding device is the range of the slow mode (resonance shown in FIG. 5) in the frequency range of the low series resonance frequency of the two series resonance frequencies of the resonance characteristic F2 having bimodality. In the slow phase mode corresponding to the frequency fr1, the phase of the current flowing through the primary coil L1 is opposite to the phase of the current flowing through the secondary coil L2. For this reason, when the phase of the current flowing through the primary coil L1 and the phase of the current flowing through the secondary coil L2 are opposite to each other, unnecessary radiation radiated from the power supply device 1 to the surroundings is a current flowing through the primary coil L1. And the phase of the current flowing through the secondary coil L2 are suppressed as compared with the case where the phase of

  Here, the primary coil L1 and the secondary coil L2 of each embodiment may include a solenoid type coil or a spiral type coil. Solenoid type coils tend to generate greater noise than spiral type coils. For this reason, when the primary coil L1 and the secondary coil L2 include solenoid type coils, the power supply side control unit 15 determines that the operating frequency of the power supply device is the lower series of the two series resonance frequencies of the resonance characteristic F2 at that time. It is preferable to control the power supply side resonance circuit 12 so that it is in the range of the slow mode in the frequency region of the resonance frequency. Thereby, the unnecessary radiation radiated | emitted from the electric power feeder 1 to the circumference | surroundings can be reduced. On the other hand, when the primary coil L1 and the secondary coil L2 include spiral type coils, when the level of unwanted radiation falls within the design allowable range, the power supply side control unit 15 causes the operating frequency of the power supply device to resonate at that time. It is preferable to control the power supply side resonance circuit 12 so that it is in the range of the slow phase in the frequency range of the high series resonance frequency of the two series resonance frequencies of the characteristic F2. Thereby, control by the electric power feeding side control part 15 becomes easier than control in the case of using a solenoid type coil. Specifically, in the case of using a solenoid type coil, the power supply side control unit 15 has a low series of the two series resonance frequencies of the resonance characteristic F2 at that time in a frequency region where the upper limit frequency and the lower limit frequency are limited. The range of the slow mode in the frequency region of the resonance frequency is specified. For this reason, control by the electric power feeding side control part 15 becomes complicated. On the other hand, when a spiral type coil is used, the power supply side control unit 15 has a frequency range in which only the lower limit frequency is limited, and the frequency range of the higher series resonance frequency of the two series resonance frequencies of the resonance characteristic F2 at that time. Specifies the range of the slow mode at. In this case, the power supply side control unit 15 only has to lower the frequency from a frequency range higher than the range of the slow phase mode to a desired power, and the control by the power supply side control unit 15 is a control when a solenoid type coil is used. Easier than that.

As shown in FIG. 9 or FIG. 10, the power supply side resonance circuit 12 of each of the above embodiments may be composed of one capacitor Cz and two first and second bidirectional switches Qz1 and Qz2.
Here, the first and second bidirectional switches Qz1 and Qz2 are GaN (gallium nitride) having a double gate composed of first gate terminals G1-1 and G2-1 and second gate terminals G1-2 and G2-2. ) Bidirectional switch device.

  Incidentally, the first bidirectional switch Qz1 (second bidirectional switch Qz2) has four modes according to on / off signals supplied to the first gate terminal G1-1 and the second gate terminal G1-2.

  In the first mode, in the first bidirectional switch Qz1 (second bidirectional switch Qz2), an ON signal is supplied to the first gate terminal G1-1 and an OFF signal is supplied to the second gate terminal G1-2, so that the high-frequency inverter 11 Is a mode in which conduction from the coil to the primary coil L1 is possible.

  In the second mode, in the first bidirectional switch Qz1 (second bidirectional switch Qz2), when an off signal is supplied to the first gate terminal G1-1 and an on signal is supplied to the second gate terminal G1-2, In this mode, conduction from the next coil L1 to the high-frequency inverter 11 is possible.

  In the third mode, when the ON signal is supplied to both the first and second gate terminals G1-1 and G1-2 in the first bidirectional switch Qz1 (second bidirectional switch Qz2), the primary coil L1 In this mode, electrical conduction in both directions is possible with the high-frequency inverter 11.

  In the fourth mode, when the OFF signal is supplied to the first and second gate terminals G1-1 and G1-2 in the first bidirectional switch Qz1 (second bidirectional switch Qz2), the primary coil L1 In this mode, the connection with the high-frequency inverter 11 is interrupted.

  The power feeding side resonance circuit 12 shown in FIG. 9 is a resonance circuit in which a capacitor Cz and a first bidirectional switch Qz1 are connected in series, and a second bidirectional switch Qz2 is connected in parallel to the series circuit.

  10 is a resonance circuit in which a capacitor Cz and a first bidirectional switch Qz1 are connected in parallel, and a second bidirectional switch Qz2 is connected in series to the parallel circuit. .

The power supply side resonance circuit 12 shown in FIGS. 9 and 10 is operated as follows.
First, the first bidirectional switch Qz1 is turned off in the fourth mode when an off signal is output to both the first and second gate terminals G1-1 and G1-2. On the other hand, the second bidirectional switch Qz2 is turned on in the third mode when an ON signal is output to both the first and second gate terminals G2-1 and G2-2. As a result, both terminals of the power supply side resonance circuit 12 are short-circuited.

  Next, the second bidirectional switch Qz2 is in the fourth mode when the off signal is output to the first and second gate terminals G2-1 and G2-2 and maintains the off state. On the other hand, the first bidirectional switch Qz1 is in a state in which an ON signal is output from the OFF signal to the first gate terminal G1-1 to enter the first mode and the conduction from the high-frequency inverter 11 to the primary coil L1 is possible. . As a result, the capacitor Cz starts charging.

  When the predetermined charging time has elapsed, the second bidirectional switch Qz2 enters the fourth mode with the off signal being output to both the first and second gate terminals G2-1 and G2-2, and is in the off state. To maintain. On the other hand, the first bidirectional switch Qz1 outputs the ON signal from the ON signal to the first gate terminal G1-1, and outputs the ON signal from the OFF signal to the second gate terminal G1-2. Thus, conduction from the primary coil L1 to the high-frequency inverter 11 is possible. As a result, the capacitor Cz starts discharging.

  When a predetermined discharge time elapses, the first bidirectional switch Qz1 outputs an ON signal to both the first and second gate terminals G1-1 and G1-2, enters the third mode, and enters a short-circuit state. Become. On the other hand, the second bidirectional switch Qz2 is in a short-circuited state when the ON signal is output to both the first and second gate terminals G2-1 and G2-2 to enter the third mode.

As a result, the first and second bidirectional switches Qz1 and Qz2 become fully conductive, and the residual charge in the capacitor Cz is discharged.
The above operation is performed once or a plurality of times during one cycle of a high-frequency current having a predetermined drive frequency fz, and the charge / discharge time is controlled, so that the apparent capacity of the capacitor Cz, that is, FIG. The capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 shown in FIG. 10 can be varied.

The power supply side resonance circuit 12 of each of the above embodiments may be composed of one reference capacitor C0 and two first and second switching elements Qx1 and Qx2.
That is, as shown in FIG. 9, the power supply side resonance circuit 12 may be implemented by connecting the reference capacitor C0 and the first switching element Qx1 in series and connecting the second switching element Qx2 in parallel to the series circuit. Good.

  In addition, as shown in FIG. 10, the reference capacitor C0 and the first switching element Qx1 are connected in parallel, and the second switching element Qx2 is connected in series to the parallel circuit. Also good.

  In the second embodiment, when controlling the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21, one of the plurality of capacitors Cx1 to Cx5 is selected. This may be performed so that the power reception side control unit 25 can simultaneously select a plurality of capacitors and control the capacitor capacity (resonance parameter) of the power reception side resonance circuit 21.

  In the second embodiment, the capacitors Cx1 to Cx5 of the power receiving resonance circuit 21 have different capacitor capacities, but may have the same value. In this case, the power receiving side control unit 25 outputs selection control signals SLSx1 to SLSx5 to the power receiving side resonance circuit 21 so that a plurality of capacitors can be selected simultaneously and the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21 can be controlled. Implement as follows.

In the second embodiment, the power receiving side resonance circuit 21 is configured by connecting a plurality of capacitors Cx1 to Cx5 in parallel and connecting the parallel circuit in series to the reference capacitor Cx0.
As shown in FIG. 11, the power receiving-side resonance circuit 21 may be configured by connecting a plurality of resonance coils Lx1 to Lx5 in parallel, and a resonance capacitor Cx in series with the parallel circuit. That is, the power reception side resonance circuit 21 includes a variable coil connected in series to the secondary coil L2. The power reception side control unit 25 may adjust the inductance (resonance parameter) of the power reception side resonance circuit 21 by appropriately turning on / off the switching elements Qx1 to Qx5.

Of course, in this case as well, the power receiving side control unit 25 may simultaneously select a plurality of coils and control the inductance (resonance parameter) of the power receiving side resonance circuit 21.
Furthermore, you may set the some coils Lx1-Lx5 to the inductance of the same value. In this case, the power receiving side control unit 25 may simultaneously select a plurality of coils and control the inductance (resonance parameter) of the power receiving side resonance circuit 21.

The power receiving side resonance circuit 21 of the second embodiment may be configured by a series circuit of a capacitor and a coil.
Further, the power-receiving-side resonance circuit 21 may be configured as shown in FIG. 9 or FIG. 10, and the capacitor capacity (resonance parameter) of the power-receiving-side resonance circuit 21 may be adjusted.

  In the second embodiment, the capacitor capacities (resonance parameters) of both the power supply side resonance circuit 12 and the power reception side resonance circuit 21 are adjusted so that the predetermined drive frequency fz is in the slow phase range. I made it. However, the control of the capacitor capacity (resonance parameter) of the power supply side resonance circuit 12 may be omitted. That is, only the capacitor capacity (resonance parameter) of the power receiving side resonance circuit 21 may be controlled so that the predetermined drive frequency fz is positioned in the slow phase mode.

Claims (20)

A non-contact power feeding device,
A power feeding device including an inverter, a primary coil, and a power feeding side resonance circuit provided between the inverter and the primary coil;
A power receiving device that includes a secondary coil that is magnetically coupled to the primary coil and obtains energy from the primary coil, and converts the energy obtained by the secondary coil to generate output power.
A mode determination circuit for determining whether the operation mode of the inverter is a phase advance mode or a phase delay mode;
A control circuit for controlling a resonance parameter of the power supply side resonance circuit so that the operation mode becomes a slow phase mode ;
The resonance characteristic in the coupled state of the primary coil and the secondary coil is a bimodal characteristic having two series resonance frequencies,
The power reception device transmits a secondary current detection device that detects a secondary current flowing through the power reception device and information including a current value of the secondary current detected by the secondary current detection device to the power supply device. Side communication circuit,
The power feeding device includes a power feeding side communication circuit that receives the information transmitted from the power receiving side communication circuit,
The control circuit controls a resonance parameter of the power supply side resonance circuit so that an operating frequency of the power supply device is a frequency close to a low series resonance frequency of the two series resonance frequencies, and from the power supply side communication circuit Based on the supplied information, a phase difference between the primary current and the secondary current is acquired, and according to the acquired phase difference between the primary current and the secondary current, the power supply side resonance circuit A non-contact power feeding device that controls resonance parameters .   A non-contact power feeding device,
  A power feeding device including an inverter, a primary coil, and a power feeding side resonance circuit provided between the inverter and the primary coil;
  A power receiving device that includes a secondary coil that is magnetically coupled to the primary coil and obtains energy from the primary coil, and converts the energy obtained by the secondary coil to generate output power.
  A mode determination circuit for determining whether the operation mode of the inverter is a phase advance mode or a phase delay mode;
  A control circuit for controlling a resonance parameter of the power supply side resonance circuit so that the operation mode becomes a slow phase mode;
  The resonance characteristic in the coupled state of the primary coil and the secondary coil is a bimodal characteristic having two series resonance frequencies,
  The power reception device transmits a secondary current detection device that detects a secondary current flowing through the power reception device and information including a current value of the secondary current detected by the secondary current detection device to the power supply device. Side communication circuit,
  The power feeding device includes a power feeding side communication circuit that receives the information transmitted from the power receiving side communication circuit,
  The control circuit controls a resonance parameter of the power supply side resonance circuit so that an operating frequency of the power supply device is a frequency close to a high series resonance frequency of the two series resonance frequencies, and from the power supply side communication circuit Based on the supplied information, a phase difference between the primary current and the secondary current is acquired, and according to the acquired phase difference between the primary current and the secondary current, the power supply side resonance circuit Non-contact power feeding device that controls resonance parameters. In the non-contact electric power feeder of Claim 1 or 2 ,
The mode determination circuit includes:
A primary current detection device for detecting a primary current flowing in the power supply device;
The non-contact power feeding device, wherein the mode determination circuit determines whether an operation mode of the inverter is a phase advance mode or a phase delay mode according to the primary current detected by the primary current detection device. In the non-contact electric power feeder of any one of Claims 1-3 ,
The power supply device
A detection coil provided in the vicinity of the primary coil for detecting magnetic flux;
The control circuit includes:
A non-contact power feeding device that controls a resonance parameter of the power feeding side resonance circuit according to a magnetic flux detected by the detection coil. In the non-contact electric power feeder of any one of Claims 1-4 ,
The power supply side resonance circuit is:
A variable capacitor connected in series with the primary coil;
The contactless power feeding device, wherein the resonance parameter includes a capacitor capacity of the variable capacitor. In the non-contact electric power feeder of Claim 5 ,
The variable capacitor is
A plurality of series circuits, each of the plurality of series circuits including a switching element and a capacitor connected in series;
The plurality of series circuits are non-contact power feeding devices connected in parallel. In the non-contact electric power feeder of Claim 5 ,
The variable capacitor is
A series circuit including a bidirectional switching element and a capacitor connected in series;
A non-contact power feeding device including a bidirectional switching element connected in parallel to the series circuit. In the non-contact electric power feeder of Claim 5 ,
The variable capacitor is
A parallel circuit including a bidirectional switching element and a capacitor connected in parallel;
And a bidirectional switching element connected in series to the parallel circuit. In the non-contact electric power feeder of any one of Claims 1-4 ,
The power supply side resonance circuit is:
A variable coil connected in series with the primary coil;
The non-contact power feeding device, wherein the resonance parameter includes an inductance of a variable coil. The contactless power supply device according to claim 9 , wherein
The variable coil is
A plurality of series circuits, each of the plurality of series circuits including the plurality of series circuits including a switching element and a coil connected in series;
The non-contact power feeding device, wherein the plurality of series circuits are connected in parallel. In the non-contact power feeding device according to any one of claims 1-10,
The power supply device
Including a power supply side communication circuit for transmitting determination information by the mode determination circuit to the power receiving device;
The power receiving device is:
A power-receiving-side resonance circuit connected in series to the secondary coil;
A power receiving side communication circuit that receives determination information by the mode determination circuit transmitted from the power supply side communication circuit;
A non-contact power feeding apparatus comprising: a power receiving side control circuit that controls a resonance parameter of the power receiving side resonance circuit in accordance with determination information by the mode determination circuit supplied from the power receiving side communication circuit. In the non-contact electric power feeder of Claim 11 ,
The power receiving side resonance circuit is:
A variable capacitor connected in series with the secondary coil;
The contactless power feeding device, wherein the resonance parameter includes a capacitor capacity of the variable capacitor. The contactless power supply device according to claim 12 ,
The variable capacitor is
A plurality of series circuits, each of the plurality of series circuits including the plurality of series circuits including a switching element and a capacitor connected in series;
The plurality of series circuits are non-contact power feeding devices connected in parallel. The contactless power supply device according to claim 12 ,
The variable capacitor is
A series circuit including a bidirectional switching element and a capacitor connected in series;
A non-contact power feeding device including a bidirectional switching element connected in parallel to the series circuit. The contactless power supply device according to claim 12 ,
The variable capacitor is
A parallel circuit including a bidirectional switching element and a capacitor connected in parallel;
A non-contact power feeding device including a bidirectional switching element connected in series to the parallel circuit. In the non-contact electric power feeder of Claim 11 ,
The power receiving side resonance circuit is:
A variable coil connected in series with the secondary coil;
The non-contact power feeding device, wherein the resonance parameter includes an inductance of the variable coil. The contactless power supply device according to claim 16 ,
The variable coil is
A plurality of series circuits, each of the plurality of series circuits including a plurality of series circuits including a switching element and a coil connected in series;
The non-contact power feeding device, wherein the plurality of series circuits are connected in parallel. In the non-contact power feeding device according to any one of claims 11 to 17,
The power receiving device is:
An output power detection circuit for detecting the output power;
The non-contact power feeding device, wherein the power reception side control circuit controls a resonance parameter of the power reception side resonance circuit based on the output power detected by the output power detection circuit. In the non-contact power feeding device according to any one of claims 1 to 18
A contactless power feeding device in which the drive frequency of the inverter does not change. It is a starting method of the non-contact electric supply device according to any one of claims 1 to 19 ,
By setting the resonance parameters of the feeding-side resonant circuits to a predetermined value, and starting the power supply device,
According to the elapsed time since by starting the power supply device, smaller than said predetermined value the resonance parameters of the power supply-side resonant circuit, starting method of the non-contact power feeding device.