JP6002625B2 - Permanent magnet synchronous machine and compressor using the same - Google Patents

Description

  The present invention relates to a permanent magnet synchronous machine and a compressor using the same.

  In the permanent magnet synchronous machine, an interior permanent magnet (hereinafter, IPM) structure in which a permanent magnet is embedded in a rotor is widely adopted. In the IPM structure, since the ratio of the direct-axis inductance Ld and the horizontal-axis inductance Lq, the so-called salient pole ratio, is increased, it has been said that reluctance torque can be used in addition to magnet torque.

  As a background art of a permanent magnet synchronous machine utilizing reluctance torque, there is a synchronous machine described in Japanese Patent Application Laid-Open No. 2001-119875 (Patent Document 1). In this publication, the rotor 100 has a structure in which a magnetic salient pole type rotor part 102 and a magnet type rotor part 101 are coupled in series in the axial direction, and the magnetic salient pole type magnetic pole of the magnetic salient pole type rotor part 102 is provided. The magnetic flux and the magnetic flux of the magnet-type rotor part 101 permanent magnet type field pole are linked to a common multilayer armature coil. By configuring in this way, the relative angle of both rotor parts is set optimally compared to a synchronous machine that generates a combined torque of reluctance torque by magnetic salient pole type field poles and magnet torque by permanent magnet type field poles. This increases the combined torque per permanent magnet amount.

Japanese Patent Laid-Open No. 2001-11985

  In the synchronous machine of Patent Document 1, the salient pole ratio is increased by using an IPM structure, and reluctance torque is utilized. However, depending on the application, output, and motor size, there is an IPM structure, that is, it is difficult to utilize the reluctance torque even if the salient pole ratio is increased. This is because the magnitude of the reluctance torque depends not only on the magnitude of the salient pole ratio but also on the relative relationship with the magnet torque.

  However, this viewpoint has been overlooked in the conventional design theory. For this reason, reluctance torque cannot be used and output and efficiency cannot be improved. On the other hand, because the salient pole ratio is large, inductance increases and iron loss increases or speeding up may be difficult. .

  An object of the present invention is to enable torque improvement, efficiency improvement, and high-speed rotation even when it is difficult to use reluctance torque in a permanent magnet synchronous machine.

  In order to achieve the above object, in the present invention, in a permanent magnet synchronous machine having a rotor composed of permanent magnets arranged to form a plurality of poles, a stator coil interlinkage magnetic flux Ψp by the permanent magnets, Current I Arms The direct axis inductance Ld and the horizontal axis inductance Lq when energized satisfy the relationship of Equation 1,

The magnetic flux saturation of the stator core is alleviated by satisfying the relationship of Equation 2 between the stator linkage flux Ψ and the Ψp during driving.

  According to the present invention, torque and efficiency are improved, and high-speed rotation is possible.

  Problems, configurations, and effects other than those described above will be clarified by the following description of embodiments.

The figure which shows a stator and a rotor by the cross section perpendicular | vertical to a rotating shaft about the permanent magnet synchronous machine in 1st Example of this invention. The figure which shows the relationship of number 3 concerning this invention. Explanatory drawing of the torque characteristic in 1st Example of this invention. Permanent magnet motor vector illustration. The figure which shows a rotor by the cross section perpendicular | vertical to a rotating shaft about the permanent magnet synchronous machine in 1st Example of this invention. The figure which shows a rotor by the cross section perpendicular | vertical to a rotating shaft about the permanent magnet synchronous machine in 1st Example of this invention. An example of the motor characteristic in 2nd Example of this invention. The stator coil connection diagram of a 6 pole 9 slot three phase motor. The principle explanatory drawing of magnet torque and reluctance torque. Permanent magnet motor vector illustration. The fragmentary sectional view which shows the rotor of the permanent magnet synchronous machine which is a comparative example with this invention with a cross section perpendicular | vertical to a rotating shaft. The cross-section figure of the compressor in the 3rd Example of this invention.

  Embodiments of the present invention will be described below with reference to the drawings. In the following description, the same symbols are attached to the same components. Their names and functions are the same, and duplicate descriptions are avoided. Further, in the following description, the inner rotor is targeted, but the effect of the present invention is not limited to the inner rotor, and can be applied to an outer rotor having a similar configuration. is there.

  Further, the winding method of the stator may be concentrated winding or distributed winding. Further, the number of rotor poles and the number of phases of the stator coils are not limited to the configuration of the embodiment. In the following description, an inverter-driven permanent magnet motor is targeted. However, the effect of the present invention can also be applied to a self-starting permanent magnet motor.

  Hereinafter, a first embodiment of the present invention will be described with reference to FIGS. In describing the present embodiment, FIGS. 8 to 11 are referred to.

  FIG. 1 is a diagram showing a stator and a rotor in a cross section perpendicular to a rotation axis in a permanent magnet synchronous machine according to a first embodiment of the present invention.

  FIG. 2 is a diagram showing the relationship of Equation 3 according to the present invention.

  FIG. 3 is an explanatory diagram of torque characteristics in the first embodiment of the present invention.

  FIG. 4 is a vector diagram of a permanent magnet motor.

  5 and 6 are views showing the rotor in a cross section perpendicular to the rotation axis in the permanent magnet synchronous machine according to the first embodiment of the present invention.

  FIG. 8 is a stator coil connection diagram of a 6-pole 9-slot three-phase motor.

  FIG. 9 is a diagram illustrating the principle of magnet torque and reluctance torque.

  FIG. 10 is a vector diagram of a permanent magnet motor.

  FIG. 11 is a partial cross-sectional view showing a rotor of a permanent magnet synchronous machine, which is a comparative example with the present invention, in a cross section perpendicular to the rotation axis.

  The permanent magnet synchronous machine of a present Example is demonstrated using FIG.

  In the permanent magnet synchronous machine of the present embodiment, the rotor 1 is provided on the inner peripheral side of the stator 9. The rotor 1 is rotatably held by a bearing (not shown) via a gap G with respect to the stator 9.

  The stator 9 includes a stator core 10 having teeth 11 and a stator winding 12 wound around the teeth 11. The stator winding 12 arranges three-phase windings U, V, W in the circumferential direction in order. In each of the U phase, V phase, and W phase, three coils are connected in series (see FIG. 8). A total of nine coils 12u1, 12u2, 12u3, 12v1, 12v2, 12v3, 12w1, 12w2, and 12w3 are separately wound around each tooth 11 to constitute a concentrated permanent magnet synchronous machine.

  For this purpose, the stator 9 is provided with teeth 11 and nine slots. The rotor 1 is composed of a rotor core 2 having a permanent magnet housing hole 4 and permanent magnets 3 arranged to form 6 poles (number of pole pairs p = 3). A through hole 6a through which a shaft (rotating shaft, output shaft) 6 passes is formed at the center of the rotor 1, and the shaft 6 is inserted through the through hole 6a.

  In the permanent magnet synchronous machine of this embodiment, as shown in FIG. 1, the rotor 1 has a square-shaped magnet housing hole 4, and the permanent magnet 3 is embedded in the magnet housing hole 4. The permanent magnet 3 is inserted into the magnet accommodation hole 4, and a plurality of permanent magnets 3 and magnet accommodation holes 4 are provided along the circumferential direction, whereby a plurality of poles 8 are provided along the circumferential direction inside the rotor 1. Composed.

  A linear flux inductance Ld (H) and a horizontal axis inductance Lq (when the stator coil is energized with the interlinkage magnetic flux Ψp (Wb) for one phase of the stator coil by the permanent magnet 3 and the phase current effective value Irms (Arms). H) has the following relationship:

  Further, the stator flux linkage Ψ during driving and the Ψp satisfy the relationship of Equation 4.

  First, the physical quantity of Equation 3 and the principle of generation of reluctance torque will be described with reference to FIGS. In the present embodiment, a 6-pole 9-slot three-phase motor will be described.

  For example, as shown in FIG. 8, an alternating current iu having a peak value I (the effective value at this time is Irms) is supplied from the inverter to the U-phase windings 12u1, 12u2, and 12u3 connected in series. The same applies to the V-phase windings 12v1, 12v2, 12v3 and the W-phase windings 12w1, 12w2, 12w3, but the current phase of each phase is shifted by 120 ° in electrical angle. The size of I or Irms can be obtained by using a device such as a wattmeter. Or it can obtain | require by acquiring a current waveform with an oscilloscope etc. and performing a Fourier analysis.

  The shaft 6 mechanically coupled to the rotor 1 is connected to a load, and by appropriately selecting the magnitude and phase of the current I, a rotational torque Me that balances the load is generated. The interlinkage magnetic flux Ψp for one phase of the stator coil drives the rotor 1 externally with the terminals Tu, Tv, and Tw of U, V, and W shown in FIG. 8 open, and the phase voltage peak value E0, Alternatively, it can be obtained by measuring the line voltage peak value E0 × √3. Specifically, the angular frequency ω [rad / s] when externally driven at a rotational speed N [rpm] per minute is obtained from Equation 5 and is obtained by substituting it into Equation 6. However, p is the number of pole pairs.

  Incidentally, the torque Me of the magnet motor is generally generated by attraction / repulsion between the rotating magnetic field generated by the energizing currents of the stator windings U, V, and W and the rotor magnetic poles. In the case of a magnet motor, the rotor magnetic pole often refers to a magnetic field formed by a magnet, but when considering reluctance torque, the magnetic field formed by magnetizing the rotor core due to the influence of the rotating magnetic field is also the magnetic pole. It is easy to understand when considered as a kind of.

  In addition, since the electric current and magnetic flux at the time of synchronous operation of a magnet motor are alternating current amounts, the method of converting into a dq axis coordinate system (rotating coordinate system) and handling as a direct current amount is common. In general, in the dq-axis coordinate system, the magnetic pole central axis of the rotor is the d-axis, and the axis advanced 90 ° counterclockwise with respect to the d-axis, that is, the central axis between permanent magnets having different polarities is the q-axis. To do. In this case, it is possible to consider various physical quantities such as torque based only on the relative positional relationship between the dq axis and the rotating magnetic field regardless of the rotor position.

  The principle of torque generation of the magnet motor will be described with reference to FIG. In the figure, the counterclockwise direction is the positive direction. (A) shows magnet torque. (B) shows the reluctance torque generated when the d-axis current is negative, and is due to the magnetization of the rotor q-axis. (C) shows the reluctance torque generated when the d-axis current is negative, and is due to the magnetization of the rotor d-axis.

  As shown in (a), the magnet torque is torque generated by attraction and repulsion between the magnetic flux generated on the d-axis and the magnetic field formed by the q-axis current. At this time, a radial repulsive force is generated between the magnet magnetic flux and the d-axis current magnetic field, but no rotational force is generated.

  On the other hand, as shown in (b), when the rotor q-axis is magnetized by the q-axis current magnetic field, an attractive force and a repulsive force are generated between the magnetization of the rotor q-axis and the d-axis current magnetic field. This is a reluctance torque, and when the d-axis current is negative, that is, a positive torque is obtained during field-weakening operation, and a negative torque is obtained during a magnetizing action.

  Similarly, when the rotor d-axis is easily magnetized as shown in (c), a reluctance torque is generated in relation to the q-axis current magnetic field, which is a negative torque and a magnetizing action during field-weakening operation. Sometimes the torque is positive (generally, the sum of (b) and (c) is called reluctance torque).

  The magnet torque is proportional to the amount of magnetic flux generated by the magnet if the q-axis current is constant. That is, in order to increase the magnet torque, it is necessary to increase the amount of magnets or use a strong magnet, resulting in an increase in cost. On the other hand, since the reluctance torque is proportional to the difference between the q-axis and d-axis inductances, it has been considered that the torque can be increased by configuring the rotor magnetic circuit so that the difference between the two is large. It was.

  Now, among the constituent physical quantities of Equation 3, Ψp and Irms are obtained as described above, while Ld and Lq are obtained by a rotor stationary method such as the Dalton-Cameron method or the following. There is a method of calculating backward from a vector diagram as described.

  The current, voltage, and magnetic flux during the synchronous operation of the magnet motor will be described using the vector diagram of the dq axis coordinate system of FIG.

  Taking the phase of the interlinkage flux Ψp for one phase of the stator coil by the permanent magnet as a reference, this is regarded as the d-axis, and the induced electromotive force E0, which is the time derivative of Ψp, is generated on the q-axis whose phase is advanced by 90 °. When the phase voltage V applied to the motor and the phase current I applied to the motor have a phase difference of θ and β with respect to E0, V and I are d-axis components as shown in Equations 7 and 8. Can be decomposed into q-axis components.

  10 can be measured by using a resistance measuring instrument such as a Wheatstone bridge. Further, the voltage phase difference angle θ and the current phase difference angle β can be obtained by acquiring the waveforms of E0, V, and I and determining the phase relationship of each fundamental wave component. Although FIG. 10 shows the case of using the phase voltage and phase current waveforms, for example, even when the line voltage is obtained instead of the phase voltage, the phase difference between the phase voltage and the line voltage should be considered. Thus, θ and β can be obtained in the same manner.

  Using the physical quantities obtained above, Ld and Lq can be obtained from the voltage equation of Equation 9.

  In the above, the physical quantity and reluctance torque generation principle have been described.

  Next, the basic principle of the present invention, that is, the principle capable of improving the torque, improving the efficiency, and increasing the rotation speed by satisfying the relationship of Equation 3 and satisfying the relationship of Equation 4 will be described.

  In general, the generated torque Me is expressed by the following equation represented by Equation 10 using the number of pole pairs p, the linkage flux Ψp for one phase of the stator coil by a permanent magnet, the direct current Id, and the horizontal current Iq.

  However, Id, Iq, and Ψp are peak values.

  In Equation 10, the first term in {} represents the magnet torque, and the second term represents the reluctance torque. As is apparent from this equation, the reluctance torque is proportional to Lq−Ld, Id, and Iq, respectively. For this reason, conventionally, the salient pole ratio Lq / Ld or Lq-Ld has been used as an index of the magnitude of the reluctance torque. However, how much the reluctance torque contributes to the generated torque Me is determined by a relative relationship with the magnet torque. For example, when the reluctance torque is extremely small relative to the magnet torque, even if the reluctance torque slightly fluctuates (increases / decreases), the generated torque Me is hardly affected. Therefore, in addition to the conventional salient pole ratio, another physical quantity that can take into account the relative relationship with the magnet torque needs to be newly introduced into the index representing the magnitude of the reluctance torque.

  Here, the magnet torque becomes maximum when the current phase difference angle β = 0, and the maximum value Mp, max can be expressed by the following equation from Equations 8 and 10.

  On the other hand, the reluctance torque becomes maximum when β = π / 4 (45 deg. In electrical angle), and the maximum values Mr and max can be expressed by the following equations from Equations 8 and 10.

  Since the ratio of Equations 11 and 12 is nothing but an index representing the magnitude of the reluctance torque, this ratio is defined as the reluctance torque ratio α. When using the current peak I,

When the effective current value Irms is used,

It becomes. In the present invention, Expression 14 using the current effective value Irms is used.

  As can be seen from Equation 14, in addition to the conventional Ld and Lq, ψp and Irms are newly introduced as indices representing the magnitude of the reluctance torque. Of these, Ψp is determined by the physical properties and shape of the permanent magnet, the stator winding specifications, and the motor cross-sectional shape, and can be obtained from a general induced electromotive force measurement test. Similarly, Ld and Lq are also determined by the motor configuration and energization current Irms, and can be obtained by a general motor inductance measurement method. Therefore, Ψp, Ld, and Lq are constants determined for each motor, and Expression 14 can be treated as a linear function of α and Irms.

  The reluctance torque ratio α can take any value by changing the right side of Equation 14, particularly the current value. From the viewpoint of improving the generated torque and improving the efficiency, the reluctance torque Mr as shown in FIG. Β = 45 deg. It is desirable that the generated torque Me be equal to or greater than the magnet torque maximum value Mp, max. More specifically, the permanent magnet synchronous machine is driven in the range where the current phase difference angle is 0 to 45 ° when the efficiency maximization control is performed. The generated torque Me has a minimum value when the current phase difference angle is 0 ° and 45 °. Therefore, when the current phase difference angle is 0 ° and 45 °, the reluctance torque can be utilized by making the generated torque Me equal to or greater than the magnet torque maximum value Mp, max. That is,

The relationship should be established. Organizing Equation 15

Further, when the equation 14 is further transformed, the following equation is obtained.

  From the above, it is necessary to introduce Ψp and Irms in addition to the conventional Ld and Lq as an index indicating the magnitude of the reluctance torque, and it is necessary to satisfy the relational expression 17 in order to effectively use the reluctance torque. Showed that there is.

  However, when Equation 17 is not established, that is, when the relationship of Equation 3 is established, it is difficult to utilize the reluctance torque. In such a situation, the IPM structure as shown in FIG. 11 cannot improve the output and the efficiency, but has a large q-axis inductance due to the large salient pole ratio, leading to an increase in iron loss or high speed rotation. It will be difficult.

  Therefore, it is important that the stator flux linkage Ψ during driving satisfies the relation of Mathematical Formula 4 and Ψp. The reason for this will be described with reference to FIG. FIG. 4 shows various physical quantities in the motor drive state on the dq axis, and the symbols that overlap those in FIG. 10 have the same physical meaning and are not described here.

  First, the stator interlinkage magnetic flux Ψ at the time of driving is the reaction magnetic flux LdId generated by the d-axis current Id starting from the interlinkage magnetic flux Ψp (Wb) for one phase of the stator coil by the permanent magnet 3, and the q-axis current. It is expressed as a vector sum with the reaction magnetic flux LqIq generated by Iq.

  On the dq axis shown in FIG. 4, Ψ is a direct current amount, but when viewed from an arbitrary stator coil, it is an alternating current amount. The teeth around which the stator coil is wound have hysteresis due to an alternating change in Ψ. Loss and eddy current loss, that is, iron loss occurs. In general, the hysteresis loss is proportional to the crest value of Ψ, and the eddy current loss is proportional to the square of the crest value of Ψ. Therefore, it is desirable to reduce Ψ in order to reduce the iron loss. However, in the conventional IPM structure, since Lq is generally increased aiming at utilization of reluctance torque, as is clear from FIG. 4, Ψ becomes larger than Ψp as the LqIq vector is expanded. It was easy to be.

  When reluctance torque can be used, negative Id inevitably flows. Therefore, Ψ is easily suppressed by the LdId vector, but when reluctance torque cannot be used, it is not necessary to flow negative Id, so Ψ can be suppressed. This leads to an increase in iron loss. Therefore, when the relationship of Equation 3 is established, that is, when the reluctance torque cannot be utilized, it is extremely important to simultaneously satisfy the relationship of Equation 4 from the viewpoint of reducing iron loss.

  Next, the importance of Equation 4 will be described from the viewpoint of high-speed rotation. When the voltage drop due to the electrical resistance of the stator coil is ignored during driving, the motor terminal voltage V can be regarded as equivalent to the time derivative of the stator linkage flux Ψ and can be approximated by the following equation. As shown in FIG. 4, V is 90 deg. Represented by an advanced vector.

  Assuming now that the upper limit value of the motor terminal voltage is Vmax, as can be seen from Equation 18, ω can be increased by the amount of decrease in Ψ, that is, high-speed rotation can be achieved.

  As described above, the principle that the torque can be improved, the efficiency can be improved, and the rotation speed can be increased by satisfying the relationship of Equation 3 and satisfying the relationship of Equation 4 has been described.

  By the way, as a specific configuration satisfying the relationship of Equation 3 and satisfying the relationship of Equation 4, there is a rotor structure as shown in FIG.

  In FIG. 1, the rotor 1 is provided with a slit 7 made of a non-magnetic material on the radially outer peripheral portion (outer peripheral side) of the permanent magnet 3. Further, the rotor core 2 between the magnetic poles of the adjacent poles 8 is configured to be concave on the inner peripheral side with respect to the circumferential end of the permanent magnet housing hole 4. By adopting such a configuration, the q-axis inductance is reduced, and the magnetic saturation of the stator core is alleviated. In particular, by configuring the rotor core 2 between the magnetic poles to be concave on the inner peripheral side, the q-axis magnetic flux that attempts to penetrate the radial inner peripheral portion (inner peripheral side) of the permanent magnet 3 is greatly reduced. be able to. With the above configuration, it is possible to improve torque, reduce iron loss, improve efficiency, and achieve high speed rotation.

  By the way, when the above-described permanent magnet synchronous machine is driven, the current phase difference angle β can be arbitrarily set by the configuration of the control software. However, in the configuration satisfying Equation 3, the control operation point at which the generated torque is maximized. Is 0 deg. ≦ β ≦ 22.5 deg. Exists in the range. Therefore, the torque and the efficiency can be improved more reliably by controlling the phase so as to be the above-mentioned phase.

  Note that the permanent magnet 3 may be integrally formed without being divided in the circumferential direction per pole, or a plurality of permanent magnets 3 may be arranged in the circumferential direction.

  Moreover, the permanent magnet 3 and the magnet accommodation hole 4 which comprise 1 pole are not necessarily limited to one. For example, the permanent magnet 3 constituting one pole may be divided in the circumferential direction, the magnet accommodation hole 4 may be provided in accordance with each magnet, and a rib may be provided at the boundary between adjacent accommodation holes.

  Further, the permanent magnet 3 and the magnet housing hole 4 may be divided into a plurality in the direction of the rotation axis, or may be formed integrally without being divided.

  The rotor core 2 may be composed of laminated steel plates stacked in the axial direction, may be composed of a dust core, or may be composed of amorphous metal.

  In the present embodiment, the magnet housing hole 4 is formed so as to be orthogonal to the magnetic pole central axis of the permanent magnet constituting one pole, and has a flat plate shape when viewed from the direction of the rotation axis. The permanent magnet 3 housed in the magnet housing hole 4 is also formed on a flat plate in accordance with the shape of the magnet housing hole 4. With such a configuration, the magnet molding process can be minimized, and the magnet insertion process can be simplified, so that the manufacturing cost can be reduced.

  In addition, since the magnet housing hole has a flat plate shape, the outer core area per pole of the rotor core can be reduced as compared with a V-shaped housing hole or the like, so that the q-axis inductance can be reduced accordingly. it can. In order to reduce the outer peripheral core area per pole of the rotor core, the magnet housing hole may be formed in a shape that is convex outward in the radial direction instead of a flat plate shape.

  The slit 7 may be arranged so as not to prevent the transmission of the magnet magnetic flux and at the same time prevent the transmission of the q-axis magnetic flux, and may be provided in a straight line shape or an arc shape. Moreover, you may comprise by a continuation and may divide | segment by a rib etc. and may comprise. Further, in FIG. 1, four wires are arranged per one pole, but any number may be used as long as it can be manufactured. The width of each slit 7 may be uniform or non-uniform.

  As described above, the slit 7 does not prevent transmission of the magnet magnetic flux but prevents transmission of the q-axis magnetic flux. For this reason, the slit 7 is provided so as to cross the q-axis magnetic flux with respect to the magnet magnetic flux and the q-axis magnetic flux generated on the outer peripheral side of the permanent magnet 3 of the rotor core 2 in a state where the slit 7 is not provided. It is provided so as to follow the magnet flux without crossing the magnet flux as much as possible. When the slit 7 is provided so as to meet this condition, the slit 7 is long in the direction crossing the q-axis magnetic flux (direction along the magnetic flux) (large in size) and in the direction crossing the magnetic magnetic flux (direction along the q-axis magnetic flux). The shape is short (small size or thin width).

  The slit 7 will be described in more detail with reference to FIG. The configuration of FIG. 5 is different from that of FIG. 1 in that not only the slit 7a is provided in the radially outer peripheral portion (outer peripheral side) of the permanent magnet 3, but also the slit 7b is provided in the radially inner peripheral portion (inner peripheral side). It is a point.

  In FIG. 5, the d axis passes through the rotation center (center of the shaft 6) O of the rotor 1 and the center 4 o of the magnet housing hole 4. The permanent magnet 3 is inserted so as to fill the magnet accommodation hole 4 so as to be line-symmetric with respect to the d-axis. The permanent magnet 3 may not be completely filled in the magnet housing hole 4 but may be inserted so as to leave a gap. In this embodiment, since the d-axis passes through the center of the magnetic pole, the d-axis is hereinafter referred to as a magnetic pole center line 30cl.

  The slit 7a is inclined with respect to the magnetic pole center line 30cl so as to approach the magnetic pole center line 30cl on the outer peripheral side and away from the magnetic pole center line 30cl on the inner peripheral side. That is, the slit 7a is formed to be inclined with respect to the magnetic pole center line 30cl so that the outer peripheral side end is closer to the magnetic pole center line 30cl with respect to the inner peripheral side end. Specifically, the length of the perpendicular line (distance between the outer peripheral side end 7ao and the magnetic pole center line 30cl) d7ao from the outer peripheral side end 7ao of the center line 7acl of the slit 7a to the magnetic pole center line 30cl is equal to the slit 7a. The length of the perpendicular line (the distance between the outer peripheral side end 7ai and the magnetic pole center line 30cl) d7ai from the inner peripheral side end 7ai of the center line 7ac1 to the magnetic pole center line 30cl is shorter than the slit 7a. Inclined with respect to the line 30cl.

  The slit 7a is formed on at least one side of the magnetic pole center line 30cl in one magnetic pole. In the present embodiment, slits 7a are formed on both sides of the magnetic pole center line 30cl. The slits 7a formed on both sides of the magnetic pole center line 30cl are formed symmetrically with respect to the magnetic pole center line 30cl. By forming the slits 7a symmetrically with respect to the magnetic pole center line 30cl, the design regarding the permeability between the magnet magnetic flux and the q-axis magnetic flux becomes easy. However, the slits 7a are not necessarily formed symmetrically with respect to the magnetic pole center line 30cl.

  In FIG. 5, the slit 7 a is formed in a linear shape so as to have the above-described inclination, but may be formed in an arc shape. When the slit 7a is formed in an arc shape, a convex curve may be drawn toward the magnetic pole center line 30cl along the magnetic flux.

  Next, the slit 7b shown in FIG. 5 will be described. Even if the slit 7b is not provided, the effect of the slit 7a can be obtained, and therefore the slit 7b is not necessarily provided. However, the effect described below is obtained by providing the slit 7b.

  The slit 7b is provided in the radially inner peripheral part (inner peripheral side) of the permanent magnet 3, and is made of a nonmagnetic material in the same manner as the slit 7a.

  By adopting such a configuration, the effect of reducing the q-axis inductance is further enhanced, and the magnetic saturation of the stator core can be further alleviated. As a result, the permanent magnet synchronous machine can be further rotated at a high speed, and at the same time, further torque improvement and efficiency improvement can be achieved. The slit 7b may be arranged so as not to prevent the transmission of the magnet magnetic flux and at the same time prevent the transmission of the q-axis magnetic flux, and may be provided in a straight line shape or an arc shape. Moreover, you may comprise by a continuation and may divide | segment by a rib etc. and may comprise. Further, any number may be used as long as it can be manufactured. Further, the width of each slit may be uniform or non-uniform.

  Here, another effect of the slit 7b is an improvement in the demagnetization resistance of the permanent magnet 3. The irreversible demagnetization of the permanent magnet 3 occurs when the stator coil generates an excessive magnetic field in a direction opposite to the magnetization direction of the permanent magnet 3. The magnitude of the magnetic field generated by the stator coil is proportional to the magnitude of the current and the number of turns of the winding, that is, the ampere turn, but considering the case where the ampere turn is constant, the magnetic field applied to the permanent magnet 3 (hereinafter referred to as the ampere turn) The magnitude of the demagnetizing magnetic field is determined by the balance with the gap portion, the magnetic resistance of the stator core and the rotor core. That is, the demagnetizing magnetic field (the magnetic field applied to the permanent magnet 3) decreases as the magnetic resistance of the portion other than the permanent magnet 3 increases. Here, considering the case where there is no slit 7b, since there is no element that prevents the transmission of magnetic flux in the radially inner peripheral core portion of the permanent magnet 3, the magnetic resistance is very small. On the other hand, by providing the slit 7b, the magnetic flux is transmitted along the slit 7b, so that the magnetic path is limited and the magnetic resistance is increased. As a result, the demagnetizing magnetic field (magnetic field applied to the permanent magnet 3) can be reduced, so that the demagnetization resistance of the permanent magnet 3 is improved.

  Note that the same effect as described in the present embodiment can be obtained even in the configuration shown in FIG. 6 differs from FIG. 5 in that ribs 102 are provided between the magnetic poles on the outer periphery of the rotor core 2 and q-axis holes 103 are provided on the inner periphery thereof. Even in such a configuration, the q-axis magnetic flux that attempts to pass through the radially inner peripheral portion (inner peripheral side) of the permanent magnet 3 can be greatly reduced, and the magnetic saturation of the stator can be mitigated. Further, by providing the ribs 102, the strength is improved with respect to the centrifugal load acting on the outer peripheral core of the permanent magnet 3, so that a further high speed rotation is possible. In FIG. 6, the position where the rib 102 is provided is on the outer peripheral side of the permanent magnet 3. However, if the above effect can be obtained, the rib 102 is not necessarily provided on the outer peripheral side of the permanent magnet 3. It may be provided near the circumference or may be provided on the inner circumference side of the permanent magnet 3. Further, the width of the rib 102 may be arbitrarily set within a range in which both reduction of leakage flux of the permanent magnet 3 and improvement of rotor strength can be achieved. Further, the q-axis hole 103 has a semicircular shape in FIG. 6, but the shape may not necessarily be a semicircular shape as long as the q-axis magnetic flux can be reduced. Further, in FIG. 6, only one q-axis hole 103 is provided at one position between the electrodes, but two or more plural may be provided.

  Hereinafter, a second embodiment of the present invention will be described with reference to FIG. FIG. 7 is an example of motor characteristics in the second embodiment of the present invention.

  In this embodiment, as shown in FIG. 7, in the permanent magnet synchronous machine that generates the maximum torque Me, max in the maximum current conduction state, the rotation speed when the motor terminal voltage becomes Vmax is Nsat, The rotation speed when the induced electromotive force generated by driving is Vmax is Nmax, and Nmax <Nsat is configured, thereby enabling high-speed rotation.

  As described in the first embodiment, since the voltage is expressed by Expression 18, when the relationship of Expression 4 is satisfied, Nmax <Nsat is satisfied.

  Hereinafter, a third embodiment of the present invention will be described with reference to FIG. FIG. 12 is a sectional structural view of the compressor according to the present embodiment.

  In FIG. 12, the compression mechanism unit meshes the spiral wrap 15 standing upright with the end plate 14 of the fixed scroll member 13 and the spiral wrap 18 standing upright with the end plate 17 of the turning scroll member 16. Is formed. The revolving scroll member 16 is revolved by the crankshaft 6 to perform the compression operation. Of the compression chambers 19 (19a, 19b,...) Formed by the fixed scroll member 13 and the swivel scroll member 16, the compression chamber 19 located on the outermost diameter side is accompanied by a swirl motion. The scroll members 13 and 16 move toward the center, and the volume gradually decreases.

  When both the compression chambers 19 a and 19 b reach the vicinity of the centers of the scroll members 13 and 16, the compressed gas in both the compression chambers 19 is discharged from the discharge port 20 communicating with the compression chamber 19. The discharged compressed gas passes through the gas passage (not shown) provided in the fixed scroll member 13 and the frame 21 and reaches the pressure vessel 22 below the frame 21, and the side wall of the pressure vessel 22. Is discharged from the discharge pipe 23 provided outside the compressor. A permanent magnet motor 103 composed of the stator 9 and the rotor 1 is enclosed in the pressure vessel 22, and the compression operation is performed by the rotation of the rotor 1. An oil sump 25 is provided below the permanent magnet motor 103. The oil in the oil sump 25 passes through an oil hole 26 provided in the crankshaft 6 due to a pressure difference caused by a rotational motion, and a sliding portion between the turning scroll member 16 and the crankshaft 6 and a sliding bearing 27. It is used for lubrication. A terminal box 30 for pulling out the stator coil 12 to the outside of the pressure vessel 22 is provided on the side wall of the pressure vessel 22. For example, in the case of a three-phase permanent magnet motor, terminals of U, V, and W windings are provided. There are a total of three. By applying the permanent magnet synchronous machine described in the first embodiment or the second embodiment to the permanent magnet motor 103, it is possible to drive to a higher speed, and at the same time, improve the torque and improve the efficiency. It becomes possible.

  By the way, in many current home and commercial air conditioners, the R410A refrigerant is sealed in the compression container 22, and the ambient temperature of the permanent magnet motor 103 is often 80 ° C. or more. In the future, as the adoption of R32 refrigerant having a smaller global warming potential progresses, the ambient temperature further increases, so that the reduction in Br of the magnet becomes more prominent. In such a case, by applying the permanent magnet synchronous machine described in the first embodiment or the second embodiment, it is possible to compensate for the torque decrease and the efficiency decrease due to the Br decrease. In particular, when the permanent magnet 3 is composed of a ferrite magnet, high temperature demagnetization which is a problem with a neodymium magnet does not occur in principle, which is an effective measure against an increase in ambient temperature due to the adoption of the R32 refrigerant. In addition, in applying the permanent magnet synchronous machine of the above-mentioned Example 1 or Example 2 to the compressor of a present Example, the kind of refrigerant | coolant is not restrict | limited.

  The compressor configuration may be a scroll compressor shown in FIG. 12, a rotary compressor, or a configuration having other compression mechanisms. Further, according to the present invention, as described above, a small and high output motor can be realized. Then, it becomes possible to widen the operating range, such as enabling high-speed operation. Further, in refrigerants such as He and R32, leakage from gaps is larger than refrigerants such as R22, R407C, and R410A, and in particular, low speeds. During operation, the ratio of leakage to the circulation amount is significantly increased, so that the efficiency is greatly reduced. Reducing leakage loss by reducing the size of the compression mechanism and increasing the rotational speed to obtain the same amount of circulation can be an effective means to improve efficiency during low circulation (low speed operation). It is necessary to increase the maximum number of revolutions in order to secure the circulation rate. According to the compressor provided with the permanent magnet synchronous machine according to the present invention, it is possible to increase the maximum rotation speed, which is an effective means for improving the efficiency of refrigerants such as He and R32.

DESCRIPTION OF SYMBOLS 1 ... Rotor, 2 ... Rotor iron core, 3 ... Permanent magnet, 4 ... Permanent magnet accommodation hole, 5 ... Riveting for caulking, 6 ... Shaft or crankshaft, 7a, 7b ... Slit, 8 ... Pole, 9 ... Stator DESCRIPTION OF SYMBOLS 10 ... Stator iron core, 11 ... Teeth, 12 (12u1, 12u2, 12v1, 12v2, 12w1, 12w2) ... Stator coil, 13 ... Fixed scroll member, 14 ... End plate, 15 ... Spiral wrap, 16 Rotating scroll member 17 End plate 18 Spiral wrap 19 (19a, 19b) Compression chamber 20 Discharge port 21 Frame 22 Pressure vessel 23 Discharge pipe 24 DESCRIPTION OF SYMBOLS ... Balance weight, 25 ... Oil reservoir, 26 ... Oil hole, 27 ... Sliding bearing, 30 ... Terminal box, 101 ... Rib, 102 ... q-axis hole, 103 ... Permanent magnet motor.
7

Claims (11)

A stator having a plurality of teeth and a stator coil;
A rotor arranged in a radial direction with respect to the stator through a gap and forming a magnet housing hole,
A permanent magnet synchronous machine in which a plurality of permanent magnets are arranged in the circumferential direction.
A linear-axis inductance Ld (H) and a horizontal-axis inductance Lq (when the stator coil is energized with the interlinkage magnetic flux Ψp (Wb) for one phase of the stator coil by the permanent magnet and the current effective value Irms (Arms). H) and the current effective value Irms (Arms),
Satisfying the above relationship, and at the same time, the stator flux linkage Ψ (Wb) during driving
A permanent magnet synchronous machine characterized by satisfying the above relationship. In the permanent magnet synchronous machine according to claim 1,
The rotor is arranged with a plurality of magnetic poles composed of permanent magnets inserted in the magnet housing holes in the circumferential direction,
A permanent magnet synchronous machine, wherein a slit made of a non-magnetic material is disposed on a radially outer periphery of the magnetic pole. In the permanent magnet synchronous machine according to claim 1,
The magnet housing hole is formed so as to be perpendicular to the magnetic pole central axis of the permanent magnet constituting one pole, and is flat when viewed from the rotation axis direction,
A permanent magnet synchronous machine, wherein a slit made of a non-magnetic material is disposed on a radially outer periphery of the magnetic pole. In the permanent magnet synchronous machine according to claim 2 or claim 3,
The rotor is a permanent magnet synchronous machine in which a core between adjacent magnetic poles is recessed toward an inner peripheral side from a circumferential end of the permanent magnet accommodation hole. In the permanent magnet synchronous machine according to claim 2 or claim 3,
The rotor has a rib extending in the circumferential direction between adjacent magnetic poles, and forms a hole provided on the radially inner peripheral side of the rib. In the permanent magnet synchronous machine according to any one of claims 2 to 5,
The slit is provided on at least one side of a center line passing through the rotation center of the rotor and the magnetic pole center of the magnetic pole, and an outer peripheral side end portion is closer to the central line with respect to an inner peripheral side end portion, The permanent magnet synchronous machine is formed to be inclined with respect to the center line. In the permanent magnet synchronous machine according to claim 6,
The slit is formed symmetrically with respect to the center line on both sides of the center line. In the permanent magnet synchronous machine according to any one of claims 1 to 7,
A permanent magnet synchronous machine, wherein a slit made of a non-magnetic material is disposed on a radially inner periphery of the magnetic pole. In the permanent magnet synchronous machine according to any one of claims 1 to 8,
The phase of the current supplied from the inverter to the permanent magnet synchronous machine is a lead phase of 0 ° to 22.5 ° with respect to the phase of the induced electromotive force for one phase of the stator coil by the permanent magnet. The permanent magnet synchronous machine is controlled as follows. In a compressor provided with a compression mechanism that sucks in and compresses and discharges the refrigerant, and a permanent magnet motor that drives the compression mechanism,
The compressor according to any one of claims 1 to 9, wherein the permanent magnet motor is a permanent magnet synchronous machine. The compressor according to claim 10, wherein
An R32 refrigerant is sealed in the compressor.