JP5693820B2 - Power supply - Google Patents

Description

  The present invention relates to a power supply apparatus, and more particularly to an insulated AC-DC conversion power supply apparatus suitable for high efficiency and miniaturization.

  FIG. 10 is a circuit diagram showing a schematic configuration of a main part of a conventional insulated AC-DC conversion power supply device (hereinafter simply referred to as a power supply device), and FIGS. 11 and 12 are waveform diagrams showing the operation thereof. The power supply device shown in FIG. 10 outputs a first converter (step-up chopper type active converter: hereinafter referred to as a boost converter) that rectifies an input AC voltage and converts it into a DC voltage, and the boost converter outputs the first converter. An inverter that receives a DC voltage and outputs a high-frequency AC voltage, a transformer that transforms the AC voltage output by the inverter, and a second converter that converts the AC voltage transformed by the transformer into a DC voltage again ( Hereinafter, it is referred to as a rectifier converter).

Specifically, in FIG. 10, D _{1 to} D ₄ are rectifying diodes, and a series circuit having a first connection point a connecting the anode of the rectifying diode D _{1 and} the cathode of the rectifying diode D ₂ , and the rectifying diode A first bridge rectifier circuit is configured in which a series circuit having a second connection point b connecting the anode of the diode D _{3 and} the cathode of the rectifier diode D ₄ is connected in parallel. An AC power supply 1 is connected between the first connection point a and the second connection point b in the first bridge rectifier circuit.

The DC output terminal (the cathodes of the rectifying diodes D ₁ and D ₃ and the anodes of the rectifying diodes D ₂ and D ₄ ) in the first bridge rectifier circuit is connected to one end of the first smoothing reactor L ₁ and a semiconductor switching element ( For example, a series circuit in which a MOSFET (the drain of Q ₁ ) is connected in series is connected in parallel. Between the drain and source of the MOSFET (Q ₁ ), a series circuit in which a backflow prevention diode D ₅ and a first smoothing capacitor C ₁ are connected in series is connected in parallel to constitute a boost converter. ing.

The DC output of the boost converter, that is, the DC voltage E _d1 generated across the smoothing capacitor C ₁ is applied to an inverter constituted by semiconductor switching elements (for example, MOSFETs (Q _{2 to} Q ₅ )). This inverter includes a series circuit in which the source of the MOSFET (Q ₂ ) and the drain of the MOSFET (Q ₃ ) are connected at a third connection point c, the source of the MOSFET (Q ₄ ), and the drain of the MOSFET (Q ₅ ) Are connected in parallel with a series circuit connected at a fourth connection point d. A primary winding of a transformer T having a predetermined transformer (turn ratio) is connected between the third connection point c and the fourth connection point d of the inverter (in this figure, the transformer The ratio is n: 1).

The secondary winding of the transformer T, a high-frequency alternating current inverter output [n: 1] transformers and AC is output to the second bridge rectifier constituted by the rectifier diode (D ₆ ~D ₉₎ Given to the circuit. The second bridge rectifier circuit includes a series circuit having a fifth connection point e connecting the anode of the rectifier diode D _{6 and} the cathode of the rectifier diode D ₇ , the anode of the rectifier diode D ₈ , and the rectifier diode. A series circuit having a sixth connection point f to which the cathode of D ₉ is connected is connected in parallel. The secondary winding of the transformer T is connected between the fifth connection point e and the sixth connection point f of the second bridge rectifier circuit.

A smoothing circuit composed of a series circuit of a _second smoothing reactor L ₂ and a second smoothing capacitor C ₂ is connected in parallel to the DC output terminal of the second bridge rectifier circuit to constitute a rectifier converter. A load R _L is connected to both ends of the second smoothing capacitor C ₂ .
The function of the power supply device configured as described above is as follows.
(1) The AC input is converted into a DC output having a desired voltage, and a constant output voltage is maintained regardless of variations in the input voltage and load current.
(2) Insulate the AC input side from the DC output side.
(3) The AC input current is a sine wave having a power factor [1].

Further, when the load connected to the power supply apparatus is a high-reliability requirement for information / communication equipment, the following functions are also required.
(4) Securing a predetermined output voltage even in the case of a voltage drop in a period of several ms to several cycles of a commercial AC power source, that is, a so-called instantaneous voltage drop (hereinafter referred to as a sag) (hereinafter, this function is compensated for a sag) Called).

The operation of the power supply device for realizing these functions will be described with reference to FIG.
Waveform of the input voltage V _in of the commercial AC input to the power supply, varies sinusoidally. The input voltage V _in is rectified by first diode bridge that is configured by the rectifying diode D ₁ to D _4, the rectified waveform of the rectified voltage V _r1, a full-wave rectified waveform as shown.
Here, for example, when the input voltage V _in is of positive polarity (first connection point a positive), when turning on the MOSFET (Q _1), the AC power source 1 → rectifying diode D ₁ → reactor L ₁ → MOSFET (Q ₁ ) A current flows through the path of the rectifier diode D ₄ → the AC power source 1, the voltage of the AC power source 1 is applied across the reactor L ₁ , and the current I _L increases. Next, when the MOSFET (Q ₁ ) is turned off, current flows through the path of the AC power source 1 → the rectifying diode D ₁ → the reactor L ₁ → the backflow preventing diode D ₅ → the smoothing capacitor C ₁ → the rectifying diode D ₄ → the AC power source 1. . In this case although reactor to L ₁ applied the difference voltage between the input voltage V _in of the AC power source 1 across the DC voltage E _d1 of the smoothing capacitor C ₁ across the DC voltage E _d1 by the operation of the circuit, the input voltage V _in It is kept higher than the peak value. For this reason, the current I _L flowing through the reactor L ₁ decreases.

Can be considered similarly, even if the input voltage V _in is of negative polarity (second connecting point b is positive), a description thereof will be omitted.
This power supply device can arbitrarily control the waveform and magnitude of the current I _L by controlling the ON / OFF time ratio of the MOSFET (Q ₁ ). If the current I _L is a sine wave rectified waveform as shown in FIG. 11 (the ripple is ignored for simplification), the input current I _in becomes a sine wave waveform. In addition, this power supply device can keep the DC voltage E _d1 constant by controlling the amplitude of the current I _L according to the load power.

On the other hand, an inverter composed of MOSFETs (Q _{2 to} Q ₅ ) converts the DC voltage E _d1 into a high-frequency AC voltage. That turns on the MOSFET (Q ₂₎ and _{MOSFET (Q 5), MOSFET (} Q 3) and MOSFET (Q ₄₎ positive voltage to MOSFET (Q ₄₎ is turned off to have, MOSFET (Q ₃₎ and MOSFET (Q ₄ ) is turned on and the MOSFET (Q ₂ ) and MOSFET (Q ₅ ) are turned off, a negative voltage is applied to the MOSFET (Q ₄ ).

In this way, the inverter alternately generates positive and negative voltages, obtains a high-frequency AC voltage (primary voltage V _t ), and applies it to the transformer T. (In FIG. 12, the period of the input voltage V _in and the primary voltage V _t of the transformer is represented by the same level for the sake of clarity, but generally, the commercial frequency where the input voltage V _in is 50 Hz or 60 Hz. to which the in, the primary voltage V _t of the transformer to several kHz or higher the switching frequency of the inverter to miniaturize the transformer).

The high-frequency AC voltage output from the inverter is transformed and insulated by the transformer T, and then rectified by rectifying diodes D _{6 to} D ₉ constituting a rectifying converter, and the second reactor (smoothing reactor) L ₂ and It is smoothed by the smoothing circuit consisting of a second series circuit of the smoothing capacitor C _2. Then, a DC voltage that suppresses ripple component is obtained from both ends of the smoothing capacitor C _2, the DC voltage is supplied to the load R _L.

The voltage applied to the load R _L can be controlled by a time ratio (hereinafter referred to as an inverter time ratio) at which the MOSFET (Q ₂ , Q ₅ ) or the MOSFET (Q ₃ , Q ₄ ) is turned on.
Schematically, when a voltage sag occurs in the power supply apparatus configured as described above, the supply of input power is cut off, and the DC voltage E _d1 decreases. However, this power supply, the average value of a if it is within range MOSFET (Q _2, Q ₅₎ or MOSFET (Q _3, Q ₄₎ primary voltage V _t of the transformer by increasing the duty ratio to turn on the It can be kept constant and the output voltage can be maintained.

By the way, if the power supply device is provided with a function capable of obtaining a stable DC output voltage even during a momentary drop, the efficiency decreases. Next, the reason will be described.
In order to maintain a stable DC output voltage even if the DC voltage E _d1 drops to some extent, it is necessary to make the transformation ratio of the transformer T (here, the value of n of n: 1) smaller than the original optimum value. . For example, if the DC voltage E _d1 at the normal time is kept constant at 400 V by the above operation and the DC output voltage V _out is 10 V, the transformation ratio of the transformer T necessary for operating the inverter at the maximum duty ratio [400: 10], that is, the transformation ratio n is [40] (here, the voltage drop in the circuit is ignored for simplification).

On the other hand, even if the DC voltage E _d1 drops to 200V, the transformation ratio of the transformer T necessary to maintain the DC output voltage V _out constant is [200: 10], that is, the transformation ratio n is [20]. . When the transformation ratio is set under these conditions, in normal operation, that is, when the DC voltage E _d1 is 400V, the inverter duty ratio is set to about [0.5] in order to keep the DC output voltage _Vout at 10V. Become. In this case, the loss generated in the power supply device increases for the following reason.
(1) the amplitude of the current flowing through the primary winding of the transformer T is [1 / n] of the current flowing in the smoothing reactor L _2, the current value increases as the transformation ratio n decreases. Therefore loss generated in MOSFET (Q ₂ ~Q ₅₎ and the primary winding of the transformer T constituting the inverter is increased.
(2) The rectified voltage V _r2 output from the rectifying converter is approximately [E _d1 / n], but the rectifying diodes D _{6 to} D ₉ that normally constitute the rectifying converter when the transformation ratio n is reduced. The voltage applied to becomes higher. For this reason, it is necessary to use components having higher withstand voltages for the rectifying diodes D _{6 to} D ₉ , but generally, the loss under the same conditions in the semiconductor element tends to increase as the withstand voltage increases.
(3) Since the period during which the voltage of the rectified voltage V _r2 is not applied becomes longer, it is necessary to increase the inductance value of the smoothing reactor L ₂ necessary for smoothing this. For example, in the case of no sag compensation 12, the period of the rectified voltage V _r2 is reduced to [0V], although a short time at the time of polarity switching of the primary voltage V _t of the transformer T, No Yes sag compensation In this case, normally, a voltage is not applied for about a half of the whole period, and it is necessary to supply the energy stored in the smoothing reactor L ₂ to the load R _L during this period. However to large the smoothing reactor L ₂ is not only the power supply becomes large, a new problem that increases loss in the smoothing reactor L ₂ occurs.

A voltage source inverter that avoids an increase in loss after such an inverter is known (see, for example, Patent Document 1). This voltage source inverter is configured in principle as shown in FIG. The power supply device shown in this figure is different from the power supply device shown in FIG. 10 described above in that a boost chopper for boosting a DC voltage is interposed between the boost converter and the inverter. That is, a series circuit in which one end of the reactor L ₃ and a semiconductor switching element (for example, a MOSFET (drain of Q ₆ )) are connected to both ends of the _first smoothing capacitor C ₁ provided on the output side of the boost converter. A series circuit composed of a diode D ₁₀ and a third smoothing capacitor C ₃ is connected between the drain and source of the MOSFET (Q ₆ ) to constitute a boost chopper. The chopper can also control the current flowing through the reactor L ₃ by the same operation as that of the power supply device shown in FIG. 10, and as a result, an output voltage higher than the input voltage can be obtained.

For this reason, even if the DC voltage E _d1 decreases (for example, decreases from 400 V to 200 V) at the time of an instantaneous drop, the voltage E _d2 can be kept constant (for example, 400 V) by boosting with the boost chopper. Therefore, in the above-described example, the transformer T can be designed with a transformation ratio n of [40].
Alternatively, as shown in FIG. 14, the secondary battery BAT that can be charged and discharged is connected in parallel with the smoothing capacitor C ₁ in the power supply device of FIG. 10 described above, and the voltage E _d2 is _maintained even when the power supply from the AC power supply 1 is cut off. There is also an uninterruptible power supply that supplies the power stored in the secondary battery BAT to the load _RL while keeping it substantially constant.

JP-A-2-241371 (FIG. 2)

However, the voltage source inverter described in Patent Document 1 described above has the following problems.
(1) A loss occurs in the boost chopper.
This is because the DC voltage E _d1 across the _first smoothing capacitor C ₁ is sufficiently high and the MOSFET (Q ₆ ) stops, as well as when the MOSFET (Q ₆ ) is on / off in the circuit shown in FIG. Even in this case, loss due to the winding resistance component of the reactor L ₃ and the forward voltage drop of the diode D ₁₀ occurs. For this reason, the part which suppressed the circuit loss after an inverter will be canceled. Furthermore, since a current always flows through the reactor L ₃ , it is necessary to have a large current capacity even though the time for the boosting operation is extremely short.
(2) The third smoothing capacitor C ₃ needs to have a large capacitance in order to absorb the ripple current generated by the inverter.

Originally, the first smoothing capacitor C ₁ has a sufficiently large electrostatic capacity for supplying energy at the time of a sag. Therefore, in the circuit shown in FIG. 10, the first smoothing reactor L ₁ , MOSFET (Q ₁ ), and diode It can play a role of absorbing both the ripple current generated in the circuit of D _{5 and} the ripple current of the inverter. However, in the circuit of FIG. 13, the reactor L ₃ is inserted between the inverter and the first smoothing capacitor C ₁ , so that the high frequency ripple current cannot pass. For this reason, a third smoothing capacitor C ₃ is separately required at the output stage of the boost chopper. This increases the size of the power supply device.

  Japanese Patent Application Laid-Open No. 8-185993 discloses a power supply device designed to solve this type of problem. This power supply device supplies energy from another capacitor that has been charged in advance when the voltage drops. However, in this power supply device, a capacitor that absorbs ripples in a normal state and a capacitor that supplies energy at the time of a sag are separated from each other, so that there is still a problem that the size of the device cannot be avoided.

Alternatively, in the uninterruptible power supply shown in FIG. 14, voltage fluctuation occurs due to charging / discharging of the secondary battery. In order to cope with this voltage fluctuation, the transformation ratio of the transformer T has to be set as described above, and a reduction in efficiency is inevitable.
The present invention has been made to solve such a problem, and the object of the present invention is to minimize an increase in loss due to having a function of supplying power during a power failure (power failure compensation). However, it is an object of the present invention to provide a power supply device that can achieve high efficiency and downsizing.

In order to solve the above-described problems, a power supply device of the present invention includes a first converter (step-up converter) that converts an input AC voltage into a DC voltage while controlling a power factor, and the first converter. A boost chopper that boosts and outputs the DC voltage output by the synthesizer and a ripple included in the DC voltage output by the first converter (boost converter) provided on the input side of the boost chopper is reduced below a predetermined level. A first smoothing capacitor, a first bypass diode that bypasses the boost chopper and supplies a DC voltage input to the boost chopper to the output of the boost chopper, and a third connected to the output side of the boost chopper comprising of a smoothing capacitor, and an insulating-type DC / DC converter and outputting the insulated by transformer boosted DC voltage by the step-up chopper The first converter includes a diode bridge circuit that rectifies the AC voltage, a series circuit connected in order of a reactor and a switching element to an output of the diode bridge circuit, a connection point between the reactor and the switching element, and the A backflow prevention diode connected between the first smoothing capacitor and a second bypass diode connected between a connection point between the reactor and the switching element and an output of the boost chopper. (Invention of claim 1).

The power supply apparatus, the step-up chopper is when non-operational, and outputs bypassing the DC input by the bypass diode without passing through the switching elements and a reactor boosting chopper has a boost chopper. For this reason, loss due to current flowing through the switching element of the boost chopper does not occur. The reactor of the step-up chopper only needs to withstand the current of the step-up chopper during the period when the AC input voltage is sag, and a reactor using a thin winding capable of short-time rating can be applied, and the power supply device can be downsized.

The isolated DC / DC converter of the power supply device includes an inverter connected to an output side of the boost chopper and converting a DC voltage boosted by the boost chopper into an AC voltage. Invention of 2).
When the boost chopper is not in operation, the above-described power supply device bypasses the direct current input to the boost chopper by the first bypass diode without passing through the switching element and the reactor included in the boost chopper, and supplies the bypass chopper to the subsequent inverter. be able to. For this reason, during normal times, the ripple current of the inverter can also be carried through the first bypass diode. In addition, the reactor of the step-up chopper need only be able to withstand the current of the step-up chopper during the moment when the AC input voltage is sag. Therefore, it is possible to use a reactor that uses a thin winding for short-time rating. Since the current does not flow through the switching element and the reactor included in, loss can be reduced.

The first bypass diode further includes a parallel capacitor connected in parallel (invention of claim 3).
Smoothing capacitor provided to the input side and output side of the step-up chopper in the above-described power supply device, the first is connected in parallel by a bypass diode, further said first bypass diode is momentarily turned off by influence of the ripple current The capacitor is connected to the first bypass diode in parallel and short-circuited in an AC manner, and the two smoothing capacitors are connected in parallel, so that a large capacitance can be obtained. Ripple can be removed. For this reason, the volume of the power supply device can be reduced, and the power supply device can be miniaturized.

The first bypass diode further includes a parallel capacitor connected in parallel;
Before SL parallel capacitor is characterized by having a sufficiently low impedance to the switching frequency component of the inverter (invention of claim 4).
The above-described power supply apparatus can effectively remove ripples generated by the switching operation of the inverter, and therefore can reduce noise radiated from the power supply apparatus to the outside.

Since the above-described power supply device can directly supply the AC input voltage to the subsequent inverter without passing through the switching element and the reactor included in the step-up chopper, the loss can be reduced .

The power supply apparatus described above can insulate the input side from the output side by a transformer connected to the output side of the inverter .
In the power supply apparatus, a second converter (rectifier converter) that converts an AC voltage output from the transformer into a DC voltage and outputs the converted voltage is output to the output side of the transformer. A second smoothing reactor for smoothing a DC voltage, and the inverter is operated with a switching frequency higher than that during normal operation at the time of startup, and suppresses a ripple current flowing in the second smoothing reactor. (Invention of claim 5 )

The above-described power supply device effectively suppresses the ripple current flowing in the second smoothing reactor (DC reactor) at the time of start-up, that is, the high-frequency current flowing in the smoothing capacitor connected in parallel with the load and the capacitor component of the load. Can do.
Alternatively, the power supply device of the present invention comprises a series circuit in which a secondary battery and a charge / discharge control unit that charges and discharges the secondary battery are connected in series, and is connected in parallel to the smoothing capacitor, and the charge / discharge control unit When the input AC voltage exceeds a first predetermined voltage value, the secondary battery is charged to store electric power, while when the AC voltage falls below a predetermined voltage value, the secondary battery The power stored in the battery is discharged and supplied to the load (invention of claim 6 ).

  For example, when the input AC voltage is normal (during normal operation), the above-described power supply device charges the secondary battery to store electric power, while the AC input is interrupted and the AC voltage is reduced, such as during a power failure. Even in a power supply device (uninterruptible power supply device) that decreases and supplies the power stored in the secondary battery to the load, the increase in loss can be suppressed to the minimum as described above during normal operation.

According to the power supply device of the first to fourth aspects of the present invention, an increase in loss due to the instantaneous voltage drop compensation can be minimized, and high efficiency and miniaturization of the device can be realized.
Moreover, according to the invention which concerns on Claim 5 of this invention, the direct current | flow smoothing reactor can be made into the minimum capacity | capacitance, and there can exist an outstanding effect that the further efficiency improvement and size reduction of an apparatus can be achieved.

Alternatively, the invention according to claim 6 can provide a power supply device (uninterruptible power supply device) capable of minimizing an increase in loss during normal operation and realizing high efficiency and downsizing.

1 is a circuit diagram showing a schematic configuration of a main part of a power supply device according to Embodiment 1 of the present invention. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 2 of this invention. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 3 of this invention. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 4 of this invention. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 5 of this invention. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 6 of this invention. FIG. 7 is a circuit diagram showing an example of a bidirectional switch shown in FIG. 6. The circuit diagram which shows the principal part schematic structure of the power supply device which concerns on Example 7 of this invention. The circuit diagram which shows the principal part schematic structure of the power supply device which deform | transformed Example 7 shown in FIG. The circuit diagram which shows the principal part schematic structure of the conventional power supply device. FIG. 11 is a diagram illustrating an example of an input voltage / current of the power supply device illustrated in FIG. 10, an output voltage of the boost converter, and a current flowing through the reactor. The graph which shows the relationship between the control signal and output voltage of the converter in the power supply device shown in FIG. The circuit diagram which shows the principal part schematic structure of the conventional power supply device different from FIG. The figure which shows the principal part schematic structure of the conventional uninterruptible power supply.

  Hereinafter, a power supply device according to an embodiment of the present invention will be described with reference to the accompanying drawings. 1 to 9 show examples of embodiments in the present invention, and the present invention is not limited to these drawings. In the figure, the same reference numerals as those in FIGS. 10, 13, and 14 denote the same components, and the basic configuration is the same as that of the conventional one shown in these drawings, and the description thereof will be briefly described.

FIG. 1 is a circuit diagram illustrating a schematic configuration of a main part of a power supply device according to Embodiment 1 of the present invention. The difference between the power supply device according to the first embodiment and the conventional power supply device is that the DC output of the first converter (boost converter), that is, the bypass provided to the input of the inverter by bypassing the direct current applied to the boost chopper circuit is bypassed. The diode D ₂₀ is provided. That while connecting the anode of the first bypass diode D ₂₀ to the first positive electrode side of the smoothing capacitor C _1, the connection point of the cathode of the first bypass diode D ₂₀ and diodes D ₁₀ and smoothing capacitor C ₃ Connecting. The first smoothing capacitor C ₁ is used which has a sufficiently low impedance to two times the frequency component of V _in.

In the power supply device according to the first embodiment of the present invention configured as described above, the MOSFET (Q ₆ ) is not switched during normal operation. DC applied to this for the step-up chopper is provided to be bypassed inverter by the first bypass diode D _20. Here, the DC voltages E _d1 and E _{d2 at} both ends of the first and third smoothing capacitors C ₁ and C ₃ are DC voltages that are smoothed both in the normal state and in the instantaneous drop. For this reason, the first bypass diode D ₂₀ does not need the ability to rectify the high frequency, and may be a low-speed diode. The forward voltage of the low-speed diode is lower (about ½) than that of the high-speed diode, and no current flows through the reactor L ₃ , so that the loss can be greatly reduced as compared with the conventional power supply circuit.

Further blocking diode _D time current flows in the ₁₀ is less than the number 10ms during voltage sag. Therefore, since the time for operating the step-up chopper is also several tens of ms or less, the reactor L ₃ having a short-time rating with a thin winding can be used. Therefore, the reactor L ₃ can be greatly reduced in size compared with the conventional power supply circuit. Also in the normal current, the reactor L ₃ is not interposed between the first smoothing capacitor C ₁ and the inverter because it is bypassed by the first bypass diode D _20. Therefore the normal, the first smoothing capacitor C ₁ may also play a ripple current of the inverter. For this reason, the third smoothing capacitor C ₃ only needs to withstand the step-up chopper and the ripple of the inverter during the voltage sag period, a reactor using a thin winding capable of short-time rating can be applied, and the power supply device can be miniaturized. .

More preferably, the anode of the second bypass diode D ₂₁ is connected to the connection point between the _first smoothing reactor L ₁ and the backflow prevention diode D ₅ of the boost converter, while the cathode of the second bypass diode D ₂₁ is connected. the may be connected to the connection point between the diode D ₁₀ and the smoothing capacitor C _3.
The second bypass diode D ₂₁ is a part of the current flowing through the path of the first smoothing reactor L ₁ → the backflow preventing diode D ₅ → the first smoothing capacitor C ₁ → the first bypass diode D _20. Is directly led to the _third smoothing capacitor C ₃ . With this configuration, in the power supply device according to Embodiment 1 of the present invention, the current that has passed through the two diodes of the backflow prevention diode D ₅ and the first bypass diode D ₂₀ is the second bypass diode. Since only D ₂₁ is passed, loss can be further reduced, which is preferable.

Incidentally, in the electric power supply apparatus according to a first embodiment of the present invention, the smoothing reactor L ₂ provided on the load R _L side can be used as the minimum inductance value as described above, at the start of power supply , It is necessary to perform a so-called soft start in which the DC output voltage _Vout across the second capacitor is gradually raised. This is to suppress the rush current to the capacitor component included in the second smoothing capacitor C ₂ and the load R _L.

  Therefore, only at this time, it is necessary to reduce the inverter duty ratio so that the ripple current flowing through the second smoothing reactor may be increased. If this becomes a problem, the inverter may be operated at a frequency higher than the normal operating frequency only at the time of startup. In other words, the amplitude of the ripple current is inversely proportional to the frequency, so that ripple can be suppressed. However, at this time, although there is an increase in loss such as switching loss proportional to the frequency, it is limited to a very short time during start-up, so that it does not matter in terms of both efficiency and component size.

  Note that if the AC input voltage remains (not 0V) even at the time of a momentary drop, the boost converter is continuously operated and a part of the electric power is taken from the AC input, thereby shortening the operation time of the boost chopper. It is possible to extend the dip compensation time.

Next, a power supply device according to Embodiment 2 of the present invention will be described with reference to FIG. Power supply of this second embodiment is the place different from the power supply apparatus of the first embodiment described above lies in that a capacitor C ₂₀ in parallel to the first bypass diode D _20.
In the power supply device according to Embodiment 2 of the present invention configured as described above, the first smoothing capacitor C ₁ and the third smoothing capacitor C ₃ are connected in an AC manner via the parallel capacitor C ₂₀ , as if the first This can be regarded as equivalent to connecting the smoothing capacitor C ₁ and the third smoothing capacitor C ₃ in parallel. Further, even if the first bypass diode D ₂₀ is turned off for a moment due to the influence of the ripple current, etc., the first smoothing capacitor C ₁ and the third smoothing capacitor C ₁ are connected by the capacitor C ₂₀ connected in parallel with the bypass diode D ₂₀ . The smoothing capacitor C ₃ is short-circuited in an alternating manner.

Therefore, in the power supply device according to the second embodiment of the present invention, the combined capacitance of the two smoothing capacitors C ₁ and C ₃ must be less than the capacitance of the smoothing capacitor C ₃ in the power supply device of the first embodiment described above. The electrostatic capacities of the first and third smoothing capacitors C ₁ and C ₃ can be reduced without lowering the ripple removal rate, and the overall size of the power supply device can be reduced.

  Note that the power supply device according to the second embodiment also operates the boost converter continuously when the AC input voltage remains even at the time of a sag, as in the first embodiment described above. By taking from the input, the operation time of the step-up chopper can be shortened, or the sag compensation time can be extended.

Next, a power supply device according to Embodiment 3 of the present invention will be described with reference to FIG. The difference between the power supply device of the third embodiment and the power supply devices of the first and second embodiments is that the circuit constituting the boost converter is modified. That, L ₁₀ in FIG. 3 is a reactor which is interposed in the AC power supply side. In the third embodiment, the rectifying diodes D ₂ and D ₄ in the power supply device shown in FIGS. 1 and ₂ are replaced with MOSFETs (Q ₇ and Q ₈ ), respectively.

Also instead of the second bypass diode D ₂₁ shown in FIGS. 1 and 2, first between the drain input side of the connected connection points g and inverter anode and MOSFET rectifier diode D ₁ (Q ₇₎ 3 bypass diode D ₃₀ is connected, and a fourth bypass diode D ₃₁ is connected between the connection point h where the anode of rectifier diode D ₃ and the drain of MOSFET (Q ₈ ) are connected to the input side of the inverter. To do.

Power supply unit according to Example 3 of the present invention constructed as described above, in the positive and negative half cycle of the AC power source 1 and a series circuit of a rectifying diode D ₁ and MOSFET (Q _7), a rectifying diode D ₃ and The series circuit of the MOSFET (Q ₈ ) is alternated to perform an operation equivalent to that of the series circuit constituted by the MOSFET (Q ₁ ) and the backflow prevention diode D ₅ shown in FIGS. For this reason, each series circuit is provided with bypass diodes D ₃₀ and D ₃₁ . In addition, since the operation, effect, and the like of the third embodiment are the same as those of the first embodiment, description thereof is omitted.

Next, a power supply device according to Embodiment 4 of the present invention will be described with reference to FIG. The difference between the power supply device of the fourth embodiment and the power supply devices of the first to third embodiments is that the configuration of the boost converter is changed. Specifically, a series circuit in which two MOSFETs (Q ₉ and Q ₁₀ ) are connected in series and a series circuit in which two rectifying diodes D ₃ and D ₄ are connected in series are connected in parallel. Bypass diodes (D ₃₀ , D ₃₁ ) from the connection point j between the two MOSFETs (Q ₉ , Q ₁₀ ) and the connection point k between the two rectifying diodes (D ₃ , D ₄ ) to the input of the inverter, respectively. ).

In the power supply device according to the fourth embodiment of the present invention configured as described above, the MOSFET (Q ₉ ) is turned on every half cycle in which the voltage polarity of the AC power supply 1 is inverted, and the AC is supplied via the rectifying diode D _4. Control is performed so that the current path returns to the power supply 1 and the MOSFET (Q ₁₀ ) is turned on every remaining half cycle, and the current path returns to the AC power supply 1 via the rectifying diode D ₃ . By controlling in this way, a DC voltage similar to that of the step-up converter of the third embodiment described above can be obtained.

Further the power supply device according to the fourth embodiment, the counter electromotive force generated across the reactor L ₁₀ compensates for the voltage sag is superimposed to the voltage of the AC power supply 1. This compensated voltage is applied directly to the inverter via the bypass diodes D ₃₀ and D ₃₁ . For this reason, the power supply device according to the fourth embodiment is directly supplied to the inverter without passing through the semiconductor elements (rectifier diodes D ₃ and D ₄ and MOSFETs (Q ₉ and Q ₁₀ )) constituting the boost converter. Loss can be reduced more effectively.

  Note that the power supply device according to the fourth embodiment operates the boost converter continuously when the AC input voltage remains even at the time of a sag as in the first to third embodiments described above, and a part of power By taking from the AC input, it is possible to shorten the operation time of the step-up chopper or extend the instantaneous voltage drop compensation time.

Next, a power supply device according to Embodiment 5 of the present invention will be described with reference to FIG. The difference between the power supply device of the fifth embodiment and the power supply devices of the first to fourth embodiments described above is that the configuration of the boost converter is further changed. That is, in the power supply device according to the fifth embodiment, the connection point m of each rectifying diode in two series circuits including the two rectifying diodes D ₁ and D ₂ and the rectifying diodes D ₃ and D ₄ constituting the boost converter. , N and diodes D ₄₀ and D ₄₁ are respectively provided in the path from the source to the drain of the MOSFET (Q ₂₀ ) whose source is grounded.

  Even the power supply device according to the fifth embodiment of the present invention configured as described above can achieve the same effects as those of the first to fourth embodiments described above.

Next, a power supply device according to Embodiment 5 of the present invention will be described with reference to FIG. The power supply device according to the fourth embodiment is different from the power supply devices according to the first to fifth embodiments described above in that a switch SW for short-circuiting the power supply line is provided on the power supply line on the AC input side of the boost converter.
Here, as the switch SW, for example, a bidirectional switch as shown in FIG. 7 may be applied. FIG. 7A shows a switch in which two semiconductor switches (for example, MOSFETs (Q ₃₀ , Q ₃₁ )) are connected in series so that their conduction directions are opposite to each other. This switch turns on the MOSFET (Q ₃₀ ) when the potential at the terminal a is higher than the potential at the terminal b. Then, the current flows from terminal a → MOSFET (Q ₃₀ ) → parasitic diode (D ₄₁ ) of MOSFET (Q ₃₁ ) → terminal b. Conversely, when the potential of the terminal b is higher than the potential of the terminal a, when the MOSFET (Q ₃₁ ) is turned on, the current is changed from the terminal a → the MOSFET (Q ₃₁ ) → the parasitic diode (D ₄₀ ) of the MOSFET (Q ₃₀ ) → the terminal. It flows with a.

When an IGBT is used in place of the MOSFETs (Q ₃₀ , Q ₃₁ ), two IGBTs (Q ₃₂ , Q ₃₃ ) are connected in series so that their conduction directions are opposite to each other as shown in FIG. 7B. In addition, a diode (D ₄₂ , D ₄₃ ) may be connected in antiparallel to each IGBT.
Further, as shown in FIG. 7C, a bridge circuit is constituted by four rectifying diodes (D _{50 to} D ₅₃ ), and the (cathode) connection point of the rectifying diodes D ₅₀ and D ₅₂ and the IGBT (Q ₄₀ ). The collector is connected to the (anode) connection point of the rectifying diodes D ₅₁ and D ₅₃ and the emitter of the IGBT (Q ₄₀ ) to form a switch, and the on / off of the IGBT (Q ₄₀ ) is controlled.

That is, when the IGBT (Q ₃₀ ) is turned on, this switch flows as follows: rectifier diode D ₅₀ → IGBT (Q ₄₀ ) → rectifier diode D ₅₃ → terminal b when the potential of terminal a is higher than the potential of terminal b. . Conversely, when the potential of the terminal b is higher than the potential of the terminal a, when the IGBT (Q ₃₀ ) is turned on, the current flows from the terminal b → rectifier diode D ₅₂ → IGBT (Q ₄₀ ) → rectifier diode D ₅₁ → terminal a And flow.

Alternatively, as shown in FIG. 7 (d), a reverse blocking type switching element (for example, IGBT) may be connected in antiparallel to constitute a switch. In this switch, when the potential of the terminal a is higher than the potential of the terminal b, when the IGBT (Q ₅₀ ) is turned on, a current flows from the terminal a → IGBT (Q ₅₀ ) → terminal b. Conversely, when the potential of the terminal b is higher than the potential of the terminal a, when the IGBT (Q ₅₁ ) is turned on, a current flows from the terminal b → IGBT (Q ₅₁ ) → the terminal a.

  Even the power supply device according to the sixth embodiment of the present invention configured as described above can achieve the same effects as those of the first to fifth embodiments. That is, if the AC input voltage remains even at the time of a momentary drop, the boost converter is continuously operated and a part of the electric power is taken from the AC input to shorten the operation time of the boost chopper, or It is possible to extend the sag compensation time.

Next, a power supply device according to Embodiment 7 of the present invention will be described with reference to FIG. When the power supply device of this seventh embodiment is different from the power source apparatus according to Embodiment 1-6 described above is in parallel with the smoothing capacitor C ₁ provided in the DC intermediate circuit, the charging circuit unit 10 and the secondary battery BAT An uninterruptible power supply is configured by connecting series circuits.
In the charging circuit unit 10 according to the present embodiment, a bypass diode D _d that supplies power stored in the secondary battery BAT to a load is connected in parallel to form a charge / discharge control unit. As the secondary battery BAT, a chargeable / dischargeable device such as a lead storage battery, an alkaline storage battery, a lithium ion secondary battery, or an electric double layer capacitor is used.

In the power supply device according to the seventh embodiment configured as described above, when power is supplied from the AC power supply 1 (normal time), the charging circuit unit 10 charges the secondary battery BAT and stores the power. Specifically, a circuit such as a chopper is applied to the charging circuit unit 10. Since the charging current of the secondary battery BAT during normal operation is small, the charging circuit unit 10 may be configured with a small circuit.
And when cut off the power supply from the AC power supply 1, the power stored in the battery BAT is a smoothing capacitor C ₁ via the bypass diode D _d, i.e. is supplied to the DC intermediate circuit. The direct current supplied to the direct current intermediate circuit is boosted by the boost chopper circuit described above and maintains the value of the direct current voltage _Ed2 .

Note that the voltage of the secondary battery BAT in Example 7 may be lower than the voltage E _d1 across the smoothing capacitor C ₁ . For example, when the voltage of the secondary battery BAT is lower than the DC voltage E _d1 , the charging circuit unit 10 steps down the DC voltage E _d1 to charge the secondary battery BAT. When the secondary battery BAT is discharged, the output voltage of the secondary battery BAT may be boosted by the boost chopper described above and controlled so that the output voltage E _d2 becomes a desired value.

The power supply device in Example 7 described above does not switch the MOSFET (Q ₆ ) during normal operation. DC applied to this for the step-up chopper is provided to be bypassed inverter by the first bypass diode D _20. Here, the DC voltages E _d1 and E _{d2 at} both ends of the secondary battery BAT and the third smoothing capacitor C ₃ are DC voltages that are smoothed both during normal times and during power outages. For this reason, the first bypass diode D ₂₀ does not need the performance of rectifying the high frequency, and may be a low speed diode. The forward voltage of the low-speed diode is lower (about 1/2) than that of the high-speed diode, and no current flows through the reactor L ₃ , so that the loss can be greatly reduced as compared with the conventional power supply circuit. In addition, Example 7 can obtain the same effect as Example 1 described above even during power failure compensation, but the description thereof is omitted because it is as described in Example 1.

Alternatively, in the seventh embodiment shown in FIG. 8, a series circuit of the secondary battery BAT and the charging circuit unit 10 is connected in parallel with the smoothing capacitor C _{1 of} FIG. 1 showing the power supply device according to the first embodiment of the present invention. those, but may have a configuration that is connected in parallel with the smoothing capacitor C ₁ according to the series circuit in Figures 2-6 showing an embodiment 2-6.
In the power supply device according to the seventh embodiment, for example, a plurality of power conversion units (DC / DC converters) 20 may be connected in parallel as a load as shown in FIG. As described above, the power conversion unit 20 includes an inverter composed of four MOSFETs (Q _{2 to} Q ₅ ), a transformer T connected to the output of the inverter to transform a voltage, and an output side of the transformer T A bridge rectifier circuit (converter) composed of four rectifier diodes (D _{6 to} D ₉ ) connected to the converter, and a smoothing circuit including a reactor L ₂ and a smoothing capacitor C ₂ for smoothing the output of the converter. . A load R _L is connected in parallel with the smoothing capacitor C ₂ . In addition, you may comprise the power converter 20 so that only an inverter may be combined or an inverter and the transformer T may be combined and an alternating current may be output.

  The power supply device configured as described above and supplying power to a load in which a large number of power conversion units 20 are connected in parallel shares the secondary battery BAT among the plurality of power conversion units 20. The maintenance and management of the secondary battery BAT is facilitated as compared with the conventional system having each secondary battery. In addition, in a conventional configuration in which a DC / DC converter has a converter that converts an AC voltage to a DC voltage on the input side, for example, as a plurality of power conversion units, when a secondary battery is shared, the output of each converter is unbalanced (Cross current) may occur. However, in the power supply device according to Example 7 of the present invention, only the first converter is configured to charge the secondary battery BAT, so that no cross current occurs between the converters. It is extremely effective in practical use.

Thus, the power supply apparatus of the present invention can minimize the increase in loss during normal operation due to the instantaneous voltage drop compensation function or the power supply function during a power failure (power failure compensation function), and the high efficiency of the device. There are significant practical effects such as realization and miniaturization.
The power supply device of the present invention is not limited to the above-described embodiment, and various modifications may be made without departing from the scope of the present invention.

1 AC power supply C ₁ smoothing capacitor C ₁ , C ₂ , C ₃ smoothing capacitor C ₂₀ parallel capacitor D ₁ -D ₄ , D ₆ -D ₉ , D ₄₀ -D ₄₃ Rectifier diode D ₅ , D ₁₀ Backflow prevention diode D ₂₀ D ₂₁ , D ₃₀ , D ₃₁ Bypass diode D ₄₀ , D ₄₁ Diode L ₁ , L ₂ Smoothing reactor L ₃ , L ₁₀ Reactor R _L Load SW Switch T Transformer

Claims (6)

A first converter that converts the input AC voltage into a DC voltage while controlling the power factor and outputs the DC voltage;
A step-up chopper that boosts and outputs the DC voltage output by the first converter;
A first smoothing capacitor which is provided on the input side of the boost chopper and reduces a ripple included in the DC voltage output from the first converter to a predetermined level or less;
A first bypass diode that applies a DC voltage input to the boost chopper to the output of the boost chopper by bypassing the boost chopper;
A third smoothing capacitor connected to the output side of the boost chopper;
An isolated DC / DC converter that outputs the DC voltage boosted by the boost chopper after being insulated by a transformer ;
With
The first converter includes a diode bridge circuit that rectifies the AC voltage, a series circuit connected in order of a reactor and a switching element between DC output terminals of the diode bridge circuit, and a connection point between the reactor and the switching element. And a backflow prevention diode connected between the first smoothing capacitor and a second bypass diode connected between a connection point of the reactor and the switching element and an output of the boost chopper. A power supply device comprising: The power supply device according to claim 1,
The insulated DC / DC converter is provided with one or more inverters connected to the output side of the boost chopper and converting a DC voltage boosted by the boost chopper into an AC voltage.   The power supply device according to claim 1, wherein the first bypass diode further includes a parallel capacitor connected in parallel. The first bypass diode further includes a parallel capacitor connected in parallel;
The power supply apparatus according to claim 2, wherein the parallel capacitor has a sufficiently low impedance with respect to a switching frequency component of the inverter. The power supply device according to any one of claims 3 to 4,
The insulated DC / DC converter is
And a transformer connected to the output side of the inverter;
A second converter that converts an alternating voltage output from the transformer into a direct current voltage and outputs the converted voltage;
A second smoothing reactor for smoothing the DC voltage output by the second converter,
The inverter operates at a higher switching frequency than that during normal operation at the time of startup, and suppresses a ripple current flowing in the second smoothing reactor. The power supply device according to any one of claims 1 to 5,
A series circuit in which a secondary battery and a charge / discharge control unit for charging / discharging the secondary battery are connected in series is connected in parallel with the first smoothing capacitor,
The charge / discharge control unit, when the input AC voltage exceeds a predetermined voltage value, charges the secondary battery and stores electric power,
When the AC voltage falls below a predetermined voltage value, the power stored in the secondary battery is discharged and supplied to a load.

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