JP4882706B2 - Device for measuring input / output characteristics of analog circuit including operational amplifier and method for measuring input / output characteristics of analog circuit including operational amplifier - Google Patents

Description

  The present invention relates to an input / output characteristic measuring device for an analog circuit including an operational amplifier incorporated in a voltage converter device for a vehicle, and in particular, a resistance value for adjusting an offset and gain of an output signal of the operational amplifier to a target value. The present invention relates to an input / output characteristic measuring apparatus for an analog circuit including an operational amplifier for deleting an adjustment circuit element provided in advance based on the resistance value, and an input / output characteristic measuring method for an analog circuit including an operational amplifier.

  In recent years, in vehicle equipment, as a measure for improving efficiency and saving energy, the vehicle drive system 10 having the electric motor 11 that generates the driving force shown in FIG. 8 includes a power source 12, a step-up / down converter 13, and an inverter 14. It is. However, the electric motor 11 is a three-phase motor when the vehicle is driven, but becomes a generator when the vehicle is braked. An arrow Y1 indicates the direction of energy that flows when the vehicle is driven, and an arrow Y2 indicates the direction of energy that flows when the vehicle is braked.

The power source 12 includes a power supply voltage from an overhead wire or a battery connected in series.
The step-up / down converter 13 boosts the voltage V _L (eg, 280 V) of the power source 12 to a voltage V _H (eg, 750 V) suitable for driving the motor 11 when the vehicle is driven, and serves as a motor that serves as a generator when the vehicle is braked. The voltage V _H (for example, 750 V) generated from the voltage 11 is stepped down to the voltage V _L (for example, 280 V) of the power supply circuit to perform a power regeneration operation.

The inverter 14 performs ON / OFF control of switching elements in the inverter 14 so that a current flows to each phase of the three-phase motor 11 from the voltage V _H boosted by the step-up / down converter 13 when the vehicle is driven. The speed of the vehicle is changed according to the frequency. Further, at the time of vehicle braking, the switching element is ON / OFF controlled in synchronism with the voltage generated in each phase of the motor 11, so-called rectification operation is performed, and the DC voltage is regenerated.

  Next, a detailed configuration of the step-up / down converter 13 is shown in FIG. 9 and will be described. The step-up / down converter 13 is roughly configured to include a reactor 16, a capacitor 17, two switching elements 21 and 22, and control circuits 23 a and 23 b that control the switching elements 21 and 22. As shown in FIG. 9, the switching elements 21 and 22 of the drive system of recent vehicle equipment include a diode 27 (or 28) in parallel between the IGBT 25 (or 26) and the emitter / collector of the IGBT 25 (or 26). Is connected. That is, the diode 27 (or 28) is connected so that a current flows in a direction opposite to the current flowing through the IGBT 25 (or 26).

The principle of the step-up / step-down operation of the step-up / down converter 13 will be described. Further, FIG. 10 shows a waveform of a current flowing through the reactor 16 at the time of boosting.
First, the boosting operation will be described. As shown in time t0 to t1, time t2 to t3, and time t4 to t5 in FIG. 10, when the IGBT 25 of the switching element 21 is turned on (conductive), the current I flows through the reactor 16, and the reactor 16 (inductance L ) energy ^LI 2/2 is stored in the.

On the other hand, when the IGBT 25 of the switching element 21 is turned off (non-conducting) between the times t1 and t2, between the times t3 and t4, and after the time t5, the current I flows through the diode 28 of the switching element 22 and the reactor 16 Is stored in the capacitor 17.
Next, the step-down operation will be described. IGBT26 is ON of the switching element 22 (conductive), the current I flows in the reactor 16, the energy of the ^LI 2/2 is stored in the reactor 16.

On the other hand, when the IGBT 26 of the switching element 22 is turned off (non-conducting), a current flows through the diode 27 of the switching element 21, and the energy stored in the reactor 16 is regenerated to the power supply 12.
Thus, by changing the ON time (ON duty) of the switching element 21 or 22, the voltage of the step-up / step-down can be adjusted, and an approximate value can be obtained by the following equation.
V _L / V _H = ON duty (%)
V _L : power supply voltage V _H : voltage after boosting ON duty: ratio of conduction period to switching cycle of switching element 21 or 22.
However, the actual variation of the load, since the power supply voltage, etc. variations, monitors the voltage V _H after buck, so that the target value, the control of the ON time of the switching elements 21, 22 (ON-duty) I do.

  FIG. 11 is a block diagram of the step-up / down converter IPM 30. The IPM 30 is broadly divided into an upper arm switching unit 31, a lower arm switching unit 32, and a control unit 23. The IPM 30 includes the switching units 31 and 32 on the high voltage circuit side, and the low voltage circuit side. It is necessary to electrically insulate from the control unit 23, and for this reason, signals are exchanged using photocouplers 34, 35, 36, 37, 38, a pulse transformer (not shown), and the like.

  The switching unit 31 of the upper arm includes a temperature detecting diode 40 embedded in the same chip as the switching element 22 described above, and a temperature between two resistors 41 and 42 connected in series between the emitter of the IGBT 26 and the ground. An IGBT protection circuit 43 connected to the anode side of the detection diode 40, a gate driver 44 connected between the output side of the IGBT protection circuit 43 and the gate side of the IGBT 26, and the anode of the temperature detection diode 40 And an IGBT chip temperature detection unit 45 connected to the side.

The switching unit 32 of the lower arm includes a temperature detection diode 50 embedded in the same chip as the switching element 21 described above, and between two resistors 51 and 52 connected in series between the emitter of the IGBT 25 and the ground. An IGBT protection circuit 53 connected to the anode side of the temperature detection diode 50, a gate driver 54 connected between the output side of the IGBT protection circuit 53 and the gate side of the IGBT 25, and the temperature detection diode 50 the IGBT chip temperature detecting unit 55 connected to the anode side, it is constituted by a VH detection circuit 56 for detecting the voltage V _H of the boosted.

The VH detection circuit 56 includes a voltage dividing circuit 57 that divides the input voltage V _H , a level adjustment circuit 58 that adjusts the level of the voltage divided by the voltage dividing circuit 57, and a triangular wave generator that generates a triangular wave 59 and a comparator 60 that compares the triangular wave with the voltage after level adjustment, and outputs a voltage of “L” or “H” level obtained as a result of the comparison to the photocoupler 38.

The control unit 23 smoothes a signal “1” corresponding to “0” or “H” corresponding to “L” from the photocoupler 38 and converts it to a DC level, and this LPF (Low Pass Filter) 62 The VH comparator 63 that compares the DC level from the LPF 62 with the step-up / step-down command value, and the boosted voltage V _H is a predetermined voltage value corresponding to the step-up / step-down command value according to the comparison result of the VH comparator 63. A gate signal generator 64 for outputting a gate signal to the photocouplers 34 and 36 is provided.

In the IPM 30 having such a configuration, the target portion of the present invention is that the temperature detection diodes 40 and 50 embedded in the same chip as the switching elements 22 and 21 are used to control the operating state of the IPM 30 as a system. The IGBT chip temperature detectors 45 and 55 measure the chip temperature of the IGBTs 26 and 25 using the VF voltage.
The IGBT chip temperature detectors 45 and 55 are represented by an internal block diagram in FIG. 12 as a representative of the IGBT chip temperature detector 45 of the switching unit 31 of the upper arm and will be described.

  The IGBT chip temperature detection unit 45 has a constant current source 70 connected to the anode side of the temperature detection diode 40 on the high voltage circuit side, and a + input connected between the constant current source 70 and the temperature detection diode 40. A buffer circuit (simply referred to as a buffer) 71 using the operational amplifier, a level converter 77, a triangular wave generator 78, a comparator 79 connected to the output side of the triangular wave generator 78 and the level converter 77, and this comparator A FET (Field Effect Transistor) 81 having a gate connected to the output side of 79 via a resistor 80 and a drain connected to the photocoupler 35 of the digital-analog converter 90 via a resistor 82 is provided. Has been.

The level converter 77 includes an operational amplifier 73 having a negative input connected to the output of the buffer circuit 71 via a resistor 72, a resistor 74 connected between the input and output of the operational amplifier 73, a first power supply Vcc1, and the like. Resistors 75 and 76 connected between the ground and the + input of the operational amplifier 73 are provided.
The digital / analog converter 90 includes a photocoupler 35, a binarization circuit 91, a buffer circuit 92, and an LPF circuit (low-pass filter) 93.

  The photocoupler 35 is connected between the first power supply Vcc1 and the FET 81 via the resistor 82, and a light emitting diode 85 having a resistor 84 connected in parallel, and a light receiving diode 87 that receives light emitted from the light emitting diode 85. The light receiving diode 87 is connected between the base of the transistor 88 and the second power source Vcc2, and the resistor 89 is connected between the cathode of the light receiving diode 87 and the collector of the transistor 88. Has been.

The binarization circuit 91 is connected to the emitter of the transistor 88 of the photocoupler 35. The buffer circuit 92 is an operational amplifier in which the + input is connected to the output side of the binarization circuit 91 and the -input and the output are connected. And an LPF circuit 93 is connected to the output of the buffer circuit 92.
When the temperature of the IGBT 26 is measured by the IGBT chip temperature detecting unit 45 as described above, a constant current is supplied from the constant current source 70 to the temperature detecting diode 40 embedded in the same chip as the IGBT 26. As a result, the forward voltage drop VF (also referred to as VF voltage signal) of the temperature detecting diode 40 becomes a voltage value proportional to the temperature as shown in FIG. In other words, when the chip temperature of the temperature detecting diode 40 is 165 ° C., for example, VF = 1.5V, and for example, 25 ° C., VF = 2.0V is obtained.

FIG. 14 shows details of the VF / PWM conversion circuit 100 including the buffer circuit 71, the level converter 77, the triangular wave generator 78, and the comparator 79.
The triangular wave generator 78 includes resistors R21, R22, R23, which are connected as illustrated between the comparator 101 and the operational amplifier 102, and the-, + input terminals and output terminals of these 101, 102, the power supply Vcc1, and the ground. R24, R25, R26 and a capacitor C11 are provided. The same components as those in FIG. 12 will be described using the same reference numerals.

A triangular wave signal is generated from a triangular wave generator 78 between a predetermined upper limit value and a lower limit value.
The forward voltage drop VF of the temperature detection diode 40 is converted in impedance by the buffer circuit 71, and then the level converter 77 matches the upper limit value of the triangular wave signal with the high-temperature (eg, 165 ° C.) side VF. Amplification and level addition / subtraction are performed so that the lower limit value of the signal matches the low temperature (eg, 25 ° C.) side VF.
That is, the level converter 77 expands the width of the VF voltage signal (gain adjustment) so that the width level of the VF voltage signal matches the level (amplitude) of the upper and lower limits of the triangular wave signal. The upper and lower levels of the level of the expanded VF voltage signal coincide with the upper and lower positions of the triangular wave (offset adjustment). The gain and offset are adjusted as follows.

  In FIG. 14, the voltage of the power supply Vcc1 is divided by resistors R11 and R12 to be the + input of the operational amplifier 73, and the offset amount is determined by the resistor R13 connected between the power supply Vcc1 and the -input of the operational amplifier 73. The gain of the operational amplifier 73 is determined by the resistor R14 connected between the output of the buffer circuit 71 and the negative input of the operational amplifier 73 and the resistor R15 connected between the negative input and the output of the operational amplifier 73.

After this level adjustment, the comparator 79 at the subsequent stage compares the output voltage Vlev of the level converter 77 with the output voltage Vtri of the triangular wave generator. If Vlev> Vtri, the output of the comparator 79 is “L”. When Vlev <Vtri, “H” is set.
The duty of the output pulse of the comparator 79 generated by this operation is proportional to the VF voltage signal. For example, the duty 0% is a low temperature (eg, 25 ° C.) side VF, and 100% is a high temperature (eg, 165 ° C.) side VF. Are transmitted from the switching units 31 and 32 to the binarization circuit 91 of the control unit 23 as a PWM signal.

  In the binarization circuit 91, the PWM signal is generated with a voltage (binarization signal V 1 / V 2) of V 1 when the duty of the PWM signal is 0% and V 2 when the duty of the PWM signal is 100%. When this binarized signal V1 / V2 is impedance-converted by the buffer circuit 92 and then smoothed by the LPF circuit 93 and converted to a direct current level, it is insulated from each arm corresponding to the voltage VF across the temperature detection diode 40. An output voltage (IGBT chip temperature voltage signal) Vout can be obtained.

  The voltage signal Vout proportional to the IGBT chip temperature obtained in this way is transmitted to a higher system (not shown) of the buck-boost converter 13, and the system constantly detects the temperature of the IGBTs 25 and 26, for example, When the IGBT chip temperature exceeds the predetermined temperature T1, the switching frequency is halved, and when the IGBT chip temperature exceeds the predetermined temperature T2, the protection function for stopping the switching (step-up / step-down operation) is activated.

  Since the operation of this protection function affects the driving of the vehicle, the chip temperatures of the IGBTs 25 and 26 must be accurately measured, and an accuracy of approximately ± 5% is required. The error factors at the time of measuring the chip temperature can be broadly divided into variations in the forward voltage drop VF value and temperature coefficient of the temperature detection diodes 40 and 50 embedded in the IGBT chip, the buffer circuit 71, the level converter 77, There are two types of circuit system variations including a triangular wave generator 78, a photocoupler (PWM signal isolation transmission circuit) 35, a binarization circuit 91, a buffer circuit 92, and an LPF circuit 93.

The variations in the VF values of the temperature detection diodes 40 and 50 are mainly caused by the semiconductor process. Therefore, for example, ± 3% of 60% of the total allowable error of ± 5% is a variation in the VF value. In the circuit system, it is necessary to suppress the error to ± 2%. Therefore, each circuit is required to have a performance with an error of ± 0.5%.
For this reason, it is necessary to use highly accurate circuit elements such as resistance elements, constant voltage elements, operational amplifiers, etc., but the environmental temperature of the vehicle is assured to operate in a wide range of −40 to + 105 ° C., and high reliability for vehicles. And from the point that prompt response when a complaint is generated is required, it must be selected from an in-vehicle compatible IC.

In the VF / PWM conversion circuit 100 shown in FIG. 14, the forward direction proportional to the temperature generated in the temperature detection diode 40 by the constant current IF supplied from the constant current source 70 (not shown in FIG. 14, see FIG. 12). The drop voltage (VF = 1.5 V when the chip temperature is 165 ° C., VF = 2.0 V when the chip temperature is 25 ° C.) is impedance-converted by the buffer circuit 71 and supplied to the level converter 77.
Since the potential of the power supply Vcc1 is fixed to the potential Vcc11 obtained by dividing the potential of the power supply Vcc1 by the resistors R11 and R12 at the + input terminal of the operational amplifier 73 of the level converter 77, the output voltage of the operational amplifier 73 is expressed by the following equation (1). Is done.

  On the other hand, the upper limit value Vsu and the lower limit value Vsd of the triangular wave signal from the triangular wave generator 78 are expressed by the following equations (2) and (3). The power source Vcc1 is fixed to the potential Vcc12 obtained by dividing the power supply Vcc1 by the resistors R21 and R22 at the negative input terminal of the comparator 101.

However, V _ic3LOW is an “L” level output of the comparator 101. “//” is a simplified notation of the combined value when the resistors shown before and after that are connected in parallel. For example, “R ₂₄ // R ₂₅ ” in the equation (3) is R ₂₄ and R ₂₅ . The combined resistance value when is connected in parallel. The same applies to the following.
Such a triangular wave of the upper limit value Vsu and lower limit value Vsd of the output signal of the triangular wave generator 78 and the output of the level converter 77 are compared by the comparator 79 and expressed by the following equations (4) to (6). A PWM signal having a pulse width proportional to the temperature is generated.

  This PWM signal is insulated by the photocoupler 35 of the digital / analog converter 90 whose detailed configuration is shown in FIG. 15, and then transmitted to the binarization circuit 91, the buffer circuit 92, and the LPF circuit 93. The relationship between the duty of the PWM signal and the output of the LPF circuit 93 (IGBT chip temperature voltage signal Vout) is expressed by the following equation (7).

_{However, V ce} is the voltage between the collector and emitter of the saturation Tr600, is generally 0.15V. V _LPF is an output of the LPF circuit 93.
In these formulas (1) to (7), if a high-precision resistor of ± 0.1% is used, the error in the output of the LPF circuit 93 depends on variations in the power supplies Vcc1 and Vcc2.

In particular, since Vcc1 is used in a circuit that handles a signal having a full span of 500 mV, a highly stable and highly accurate voltage source is required, and a highly accurate shunt regulator must be used. Further, since Vcc2 handles a signal having a full span of 4V, higher accuracy than Vcc1 is not required.
Variations in the potential Vcc1 when the shunt regulator is used as the power supply Vcc1 and the potential Vcc2 when the standard regulator is used as the power supply Vcc2 can be treated as a normal distribution.

In the voltage variation of these reference voltage source is above formula _{(1) ~ (7),} V cc1, the value of _{V cc2} is changed, the output of the LPF circuit 93 in proportion to the temperature, the temperature range is the output voltage at 130 ° C. The span assigned to the width of 4V and the offset assigned to the output of 4.5V at a temperature of 25 ° C. will be affected.
The effect on the output of the LPF circuit 93 in the case of varying the aforementioned _{V cc1} 16 and _17, 18 and 19 the effect on the output of the LPF circuit 93 in the case of varying the _{V cc2} .

V _cc1, if the distribution of the variation in the output voltage of the _{V cc2} was a normal distribution, in the range from the center value of the distribution to the 3 [sigma], the error and interval in cumulative distribution ratio caused IGBT chip temperature voltage signal (LPF output) Vout Statistical calculations were made. As a result, at 1.2σ or less (77% of the population), the temperature measurement by the circuit can be suppressed to a maximum of ± 2% or less, but the remaining 23% exceeds ± 2%. In the illustrated level converter 77, the resistance value must be changed by using the resistor R13 for offset adjustment and R15 for gain adjustment.

For this reason, with regard to the resistors R13 and R15, an element having a low resistance value is mounted in advance so that it can be adjusted within ± 5σ, and this is performed by partially cutting the resistance pattern with a laser trimming device. Match the target adjustment value.
In order to obtain this target value, for example, a voltage of 1.607V corresponding to a chip temperature of 135 ° C. and 1.946V corresponding to 40 ° C. are connected to terminals connected to temperature detection diodes 40 and 50 built in the IGBT on the circuit board. Is input as a simulated VF signal and calculated from two LPF output signal levels obtained at that time, or a method of feeding back an error with respect to a target value of the LPF output signal while trimming a resistance value with a laser trimming device . Apart from this, there is also a technique in which the resistors R13 and R15 are not mounted and are mounted after the adjustment resistance value is determined by a test.

As an input / output characteristic adjustment method of an analog circuit (level converter 77) using this type of conventional operational amplifier, there are methods described in Patent Documents 1 and 2, for example.
Japanese Patent Laid-Open No. 2005-2909 Japanese Patent Laid-Open No. 2004-279324

  By the way, in the level converter 77 corresponding to an analog circuit using a conventional operational amplifier, as described above, an element having a low resistance value is mounted in advance, and the resistance pattern is partially applied by a laser trimming apparatus. By cutting, it matches the target adjustment value. However, in this trimming process, since the adjustment resistance value is lower than the original value, it is necessary to perform trimming of the resistance value for the total number of products. For 1.2σ or less (77% of the population), Although the adjustment of the resistance value is not necessary, the trimming man-hour is inevitably generated, and the circuit manufacturing cost is increased accordingly.

In the case of cutting with a thin laser beam, the resistance pattern is partially cut, and after this trimming, a protective film is coated on the resistance element, but this deteriorates due to the heat cycle during use, and moisture in the air adheres. Since the resistance value may change, the reliability is low accordingly.
Furthermore, the method of performing the post-mounting when the adjustment resistance value described above is determined is that the circuit board and the initial mounted circuit element are subjected to high-temperature heating twice because of the post-mounting, thereby reducing the reliability of the circuit element. To do.

  In order to eliminate these drawbacks, there is a method in which a plurality of resistors are connected in advance to the input / output side of the operational amplifier, and these resistors are disconnected so that the offset and gain of the output signal of the operational amplifier become target values. Conceivable. However, this method cannot be adjusted while reflecting the tendency by changing the resistance value stepwise as in the above trimming method. Therefore, the resistance value (adjustment value) for adjusting the offset and gain is not possible. However, there is a problem that the adjustment value cannot be easily obtained.

  The present invention has been made in view of such problems, and can easily determine an adjustment value (resistance value) for adjusting the offset and gain of the output signal of the operational amplifier to a target value. An analog circuit input / output characteristic measuring apparatus and operation including an operational amplifier capable of deleting an adjustment circuit element (resistor) provided in advance so that the offset and gain become target values based on the value An object of the present invention is to provide a method for measuring input / output characteristics of an analog circuit including an amplifier.

To achieve the above object, an apparatus for measuring input / output characteristics of an analog circuit including an operational amplifier according to claim 1 of the present invention is an input / output of an analog circuit including an operational amplifier in which circuit elements for adjusting offset and gain are combined. In the characteristic measurement device, a signal source that applies a plurality of known voltages to the input terminal of the analog circuit, and the output voltage of the operational amplifier and the voltage of the output terminal of the analog circuit when the signal source is applied The input / output characteristics of the operational amplifier from the relationship between the measuring means for measuring the power supply voltage for supplying the offset current of the operational amplifier and the signal voltage applied to the input terminal of the analog circuit and the output voltage of the operational amplifier. A first input / output characteristic is obtained, and from the output side of the operational amplifier from the relationship between the output voltage of the operational amplifier and the output voltage of the analog circuit. The second input / output characteristic which is the input / output characteristic of the output terminal of the analog circuit is obtained, and the operational amplifier is requested by using the second input / output characteristic to set the input / output characteristic of the analog circuit as the target characteristic. obtains the input and output characteristics to be such that said comparing the first input-output characteristic and input-output characteristic to be the request, it coincides with the input-output characteristic which the first input-output characteristic is the required Computation means for obtaining an adjustment value for adjusting the adjustment circuit element in order to adjust the offset and gain of the operational amplifier is provided.

According to this configuration, it is possible to obtain the adjustment value of the gain of the operational amplifier and the adjustment value of the offset at a time so as to obtain the desired input / output characteristic by minimizing the places where the input / output characteristic of the analog circuit is measured. Can do. Based on these adjustment values, the adjustment circuit element provided in advance can be adjusted so that the offset and gain become target values. According to the present invention, there is provided an apparatus for measuring input / output characteristics of an analog circuit including an operational amplifier according to claim 2. In the case of a circuit, the input / output characteristics of the impedance conversion circuit are not measured.
According to this configuration, even when the circuit from the input terminal of the analog circuit to the operational amplifier is an impedance conversion circuit, it is possible to appropriately determine the offset and gain adjustment values.

According to a third aspect of the present invention, there is provided an input / output characteristic measuring apparatus for an analog circuit including an operational amplifier according to a third aspect of the present invention. It is characterized by using a measured value of the power supply voltage that supplies the offset current of the amplifier.
According to this configuration, a more accurate offset adjustment value can be obtained.

  According to a fourth aspect of the present invention, there is provided the analog circuit input / output characteristic measuring apparatus including the operational amplifier according to any one of the first to third aspects, wherein a temperature detection diode is connected to the input terminal of the analog circuit. And a current measuring means for measuring the forward current supplied to the diode when the diode has a constant current source for supplying a constant forward current to the diode. The amount of deviation between the measured value of the direction current and the specified value of the forward current is obtained, and the amount of deviation of the forward voltage of the diode when the forward current of the amount of deviation is supplied based on the amount of current deviation. In other words, the correction is performed by shifting the voltage value applied to the input terminal of the analog circuit from the specified value based on the voltage deviation amount.

  An input / output characteristic measuring apparatus for an analog circuit including an operational amplifier according to claim 5 of the present invention is the analog circuit input / output characteristic measuring apparatus according to claim 4, wherein when the calculation means performs the correction, the voltage deviation amount and the current deviation amount are A correction coefficient is obtained from the relationship, a correction value is obtained by multiplying the correction coefficient and the current deviation amount, and a voltage applied to the input terminal of the analog circuit is corrected by the correction value.

  According to the configurations of the fourth and fifth aspects, the constant current supplied from the constant current source to the temperature detecting diode fluctuates from the specified value, and the fluctuation causes the forward voltage of the diode to shift. Since the voltage is applied to the input terminal of the analog circuit, in the present invention, the amount of shift in the forward voltage of the diode is obtained, and the applied voltage to the input terminal of the analog circuit is shifted from the specified value based on the amount of voltage shift. Thus, the input / output characteristics of the analog circuit can be adjusted in accordance with fluctuations in the constant current.

According to a sixth aspect of the present invention, there is provided a method of measuring input / output characteristics of an analog circuit including an operational amplifier, including an analog circuit including an operational amplifier in which circuit elements for adjusting offset and gain are combined, and an input terminal of the analog circuit. A signal source that applies a plurality of known voltages, and a power supply voltage that supplies an output voltage of the operational amplifier, a voltage of an output terminal of the analog circuit, and an offset current of the operational amplifier during the application by the signal source A first input / output characteristic, which is an input / output characteristic of the operational amplifier, is obtained from a relationship between a measuring means for measuring a signal voltage applied to an input terminal of the analog circuit and an output voltage of the operational amplifier; Is the input / output characteristic of the output terminal of the analog circuit from the output side of the operational amplifier from the relationship between the output voltage of the analog circuit and the output voltage of the analog circuit Of the determined input-output characteristic, for the target characteristic output characteristic of the analog circuit, determine the input-output characteristics required for the operational amplifier by using the second input-output characteristic, the input is the requested Compare the output characteristic with the first input / output characteristic, and adjust the offset and gain of the operational amplifier so that the first input / output characteristic matches the required input / output characteristic . When having a calculation means for obtaining an adjustment value for adjusting a circuit element, a temperature detection diode connected to the input terminal of the analog circuit, and a constant current source for supplying a constant forward current to the diode, Current measuring means for measuring a forward current supplied to the diode, and the computing means obtains a deviation amount between a measured value of the forward current in the current measuring means and a prescribed value of the forward current. Electric Based on the amount of deviation, the amount of deviation of the forward voltage of the diode when the forward current of the amount of deviation is supplied is obtained, and the applied voltage to the input terminal of the analog circuit is determined based on the amount of voltage deviation. In an input / output characteristic measuring method for an analog circuit including an operational amplifier for performing a correction shifted from a specified value, an adjustment limit range of the input / output characteristic of the operational amplifier is adjusted from an allowable error with respect to the specified value, the offset adjustment resolution, and the current measuring means A value obtained by subtracting each value of the measurement error and the error margin at is set to a range expanded in the positive and negative directions with respect to the specified value.
According to this configuration, the input / output characteristics of the analog circuit can be measured to the minimum, so that the operational amplifier of the analog circuit can be used when obtaining the input / output characteristics within the allowable error range (VF adjustment range). The man-hours for gain adjustment and offset adjustment can be reduced.

According to a seventh aspect of the present invention, there is provided a method for measuring input / output characteristics of an analog circuit including an operational amplifier according to the sixth aspect, wherein when the adjustment limit range is exceeded, the offset and gain of the operational amplifier are adjusted. Features.
According to this configuration, the offset and gain of the operational amplifier can be adjusted efficiently.

According to claim 8 of the present invention, in the method for measuring input / output characteristics of an analog circuit including an operational amplifier according to claim 7, when adjusting the offset and gain of the operational amplifier, after adjusting the gain, the offset adjustment is performed. It is characterized by performing.
According to this configuration, it is not necessary to repeatedly adjust the offset and gain, and the number of adjustment steps can be reduced.

  As described above, according to the present invention, it is possible to easily obtain an adjustment value (resistance value) for adjusting the offset and gain of the output signal of the operational amplifier to the target value, and based on this adjustment value, There is an effect that an adjustment circuit element (resistor) provided in advance can be deleted so that the offset and gain become target values.

Hereinafter, embodiments of the present invention will be described with reference to the drawings. However, parts corresponding to each other in all the drawings in this specification are denoted by the same reference numerals, and description of the overlapping parts will be omitted as appropriate.
(First embodiment)
FIG. 1 is a circuit diagram showing a configuration of an input / output characteristic measuring apparatus for a circuit under test 302 which is an analog circuit using an operational amplifier according to the first embodiment of the present invention.
FIG. 2 is an input / output characteristic diagram of the level converter of the input / output characteristic measuring apparatus according to the present embodiment.
FIG. 3 is an input / output characteristic diagram of the analog / PWM converter and the PWM / analog converter of the input / output characteristic measuring apparatus according to the present embodiment.
FIG. 4 is a flowchart for explaining a method of measuring input / output characteristics of a circuit under test by the input / output characteristic measuring apparatus according to the present embodiment.

FIG. 5 is a circuit diagram showing a configuration of a VF / PWM conversion circuit in which adjustment values of offset and gain in the input / output characteristic measuring apparatus according to the present embodiment are reflected in resistance value adjustment.
6 shows the configuration of each offset adjustment resistor and gain adjustment resistor in the level converter of the VF / PWM conversion circuit shown in FIG. 5, (a) is the configuration before adjusting the resistance value, (b). These are figures which show the structure after resistance value adjustment.

FIG. 7 shows another configuration of each offset adjustment resistor and gain adjustment resistor in the level converter of the VF / PWM conversion circuit shown in FIG. 5, (a) is a configuration before resistance value adjustment, b) is a diagram showing a configuration after resistance value adjustment.
First, referring to FIG. 5 to FIG. 7, a plurality of resistors (adjustment circuit elements) are connected in advance to the input / output side of the operational amplifier, and the offset and gain of the output signal of the operational amplifier are connected to these resistors. A description will be given of the VF / PWM conversion circuit 110 to which a configuration for cutting to a target value is applied.

  That is, in the VF / PWM conversion circuit 110, a plurality of resistors are deleted based on the adjustment values (resistance values) of the offset and gain of the operational amplifier measured by the input / output characteristic measuring apparatus 300 of the present embodiment. This is the target circuit. 14 is different from the VF / PWM conversion circuit 100 shown in FIG. 14 in that the level converter 120 includes one offset setting resistor R13 and a set of three offset fine adjustment resistors as a first parallel circuit. R13A, R13B, R13C and a set of three offset fine adjustment resistors R16A, R16B, R16C as a second parallel circuit, and a set of three gain adjustment resistors R14A, R14B, R14C as a third parallel circuit And a set of three gain adjusting resistors R15A, R15B, R15C as the fourth parallel circuit, and the offset and gain of the output signal of the operational amplifier 73 are adjusted by separating the desired resistor R from the parallel circuit. It is in doing so.

The offset setting resistor R13 is a conventional resistor R13 for offset setting.
More specifically, the potential of the positive input terminal of the operational amplifier 73 is set to ½ of the voltage of the power supply Vcc1 by setting the resistance value of the resistor R11 = the resistance value of the resistor R12. One set of offset fine adjustment resistors R13A, R13B, R13C between the input terminals and another set of offset fine adjustment resistors R16A, R16B, R16C between the ground and the negative input terminal of the operational amplifier 73. Are connected in parallel.
In this circuit configuration, one offset fine adjustment resistor R13A, R13B, R13C changes the output potential of the operational amplifier 73 in the negative direction, and the other offset fine adjustment resistor R16A, R16B, R16C is the output potential of the operational amplifier 73. Is changed in the positive direction to play a role of fine adjustment of the offset.

  Here, the combined resistance value of the first parallel circuit (resistors R13A, 13B, 13C) and the combined resistance value of the second parallel circuit (resistors 16A, 16B, 16C) are made the same, that is, the resistor R13A = R16A. , R13B = R16B, and R13C = R16C, offset adjustments cancel each other in the state where all of the resistors R13A, R13B, R13C, R16A, R16B, and R16C are mounted. Therefore, an adjustment step is not necessary for 1.2σ or less (77% of the population) that originally does not require adjustment, and the initial level adjustment can be performed only by the offset setting resistor R13.

If the resistance values are R13B = 1/2 × R13A and R13C = 1/4 × R13A, 1 to 3 resistors R are removed from R13A, R13B, R13C and R16A, R16B, R16C. With the combination of the resistors R, offset adjustment at equal intervals can be performed in 14 steps of total positive and negative.
On the other hand, as a gain adjustment, a fourth parallel circuit in which a plurality of resistors R15A, R15B, and R15C are connected in parallel as a resistor that is connected between the negative input terminal and the output terminal of the operational amplifier 73 and determines the numerator of the amplification factor. Using a circuit, this is a set of gain adjusting resistors. Further, a third resistor in which a plurality of resistors R14A, R14B, and R14C are connected in parallel as a resistor that is connected between the negative input terminal of the operational amplifier 73 and the output terminal of the buffer 71 in the previous stage and determines the denominator of the amplification factor. A parallel circuit is used, and this is another set of gain adjusting resistors.

  The resistance value of each resistor is selected so that the combined resistance value of the gain adjusting resistors R14A, R14B, and R14C and the combined resistance value of R15A, R15B, and R15C become initial values for obtaining a desired gain. For setting the gain (gain) of the operational amplifier, one resistor is provided between the −input terminal and the output terminal of the operational amplifier 73 and between the −input terminal of the operational amplifier 73 and the output terminal of the buffer 71. It is essential to connect the above. For this reason, one (for example, R15A and R16A) is not cut | disconnected, respectively, among the resistors which comprise a 3rd parallel circuit and a 4th parallel circuit.

Actually, the gain is the parallel resistance value that determines the numerator of the amplification factor by the combination of the resistors R15A, R15B, and R15 connected in parallel between the negative input terminal and the output terminal of the operational amplifier 73, and the negative input of the operational amplifier 73. The resistance of 96 series is determined by the ratio of the parallel resistance value that determines the denominator of the amplification factor by the combination of resistors R13A, R13B, and R13C connected in parallel between the terminal and the output terminal of the buffer 71. What is necessary is just to select the resistance value of each parallel circuit so that adjustment can be carried out at substantially equal intervals by combination.
The output of the operational amplifier 73 provided with these offset adjustment resistors R13, R13A to R13C and R16A to R16C, and gain adjustment resistors R14A to R14C and R15A to R15C is expressed by the following equation (8).

In this equation (8), in order to perform offset and gain adjustment, the output voltage V _lev of the operational amplifier 73 is obtained by substituting ∞ into the resistance value of the resistor R to be removed or to remove the resistance film.
However, since the offset amount also changes due to the gain adjustment, depending on the offset change amount, the offset amount needs to be corrected by the adjustment.

Next, an offset and gain adjustment method will be described with reference to FIG. FIG. 6 shows the configuration of each offset adjustment resistor R13, R13A to R13C and R16A to R16C, and the gain adjustment resistors R14A to R14C and R15A to R15C, where (a) is the configuration before the resistance value adjustment, (B) is a figure which shows the structure after resistance value adjustment.
As shown in FIG. 6A, the resistor R is fixed to a resistor mounting pad in which a copper wiring pattern 202 is welded and fixed to a land portion 201, and a chip resistor portion 203 is fixed by solder 204 by surface mounting means (not shown). Has been. The surface of the chip resistor portion 203 is coated with a protective film after a thick film resistor is applied or baked on the ceramic substrate or a metal foil film is formed by sputtering or the like.

  As shown in FIG. 6B, the protective film in the chip resistor unit 203 and the resistor R which is unnecessary and disconnected from the parallel circuit for offset or gain adjustment with respect to the resistor R The resistance film removal region 203a in the desired range of the thick film resistor or metal foil film is cut and removed with a laser beam (not shown). By this adjustment, the unnecessary resistor is disconnected from the parallel circuit, and the offset value or gain can be set to a predetermined value by changing the resistance value of the parallel circuit.

  In addition, as shown in FIG. 7B, when the resistor R that is no longer needed is disconnected from the parallel circuit, the soldering region of the chip resistor 203 is heated with a laser beam and the solder 204 is dissolved. The chip resistor unit 203 may be removed. In this case, the chip resistor 203 may be removed while the solder 204 is melted by pressing the soldering iron against both ends of the chip resistor 203. Even if it does in this way, the resistor which became unnecessary from the parallel circuit can be disconnected, and the resistance value of a parallel circuit can be changed and offset or gain can be made into a predetermined value.

In the circuit configuration of the VF / PWM conversion circuit 110, the description is limited to the voltage variation of the power sources Vcc1 and Vcc2. However, for example, the variation due to the temperature characteristics of the VF of the temperature detection diodes 40 and 50, and the temperature detection diode It is also possible to compensate for variations in the constant current IF applied to 40 and 50.
As described above, in the level converter 120, the potential of the positive input terminal of the operational amplifier 73 is set to half, and between the negative input terminal of the operational amplifier 73 and the power source and between the negative input terminal and the ground. The same number of offset adjusting resistors R13A to R13C and R16A to R16C are connected in parallel, and the resistors that are no longer necessary for offset adjustment are disconnected from the parallel circuit.

  By this separation, the combined resistance value of the parallel circuit can be changed to a necessary value, and the offset of the output signal of the operational amplifier 73 can be adjusted to a predetermined value. This also eliminates the need for the resistor trimming process for products with a circuit element variation of 1.2σ or less (77% of the population) among all products, thereby reducing product costs. It has become.

  Also, if adjustment is necessary, the resistance element of the target value is disconnected from the parallel circuit. Specifically, the resistor is removed from the circuit board, or the resistor coating of the resistor is widened with a laser beam or the like. It can be completely cut and removed. In addition, since the resistors that are no longer needed are separated from the parallel circuit, they are excellent in terms of deterioration resistance against the use environment of the product, and even when used for in-vehicle use, it is possible to maintain high reliability.

Further, one more resistor R13 is connected in parallel between the negative input terminal of the operational amplifier 73 and the power source Vcc1 than between the negative input terminal and the ground, and the single resistor R13 connected in large numbers is excluded. The parallel resistance values of the resistors R13A to R13C between the input terminal and the power source Vcc1 and the resistors R16A to R16C between the input terminal and the ground are made equal.
Since they are equal, offset adjustments cancel each other out. In this case, the initial output level (offset) of the operational amplifier 73 is limited only by an extra resistor R13 connected in parallel between the negative input terminal and the power supply Vcc1. Amount) can be set.

  Further, the resistance values of a plurality of resistors R13A to R13C except for the resistor R13, which is one more connected in parallel between the input terminal and the power source Vcc1, and the input terminal connected in parallel to the ground. The ratio of the resistance values of the plurality of resistors R16A to R16C is a value that is a power of 2. The weight of the power of 2 makes it possible to effectively change the value of the offset current.

  Further, a plurality of resistors R15A to R15C are connected in parallel as resistors for determining the numerator of the amplification factor between the −input terminal and the output terminal of the operational amplifier 73, and the −input terminal and the −input terminal are connected in parallel. A plurality of resistors R14A to R14C are connected in parallel as resistors for determining the denominator of the same amplification factor between the output terminal of the buffer 71, which is a preceding circuit to be connected, and these resistors R14A to R14C and Among the resistors R15A to R15C, a resistor that has become unnecessary due to gain adjustment is disconnected from the parallel circuit. For disconnection from the parallel circuit, the resistance film of the resistor may be cut and removed, or the resistor itself may be removed. As a result, gain adjustment can be easily performed.

  In the above example, the voltage of the power supply Vcc1 is divided in half by the resistors R11 and R12. However, the present invention is not limited to this. That is, in addition to the resistor R13, a plurality of resistors are connected in parallel between the negative input terminal of the operational amplifier 73 and the power source Vcc1, and the first current flowing into the operational amplifier 73 through the resistor and the negative A plurality of resistors are connected in parallel between the input terminal and the ground, and the voltage dividing ratio of the power supply voltage and the plurality of resistors are set so that the second current flowing out from the operational amplifier 73 through the resistors becomes equal. If the resistance value is selected, the offset adjustment is canceled out, and the adjustment process is not required for 1.2σ or less (77% of the population) which originally does not require adjustment, and the initial value is set only by the offset setting resistor R13. The level can be adjusted.

Further, in each of the parallel circuits, the resistance values of the plurality of resistors constituting the parallel circuit are different from each other, and can be adjusted by selecting a resistance value that is a power of 2 with respect to the resistance value of the reference resistor. Is easy. Needless to say, the resistance value of the parallel circuit can be adjusted by disconnecting the resistor as in the above example.
Next, when the resistor is cut or removed as described above, and the offset and gain of the operational amplifier are set to the target values, the input / output characteristic measuring apparatus 300 shown in FIG. The characteristic contents of this embodiment for obtaining a resistance value for adjusting the offset and gain to the target values will be described.

The input / output characteristic measurement apparatus 300 includes a circuit under measurement 302 that is a temperature detection system circuit, a measurement signal source 304, a first voltage measurement unit 306, a second voltage measurement unit 307, and a third voltage measurement. A unit 308 and a calculation unit 310 are provided.
The circuit under measurement 302 includes the buffer 71, the level converter 120, the triangular wave generator 78, the analog / PWM converter (operational amplifier) 79 shown in FIG. 5, and the PWM / analog converter 90a shown in FIG. Become.

The measurement signal source 304 inputs a predetermined voltage VF to the circuit under measurement 302. The input signal voltage VF is a voltage corresponding to both voltages VF of the temperature detecting diode 40 shown in FIG.
The first voltage measurement unit 306 measures the output voltage of the level converter 120. The output voltage is set to V _{LEV_M} .
The second voltage measuring unit 307 measures the output voltage of the PWM / analog converter 90a. The output voltage is set to _VCTI .
The third voltage measurement unit 308 measures the power supply voltage Vcc1 of the level converter 120 and the triangular wave generator 78.

The calculation unit 310 is an adjustment value for adjusting the offset and gain of the output signal of the operational amplifier of the circuit under test 302 to the target values based on the measurement results of the first to third voltage measurement units 306 to 307. (Resistance value) is obtained by arithmetic processing as follows.
In such a configuration, several stages of voltages are applied as the input signal voltage VF so that the output voltage V _CTI is 0% to 100%, and the output voltages V _{LEV_M} and V _CTI with respect to the input signal voltage VF are set to the first voltage. Measurement is performed by the first and second voltage measuring units 306 and 307.

From the input signal voltage VF and the measured output voltages V _{LEV_M} and V _CTI by the calculation unit 310, VF and V _{LEV_M} (mV) which are input / output characteristics of the level converter 120 shown by a straight line in FIG. And the relationship between V _{LEV_M} and V _CTI (mV), which are input / output characteristics of the analog / PWM converter 79 and the PWM / analog converter 90a, which are indicated by straight lines bent vertically in FIG.

Then, if regression line processing is performed using the data of the portions having the linear relationship, the following relational expression (9) representing the input / output characteristics can be obtained. The reason why the expression expressing the input value with respect to the output value is used for this expression (9) is that the output specified value of the temperature detection system circuit is determined regardless of the characteristics of the temperature detection diode 40 and the characteristics of the circuit. It is.
The linear regression equation from V _CTI to V _{LEV_M} is
V _{LEV_M} = γ × V _CTI + δ (9)

Here, if the values at 0% and 100% of the output regulation value V _CTI of the temperature detection system circuit are, for example, V _{CTI_H} = 0.5V at 140 ° C. and V _{CTI_L} = 4.5V at 25 ° C., V _LEV Is expressed by the following equations (10) and (11).
V _{LEV_M_H} = γ × V _{CTI_H} + δ (10)
V _{LEV_M_L} = γ × V _{CTI_L} + δ (11)
The _{V LEV_M_L, V LEV_M_H 0%} output of the _{V CTI,} which means the output voltage of the level converter 120 required to 100%.
The linear regression equation of _{VF _M} from the V _{LEV_M,
VF _M = α × V LEV_M +} β ... (12)

Using this equation (12), the values of VF with respect to the voltage values V _{LEV_M_L} and V _{LEV_M_H} of V _LEV corresponding to 0% and 100% of the output specified value V _CTI of the temperature detection system circuit are expressed by the following equations (13) and (13): 14).
VF _{M_H} = α × V _{LEV_M_H} + β (13)
VF _{M_L} = α × V _{LEV_M_L} + β (14)
Thus, by using the regression line in two steps, 0% of the output prescribed value _{V CTI} of the temperature detection system circuits, VF value _VF m_h equivalent to _100% Motomari is _{VF M_L,} temperature sensing system circuits Input / output characteristics reflecting variations in the circuit under measurement 302 can be obtained.

Next, in the process of gain adjustment and offset adjustment, in order to obtain input / output characteristics using circuit equations, first, the third voltage measurement unit 308 measures the power supply voltage Vcc1 through which the offset current of the level converter 120 flows. .
The following equation (15) is a circuit equation for _obtaining a theoretical value of the output voltage V _LEV of the level converter 120 from the input signal voltage VF. As shown in FIG. 5, the + input potential of the operational amplifier 73 of the level converter 120 becomes a voltage value of Vcc1 / 2 if the resistance values of the resistors R11 and R12 are made equal, and the negative input potential of the operational amplifier 73 is equivalent. The potential is Vcc1 / 2. On the other hand, if R13A = R16A, R13B = R16B, and R13C = R16C, the offset current of the operational amplifier 73 flows only through the resistor R13.

However, // indicates resistance parallel.
Although the calculated value of V _{LEV_C} with respect to the input signal voltage VF is obtained by the above equation (15), the circuit constant used in the circuit equation is a nominal value and actually has an error.
Therefore, the measured value V _{LEV_M} of V _LEV when the same VF potential is input is compared with the theoretical value V _{LEV_C of} V _LEV , the regression line processing is performed, and the gain correction value represented by the following equation (16): The offset correction value can express the deviation from the nominal value due to the circuit constant and the operational amplifier.
V _{LEV_M} = V _{LEV_C} × V _{g_C} + V _{o_C} (16)
Where V _{g — C is} the theoretical correction value of the gain of the level converter 120.
V _{o_C} : Theoretical correction value of the offset of the level converter 120.

By doing so, the actual characteristics of the level converter 120 can be estimated by correcting the theoretical values of the circuit equations.
_VF m_h already _{described, VF M_L} 0% of the output prescribed value _{V CTI} of the temperature detection system circuits, shows the ability input range of VF corresponding to 100%, VF _{S_H,} VF which require VF _{S_L} to the circuit board _{Assuming the} input range, the gain correction value V _{g — c} is expressed by the following equation (17).

The resistors that determine the gain are R15A to 15C in the numerator of the expression representing the gain and R14A to R14C in the denominator. R15A and R14A are main resistors that determine the approximate value of the gain, and resistors R15B, R15C Compared to R14B and R14C, it has a low resistance value.
Therefore, R15B, R15C, R14B, and R14C adjust the gain, and gain correction is -2.6%, -1.73%, -0.86%, + 0.83%, and +1.64 by combining these gains. %, + 2.50% can be set, and the width of the VF input range can be set to a desired value by selecting the combination closest to the above Gadj.
On the other hand, the output voltage of the level converter 120 after gain adjustment is expressed by the right side of the following equations (18) and (19), and the offset current is adjusted so as to be a value close to V _LEV .

R16: resistance value corresponding to the denominator of gain after gain adjustment.
R15: resistance value corresponding to the numerator of gain after gain adjustment.
Equations (20) and (21) are obtained by modifying the above equations (18) and (19) to obtain the offset current (i _H, i _L ).

However, R13: Resistance value of the main resistor for offset adjustment.
In this way, the adjustment value (i _H, i _L ) of the offset current for adjusting the output of the level converter 120 is obtained.
However, since gain calculation cannot set a calculated value, the values of i _{H and} i _L are different. In practice, the average value I _{O is obtained} by the following equation (22) for adjustment.
I _O = (i _H + i _L ) / 2 (22)
The resistance value of the resistor to be deleted from this offset adjustment current is determined by the following equation (23).
R _O = Vcc1 / 2 / I _O (23)

I _O is the fact that with a positive or negative value, R _O computational is held positive and negative values, this is only expresses the direction of flow offset current. Therefore, when R _O is positive, the resistor on the R16 side is deleted and current imbalance is caused to flow an offset current from the resistor on the R13 side.
On the other hand, when R _O is negative, the resistor on the R13 side is deleted to cause current imbalance, thereby drawing an offset current into the resistor on the R16 side. The offset resistance _{R O} is also similar to the gain adjustment values close R13, R13A, R13B, R13C, R16A, R16B, may be selected from R16C.

  As described above, after the input / output characteristics of the circuit under measurement 302 which is the temperature detection system circuit are grasped by the input / output characteristics measurement apparatus 300 of the analog circuit using the operational amplifier according to the present embodiment, the device under measurement is measured. The input / output characteristics (offset and gain) of the circuit 302 are adjusted by the method shown in the flowchart of FIG.

In step S1, the input / output characteristics of the circuit under test 302 are measured. That is, a known multi-level voltage VF is input to the buffer 71 which is an input unit of the circuit under test 302. With measuring the output characteristic of _{V CTI} (output voltage of the temperature detection system _circuit) the output voltage of the output voltage _{V LEV_M} and PWM / analog converter 90a of the level converter 120 corresponding to the value of the input signal voltage VF, level The converter 120 measures the voltage value Vcc1 of the voltage source that supplies the offset current.

In step S2, input / output characteristics of the analog / PWM converter 79 and the PWM / analog converter 90a are determined. That is, the measured value of the output voltage _{V CTI} of the output voltage _{V LEV_M} and PWM / analog converter 90a of the level converter 120 based on the relational expression in the region having the proportion calculated by the regression line process. Using this calculated relationship, 0% of the output voltage _{V CTI} of PWM / analog converter 90a, obtains the range of the output voltage _{V LEV_M} level converter 120, which corresponds to 100%.

In step S3, the input / output characteristics of the level converter 120 are determined. That is, the input / output characteristics of the level converter 120 are calculated by regression line processing based on the measured value of the output voltage V _{LEV_M} of the level converter 120 and the set value of the input signal voltage VF of the circuit under test 302. Here, by combination of relationship in a region having the proportional relation between the output voltage _{V CTI} of PWM / analog converter 90a for the output voltage _{V LEV_M} level converter 120, the output voltage _{V CTI} of PWM / analog converter 90a The effective range of the input voltage of the circuit under test 302 corresponding to 0% and 100% is obtained.

In step S4, the calculated value of the input / output characteristic of the level converter 120 is corrected. That is, determined by the PWM / 0% of the output voltage _{V CTI-analog} converter 90a, to the input voltage of the circuit under test 302, corresponding to 100%, the circuit calculation applying the circuit constant of the unadjusted level converter 120 and the output voltage range of the level converter 120, 0% of the output voltage _{V CTI} of PWM / analog converter 90a, compared with the range of the output voltage _{V LEV_M} level converter 120, which corresponds to 100%, the difference Treated as offset and gain correction values as deviations from nominal circuit constants.

In step S5, the gain characteristic of the level converter 120 is adjusted. That is, the ratio of the input signal voltage VF to the effective range of the voltage range to be set in the circuit under test 302 is obtained, and the adjusted gain is closest to the reciprocal × the gain of the level converter 120 before adjustment. Then, a part of the gain resistor of the level converter 120 is deleted.
In step S6, the offset characteristic of the level converter 120 is adjusted. That is, the output voltage range of the level converter 120 with respect to the voltage range (0%, 100%) to be set in the circuit under test 302 is obtained by using the gain after deleting the gain resistor. PWM / 0% of the output voltage _{V CTI-analog} converter 90a, compared with the range of the output voltage _{V LEV_M} level converter 120, which corresponds to 100%, the offset current for adjustment as the deviation range is minimized Then, an adjustment resistance value is obtained from the voltage value Vcc1 of the voltage source, and a resistor close to the obtained adjustment resistance value is deleted from the resistor array on the side opposite to the side where the offset current is to flow.

  As described above, the input / output characteristic measuring apparatus 300 according to the first embodiment reduces the number of places where the input / output characteristics of the circuit under measurement 302 are measured to the minimum, and the amplification of the amplifier so as to obtain the desired input / output characteristics. The ratio (gain) adjustment value and the offset adjustment value can be obtained at a time. Then, based on those adjustment values, a resistor, which is an adjustment circuit element provided in advance, can be deleted so that the offset and gain become target values.

(Second Embodiment)
FIG. 20 is a circuit diagram showing a configuration of an input / output characteristic measuring apparatus for a circuit under test that is an analog circuit using an operational amplifier according to the second embodiment of the present invention.
The input / output characteristic measuring circuit 400 shown in FIG. 20 is different from the input / output characteristic measuring circuit 300 shown in FIG. 1 in that the circuit under test 402 has a constant forward current IF in the temperature detecting diode 40 shown in FIG. A constant current source 70 that supplies (IF current) is provided, and fluctuations in the forward voltage VF (VF voltage) of the temperature detection diode 40 due to variations in IF current from the constant current source 70 can be corrected. is there. In addition, the input / output characteristic measurement circuit 400 includes a current measurement unit 404, a calculation unit 410, and a switch 406 for connecting / disconnecting the measurement power supply 304 in order to correct a variation in the VF voltage.

The current measurement unit 404 measures the IF current and outputs the measurement value to the calculation unit 410. Based on the measured value of the IF current, the calculation unit 410 performs calculation processing for correcting the fluctuation of the VF voltage as described below. Note that the arithmetic unit 410 has the same arithmetic processing function as the arithmetic unit 310 of FIG. 1 other than the arithmetic processing for correcting the fluctuation of the VF voltage.
FIG. 21 shows VF / IF characteristics using the temperature of the temperature detection diode as a parameter, and shows that the VF voltage fluctuates as the IF current fluctuates. FIG. 22 shows the IF dependence of the temperature coefficient of the VF voltage. When the IF current varies by ± 5%, the VF temperature coefficient varies by ± 0.15%. FIG. 23 shows the IF current dependence of the VF voltage at 25 ° C. From this it can be seen that the VF voltage and the IF current have a linear relationship.

Each of FIGS. 21 to 23 has a linear relationship, but as described above, the IF dependency of the temperature coefficient of the VF voltage is a variation of ± 0.15%, which is ± 3% allocated to the entire circuit 402 to be measured. Since it is sufficiently small with respect to the error, it can be ignored.
Therefore, the correction of the VF voltage that fluctuates due to the deviation of the IF current may be uniquely corrected regardless of the temperature, as shown in FIG. Since the VF voltage of the temperature detection diode 40 varies greatly depending on the temperature and also varies depending on the IF current, it is necessary to measure the VF voltage with the IF current as a fixed value. Deviation from the fixed value.

The amount of deviation of the VF voltage due to the deviation of the IF current is substantially constant within the lot of the temperature detection diode 40 and between lots, and even if the temperature of the temperature detection diode 40 changes as shown in FIG. The effect of IF current deviation is generally constant.
Accordingly, ΔVF / ΔIF of the temperature detecting diode 40 is obtained in advance from the measured value as shown in FIG. 23, and this ΔVF / ΔIF is set as the correction coefficient C _{ΔVF / ΔIF} in the calculating unit 410. From the product of the correction coefficient C _{ΔVF / ΔIF} and the deviation amount ΔIF from the specified value of the IF current, the deviation amount ΔVF from the original specified value of the VF voltage value is obtained.

The correction formula of the VF voltage used for calculation in the calculation unit 410 is expressed as follows.
VF voltage at a defined value IF _S forward current IF is as follows.
VF _{SS_H} (High-temperature side forward voltage)
VF _{SS_L} (low temperature side forward voltage)
VF voltage at a current IF _M forward current IF is shifted from the specified value IF _S is as follows.
_{VF S_H = VF SS_H + (IF} M -IF S) × C ΔVF / ΔIF ... (24)
_{VF S_L = VF SS_L + (IF} M -IF S) × C ΔVF / ΔIF ... (25)

In this way, the forward current IF is also deviate from the specified value IF _S, it is possible to obtain the corresponding VF value _{(VF S_H, VF S_L).} As described in the first embodiment, these VF _{M_H} and VF _{M_L} are VF input ranges required for the circuit board, and the VF _{S_H} and VF _{S_L} obtained by the above equations (24) and (25) are used. By substituting into the above equation (17), the gain correction value V _{g — c} shown in the equation (17) can be obtained.
That is, after the VF input ranges VF _{S_H} and VF _{S_L} required for the circuit board are obtained, the characteristics after the buffer 71 of the circuit under test 402 are compensated as described in the first embodiment.

  As described above, the input / output characteristic measuring apparatus 400 according to the second embodiment corrects the fluctuation of the forward voltage VF of the temperature detection diode 40 caused by the variation in the IF current from the constant current source 70, and then performs the first operation. As in the first embodiment, the number of locations where the input / output characteristics of the circuit under test 402 are measured is minimized, and the adjustment value and offset of the amplification factor (gain) of the amplifier are adjusted so that the desired input / output characteristics are obtained. Adjustment values can be obtained at a time.

(Third embodiment)
25 and 26 are first and second flowcharts for explaining an input / output characteristic measurement method for a circuit under measurement, which is an analog circuit using an operational amplifier according to the third embodiment of the present invention. .
FIG. 27 is a diagram for explaining a method for adjusting input / output characteristics of a circuit under test (temperature measurement circuit) that is an analog circuit using the operational amplifier according to the present embodiment.
FIG. 28 is a diagram for explaining the presence / absence of gain adjustment of a circuit under test (temperature measurement circuit) that is an analog circuit using the operational amplifier according to the present embodiment.
FIG. 29 is a diagram for explaining the presence / absence of offset adjustment of a circuit under test (temperature measurement circuit) that is an analog circuit using the operational amplifier according to the present embodiment.

First, FIG. 27 shows an allowable value for the specified value (set VF value) of the VF voltage when the temperature of the circuit under measurement 402 is measured using the temperature detection diode 40 of the input / output characteristic measuring apparatus 400 shown in FIG. The error, measurement error, and adjustment range were described as follows. That is, the solid line K1 is set VF value (prescribed value), while the solid line K1 and the broken line K2 and K3 tolerance _{VF -ER,} while the solid line K1 and the one-dot chain line K4 and K5 VF adjustment range _{VF S-H,} VF _{S -L} . Further, T1 represents a low temperature side, and T2 represents a high temperature side value.

With reference to FIG. 27, a method of correcting the input / output characteristics of the circuit under measurement 402 by gain adjustment and offset adjustment will be described.
In the above equations (24) and (25), the specified value (set VF value) of the VF voltage of the temperature detection diode 40 at T1 and T2 after the IF current value is corrected is represented by the following symbols. The
Setting VF value:
VF SH (High _- temperature side forward voltage)
VF SL (Low _- temperature forward voltage)

The offset setting resistor R13 and the offset fine adjustment resistors R13A, R13B, R13C, R16A, R16B, R16C, as described above, so as to guarantee the temperature accuracy with the allowable error VF- _ER for the set VF value, The offset and gain must be adjusted by the gain adjusting resistors R14A, R14B, R14C, R15A, R15B, and R15C, but the following items (a1) to (a3) need to be considered. These (a1) to (a3) are also shown in FIG.

The offset setting resistor R13 and the offset fine adjustment resistors R13A, R13B, R13C, R16A, R16B, and R16C are also referred to as offset adjustment resistors in the following.
( _A1 ) Offset adjustment resolution: VF- _{ER_OFF}
Since the offset adjustment in this embodiment is performed using several types of adjustment resistors consisting of power values, 1/2 of the offset adjustment step is set with an error due to the fact that only discrete adjustment is possible. .
(A2) Measurement system error (reproducibility): VF- _{ER_MEAS}
This indicates the stability and reproducibility of the device for measuring the input / output characteristics of the circuit under test 402.
( _A3 ) Margin: VF- _MARJIN
This is a margin for allowing the adjusted VF value to guarantee the set value with a margin within the allowable error range.

Allowable error: From VF- _ER , a value in consideration of the above items is the VF adjustment range shown in the following equations (26) to (29). In each expression showing the following adjustment ranges, the maximum value of the adjustment range is represented by _MAX and the minimum value is represented by _MIN . Moreover, in FIG. 27, it described as VF _S-H and VF _S-L .
Adjustment range of high-temperature forward voltage:
_{VF S-H_MAX = VF S-} H + (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (26)
_{VF S-H_MIN = VF S-} H - (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (27)
Low temperature side forward voltage adjustment range:
_{VF S-L_MAX = VF S-} L + (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (28)
_{VF S-L_MIN = VF S-} L - (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (29)

In this way, the adjustment range of the forward voltage on the low temperature side and the high temperature side is defined, and the VF value at the low temperature and high temperature corresponding to the predetermined output value in the circuit under test 402 that is the temperature detection circuit is gain adjusted and offset. Control within the specified range by adjustment.
The order of the gain adjustment and the offset adjustment is such that the offset value changes when the gain adjustment is performed. Therefore, the offset adjustment is performed after the gain adjustment. Thereby, the adjustment efficiency can be increased.

First, gain adjustment will be described with reference to the flowchart of FIG. 25 and FIG. However, FIG. 28 shows the VF adjustment maximum range VMAX obtained from the above VF adjustment ranges VF _{S-H_MAX} , VF _{S-H_MIN} , VF _{S-L_MAX} , VF _{S-L_MIN,} and the VF adjustment minimum range VMIN showed that.
In step S11 of FIG. 25, a VF value at a high temperature and a low temperature corresponding to a predetermined output value of the circuit under test 402 evaluated by the input / output characteristic measuring apparatus 400 is measured, and the VF value at the high temperature is VF _{M_H} , _Is set to VF _{M_L} . The high and low VF values obtained by this measurement are shown by solid lines K11 and K12 or broken lines K13 and K14 in FIG.

In step S12, the temperature change of the VF value is calculated. If the amount of change in VF between the high and low temperatures of the circuit under test 402 at this time is ΔVF _M , then ΔVF _M = VF _{M_H} −VF _{M_L} .
Next, in step S13, it is determined whether or not the calculated ΔVF _M is within the gain adjustment range. This obtains the adjustment range of ΔVF from the above-mentioned adjustment range of VF (VF _{S-H_MAX} , _{VFS -H_MIN} , _{VFS-L_MAX} , _{VFS-L_MIN} ). This is expressed by the following equations (30) and (31).
ΔVF _{S_MAX} = VF _{S−H_MAX} −VF _{S−L_MIN} (30)
ΔVF _{S_MIN} = VF _{S−H_MIN} −VF _{S−L_MAX} (31)
Then, ΔVF _M , ΔVF _{S_MIN} , and ΔVF _{S_MAX} are compared. As a result, _when the relationship of ΔVF _{S_MIN} ≦ ΔVF _M ≦ ΔVF _{S_MAX} is satisfied, gain adjustment is not necessary as shown in step S14. This is the case of the solid lines K11 and K12 shown in FIG.

On the other hand, as shown by broken lines K13 and K14 in FIG. 28, when the above relationship is not satisfied, the process proceeds to step S15, and it is necessary to perform gain adjustment. In this case, in order to reduce the number of resistors for gain adjustment as much as possible, it is determined by the following equation (32) which of ΔVF _{S_MIN} and ΔVF _{S_MAX} obtained above is close to the value of ΔVF _M. It is necessary to set the target value ΔVF- _SS for adjusting the VF.
| ΔVF _M −ΔVF _{S_MIN} | <| ΔVF _M −ΔVF _{S_MAX} | (32)
That is, the gain adjustment target is determined by this equation (32).
As a result, when the relationship of the above equation (32) is satisfied, the gain adjustment target is ΔVF _−SS = ΔVF _{S_MIN} as shown in step S16. On the other hand, when the relationship of the above equation (32) is different, as shown in step S17, the gain adjustment target ΔVF _−SS = ΔVF _{S_MAX} .

Next, in step S18, the gain adjustment amount is calculated as in the following equation (33).
Gadj = (ΔVF _SS −ΔVF _M ) / ΔVF _M (33)
Next, in step S19, the gain adjustment resistors R14A, R14B, R14C, R15A, R15B, and R15C are removed and the gain is adjusted so that the gain adjustment target ΔVF− _SS is obtained. The gain adjustment amount at this time is expressed by the above equation (33).
By adjusting in this way, conventionally, the gain adjustment target ΔVF _−SS = 0 was set and gain adjustment was made so as to approach this, but it is not necessary to adjust ΔVF _{S_MIN} or ΔVF _{S_MAX} , in other words, Therefore, since the VF adjustment range can be narrowed, the man-hours for deleting the gain adjustment resistor can be reduced accordingly.

Next, offset adjustment will be described with reference to the flowchart of FIG. 26 and FIG.
In step S20 of FIG. 26, the input / output characteristics of the circuit under measurement 402 change due to the gain adjustment in the previous process. Therefore, the estimated VF at a high temperature corresponding to the predetermined output value after gain adjustment: VF _{M_H_G} VF estimated value at low temperature: VF _{M_L_G} is obtained from the following equations (34) and (35). In addition, the estimated high and low VF values are indicated by a solid line K21 or a broken line K22 in FIG.

VF estimated value after gain adjustment of high-temperature side forward voltage:
VF _{M_H_G} = {(Vcc1 / 2−V _{LEV_M_H} + Vo_c) / (R _GAIN2 ) −5VP / 2 / (R ₁₃ )} × {(R _GAIN1 ) / Vg_c} + Vcc 1/2 (34)
VF estimated value after gain adjustment of high-temperature side forward voltage:
VF _{M_L_G} = {(Vcc1 / 2−V _{LEV_M_L} + Vo_c) / (R _GAIN2 ) −5VP / 2 / (R ₁₃ )} × {(R _GAIN1 ) / Vg_c} + Vcc 1/2 (35)

However, in the level converter 120 (see FIG. 5) of the circuit under test 402, R11 = R12 and the + input of the operational amplifier 73 is set to a voltage value of Vcc1 / 2.
R _GAIN1 : The combined resistance after gain adjustment in R15A to R15C, which is a numerator of the amplification factor.
R _GAIN2 : The combined resistance after gain adjustment in R14A to R14C, which is the denominator of the amplification factor.

Here, it is necessary to suppress the temperature measurement value within the allowable error range with respect to the specified value, and the adjustment is performed within the same range as the gain adjustment.
Adjustment range of high-temperature forward voltage:
_{VF S-H_MAX = VF S-} H + (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (36)
_{VF S-H_MIN = VF S-} H - (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (37)
Low temperature side forward voltage adjustment range:
_{VF S-L_MAX = VF S-} L + (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (38)
_{VF S-L_MIN = VF S-} L - (VF -ER -VF -ER_OFF -VF -ER_MEAS -VF -MARJIN) ... (39)

Next, in step S21, the following equations (40) and (41) are used to determine whether or not the low-temperature side and high-temperature side VF estimated values after gain adjustment of the circuit under test 402 are within their adjustment ranges. Confirm by the formula.
Hot side forward voltage:
VF _{S-H_MIN} ≦ VF _{M_H_G} ≦ VF _{S-H_MAX} (40)
Low-temperature forward voltage:
VF _{S-L_MIN} ≤ VF _{M_L_G} ≤ VF _{S-L_MAX} (41)
As a result of this determination, if both the low-temperature side and high-temperature side VF estimation values are satisfied, offset adjustment becomes unnecessary as shown in step S22. This is the case of the solid line K21 shown in FIG.

On the other hand, as indicated by the broken line K22, when the above relationship is not satisfied, the process proceeds to step S23, and it is necessary to perform offset adjustment. In this case, it is necessary to examine the positions of the VF estimated values on the high temperature side and the low temperature side with respect to the specified value.
First, in step S23, an error of the high-temperature side VF estimation value with respect to the specified value is obtained from the following equation (42).
Error on the high temperature side:
_{EVM_H_G_1} = | _{VFM_H_G−} VFS _{−H_MAX} |, _{EVM_H_G_2} = | _{VFM_H_G−} VFSH _−MIN | (42)

These EVF _{M_H_G_1} and EVF _{M_H_G_2} are compared, and the larger one is treated as the maximum error. That is, if EVF _{M_H_G_1} > EVF _{M_H_G_2} , in step S24, _{EVM_H_G_} = _{VFM_H_G−} VFS _{−H_MAX} . _In the case of _{EVF M_H_G_1 <EVF M_H_G_2,} in step _S25, the _{EVF M_H_G = VF M_H_G -VF S-} H_MIN.

Next, in step S26, an error of the low-temperature side VF estimation value with respect to the specified value is obtained from the following equation (43).
Low temperature error:
_{EVF M_L_G_1 = | VF M_L_G -VF S} -L_MAX |, EVF M_L_G_2 = | VF M_L_G -VF S-L_MIN | ... (43)
These EVF _{M_L_G_1} and EVF _{M_L_G_2} are compared, and the larger one is treated as the maximum error. That is, if EVF _{M_L_G_1} > EVF _{M_L_G_2} , in step S27, _{EVM_H_G_} = _{VFM_L_G−} VFS _{−L_MAX} . If EVF _{M_L_G_1} <EVF _{M_L_G_2} , in step S28, _{EVM_L_G} = _{VFM_L_G−} VFS _{−L_MIN} .

Next, in step S29, and an error _{EVF M_L_G} errors _{EVF M_H_G} high temperature side of the low temperature side obtained _{above, | EVF M_H_G |> | EVF} M_L_G | compared as, offset adjustment the larger of the error _Treat as quantity EVF _{M_G} .
Error comparison between low temperature side and high temperature side:
If | EVF _{M_H_G} |> | EVF _{M_L_G} |, in step S30, the offset adjustment amount EVF _{M_G} = EVF _{M_H_G} .
If | EVF _{M_H_G} | <| EVF _{M_L_G} |, the offset adjustment amount EVF _{M_G} = EVF _{M_L_G} is set in step S31.

Next, in step S32, an offset current value I _MO for deriving a resistance adjustment value is obtained from the offset adjustment amount EVF _{M_G} obtained as described above as shown in the following equation (44).
I _MO = EVF _{M_G} / R _GAIN2 (44)
Next, in step S33, the offset adjustment resistance value Roff is obtained by the following equation (45) using the offset current value obtained above.
Roff = Vcc1 / (I _MO × 2) (45)

Next, in step S34, if the offset adjustment resistance value Roff is positive, the offset adjustment resistors R13 and R13A to R13C are deleted (removed) with the closest value, and if negative, the offset adjustment resistance value Roff is offset adjustment. The resistor having the closest value on the resistors R16A to R16C side is deleted (removed).
Thus, conventionally, by setting the offset error 0, had been offset adjustment so as to approach thereto, tolerance _VF -ER shown in FIG. _{27 - (VF -ER_OFF + VF -ER_MEAS} + VF -MARJIN) worth of It is not necessary to perform adjustment, and the man-hour for deleting the offset adjusting resistor can be reduced by this amount. Further, by deleting the offset adjusting resistor, the gain adjustment and the offset adjustment are completed in step S35.

  As described above, according to the input / output characteristic measuring method for the circuit under measurement which is an analog circuit using the operational amplifier according to the third embodiment, first, the level converter 120 of the circuit under measurement 402 in the input / output characteristic measuring apparatus 400 is used. When the gain adjustment is performed, a VF range to be allowed for the circuit under measurement 402 that is a temperature detection system is calculated. That is, the remainder obtained by subtracting the minimum offset adjustment error, the input / output characteristic measurement error, and the error margin from the allowable error is added to or subtracted from the VF design value (set VF value) in the circuit design of the circuit to be measured 402. The value (value expanded in the positive / negative direction) is set as the VF range allowed for the circuit under measurement 402.

  Compared with the measured value of the input voltage of the temperature detection system with respect to the VF range allowed for the circuit under test 402, if the measured value is within the allowed VF range, gain adjustment is not performed. On the other hand, if the actual measurement value is outside the allowable VF range, a comparison is made to determine which of the maximum value and minimum value of the allowable VF range is closest to the actual measurement value, and the ratio between the closest allowable VF value and the actual measurement value. Ask for. Ax is the product of the reciprocal of this ratio and the gain Gx of the level converter 120 before adjustment. When the previous ratio is 1 or more, the gain adjusting resistor is deleted so that the gain closest to Ax is obtained when Gx ≧ Ax, and when the ratio is 1 or less, the closest to Ax is obtained when Gx <Ax. Remove the gain adjustment resistor to gain.

  Following this gain adjustment, the level converter 120 offset adjustment is performed. That is, by using the gain after deleting the gain adjusting resistor, the output range of the level converter 120 with respect to the voltage range to be set in the circuit under measurement 402 that is the temperature detection system is obtained. The output voltage range of the level converter 120 corresponding to the output voltage range is compared, and the offset current for adjustment is obtained so that the deviation of the range is minimized. Then, the offset adjustment resistance value is obtained from the voltage source voltage value, and the offset adjustment resistor close to the previously obtained offset adjustment resistance value is deleted from the resistor string on the side opposite to the side where the offset current is to flow.

  By performing the gain adjustment and the offset adjustment in this way, the locations where the input / output characteristics of the circuit under measurement 402 are measured in the input / output characteristic measuring apparatus 400 can be minimized. In obtaining the characteristics, the man-hours for gain adjustment and offset adjustment of the level converter 120 of the circuit under test 402 can be reduced.

1 is a circuit diagram showing a configuration of an input / output characteristic measuring apparatus for a circuit under measurement that is an analog circuit using an operational amplifier according to a first embodiment of the present invention. It is an input-output characteristic figure of the level converter of the input-output characteristic measuring apparatus which concerns on this Embodiment. It is an input / output characteristic diagram of an analog / PWM converter and a PWM / analog converter of the input / output characteristic measuring apparatus according to the present embodiment. It is a flowchart for demonstrating the input / output characteristic measuring method of the to-be-measured circuit by the input / output characteristic measuring apparatus which concerns on this Embodiment. It is a circuit diagram which shows the structure of the VF / PWM conversion circuit to which the level converter which is an analog circuit using the operational amplifier which concerns on this Embodiment is applied. The structure of each offset adjustment resistor and the gain adjustment resistor in the level converter is shown, (a) is a configuration before resistance value adjustment, (b) is a diagram showing a configuration after resistance value adjustment. The other structure of each offset adjustment resistor and the gain adjustment resistor in the level converter is shown, (a) is a configuration before resistance value adjustment, (b) is a diagram showing a configuration after resistance value adjustment. is there. It is a block diagram which shows the structure of a vehicle drive system. It is a block diagram which shows the structure of the buck-boost converter in a vehicle drive system. It is a current waveform figure which flows into a reactor at the time of voltage boosting operation of a buck-boost converter. It is a block diagram which shows the structure of IPM for step-up / down converters. It is a block diagram which shows the structure of the IGBT chip | tip temperature detection part in IPM for buck-boost converters. It is a temperature characteristic figure of the forward voltage of the IGBT chip temperature detection diode by the constant current circuit in an IGBT chip temperature detection part. It is a circuit diagram which shows the structure of the VF / PWM conversion circuit using the conventional level converter. It is a circuit diagram which shows the structure of the digital-analog converter in IPM for buck-boost converters. It is a figure which shows the span change of the IGBT chip | tip temperature voltage signal at the time of fluctuating the voltage of said 1st power supply. It is a figure which shows the offset change of the IGBT chip | tip temperature voltage signal at the time of fluctuating the voltage of said 1st power supply. It is a figure which shows the span change of the IGBT chip | tip temperature voltage signal at the time of fluctuating the voltage of said 2nd power supply. It is a figure which shows the offset change of IGBT chip | tip temperature voltage signal at the time of fluctuating the voltage of said 2nd power supply. It is a circuit diagram which shows the structure of the input / output characteristic measuring apparatus of the to-be-measured circuit which is an analog circuit using the operational amplifier which concerns on the 2nd Embodiment of this invention. It is a VF / IF characteristic diagram using the temperature of the temperature detection diode of the circuit under test as a parameter. It is IF dependence figure of the temperature coefficient of VF voltage of the said temperature detection diode. It is an IF current dependence figure of VF voltage in 25 degreeC of the said temperature detection diode. It is a figure which shows IF current dependence of the temperature characteristic of VF voltage of the said diode for temperature detection. It is a 1st flowchart for demonstrating the input / output characteristic measuring method of the to-be-measured circuit which is an analog circuit using the operational amplifier which concerns on the 3rd Embodiment of this invention. It is a 2nd flowchart for demonstrating the input-output characteristic measuring method of the to-be-measured circuit which is an analog circuit using the operational amplifier which concerns on the 3rd Embodiment of this invention. It is a figure for demonstrating the adjustment method of the input-output characteristic of the to-be-measured circuit (temperature measurement circuit) which is an analog circuit using the operational amplifier which concerns on 3rd Embodiment. It is a figure for demonstrating the presence or absence of the gain adjustment of the to-be-measured circuit (temperature measurement circuit) which is an analog circuit using the operational amplifier which concerns on 3rd Embodiment. It is a figure for demonstrating the presence or absence of the offset adjustment of the to-be-measured circuit (temperature measurement circuit) which is an analog circuit using the operational amplifier which concerns on 3rd Embodiment.

Explanation of symbols

DESCRIPTION OF SYMBOLS 10 Vehicle drive system 11 Electric motor 12 Power supply 13 Buck-boost converter 14 Inverter 16 Reactor 17, C119, C604, C631 Capacitor 21, 22 Switching element 23a, 23b Control circuit 25, 26 IGBT
27, 28, 84 Diode 30 IPM for buck-boost converter
31 Upper Arm Switching Unit 32 Lower Arm Switching Unit 34, 35, 36, 37, 38 Photocoupler 40, 50 Temperature Detection Diode 41, 42, 51, 52, 80, 82, 89, R11, R12, R14, R15, R628, R637 Resistor 43, 53 IGBT protection circuit 44 Gate driver 45, 55 IGBT chip temperature detection unit 56 VH detection circuit 57 Voltage division circuit 58 Level adjustment circuit 59 Triangular wave generator 60 Comparator 62 LPF
63 VH comparator 64 Gate signal generator 70 Constant current source 71, 92 Buffer circuit 73, 101, 102 Operational amplifier 77, 120 Level converter 78 Triangle wave generator 79 Comparator (analog / PWM converter)
85 Light-emitting diode 87 Light-receiving diode 88, TR600 Transistor 90 Digital-analog converter 90a PWM / analog converter 91 Binary circuit 93 LPF circuit 300, 400 Input / output characteristic measuring device 302, 402 Circuit under test 304 Power supply for measurement 306 1 voltage measurement unit 307 second voltage measurement unit 308 third voltage measurement unit 310, 410 calculation unit 404 current measurement unit 406 switch R13 offset setting resistor R13A, R13B, R13C, R16A, R16B, R16C offset fine adjustment Resistor R14A, R14B, R14C, R15A, R15B, R15C Gain adjusting resistor Vcc1 First power supply (or power supply voltage)
Vcc2 Second power supply (or power supply voltage)
Vout IGBT chip temperature voltage signal (LPF output)

Claims (8)

In an input / output characteristic measuring device for an analog circuit including an operational amplifier in which circuit elements for adjusting offset and gain are combined,
A signal source for applying a plurality of known voltages to an input terminal of the analog circuit;
Measuring means for measuring an output voltage of the operational amplifier, a voltage of an output terminal of the analog circuit, and a power supply voltage for supplying an offset current of the operational amplifier during the application by the signal source;
A first input / output characteristic that is an input / output characteristic of the operational amplifier is obtained from a relationship between a signal voltage applied to an input terminal of the analog circuit and an output voltage of the operational amplifier, and the output voltage of the operational amplifier and the analog circuit In order to obtain the second input / output characteristic which is the input / output characteristic of the output terminal of the analog circuit from the output side of the operational amplifier from the relationship with the output voltage of the operational amplifier, and to set the input / output characteristic of the analog circuit as the target characteristic, It obtains the input and output characteristics required of the operational amplifier with a second input-output characteristic, comparing the first input-output characteristic and input-output characteristic to be the request, the first input-output characteristic Computing means for obtaining an adjustment value for adjusting the adjustment circuit element in order to adjust the offset and gain of the operational amplifier so as to match the required input / output characteristics. Device for measuring input / output characteristics of analog circuits including operational amplifiers. 2. The calculation according to claim 1, wherein the measurement unit does not measure input / output characteristics of the impedance conversion circuit when a circuit from the input terminal of the analog circuit to the input of the operational amplifier is an impedance conversion circuit. Device for measuring input / output characteristics of analog circuits including amplifiers. 3. The operational amplifier according to claim 1, wherein when calculating the offset adjustment value of the operational amplifier, the arithmetic means uses a measured value of a power supply voltage that supplies an offset current of the operational amplifier. Including analog circuit input / output characteristics measurement equipment. When a temperature detection diode is connected to the input terminal of the analog circuit and has a constant current source for supplying a constant forward current to the diode, a current measuring means for measuring the forward current supplied to the diode With
The arithmetic means obtains a deviation amount between a measured value of the forward current in the current measuring means and a prescribed value of the forward current, and based on the current deviation amount, the forward current of the deviation amount is supplied. 4. A shift amount of a forward voltage of the diode at the time is obtained, and correction is performed to shift an applied voltage to an input terminal of the analog circuit from a specified value based on the voltage shift amount. An input / output characteristic measuring apparatus for an analog circuit including the operational amplifier according to any one of the above. When performing the correction, the calculation means obtains a correction coefficient from the relationship between the voltage deviation amount and the current deviation amount, multiplies the correction coefficient and the current deviation amount to obtain a correction value, and calculates the correction value. The input / output characteristic measuring apparatus for an analog circuit including an operational amplifier according to claim 4, wherein a voltage applied to an input terminal of the analog circuit is corrected. An analog circuit including an operational amplifier in which circuit elements for adjusting the offset and gain are combined, a signal source that applies a plurality of known voltages to the input terminal of the analog circuit, and the calculation at the time of the application by the signal source An output voltage of the amplifier, a voltage at the output terminal of the analog circuit, a measuring means for measuring a power supply voltage for supplying an offset current of the operational amplifier, a signal voltage applied to the input terminal of the analog circuit, and the operational amplifier A first input / output characteristic, which is an input / output characteristic of the operational amplifier, is obtained from the relationship with the output voltage, and the analog from the output side of the operational amplifier from the relationship between the output voltage of the operational amplifier and the output voltage of the analog circuit. The second input / output characteristic which is the input / output characteristic of the output terminal of the circuit is obtained, and the second input / output characteristic of the analog circuit is set as the target characteristic. Obtains the input and output characteristics required of the operational amplifier by using the input-output characteristic, comparing the first input-output characteristic and input-output characteristic to be the request, the first input-output characteristic is the request Calculating means for adjusting the adjustment circuit element to adjust the offset and gain of the operational amplifier so as to match the input / output characteristics, and temperature detection connected to the input terminal of the analog circuit And a current measuring means for measuring a forward current supplied to the diode when the diode has a constant current source for supplying a constant forward current to the diode, and the computing means includes the current The amount of deviation between the measured value of the forward current in the measuring means and the prescribed value of the forward current is obtained, and the forward direction of the diode when the forward current of the amount of deviation is supplied based on the amount of current deviation. Voltage Obtains the displacement amount, in input-output characteristic measuring method of the analog circuit including an operational amplifier to correct for shifting the voltage shift amount the voltage applied to the input terminal of the analog circuit based on the specified value,
The adjustment limit range of the input / output characteristics of the operational amplifier is set to a value obtained by subtracting each value of the offset adjustment resolution, the measurement error in the current measuring means, and the error margin from the allowable error with respect to the specified value. A method for measuring input / output characteristics of an analog circuit including an operational amplifier, characterized in that the range is expanded in the positive and negative directions.   The method for measuring input / output characteristics of an analog circuit including an operational amplifier according to claim 6, wherein when the adjustment limit range is exceeded, the offset and gain of the operational amplifier are adjusted.   8. The method for measuring input / output characteristics of an analog circuit including an operational amplifier according to claim 7, wherein when adjusting the offset and gain of the operational amplifier, the gain is adjusted and then the offset is adjusted.

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