JP4775168B2 - Control device for three-phase rotating machine - Google Patents

Description

  The present invention relates to a control device for a three-phase rotating machine that controls an output of the three-phase rotating machine by operating a switching element of an inverter that supplies electric power to the three-phase rotating machine.

  This type of control device calculates a command value (command voltage) of a voltage to be applied to each phase in order to feedback control the current flowing in each phase of the three-phase motor to a command value, A device that performs PWM control for operating a switching element of an inverter based on the size of the carrier has been proposed. Thereby, the voltage applied to each phase of the three-phase motor can be used as a command voltage, and the current flowing through each phase can be feedback-controlled to the command value.

  In addition, in the high-speed rotation region of the three-phase rotating machine, so-called rectangular wave control is performed in which the ON / OFF cycle of the switching element of the inverter substantially matches the rotation cycle of the electrical angle of the three-phase rotating machine (Patent Document 1). 2).

  However, when the rectangular wave control is performed in the high rotation speed region and the PWM control is performed in other regions, the torque may change abruptly when switching from the rectangular wave control to the PWM control.

In addition to those that perform the rectangular wave control and the PWM control described above, the control device that performs the rectangular wave control and the current control that feedback-controls the detected value of the current flowing through the three-phase rotating machine to the command value. Such a situation in which torque fluctuation may occur in accordance with switching from rectangular wave control to current control is also generally common.
JP 2000-50689 A JP 2002-223590 A

  The present invention has been made in order to solve the above-described problems, and its purpose is to perform current control for feedback control of a detected value of current flowing through a three-phase rotating machine to a command value and rectangular wave control. An object of the present invention is to provide a control device for a three-phase rotating machine capable of suitably suppressing torque fluctuations associated with switching from rectangular wave control to current control.

  Hereinafter, means for solving the above-described problems and the operation and effects thereof will be described.

According to a first aspect of the present invention, a rectangular wave that operates the switching element to make the period of change in voltage applied to each phase of the three-phase rotating machine substantially coincide with the rotation period of the electrical angle of the three-phase rotating machine. Control means, current control means for feedback-controlling the detected value of the current flowing through the three-phase rotating machine to a current corresponding to a command value on the dq axis for the current flowing through the three-phase rotating machine, and the command value Storage means for storing information about possible values, and current flowing through the three-phase rotating machine based on the detected value of the current flowing through the three-phase rotating machine and the information during control by the rectangular wave control means when the value on the d-axis and q-axis which substantially coincides possible values and as the command value, and a switching means for switching from control by the rectangular wave control means control by the current control means, the switching The stage includes a calculation unit that calculates a current vector that is symmetric to an actual current vector that is a current vector on the dq axis of the current flowing through the three-phase rotating machine with respect to a curve in which the command value is drawn on the dq axis. When the symmetrical current vector and the actual current vector substantially match, the values on the d-axis and q-axis of the current flowing through the three-phase rotating machine substantially match the values that can be taken as the command value. The switching is performed .

  In the above configuration, when switching the current from the rectangular wave control to the current control when the values on the d-axis and q-axis of the current by the rectangular wave control substantially match the values that can be taken as the command value, Variations in the flowing current can be suppressed. For this reason, the fluctuation | variation of the torque accompanying switching can be suppressed suitably.

  The command value on the dq axis occupies a one-dimensional space in the dq axis plane. In other words, it is expressed by a curve. For this reason, by performing the process related to switching based on the above information, for example, the number of data to be stored for the process related to switching can be reduced as compared with the case of storing a region where rectangular wave control is performed. .

By the way, when the value on the dq axis of the current flowing through the three-phase rotating machine is on a curve drawing the command value on the dq axis, the actual current vector matches the symmetric current vector. For this reason, it is possible to preferably determine that the values on the d-axis and the q-axis for the current flowing through the three-phase rotating machine substantially match the values that can be taken as the command values based on these substantially matches.

According to a second aspect of the present invention, in the first aspect of the present invention, the calculating means includes a q-axis component of the symmetric current vector based on the value on the d-axis of the current flowing through the three-phase rotating machine and the information. And means for calculating the d-axis component of the symmetric current vector based on the value on the q-axis of the current flowing through the three-phase rotating machine and the information.

  The command value on the q-axis when the command value on the d-axis takes the value on the d-axis of the current flowing through the three-phase rotating machine becomes the q-axis component of the symmetric current vector. The command value on the d-axis when the command value on the q-axis takes the value on the q-axis of the current flowing through the three-phase rotating machine is the d-axis component of the symmetric current vector. For this reason, in the said structure, a symmetrical electric current vector can be calculated appropriately.

According to a third aspect of the present invention, in the first or second aspect of the invention, the current control means determines the detected values of the respective phases based on the detected values of the currents of the respective phases flowing through the three-phase rotating machine. Conversion means for converting to the above current and means for performing the feedback control based on the difference between the converted current and the command value are provided.

  In the above configuration, since the current control means includes the conversion means, the conversion means can be used in the switching means.

The invention according to claim 4 is the invention according to any one of claims 1 to 3 , wherein the command value is set to a value capable of generating a required torque for the three-phase rotating machine with a minimum current. It is characterized by.

  According to the above configuration, the power required to generate the output torque in the control by the current control unit can be minimized.

(First embodiment)
Hereinafter, a first embodiment in which a control device for a three-phase rotating machine according to the present invention is applied to a control device for a three-phase motor mounted on a hybrid vehicle will be described with reference to the drawings.

  In FIG. 1, the whole structure of the control system of the electric motor 4 is shown.

  The illustrated electric motor 4 is composed of an embedded magnet synchronous motor (IPMSM). In addition, an inverter 10 is connected to the three phases (U phase, V phase, and W phase) of the electric motor 4. This inverter 10 is a three-phase inverter, and switching elements 12 and 14 (U-phase arm) and switching elements 16 and 18 (V-phase) are connected to electrically connect each of the three phases to the positive side or negative side of the battery 42. Arm) and switching elements 20, 22 (W-phase arm) in parallel. Furthermore, the inverter 10 includes flywheel diodes 24 to 34 connected in antiparallel to the switching elements 12 to 22. A connection point for connecting the switching element 12 and the switching element 14 in series is connected to the U phase of the electric motor 4. A connection point for connecting the switching element 16 and the switching element 18 in series is connected to the V phase of the motor 4. Furthermore, a connection point for connecting the switching element 20 and the switching element 22 in series is connected to the W phase of the electric motor 4. Incidentally, these switching elements 12-22 are comprised by the insulated gate bipolar transistor (IGBT) in this embodiment.

  A smoothing capacitor 40 is connected to both ends of each pair of switching elements 12 and 14, switching elements 16 and 18, and switching elements 20 and 22 of the inverter 10.

  On the other hand, the microcomputer (microcomputer 50) includes a central processing unit and a memory 51. The microcomputer 50 includes a voltage sensor 44 that detects the voltage VB across the battery 42, a position sensor 52 that detects the rotation angle of the output shaft of the electric motor 4, and a current sensor 54 that detects the current flowing in the U phase and the V phase. , 56 are captured. The microcomputer 50 calculates the current flowing through the W phase from the current iu flowing through the U phase and the current iv flowing through the V phase based on Kirchhoff's law. The microcomputer 50 operates the switching elements 12 to 22 via the gate drive circuits 60 to 70 based on the rotation angle of the output shaft of the electric motor 4 and the currents flowing through the three phases.

  FIG. 2 shows a block diagram of processing performed by the microcomputer 50. In the present embodiment, the output torque of the electric motor 4 is controlled to the required torque by triangular wave PWM control and rectangular wave control. In the following, the processing shown in FIG. 2 will be described in the order of processing related to triangular wave PWM control, processing related to rectangular wave control, and processing related to switching between these two controls.

<PWM control>
The three-phase / two-phase conversion unit 80 includes an actual current iu flowing through the U phase and an actual current iv flowing through the V phase detected by the current sensors 54 and 56, and an actual current iw flowing through the W phase calculated based on these. Is a part for generating a real current id and a real current iq by converting the coordinates to the dq axis. Incidentally, since the rotation angle of the electric motor 4 is used for the coordinate conversion, the rotation angle θ detected by the position sensor 52 is input to the three-phase / two-phase conversion unit 80. On the other hand, the command current generator 82 is a part that generates command currents iqc and idc in accordance with the required torque Tc. These command currents iqc and idc are current command values on the dq axis.

  Based on the difference between the command current idc and the actual current id, the PI control unit 84 calculates a proportional term and an integral term. The sum of these calculated values is output from the PI controller 84 as the first command voltage vd1. Further, based on the difference between the command current iqc and the actual current iq, the proportional term and the integral term are calculated by the PI control unit 86. The sum of these calculated values is output by the PI controller 86 as the first command voltage vq1. Here, the behavior of the first command voltages vd1 and vq1 will be described.

Voltages vu, vv, vw applied to each of the three phases, currents iu, iv, iw flowing through the three phases, and counter electromotive forces eu, ev, ew generated in the three phases, respectively, and the resistance R of the motor 4 The relationship between the self-inductance L ′, the mutual inductance M, and the time differential operator P is as follows.

vu = (R + PL ′) × iu−1 / 2 × PM × iv−1 / 2 × PM × iw + eu
vv = -1 / 2 * PM * iu + (R + PL ') * iv-1 / 2 * PM * iw + ev
vw = −1 / 2 × PM × iu −1 / 2 × PM × iv + (R + PL ′) × iw + ew

Here, when dq-axis conversion is performed, the voltages vd and vq of the d-axis and the q-axis are represented by the rotation speed ω of the electrical angle, the inductance Ld on the d-axis, the inductance Lq on the q-axis, and the counter electromotive force ωφ. The following formulas (cd) and (cq) are obtained. Note that the rotation speed of the electrical angle is a value obtained by multiplying the rotation speed of the electric motor 4 by the number of pole pairs of the electric motor 4.

vd = (R + PLd) × id−ωLq × iq (cd)
vq = ωLd × id + (R + PLq) × iq + ωφ (cq)

As shown in the above formulas (cd) and (cq), each axis component of the voltage applied to the motor 4 is not only a term proportional to the same axis component of the current flowing through the motor 4, but also different axes. It includes terms proportional to the components and back electromotive force ωφ (hereinafter referred to as interference terms).

  Therefore, in the present embodiment, the non-interacting control unit 88 calculates these interference terms based on the actual current id and the actual current iq to calculate the zeroth command voltages vd0 and vq0. Then, the d-axis command voltage vdc1 is calculated as the sum of the first command voltage vd1 and the zeroth command voltage vd0, and the q-axis command voltage vqc1 is calculated as the sum of the first command voltage vq1 and the zeroth command voltage vq0. To do.

  The d-axis command voltage vdc1 and the q-axis command voltage vqc1 are taken into the two-phase / three-phase converter 92. The two-phase / three-phase converter 92 converts the d-axis command voltage vdc1 and the q-axis command voltage vqc1 into a U-phase command voltage vuc1, a V-phase command voltage vvc1, and a W-phase command voltage vwc1. To do. These command voltages vuc 1, vvc 1, vwc 1 are voltages to be applied to each phase when a command current is passed through each phase of the electric motor 4. These command voltages vuc1, vvc1, and vwc1 are basically sine waves and the centers of the voltages are zero. However, when the modulation rate of the command voltages vuc1, vvc1, and vwc1 is large based on the voltage of the battery 42 detected by the voltage sensor 44, the final command voltage vuc1, vvc1 is obtained by superimposing a predetermined harmonic on the sine wave. , Vwc1. The command current of each phase of the electric motor 4 means a command current in each of the three phases determined by the command currents idc and iqc.

  These command voltages vuc1, vvc1, and vwc1 are applied to the non-inverting input terminals of the comparators 94, 96, and 98, respectively. Comparators 94, 96, and 98 compare the command voltages vuc 1, vvc 1, and vwc 1 with the triangular carrier wave generated by the triangular wave generator 100. The output signals gu1, gv1, and gw1 of the comparators 94, 96, and 98 are obtained by pulse width modulation (PWM) of the command voltages vuc1, vvc1, and vwc1, respectively.

  The output signals gu1, gv1, and gw1 are taken into the switching unit 102. Then, a signal output from the switching unit 102 and an inverted signal thereof by the inverters 104, 106, and 108 are taken into the deadtime generation unit 110. The Deadtime generating unit 110 shapes the waveform of each of the output signals and the inverted signal corresponding to the signals so as to avoid the overlapping of the timings of the edge portions. The waveform-shaped signal includes an operation signal gup for operating the U-phase switching element 12, an operation signal gun for operating the U-phase switching element 14, and an operation signal gvp for operating the V-phase switching element 16, V-phase. The operation signal gvn for operating the switching element 18, the operation signal gwp for operating the W-phase switching element 20, and the operation signal gwn for operating the W-phase switching element 22.

  In the above configuration, when the output signals gu1, gv1, and gw1 are selected by the switching unit 102, the actual currents iu, iv, and iw are made to follow the three-phase currents (command currents) determined by the command currents idc and iqc. The switching elements 12 to 22 are operated by the control. At this time, the voltages applied to the three phases follow the command voltages vuc1, vvc1, and vwc1.

<Rectangular wave control>
The torque estimation unit 120 estimates the output torque of the electric motor 4 based on the actual currents id and iq on the dq axis output from the three-phase / two-phase conversion unit 80. The estimated torque Te may be calculated by the following equation using, for example, the torque constant Kt, d-axis inductance Ld, and q-axis inductance Lq of the electric motor 4.

Te = Kt × iq− (Ld−Lq) × id × iq
The vqc calculation unit 122 calculates the command voltage vqc2 on the q axis based on the difference between the required torque Tc and the estimated torque Te. On the other hand, the vdc calculation unit 124 calculates the command voltage vqc2 on the d-axis based on the command voltage vqc2 and the voltage VB of the battery 42. The vqc calculation unit 122 and the vdc calculation unit 124 perform processing for determining the phase of the voltage vector while the length of the voltage vector determined by the command voltages vqc2 and vdc2 is determined according to the voltage VB of the battery 42. . Then, the two-phase / three-phase conversion unit 126 converts the command voltages vqc2 and vdc2 into three-phase command voltages vuc2, vvc2, and vwc2. These command voltages vuc2, vvc2, and vwc2 are substantially sinusoidal signals. In addition, the output signal generation unit 128 generates output signals gu2, gv2, and gw2 based on the command voltages vuc2, vvc2, and vwc2. Here, the output signal gu2 becomes logic “H” when the command voltage vuc2 is zero or more, and becomes logic “L” when it is less than zero. Further, the output signal gv2 becomes logic “H” when the command voltage vvc2 is equal to or greater than zero, and becomes logic “L” when the command voltage vvc2 is less than zero. Further, the output signal gw2 becomes logic “H” when the command voltage vwc2 is zero or more, and becomes logic “L” when the command voltage vwc2 is less than zero. These output signals gu2, gv2, and gw2 are output to the switching unit 102.

  The command voltages vuc2, vvc2, and vwc2 have a period that is substantially equal to the rotation period of the electrical angle of the electric motor 4. For this reason, in the output signals gu2, gv2, and gw2, the repetition period of the logic “H” and the logic “L” is substantially the same as one period of the electrical angle. For this reason, when the output signals gu2, gv2, and gw2 are selected by the switching unit 102 in the above configuration, the upper switching elements 12, 16, and 20 and the lower switching elements 14, 18, and 22 of each phase arm are alternated. The cycle of turning on and off substantially coincides with one cycle of the electrical angle. For this reason, at the time of the rectangular wave control in which the output signals gu2, gv2, and gw2 are selected by the switching unit 102, the voltage applied to each phase of the electric motor 4 changes to a rectangular wave shape, and the cycle of the change is an electrical angle. It becomes substantially equal to one cycle.

<Switching process>
FIG. 3 shows a region where PWM control is performed and a region where rectangular wave control is performed. As shown in the figure, the PWM control is performed from the low rotation speed region to the medium rotation speed region, and the high rotation speed region is the region where the rectangular wave control is performed. The boundary between the region for performing PWM control and the region for performing rectangular wave control is on the lower rotational speed side as the required torque Tc is larger. Here, the reason why the PWM control is switched to the rectangular wave control in the high rotation speed region is as follows.

  The upper limit value of the voltage that can be applied to each phase of the electric motor 4 is the voltage VB of the battery 42. Therefore, when the maximum value of the command voltages vuc1, vvc1, and vwc1 is “½” or more of the voltage VB, in other words, when the modulation factor is “1” or more, the voltage is actually applied to each phase of the motor 4. Cannot be set to the command voltages vuc1, vvc1, vwc1. FIG. 4A shows the transition of the voltage applied to each phase when the modulation rate is “1”, and FIG. 4B shows the change applied to each phase when the modulation rate is greater than “1”. The transition of the applied voltage is shown. As shown in the figure, when the modulation rate is larger than “1”, the amplitude of the voltage applied to each phase is limited by “½” of the voltage VB of the battery 42. Must not. However, even in this case, as compared with the voltage shown in FIG. 4A, the utilization of the voltage is improved only in the region indicated by the oblique line in FIG. Thereby, the effective value of the voltage applied to each phase can be increased as compared with that shown in FIG. For this reason, it is possible to flow a three-phase command current determined by the command currents idc and iqc to the motor 4. Therefore, even if the maximum value of the command voltages vuc1, vvc1, and vwc1 is equal to or greater than “½” of the voltage VB, the PWM control is continued to cause the motor 4 to have a three-phase determined by the command currents idc and iqc. It is possible to pass an electric current.

  As the maximum values of the command voltages vuc1, vvc1, and vwc1 increase, finally, the voltage applied to each phase of the motor 4 is “VB / 2” in the same cycle as the command voltages vuc1, vvc1, and vwc1. ”And“ −VB / 2 ”. However, theoretically, it is known that the controllability by PWM control is extremely lowered when the modulation rate becomes “1.28”. For this reason, in this embodiment, the maximum value of the command voltages vuc1, vvc1, and vwc1 is a value that is “1.28 / 2” times the voltage VB of the battery 42, thereby switching from PWM control to rectangular wave control.

  Specifically, the switching control unit 130 illustrated in FIG. 2 takes in the command voltages vdc1 and vqc1 that define the command voltages vuc1, vvc1, and vwc1, and operates the switching unit 102 based on the command voltages. FIG. 5 shows a procedure of processing related to switching from PWM control to rectangular wave control among the processing performed by the switching control unit 130. This process is repeatedly executed by the microcomputer 50 at a predetermined cycle, for example, during a period in which PMW control is performed.

  In this series of processes, first, in step S10, it is determined whether or not the length of the voltage vector determined by the command voltages vdc1 and vqc1 is greater than or equal to the limit voltage VL. Here, the limit voltage VL is a value obtained by multiplying the voltage VB by the square roots of “1.28” and “3/8”. The voltage vector length on the dq axis is obtained by multiplying the maximum value of the command voltages vuc1, vvc1, and vwc1 by the square root of “3/2”. When the value when the modulation factor is “1.28” is used as the maximum value, this is a value obtained by multiplying “VB / 2” by “1.28”. For this reason, it is possible to determine whether or not the maximum value of the command voltages vuc1, vvc1, and vwc1 is equal to or larger than the value obtained by multiplying “VB / 2” by “1.28” by the above step S10. When an affirmative determination is made in step S10, in step S12, the switching unit 102 is operated to select the output signals gu2, gv2, and gw2, thereby switching from PWM control to rectangular wave control.

  When a negative determination is made in step S10 or when the process of step S12 is completed, this series of processes is temporarily ended.

  FIG. 6 shows currents on the dq axis that can be taken by PWM control and rectangular wave control. In the figure, a command current curve CL indicated by a solid line is a curve drawn by the command currents idc and iqc generated by the command current generator 82. This curve (command current idc, iqc) is appropriately set according to a request for control of the electric motor 4, but in the present embodiment, the required torque Tc can be realized with a minimum current on the dq axis. Is set by the current. On the other hand, what is indicated by a two-dot chain line in the figure is a limit curve LL that defines a boundary of current that can actually flow through the electric motor 4 on dq. The limit curve LL is determined based on the voltage VB of the battery 42 and the rotation speed. For this reason, during PWM control, the actual currents iq and id cannot exceed the upper limit PM that is the intersection of the command current curve CL and the limit curve LL. Therefore, when the command currents iqc and idc reach the upper limit PM, the control is switched to the rectangular wave control. By switching to the rectangular wave control, the current vector determined by the command currents iqc and idc shifts to the vector V1 by advancing the phase with respect to the vector V2. Thereby, the electric motor 4 can be controlled to a higher rotational speed.

  As described above, when the rectangular wave control is performed, generally, the current on the dq axis does not coincide with the current defined by the command current curve CL. Therefore, when switching from the rectangular wave control to the PWM control, the current flowing through the electric motor 4 changes greatly, and as a result, the output torque of the electric motor 4 may fluctuate.

  Therefore, in the present embodiment, information on the values that can be taken by the command currents idc and iqc is stored in the command current information storage unit 132 shown in FIG. 2, and values on the d-axis and q-axis for the current flowing through the motor 4 are stored. Is substantially the same as the value that can be taken as the command current iqc, switching from the rectangular wave control to the PWM control suppresses fluctuations in the output torque associated with the switching. Here, the command current information storage unit 132 is configured by the memory 51 shown in FIG. The command current information storage unit 132 stores information about the command current curve CL. This information may be map data that defines the relationship between the command current idc on the d-axis and the command current iqc on the q-axis, or may be a model formula that expresses the command current curve CL.

  Specifically, the coincidence is determined in the manner shown in FIG. That is, an actual current vector Ir that is a current vector on the dq axis of a current flowing through the motor 4 and a current vector Is that is symmetric with respect to the command current curve CL are calculated. It is determined that the values on the d-axis and the q-axis for the flowing current substantially match the values that can be taken as the command currents idc and iqc.

  FIG. 8 shows a procedure of processing related to switching to PWM control according to the present embodiment. This process is performed by the switching control unit 130 of FIG. 2, and specifically, is repeatedly executed by the microcomputer 50 at a predetermined period during a period in which rectangular wave control is performed.

  In this series of processing, first, in step S20, an actual current vector Ir is acquired. In other words, the actual currents id and iq are acquired. In the subsequent step S22, the d-axis component ids of the symmetric current vector Is is calculated based on the actual current vector iq that is the q-axis component of the actual current vector. This can be calculated by setting the d-axis component ids so that “ids, iq” is a point on the command current curve CL. Subsequently, in step S24, based on the actual current vector id which is the d-axis component of the actual current vector, the q-axis component iqs of the symmetric current vector Is is calculated. This can be calculated by setting the q-axis component iqs so that “id, iqs” is a point on the command current curve CL.

  Subsequently, in step S26, it is determined whether or not the symmetric current vector Ie and the actual current vector Ir substantially match. This determination may be made, for example, by comparing each component on the dq axis. Alternatively, it may be performed based on a comparison of vector lengths. When an affirmative determination is made in step S26, since the actual currents id and iq are considered to be on the command current curve CL, the process proceeds to step S28 to switch to PWM control. Incidentally, when the rectangular wave control is performed, the values of the PI control units 84 and 86 are fixed to zero.

  When a negative determination is made in step S26 or when the process of step S28 is completed, this series of processes is temporarily ended.

  FIG. 9 shows a time chart regarding the transition of the current vector by the switching process according to the present embodiment. As shown in FIG. 9 (a), when the length of the command voltage vector (vdc1, vqc1) on the dq axis reaches the limit voltage VL, the process shifts to the rectangular wave control, so that the symmetrical current vector Is and The actual current vector Ir does not match. By switching to rectangular wave control when the length of the command voltage vector becomes the limit voltage VL in this manner, switching can be performed while suppressing fluctuations in output torque. Moreover, by switching to the rectangular wave control, the voltage utilization factor (effective value of the primary component of the line voltage with respect to the voltage VB of the battery 42) in the high rotation speed region can be improved, and the rotation speed of the motor 4 can be increased. It is possible to control the rotation speed. Further, as shown in FIG. 9B, when the symmetrical current vector Is substantially matches the actual current vector Ir, switching to PWM control is performed while suitably suppressing fluctuations in the actual current vector. be able to.

  According to the embodiment described in detail above, the following effects can be obtained.

  (1) Based on the information stored in the command current information storage unit 132, during rectangular wave control, the values on the d-axis and the q-axis of the current flowing through the motor 4 are the values of the command currents idc and iqc of the PWM control. When it almost coincided with a possible value, the control was switched to PWM control. Thereby, the fluctuation | variation of the electric current which flows into the electric motor 4 at the time of switching can be suppressed. For this reason, the fluctuation | variation of the torque accompanying switching can be suppressed suitably. In addition, the command current on the dq axis occupies a one-dimensional space in the dq axis plane (represented by a curve). For this reason, the number of data to be stored for the processing related to the switching is compared with the case where the area for performing the rectangular wave control is stored by performing the processing related to the switching based on the information in the command current information storage unit 132, for example. Can also be reduced.

  (2) A current vector Is that is symmetric to the actual current vector Ir with respect to the command current curve CL, and when the symmetric current vector Is and the actual current vector Ir substantially match, d about the current flowing through the motor 4 It was determined that the values on the axis and the q-axis substantially coincided with the values that can be taken as the command currents idc and iqc. Thereby, it can be suitably determined whether or not there is a match between the values on the d-axis and the q-axis for the current flowing through the motor 4 and the values that can be taken as the command currents idc and iqc.

  (3) The q-axis component iqs of the symmetric current vector Is is calculated based on the information stored in the command current information storage unit 132 and the actual current id, and the information stored in the command current information storage unit 132 and the actual current Based on iq, the d-axis component ids of the symmetric current vector Is was calculated. Thereby, the symmetrical current vector Is can be calculated appropriately.

  (4) A three-phase two-phase conversion unit 80 that converts the three-phase actual currents iu, iv, and iw into the actual currents id and iq on the dq axis is provided, and the difference between the actual currents id and iq and the command currents idc and iqc PWM control was performed by performing feedback control based on the above. Thereby, the switching control unit 130 can divert the three-phase / two-phase conversion unit 80.

  (5) The command currents idc and iqc of the PWM control are set to values that can generate the required torque Tc for the electric motor 4 with the minimum current. Thereby, the electric power required for generating the output torque in the PWM control can be minimized.

(Second Embodiment)
Hereinafter, the second embodiment will be described with reference to the drawings with a focus on differences from the first embodiment.

  FIG. 10 shows a procedure of processing related to switching to PWM control according to the present embodiment. This process is performed by the switching control unit 130 shown in FIG. 2, and specifically, is repeatedly executed by the microcomputer 50 at a predetermined period during a period of rectangular wave control.

  In this series of processing, first, actual currents id and iq are acquired in step S30. In the subsequent step S32, the actual currents id and iq are substituted into the model formula f that determines the command currents idc and iqc, and it is determined whether or not the output value at that time is substantially zero. Here, the model formula satisfies “f (idc, iqc) = 0”, and when “f (id, iq)” is substantially zero, the actual currents id and iq are on the command current curve CL. It means that it is almost coincident with the point. Therefore, whether or not the values on the d-axis and the q-axis for the current flowing through the electric motor 4 substantially match the values that can be taken by the PWM control command currents idc and iqc, based on whether or not it is substantially zero. Can be judged. If an affirmative determination is made in step S32, the control is switched to PWM control in step S34.

  When a negative determination is made at step S32 or when the process at step S34 is completed, this series of processes is temporarily terminated.

  According to this embodiment described above, in addition to the effects (1), (4), and (5) of the first embodiment, the following effects can be obtained.

  (6) When the output of the model formula when substituting the actual currents id and iq into the model formula is substantially zero, the values on the d-axis and the q-axis for the current flowing through the motor 4 are the PWM control command currents It was determined that the values of idc and iqc could be substantially the same. Thereby, the number of data stored in the command current information storage unit 132 can be suitably reduced, and the above determination can be made by a simple method.

(Other embodiments)
Each of the above embodiments may be modified as follows.

  In the second embodiment, the model formula is quantified by “f (idc, iqc) = 0”, but not limited to this, “f (idc, iqc) = A (A: an arbitrary integer) " In this case, it is only necessary to determine whether or not the output of the model formula substantially matches A in step S32 of FIG.

  Switching from PWM control to rectangular wave control is not limited to the case where the command voltages vuc1, vvc1, and vwc1 are equal to or higher than the value obtained by multiplying the voltage VB of the battery 42 by “1.28 / 2”. However, it is desirable to perform switching when the voltage VB of the battery 42 is equal to or greater than a predetermined value equal to or less than a value obtained by multiplying the voltage VB of “1.28 / 2”.

  The rectangular wave control is not limited to the process illustrated in FIG. For example, the technique described in Patent Document 1 may be used.

  The PWM control is not limited to the process illustrated in FIG. For example, the non-interacting control unit 88 may not be provided. Further, the carrier wave for PWM control is not limited to a triangular wave but may be a sawtooth wave or the like. Further, not only the command currents idc and iqc on the dq axis are obtained from the request torque Tc, but the three-phase command currents iuc, ivc and iwc are directly obtained from the request torque Tc, and the command voltages vuc1, vvc1 and vwc1 are obtained based on this. May be calculated. Here, when the command voltages vuc1, vvc1, and vwc1 are obtained from the command currents iuc, ivc, and iwc, the relational expression that determines the relationship between the three-phase current and the three-phase voltage may be used.

  The current control for feedback control of the detected value of the current flowing in each phase of the motor 4 to the current corresponding to the command currents idc and iqc on the dq axis is not limited to the PWM control. For example, each of the two input terminals of the hysteresis comparator has one phase of each of the three-phase command currents iuc1, ivc1, and iwc1 determined based on the command currents idc and iqc, and the other has the same currents iu, iv, and iw. The instantaneous current value control may be performed by inputting one phase.

  -The three-phase motor is not limited to IPMSM. Further, the three-phase rotating machine is not limited to a three-phase motor, and may be, for example, a three-phase generator.

  The control device for the three-phase rotating machine is not limited to the microcomputer 50 but may be a dedicated integrated circuit (IC), for example.

The figure which shows the electric motor concerning 1st Embodiment, and its control system. The block diagram which shows the process of the output control of the electric motor concerning the embodiment. The figure which shows the area | region of PWM control and rectangular wave control concerning the embodiment. The time chart which shows the problem of PWM control. The flowchart which shows the procedure of the switching process from PWM control concerning the said embodiment to rectangular wave control. The figure explaining the switching conditions from the rectangular wave control concerning the said embodiment to PWM control. The figure explaining the switching method from rectangular wave control to PWM control concerning the embodiment. 6 is a flowchart showing a procedure for switching processing from rectangular wave control to PWM control according to the embodiment; The time chart which shows transition of the current vector by the said switching process. The flowchart which shows the procedure of the switching process from the rectangular wave control concerning 2nd Embodiment to PWM control.

Explanation of symbols

  DESCRIPTION OF SYMBOLS 4 ... Electric motor, 10 ... Inverter, 12-22 ... Switching element, 50 ... Microcomputer (one Embodiment of the control apparatus of a three-phase rotary machine).

Claims (4)

In a control device for a three-phase rotating machine that controls the output of the three-phase rotating machine by operating a switching element of an inverter that supplies power to the three-phase rotating machine,
Rectangular wave control means for operating the switching element to make the period of change in the voltage applied to each phase of the three-phase rotating machine substantially coincide with the rotation period of the electrical angle of the three-phase rotating machine;
Current control means for feedback-controlling the detected value of the current flowing through the three-phase rotating machine to a current according to a command value on the dq axis for the current flowing through the three-phase rotating machine;
Storage means for storing information about possible values of the command value;
At the time of control by the rectangular wave control means, values on the d-axis and q-axis for the current flowing through the three-phase rotating machine are based on the detected value of the current flowing through the three-phase rotating machine and the information. Switching means for switching from the control by the rectangular wave control means to the control by the current control means when substantially equal to the value that can be taken as,
The switching means calculates a current vector that is symmetrical to an actual current vector that is a current vector on the dq axis of the current flowing through the three-phase rotating machine with respect to a curve in which the command value is drawn on the dq axis. When the symmetric current vector and the actual current vector substantially match, the values on the d-axis and the q-axis of the current flowing through the three-phase rotating machine substantially match the values that can be taken as the command value. Then, a control device for a three-phase rotating machine , wherein the switching is performed . The calculating means calculates a q-axis component of the symmetric current vector based on the value on the d-axis of the current flowing through the three-phase rotating machine and the information; and q of the current flowing through the three-phase rotating machine control apparatus for a three-phase rotary machine according to claim 1, characterized in that it comprises means for calculating a value on the axis and the d-axis component of the symmetrical current vector on the basis of said information. The current control means is a conversion means for converting the detected value of each phase into a current on the dq axis based on the detected value of the current of each phase flowing through the three-phase rotating machine, and the converted current and the command based on the difference between the value, the control unit of the three-phase rotary machine according to claim 1, wherein further comprising a means for performing the feedback control. The control device for a three-phase rotating machine according to any one of claims 1 to 3 , wherein the command value is set to a value that can generate a required torque for the three-phase rotating machine with a minimum current. .

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