JP4580679B2 - Motor drive device - Google Patents

Description

  The present invention relates to a motor drive device, and more particularly to a motor drive device that drives and controls a brushless motor by an inverter circuit.

  The brushless motor generates a counter electromotive force ωE (E: magnetomotive force (main magnetic flux) of a permanent magnet used as a field magnet, ω: shaft angular velocity of the motor) by its operation. Therefore, an equivalent circuit per phase of the brushless motor can be expressed as shown in FIG.

  In FIG. 11A, R is a primary resistance per phase of the brushless motor, L is an inductance per phase of the brushless motor, I is a primary current (phase current) of the brushless motor, and V is a terminal applied to the motor. Voltage.

  When a brushless motor is driven by an inverter circuit, a value obtained by multiplying the input voltage of the inverter circuit by the voltage conversion ratio (output voltage / input voltage <1) of the inverter circuit is the terminal voltage V of the motor.

Further, when the terminal voltage V of the brushless motor is vector-decomposed and expressed using the d-axis voltage Vd and the q-axis voltage Vq, the terminal voltage V is expressed by the following expressions (1) and (2). .

Further, when the vector diagram is drawn based on the equation (1) on the assumption that the primary resistance R is sufficiently small, the vector diagram is as shown in FIG.
However, Ld is d-axis inductance, Lq is q-axis inductance, Id is d-axis current (field current), and Iq is q-axis current (torque current). Here, the field current Id and the torque current Iq are the phase advance angle (hereinafter referred to as advance value) of the current (motor current) flowing through the motor with respect to the rotor position of the brushless motor, and the amplitude of the motor current I. When the value is Ip, it is expressed by the formula (3a) and the formula (3b).

The above equations (1) and (2) indicate that vector control of the brushless motor, that is, motor control using the field current Id and the torque current Iq is possible. Specifically, the vector control controls the command value of the field current Id to be a constant value (for example, 0), while changing the command value of the torque current Iq based on the output torque required for the brushless motor. It is to change. If the inverter circuit that drives the brushless motor is controlled based on these command values, the output torque T represented by the equation (4) can be obtained.

  The first term of Equation (4) indicates the torque component generated by the permanent magnet that is a field, that is, the magnet torque, and the second term indicates the reluctance torque generated by the saliency of the brushless motor. Therefore, when the brushless motor is a non-salient pole machine, Ld = Lq, and the above equation (4) is only the first term, and when the brushless motor is a salient pole machine, Ld ≠ Lq. In the above equation (4), the second term has a value.

この式（５）から分かるように、ブラシレスモータの回転数Ｎ、つまりブラシレスモータの軸角速度ωが高くなると、逆起電圧ωＥがこれに比例して増加することになる。従って、逆起電圧ωＥの増加をそのまま許容すると、逆起電圧ωＥの増加によりブラシレスモータの端子電圧Ｖがインバータ回路の入力電圧よりも上昇し、それ以上の回転数でブラシレスモータを駆動することができなくなる。 Further, the terminal voltage V of the motor is expressed by the following equation (5).

As can be seen from this equation (5), when the rotational speed N of the brushless motor, that is, the axial angular speed ω of the brushless motor increases, the counter electromotive voltage ωE increases in proportion thereto. Therefore, if the increase in the back electromotive voltage ωE is allowed as it is, the increase in the back electromotive voltage ωE causes the terminal voltage V of the brushless motor to rise above the input voltage of the inverter circuit, and the brushless motor can be driven at a higher rotational speed. become unable.

  As a method for coping with such a problem, there is a so-called field weakening control (see Non-Patent Document 1, for example).

  That is, this method supplies the field current Id and performs control to generate a field magnetomotive force that attenuates the field magnetomotive force of the permanent magnet, whereby the motor terminal voltage V in the high rotation range is input to the inverter circuit. It can be suppressed below the voltage. The field current Id having such a property is called a field weakening current. The field weakening current Id is determined in advance from the rotational speed N and torque T of the motor. Specifically, the correspondence between the values of the motor rotation speed N and torque T and the field weakening current Id suitable for these rotation speed N and torque T values is defined by a table (map) or the like. Has been. In the actual control of the field current Id, the value of the field weakening current Id is set to a value suitable for the torque T and the rotation speed N using the above table (for example, see Non-Patent Document 1).

  However, when the field weakening current Id is controlled using the table value as described above, the field weakening current Id becomes excessive or small as the input voltage of the inverter circuit fluctuates, and the driving efficiency of the motor is reduced. Or the required torque cannot be satisfied and the maximum rotational speed cannot be realized.

  For example, when the inverter input voltage is high, the field weakening current Id more than necessary is passed. As is clear from the vector diagram and equation (5) shown in FIG. 11B, the terminal voltage V is lowered by passing the field weakening current Id, but a current Id that does not contribute to torque generation is generated. Therefore, the efficiency is reduced.

  On the contrary, when the inverter input voltage is low, the field weakening current Id sufficient to keep the motor terminal voltage V below the inverter input voltage cannot flow, and the torque current for obtaining the necessary torque Iq cannot flow.

  Therefore, a method of detecting the inverter input voltage and calculating the field weakening current from the detected voltage and the torque required for the motor is considered (for example, see Patent Document 1).

Further, as a method for determining the field weakening current Id, the field weakening current Id is detected so that the inverter circuit output voltage becomes equal to or higher than the inverter input voltage, and the high inverter output voltage state is thus eliminated. There is also a method of controlling (see, for example, Patent Document 2).
1991 National Conference of the Institute of Electrical Engineers of Japan “No. 74, Speed Control System Using PM Motor Weakening Magnetic Flux Control” Japanese Patent No. 3146791 (FIGS. 1 and 10) JP 2000-341991 (FIG. 1)

  However, in the conventional motor driving device that controls the field weakening current of the motor according to the input voltage of the inverter circuit, when the input voltage of the inverter circuit fluctuates sharply or periodically, the input The value of field weakening current Id that is commanded varies according to the variation in voltage. In other words, the motor may exhibit a very unstable behavior due to the variation of the input voltage.

  Further, since the conventional motor drive device has a circuit for detecting the inverter input voltage, the detection accuracy and responsiveness in this circuit have an effect on the determination of the field weakening current, which is the control amount in the field weakening control. There is also.

  The present invention has been made in order to solve the above-described problems. Even if the voltage source has a steep or large fluctuation in the output voltage, the field-weakening control of the brushless motor is performed in advance. An object of the present invention is to obtain a motor drive device that can be stably performed without using a control amount such as a set table value, and thereby can increase the maximum rotation speed of a brushless motor.

The present invention is a motor drive device for driving a brushless motor, wherein an inverter circuit for converting an output voltage of a voltage source into a drive voltage and outputting the drive voltage to the brushless motor, and rotor position estimation for estimating a rotor position of the brushless motor And an inverter control unit that controls the inverter circuit so that the brushless motor is driven by a current based on the estimated rotor position, and a rotation speed determination unit that determines a command rotation speed of the brushless motor; , and the actual rotation speed detector which detects the actual rotational speed of the brushless motor, further comprising a said inverter control unit includes a rotor position which is above Symbol estimate, the phase difference between the current supplied to the brushless motor increased or decreased, the according to the rotation speed of the change of the brushless motor caused by the adjustment of the previous phase difference brushless Repeatedly adjusted so that the actual rotational speed of the motor coincides with the command rotation speed is the target value, it is characterized in.

This gun onset bright, in the motor driving apparatus, the inverter control section, the amplitude value of the current supplied to the brushless motor in a state of being fixed to the maximum value, the rotational speed of the brushless motor by increasing or decreasing the phase difference It is characterized by controlling.

This gun onset bright, in the motor driving apparatus, the maximum amplitude value of the current supplied to the brushless motor is a maximum current value to be supplied to the brushless motor is permitted, which is characterized in that It is.

According to the present invention, there is provided a motor drive device for driving a brushless motor, wherein an inverter circuit for converting an output voltage of a voltage source into a drive voltage and outputting the drive voltage to the brushless motor, and a rotor for estimating a rotor position of the brushless motor A rotational speed determination that includes a position estimation unit and an inverter control unit that controls the inverter circuit so that the brushless motor is driven by a current based on the estimated rotor position, and determines a command rotational speed of the brushless motor parts and, and the actual rotation speed detector which detects the actual rotational speed of the brushless motor, further comprising a said inverter control unit includes a rotor position which is above Symbol estimated position of the current supplied to the brushless motor the increased or decreased retardation, the blanking according to the rotation speed of the change of the brushless motor caused by the adjustment of the previous phase difference It is characterized in that the actual rotational speed of the Siles motor is repeatedly adjusted so as to coincide with the command rotational speed that is the target value, so that the input voltage of the inverter circuit can be adjusted without using a control amount such as a preset table value. Appropriate field weakening control can be performed without being affected by fluctuations.

In other words, since it does not perform complicated processing such as detecting the input voltage of the inverter and calculating the field-weakening control amount from the value, field-weakening control can be performed with a very simple circuit configuration. Since no detection error or calculation error of the field-weakening control amount occurs, stable field-weakening control can be performed even if the inverter input voltage fluctuates excessively.
As a result, stable drive control of the brushless motor can be realized with a simple circuit configuration.

According to this gun onset bright, in the motor driving apparatus, the inverter control section, the amplitude value of the current supplied to the brushless motor in a state of being fixed to the maximum value, the brushless motor by increasing or decreasing the phase difference Since the rotational speed is controlled, the rotational speed control is performed in a state where fluctuations in the current flowing through the brushless motor are suppressed, and further stable field-weakening control can be realized.

According to this gun onset bright, in the motor driving apparatus, the maximum amplitude value of the current supplied to the brushless motor is a maximum current value to be supplied to the brushless motor is permitted, and wherein the Therefore, even if the field weakening control is performed, a current that the brushless motor does not permit, that is, a current that demagnetizes the brushless motor does not flow, and a safe driving device can be provided.

  In addition, since the rotation speed is controlled by adjusting the phase difference in a state where the current amplitude value is held at the maximum current value permitted to be supplied to the brushless motor, the smallest field weakening current The required number of revolutions is realized, and as a result, the motor can be driven with the most efficient current advance value.

Embodiments of the present invention will be described below.
(Embodiment 1)
FIG. 1 is a block diagram for explaining a motor driving apparatus according to Embodiment 1 of the present invention.
The motor driving apparatus 100a according to the first embodiment is configured to drive the brushless motor 2 at a required number of revolutions with the voltage source 1 as an input, and the motor current phase with respect to the rotor position of the motor. The field weakening control of the brushless motor 2 is performed by changing the advance angle (advance value) β.

  In the first embodiment, the motor current advance value β is controlled such that the deviation between the command rotational speed for the motor and the actual rotational speed is zero. In the prior art, the control target in the field weakening control is the field weakening current Id. However, in the field weakening control, the advance value β of the motor current in the first embodiment and the field weakening current Id shown in the prior art are used. Is almost the same control object.

Hereinafter, the inverter circuit 3 and the inverter control unit 4a constituting the motor driving device 100a will be described in detail.
The inverter circuit 3 converts the output voltage of the voltage source 1 into a three-phase alternating current based on the drive signal Sg output from the inverter control unit 4a and supplies it to the brushless motor 2.

  The inverter circuit 3 includes first and second switching elements 31 and 32 connected in series, third and fourth switching elements 33 and 34 connected in series, and fifth and sixth switching elements 35 connected in series. And 36. One ends (high potential side terminals) of the first, third, and fifth switching elements 31, 33, and 35 are commonly connected, and the common connection point (one input node) is one output node 1a of the voltage source 1. It is connected to the. The other ends (low potential side terminals) of the second, fourth, and sixth switching elements 32, 34, and 36 are commonly connected, and the common connection point (the other input node) is the other output of the voltage source 1. It is connected to the node 1b. The first to sixth switching elements 31 to 36 have first to sixth diodes 41 to 46 connected in antiparallel, respectively. The connection point 3a between the first and second switching elements 31 and 32 is the first output node of the inverter circuit 3, and the connection point 3b between the third and fourth switching elements 33 and 34 is the inverter circuit 3. A connection point 3 c between the second output node and the fifth and sixth switching elements 35 and 36 is a third output node of the inverter circuit 3. The first to third output nodes 3 a to 3 c of the inverter circuit 3 are input nodes for each phase of the three-phase input of the motor 2.

  In the first embodiment, the inverter circuit 3 is a circuit having a three-phase full bridge configuration. However, the inverter circuit 3 may have any circuit configuration as long as it can output a three-phase alternating current. . For example, the inverter circuit 3 may be configured by using a capacitor in a circuit portion corresponding to one phase of the three-phase AC output. The inverter circuit 3 may be one in which a snubber circuit is added to each switching element.

  The voltage source 1 has a variable output level, outputs a voltage obtained by rectifying the output voltage of an AC power supply (not shown) by a rectifier circuit, and the output voltage is smoothed. For example, a power source with a small-capacitance capacitor on the output side or a battery with a small capacity can be considered.

  That is, the voltage source 1 is not limited to the one that always outputs a DC voltage of a specified level, but the output voltage level fluctuates instantaneously, for example, the output voltage level is about half of the specified level, or It may be one that drops to zero level.

  The inverter control unit 4a supplies a drive signal (gate signal) Sg to the inverter circuit 3 so that the brushless motor 2 is driven at a rotational speed desired by the user. The value determination unit 6 a and the drive signal generation unit 7 are configured.

  Here, the rotor position estimation unit 5 estimates the rotor position from the current (motor current) I actually supplied to the brushless motor 2 by the inverter circuit 3. Here, the specific method for estimating the rotor position is not limited to the method for estimating the rotor position from the motor current I, but a method using the induced voltage of the brushless motor 2 or a position sensor attached to the brushless motor. The rotor position may be estimated based on the detected output.

  The advance value determination unit 6a is configured to differentiate the command rotational speed fo indicated by an external command signal generated by the user's operation or the like and the rotor position θ estimated by the rotor position estimation unit 5 of the brushless motor 2 obtained. The advance value β of the current supplied to the brushless motor 2 is determined from the actual rotational speed f. In other words, the advance value determination unit 6a determines the advance value β so that the deviation between the actual rotational speed f and the command rotational speed fo becomes zero. In this way, the advance value β is determined. Specific methods include a hill climbing method and PI (proportional integration) control.

  The drive signal creation unit 7 includes a current (motor current) I output from the inverter circuit 3 to the brushless motor 2, an estimated phase (estimated position) θ of the rotor obtained by the rotor position estimation unit 5, and an advance value determination unit 6a is used as an input, and the drive signal Sg is output to the inverter circuit 3 so that the phase of the motor current I advances from the estimated rotor phase θ by the advance value β.

Next, the operation will be described.
In the inverter circuit 3 to which the voltage source 1 is input, the switching elements 31 to 36 are turned on / off by the drive signal Sg from the inverter control unit 4a. The output voltage of the voltage source 1 is output from the inverter circuit 3. It is converted into a three-phase alternating current and output to the motor 2. Then, the motor 2 is driven.

  At this time, the inverter control unit 4a applies to the gates of the switching elements 31 to 36 based on the command rotational speed fo indicated by the command signal from the outside and the current (motor current) I supplied to the motor 2. A pulse signal which is the drive signal Sg to be generated is generated.

Hereinafter, the operation of each unit 5, 6a and 7 of the inverter control unit 4a will be described.
In the rotor position estimation unit 5, the rotor position (rotor phase) is estimated from the current (motor current) I supplied from the inverter circuit 3 to the brushless motor 2.

  In the advance angle determination unit 6a, based on the command rotational speed fo indicated by the external command signal and the actual rotational speed f of the brushless motor 2 obtained by differentiating the rotor estimated phase θ from the rotor position estimation unit 5. Thus, the advance value β of the motor current supplied to the brushless motor 2 is determined.

  In the drive signal creation unit 7, the current (motor current) I actually output from the inverter circuit 3 to the brushless motor 2, the estimated rotor phase θ obtained by the rotor position estimation unit 5, and the advance value determination unit 6 a A drive signal Sg output to the inverter circuit 3 is generated based on the determined advance value β. Then, the inverter circuit 3 performs on / off control of each switching element by the drive signal Sg, and the inverter circuit 3 is adjusted so that the phase is advanced by the advance value β from the rotor estimated phase θ. The current I is output to the motor 2.

Hereinafter, an example of a method for determining the advance value β using the hill-climbing method will be described with reference to the flowchart shown in FIG.
In the advance angle determination unit 6a, when there is a deviation between the rotation speed command fo and the actual rotation speed f, the advance angle determination unit 6a starts the process of determining the advance value β.
First, in step S1, the absolute value (| fo−f |) of the deviation between the command rotational speed fo and the actual rotational speed f is calculated.

  Next, in step S2, based on the β increase flag, it is determined which of the process of increasing the advance value β (step S3) and the process of decreasing the advance value β (step S4) is performed. Is done. That is, if the value of the β increase flag is [−1], the process of step S3 is performed. If the value of the increase flag is [1], the process of step S4 is performed. When the process of the flow shown in FIG. 2 is first performed, in the process of step S2, the value of the β increase flag is set as an initial value in advance, either [1] or [−1] The value of

  In step S3, a process of reducing (delaying) the advance angle value β currently output is performed. The amount by which the advance value β is decreased in this step S3 may be a fixed amount determined in advance, the deviation between the rotational speed command fo and the actual rotational speed f (rotational speed deviation), or the rotational speed calculated last time. You may determine based on the difference of a deviation and the rotation speed deviation calculated this time. When the amount of decrease in the advance value β in step S3 is determined based on the rotational speed deviation as described above, the speed of mountain climbing (that is, the speed of processing for determining the advance value by the hill climbing method) is increased, and the responsiveness is high. The advance value β at which the rotational speed deviation becomes zero can be determined.

  In step S4, a process of increasing (advancing) the currently output advance value β is performed. The amount by which the advance value β is increased in step S4 may be a predetermined constant amount, the deviation (rotational speed deviation) between the command rotational speed fo and the actual rotational speed f, or the previously calculated rotational speed. You may determine based on the difference of a number deviation and the rotation speed deviation calculated this time. As described above, when the increase amount of the advance value β in step S4 is determined based on the rotational speed deviation, the climbing speed is increased, and the advanced value β at which the rotational speed deviation becomes zero with good responsiveness is determined. be able to.

  In step S5, the absolute value of the deviation between the command rotational speed fo and the actual rotational speed f is calculated again with the motor current advance value β updated to the advance value β determined in step S3 or S4. Processing is performed.

  In step S6, the absolute value of the rotation speed deviation before updating the advance value β of the motor current to the advance value β determined in step S3 or S4, and the rotation speed deviation after the update of the advance value β are calculated. If the difference from the absolute value is calculated and the advance value β is updated (the absolute value of the rotational speed deviation) is greater than the value before the advance value β is updated (the absolute value of the rotational speed deviation), the step If the process of S7 is performed and the updated value of the advance value β is equal to or smaller than the value before the update of the advance value β, the process of step S8 is performed.

  In step S7, since the direction in which the advance value β is changed is incorrect, a process of inverting the sign of the β increase flag is performed, and then the process of step S8 is performed.

  In step S8, the deviation (rotational speed deviation) between the rotational speed command fo and the actual rotational speed f is calculated, and if the rotational speed deviation is zero or within an allowable range, an advance angle determination unit. When the advance value determination process at 6a (the process in the flow of FIG. 2) is completed and the rotation speed deviation is not within the allowable range, the process of step S2 is performed again.

  If the process of adjusting the advance value β of the motor current using the hill climbing method as described above is performed, for example, the input voltage of the inverter is too low to increase the motor rotation speed to the command rotation speed fo, Even if the deviation between the rotational speed command fo and the actual rotational speed f does not become zero, the advance value β of the motor current converges to a value that can generate the most torque, and the motor 2 can be stably rotated at high speed. It becomes.

  The flow of the advance value determination process shown in FIG. 2 is an example, and this is because the process of step S8 in the flow shown in FIG. 2 is performed between the process of step S5 and the process of step S6 in the flow. It may be a thing. In this case, the same effect as the flow shown in FIG. 2 can be obtained. As can be seen from this, the processing flow for determining the advance value can take various forms.

  In addition, the advance value is determined by PI (proportional integration) control for determining the advance value β so that the deviation between the rotational speed command fo and the actual rotational speed f becomes zero instead of the hill climbing method as described above. It may be used. However, in this case, since the advance value β may diverge, it is necessary to provide a limiter value.

  Thus, in the first embodiment, the inverter circuit 3 that converts the output voltage of the voltage source 1 into three-phase alternating current and outputs it to the motor 2, and the current (motor current) supplied from the inverter circuit 3 to the motor 2 An inverter control unit 4a for controlling the advance value β, and the inverter control unit 4a determines the advance value β of the motor current so that the deviation between the command rotational speed fo and the actual rotational speed f is minimized. Therefore, stable field-weakening control of the brushless motor can be performed without using a control amount such as a preset table value.

  That is, in the motor current advance value control according to the first embodiment, since there is no detection error or calculation error of the input voltage of the inverter circuit, the fluctuation of the inverter input voltage is steep or periodic and large. However, stable field-weakening control can be performed.

  Further, in the first embodiment, since the complicated calculation processing such as detecting the input voltage of the inverter circuit 3 and calculating the advance value β from the detected value is not performed, the motor driving device is very simple. A circuit configuration is possible.

  In the first embodiment, the drive signal creation unit 7 does not limit the amplitude value of the motor current. However, the drive signal creation unit 7 has a maximum amplitude value of the current supplied to the brushless motor 2. The drive signal Sg of the inverter circuit 3 may be created so as to be held at a constant value. In this case, in the advance angle determination unit 6a, an excessive increase / decrease in the advance value β of the motor current determined based on the actual rotational speed of the motor is suppressed, and more stable field-weakening control can be realized. . Further, by setting the maximum amplitude value of the motor current held at the constant value to be the maximum current value allowed by the brushless motor 2, a current that the brushless motor does not allow even if the field weakening control is performed, that is, the brushless motor A current that deteriorates due to demagnetization does not flow, and a safe motor drive device can be provided.

  In the first embodiment, the advance value determination unit 6a calculates the advance value of the motor current between the command rotational speed fo and the actual rotational speed f regardless of the value of the current supplied to the brushless motor 2. The advance value determining unit 6a determines that the deviation is small, but when the current supplied to the brushless motor 2 is less than the allowable current, the optimum advance value ( It is also possible to output an advance value that utilizes the most reluctance torque) or a constant advance value. In this case, the rotation speed of the brushless motor 2 is controlled by the amplitude value of the supplied current.

  In such a configuration, the motor current advance value is set to the optimum advance value at a low speed that can be driven at the command rotational speed without performing field weakening control, and the field weakening control that requires field weakening control is required. At the time of rotation, the advance value of the motor current can be set to the lowest advance value that realizes the command rotation speed, and the motor can be advanced to satisfy the maximum efficiency of the brushless motor 2 over the entire rotation speed range. It can be driven with angular values.

(Embodiment 2)
FIG. 3 is a block diagram for explaining a motor drive apparatus according to Embodiment 2 of the present invention.
Similar to the motor drive device 100a of the first embodiment, the motor drive device 100b of the second embodiment receives the voltage source 1 and drives the brushless motor 2 at an arbitrary rotational speed. The field weakening control is performed by adjusting the advance value β of the motor current. In the second embodiment, the motor current advance value β is controlled in a state where the amplitude value of the current supplied to the motor is held at a constant value and the command rotational speed fo to the motor and the actual rotational speed f. And the deviation is zero.

  In other words, the motor drive device 100b includes an inverter circuit 3 that converts the output voltage of the voltage source 1 into a three-phase alternating current and outputs the same to the motor 2, and an inverter control unit 4b that controls the inverter circuit 3. Yes.

  The inverter control unit 4b supplies a drive signal Sg to the inverter circuit 3 so that the brushless motor 2 is driven at a rotational speed desired by the user. The inverter position estimation unit 5 and the advance value determination unit 6a And a command current waveform creation unit 8 b and a PWM creation unit 9.

Hereinafter, the motor drive device 100b of the second embodiment will be described in detail.
Here, the voltage source 1, the inverter circuit 3, the rotor position estimation unit 5, and the advance angle determination unit 6a are the same as those in the motor drive device 100a of the first embodiment.

  The command current waveform generator 8b receives the estimated phase θ output from the rotor position estimator 5 and the advance value β determined by the advance value determiner 6a, and the current supplied from the inverter circuit 3 to the brushless motor 2 The waveform of the command value (command current) Io is created. Specifically, the waveform of the command current Io created by the command current waveform generation unit 8 includes a command amplitude value of the current supplied to the motor (amplitude value of the command current) and an advance value β in the estimated phase θ. A sinusoidal waveform having a phase obtained by adding together is obtained. Here, the command amplitude value is a fixed value and is the maximum amplitude value allowed for the brushless motor 2.

  The PWM creation unit 9 receives the actual current (actual current) I output from the inverter circuit 3 to the brushless motor 2 and the command current Io created by the command current waveform creation unit 8b. A pulse signal that is the drive signal Sg supplied to the inverter circuit 3 is generated so that the deviation of the waveform of the current Io becomes zero. Specifically, the PWM generator 9 performs PI control on the difference between the command current Io and the actual current I so that the deviation between the waveform of the actual current I and the waveform of the command current Io becomes zero. PWM (pulse width modulation) width is determined.

Next, the operation will be described.
In the motor drive device 100b of the second embodiment, the inverter circuit 3 operates in the same manner as that of the motor drive device 100a of the first embodiment, and the motor 2 is driven by the output from the inverter circuit 3.

  At this time, the inverter control unit 4b supplies the gates of the switching elements 31 to 36 based on the command rotational speed fo indicated by the command signal from the outside and the current (motor current) I supplied to the motor 2. A pulse signal which is the drive signal Sg to be generated is generated.

Hereinafter, the operation of each unit 5, 6a, 8b and 9 of the inverter control unit 4b will be described.
In the second embodiment, the operation of the rotor position estimation unit 5 to estimate the rotor position θ from the motor current I and the operation of the advance value determination unit 6a to determine the advance value β of the motor current This is performed in the same manner as in the first mode.

  In the command current waveform creation unit 8b, the amplitude value matches the command amplitude value based on the estimated phase θ output from the rotor position estimation unit 5 and the advance value β determined by the advance value determination unit 6a. A waveform of the command current Io whose phase matches the sum of the estimated phase θ and the advance value β is generated. Here, the command amplitude value is always held at the maximum value allowed for the brushless motor 2.

  In the PWM generator 9, the PWM width of the pulse signal which is the drive signal Sg supplied to the inverter circuit 3 so that the deviation between the waveform of the actual motor current (actual current) I and the waveform of the command current Io becomes zero. Is determined. Specifically, the PWM width of the pulse signal is determined by performing PI control on the difference between the command current Io and the actual current I.

  FIG. 4 is a conceptual diagram for explaining the effect of the second embodiment. The fluctuation of the input voltage of the inverter circuit (FIG. 4A) and the change of the motor current when the advance value β is not controlled (FIG. 4). (b)) shows a change in the motor current (FIG. (c)) when the advance value β is controlled. In the figure, Io is a current commanded to flow to the motor (command current), I is a current actually flowing to the motor (actual current), and Am is a maximum amplitude value of the command current.

  When the advance value β is not controlled, in the operation section where the input voltage Vpn of the inverter circuit 3 is low, it is impossible to flow current to the motor as instructed. On the other hand, when the advance value β is controlled, the amount of current supplied to the motor is increased by the control of the advance value β in the operation period where the input voltage Vpn of the inverter circuit 3 is low. As a result, as in the second embodiment, by controlling the advance value of the motor current, even if the output voltage of the voltage source decreases, the necessary motor torque is ensured and the command rotational speed is realized. You can see that

  As described above, in the motor drive device 100b of the second embodiment, the inverter circuit 3 that converts the output voltage of the voltage source 1 into three-phase alternating current and outputs it to the motor 2, and the current supplied from the inverter circuit 3 to the motor 2 And an inverter control unit 4b for controlling the advance angle value β of (motor current). The inverter control unit 4b performs command rotation in a state where the amplitude value of the motor current command value (command current) Io is fixed to the maximum value. Since the motor advance value β is determined so that the deviation between the number fo and the actual rotational speed f is minimized, more stable field-weakening control of the brushless motor can be performed using a preset table value or the like, as in the first embodiment. This can be done without using the control amount.

  In the second embodiment, since the maximum amplitude value of the motor current held at the constant value is set to the maximum current value allowed by the brushless motor 2, the brushless motor is not permitted even if the field weakening control is performed. A current, that is, a motor current that causes the brushless motor to deteriorate due to demagnetization does not flow, and a safe motor driving device can be provided.

(Embodiment 3)
FIG. 5 is a block diagram for explaining a motor drive apparatus according to Embodiment 3 of the present invention.
Similar to the motor drive device 100b of the second embodiment, the motor drive device 100c of the third embodiment receives the voltage source 1 and drives the brushless motor 2 at an arbitrary rotational speed. The field weakening control is performed by adjusting the advance angle value β of the motor current so that the actual motor rotational speed f becomes maximum.

  In other words, the motor driving device 100c includes an inverter circuit 3 that converts the output voltage of the voltage source 1 into a three-phase alternating current and outputs it to the motor, and an inverter control unit 4c that controls the inverter circuit 3.

  The inverter control unit 4c supplies a drive signal Sg to the inverter circuit 3 so that the brushless motor 2 is driven at a rotational speed desired by the user. The inverter position estimation unit 5, the advance value determination unit 6c, The command current waveform creation unit 8b and the PWM creation unit 9 are configured.

  Here, the voltage source 1, the inverter circuit 3, the rotor position estimating unit 5, the command current waveform generating unit 8b, and the PWM generating unit 9 are the same as those in the motor drive device 100b of the second embodiment.

  The advance value determining unit 6c receives the estimated phase θ output from the rotor position estimating unit 5, and is obtained by differentiation of the estimated phase θ under the condition that the amplitude value of the command current waveform is constant. The advance angle value β of the motor current is determined so that the rotation speed f of the brushless motor 2 is maximized. As a specific method for determining the advance value β, a hill climbing method can be considered.

Next, the operation will be described.
In the motor drive device 100c of the third embodiment, the rotor position estimating unit 5, the command current waveform creating unit 8b, and the PWM creating unit 9 operate in the same manner as in the second embodiment. Only the operation of the angle value determination unit 6c will be described.

FIG. 6 shows a flow of processing in which the advance value determination unit 6c determines the advance value β by the hill-climbing method.
In the third embodiment, the advance value determination unit 6c repeatedly performs the processes S11 to S18 shown in FIG. However, when the amplitude value of the command current changes, the advance value determination unit 6c performs the above steps S11 to S18 until the influence of the change in the amplitude value of the command current is settled so that the advance value β does not diverge. Stop the action to be performed.

First, in step S <b> 11, the actual rotational speed f of the motor 2 is acquired based on the rotor estimated phase from the rotor position estimating unit 5.
Next, in step S12, it is determined which of the processing in step S13 and the processing in step S14 should be performed based on a predetermined β increase flag value. That is, if the value of the β increase flag is [−1], the process of step S13 is performed. If the value of the β increase flag is [1], the process of step S14 is performed. When the flow shown in FIG. 6 is performed for the first time, in the process of step S12, the value of the β increase flag is set as an initial value in advance, either [1] or [−1] It is said.

  In step S13, a process of reducing (delaying) the advance value β currently being output is performed. The amount by which the advance value β is reduced in step S13 may be a predetermined amount, or may be determined based on the difference between the actual rotational speed f acquired last time and the actual rotational speed f acquired this time. Good. When the amount of decrease in the advance value β is determined based on the deviation as described above, the speed of climbing, that is, the speed of processing for determining the advance value β by the hill-climbing method is increased, and the actual rotational speed f is maximized with good responsiveness. The advance value β can be determined.

Further, in step S14, a process of increasing (advancing) the currently output advance value β is performed. The amount by which the advance value β is increased in step S14 may be a predetermined constant amount, or may be determined based on the difference between the actual rotational speed f acquired last time and the actual rotational speed f acquired this time. If the amount of increase in the advance value β is determined based on the deviation as described above, the speed of climbing is increased, and the advance value β that maximizes the actual rotational speed f can be determined with good responsiveness.
Thereafter, in step S15, the process of obtaining the actual rotational speed f is performed again in a state where the advance value β of the motor current is updated to the advance value β determined in step S13 or S14.

  Furthermore, in step S16, the actual rotational speed before updating the advance value β of the motor current to the advance value β determined in step S13 or S14, and the actual rotational speed after updating the advance value β. The difference is calculated, and it is determined whether or not the actual rotational speed f after updating the advance value β is decreasing. When the actual rotational speed f after updating the advance value β is smaller than the actual rotational speed f before the update, the process of step S17 is performed, and the actual rotational speed f after changing the advance value β is obtained. If it is greater than or equal to the actual number of revolutions before the update, the process of step S18 is performed.

  In step S17, since the direction in which the advance value β is changed is incorrect, a process of inverting the sign of the β increase flag is performed, and then the process of step S18 is performed.

  In step S18, it is determined whether or not the motor is stopped. If the motor is stopped, the advance value determination process in the advance angle determination unit 6c is finished. If the motor is not stopped, The process of step S12 is performed again.

  As described above, by the steps S11 to S18, it is possible to obtain an optimum advance angle value that can make maximum use of the reluctance torque of the brushless motor with a simple circuit configuration.

  As described above, in the third embodiment, the inverter circuit 3 that converts the output voltage of the voltage source 1 into three-phase alternating current and outputs it to the motor 2, and the current (motor current) supplied from the inverter circuit 3 to the motor 2 An inverter control unit 4c for controlling the advance value β, and the inverter control unit 4c sets the advance value β so that the actual motor rotational speed becomes maximum in a state where the amplitude value of the command current is kept constant. Since the pulse signal to be supplied to the inverter circuit 3 is generated based on the determined advance angle value β, the advance value of the motor current, which is the control amount of the field weakening control of the brushless motor, is optimized with a simple circuit configuration. It can be an advance value. Here, the optimum advance value is a value that allows the maximum use of the reluctance torque of the brushless motor that maximizes the motor rotation speed, so that the brushless motor satisfies the required torque. It is possible to drive with the minimum current value, and to maximize the driving efficiency of the motor.

  In the third embodiment, the advance value is controlled so that the motor rotation speed is maximized. Therefore, there is an error between the estimated rotor position and the actual rotor position due to variations in various constants constituting the brushless motor. Even if this occurs, the advance value is adjusted so that the error is absorbed. As a result, not only the maximum efficiency of the brushless motor is achieved, but also a phenomenon that an error occurs in the estimated rotor position and the brushless motor steps out can be avoided, and stable motor driving can be realized.

(Embodiment 4)
FIG. 7 is a block diagram for explaining a motor drive apparatus according to Embodiment 4 of the present invention.
Similar to the motor drive device 100b of the second embodiment, the motor drive device 100d of the fourth embodiment uses the voltage source 1 as an input and drives the brushless motor 2 at an arbitrary rotational speed. The field weakening control is performed by adjusting the advance value β of the motor current so that the amplitude value of the command current Io is minimized.

  In other words, the motor drive device 100d includes an inverter circuit 3 that converts the output voltage of the voltage source 1 into a three-phase alternating current and outputs it to the motor, and an inverter control unit 4d that controls the inverter circuit 3.

  The inverter control unit 4d supplies a drive signal Sg to the inverter circuit 3 so that the brushless motor 2 is driven at a rotational speed desired by the user. The inverter position estimation unit 5, the advance value determination unit 6d, The command current waveform creation unit 8d and the PWM creation unit 9 are configured.

  Here, the voltage source 1, the inverter circuit 3, the rotor position estimation unit 5, and the PWM creation unit 9 are the same as those in the motor drive device 100b of the second embodiment.

  The command current waveform creation unit 8d is configured such that the command rotational speed fo indicated by the command signal from the outside, the estimated phase θ of the rotor output by the rotor position estimation unit 5, and the advance angle of the motor current output by the advance value determination unit 6d Using the value β as an input, a waveform of a command current Io, which is a current that the inverter circuit 3 should supply to the brushless motor 2, is created. Specifically, the command current waveform creation unit 8d generates a sinusoidal waveform having a command amplitude value of the motor current and a phase obtained by adding the advance value β to the estimated phase θ of the command current Io. It is a waveform. Here, the command amplitude value of the motor current has zero deviation between the command rotation speed fo indicated by the external command signal and the actual rotation speed f obtained from the differential value of the estimated phase θ output from the rotor position estimation unit 5. To be determined. For example, the command amplitude value is obtained by performing PI control on the command rotational speed fo and the actual rotational speed f.

  The advance value determination unit 6d receives the command current Io created by the command current waveform creation unit 8d as input, and the amplitude value of the command current Io is minimized under the condition that the rotational speed command fo is constant. The advance value β is controlled. A hill-climbing method is conceivable as a specific control method in the advance value determination unit 6d.

  In the fourth embodiment, the advance value determination unit 6d receives the command current Io created by the command current waveform creation unit 8d. However, only the amplitude value of the command current Io may be inputted.

Next, the operation will be described.
In the fourth embodiment, the output voltage of the voltage source 1 is converted into a three-phase alternating current by the inverter circuit 3 and supplied to the motor 2 as in the third embodiment, and the motor 2 is driven.
At this time, in the inverter control unit 4d, the switching elements 31 to 36 of the inverter circuit 3 are based on the command rotational speed fo indicated by the command signal from the outside and the current (motor current) I supplied to the motor 2. Is generated as a drive signal Sg.
That is, the rotor position estimation unit 5 estimates the rotor position from the current (motor current) I supplied from the inverter circuit 3 to the brushless motor 2.

  In the command current waveform generation unit 8d, the command rotational speed fo indicated by the command signal from the outside, the estimated phase θ of the rotor output from the rotor position estimation unit 5, and the advance angle of the motor current output from the advance value determination unit 6d Based on the value β, a waveform of a command current Io that is a current that the inverter circuit 3 should supply to the brushless motor 2 is created. Specifically, in the command current waveform creation unit 8d, the amplitude value of the command current Io is calculated from the rotational speed command fo and the actual rotational speed f obtained from the differential value of the estimated phase θ output from the rotor position estimation unit 5. The deviation is determined to be zero. For example, the amplitude value of the command current Io is obtained by performing PI control on the command rotational speed fo and the actual rotational speed f. The phase of the command current is a phase obtained by adding the advance value β to the estimated phase θ of the rotor.

  In the advance angle determination unit 6d, the command current Io created by the command current waveform creation unit 8d is input, and the amplitude value of the command current Io is minimized under the condition that the rotational speed command fo is constant. The advance value β is determined. A hill-climbing method is conceivable as a specific control method of the advance value β in the advance value determining unit 6d.

  The PWM generator 9 determines the PWM width of the pulse signal that is the drive signal Sg supplied to the inverter circuit 3 so that the deviation between the actual motor current (actual current) I and the command current Io becomes zero. . Specifically, the PWM width of the pulse signal is determined by performing PI control on the difference between the command current Io and the actual current I.

FIG. 8 shows a flow of processing in which the advance value determination unit 6d determines the advance value β by the hill-climbing method.
In the fourth embodiment, the advance value determination unit 6d repeatedly performs the processes S21 to S28 shown in FIG. However, when the command rotational speed fo changes, the advance value determination unit 6d performs the above-described processes S21 to S28 until the influence of the change in the command rotational speed fo is settled so that the advance value β does not diverge. To stop.

First, in step S21, the amplitude value of the command current Io is acquired from the rotational speed command fo and the actual rotational speed f obtained by differentiation of the rotor estimated phase θ.
Next, in step S22, it is determined which of the processing in step S23 and the processing in step S24 should be performed based on a predetermined β increase flag value. That is, if the value of the β increase flag is [−1], the process of step S23 is performed. If the value of the β increase flag is [1], the process of step S24 is performed. When the process shown in FIG. 8 is first performed, in the process of step S22, the value of the β increase flag is set as an initial value in advance, either [1] or [−1]. It is said.

  In step S23, a process of reducing (delaying) the advance value β currently being output is performed. The amount by which the advance value β is reduced in this step S23 may be a fixed amount determined in advance, or determined based on the difference between the amplitude value of the command current Io acquired last time and the amplitude value of the command current Io acquired this time. Also good. If the amount of decrease in the advance value β is determined based on the deviation as described above, the speed of hill climbing, that is, the speed of processing for determining the advance value β by the hill climbing method is increased, and the amplitude value of the command current Io is high in responsiveness. The advance value β that minimizes can be determined.

  Further, in step S24, a process of increasing (advancing) the currently output advance value β is performed. The amount by which the advance value β is increased in step S24 may be a predetermined constant amount, or determined based on the difference between the amplitude value of the command current Io acquired last time and the amplitude value of the command current Io acquired this time. Also good. When the increase amount is determined based on the deviation as described above, the hill-climbing speed is increased, and the advance value β that minimizes the amplitude value of the command current Io can be determined with good responsiveness.

  Thereafter, in step S25, a process of driving the brushless motor in a state where the advance value β of the motor current is updated to the advance value β determined in step S23 or S24, and obtaining the amplitude value of the command current Io again. Done.

  Further, in step S26, the difference between the amplitude value of the command current before updating the advance value β of the motor current to the advance value β determined in step S23 or S24 and the amplitude value of the command current after the update is calculated. It is calculated and it is determined whether or not the command current amplitude value after updating the advance value β is larger than the command current amplitude value before the update. When the command current amplitude value after the advance value β is changed is larger than the command current amplitude value before the update, the process of step S27 is performed, and the command current amplitude value after the advance value β is updated. Is smaller than or equal to the command current amplitude value before the update, the process of step S28 is performed.

  In step S27, since the direction in which the advance value β is changed is incorrect, a process of inverting the sign of the β increase flag is performed, and then the process of step S28 is performed.

  In step S28, it is determined whether or not the motor is stopped. If the motor is stopped, the advance value determination process in the advance angle determination unit 6d is completed. The process of step S22 is performed again.

  As described above, the steps S21 to S28 make the best use of the reluctance torque of the brushless motor from the optimum advance value, that is, the current supplied to the brushless motor and the estimated rotor position, with a simple circuit configuration. An advance value that can be obtained is obtained.

  As described above, in the fourth embodiment, the inverter circuit 3 that converts the output voltage of the voltage source 1 into three-phase alternating current and outputs it to the motor 2, and the current (motor current) supplied from the inverter circuit 3 to the motor 2 An inverter control unit 4d that controls the advance value β, and the inverter control unit 4d keeps the command rotation speed fo constant so that the advance value β is minimized in the amplitude of the command current. Since the pulse signal to be supplied to the inverter circuit 3 is generated based on the determined advance value β, the optimum advance value can be obtained with a simple circuit configuration. Here, the optimum advance value is a value that allows the maximum use of the reluctance torque of the brushless motor that maximizes the motor rotation speed, so that the brushless motor satisfies the required torque. It is possible to drive with the minimum current value, and to maximize the driving efficiency of the motor.

  Further, in the fourth embodiment, the advance value is controlled so that the amplitude value of the command current is minimized, so that the estimated rotor position and the actual rotor position are caused by variations in various constants constituting the brushless motor. Even if an error occurs, the advance value is adjusted so that the error is absorbed. This not only achieves the maximum efficiency of the brushless motor, but also avoids the phenomenon that the brushless motor steps out due to an error in the estimated rotor position, thereby realizing stable motor driving.

(Embodiment 5)
FIG. 9 is a block diagram for explaining a motor drive apparatus according to a fifth embodiment of the present invention.
In the motor drive device 100e of the fifth embodiment, a small-capacitance capacitor 12 for charging a regenerative current from the motor is added to the input side of the inverter circuit 3 of the motor drive device 100a of the first embodiment. The capacitor 12 is connected between one output terminal 1a of the voltage source 1 and the other output terminal 1b.

Other configurations of the motor drive device 100e of the fifth embodiment are the same as those of the motor drive device 100a of the first embodiment.
Here, the capacity of the capacitor 12 may be set to a capacity that prevents damage to the apparatus due to the motor regenerative current. For example, when the motor control device controls a motor of a compressor used in a home air conditioner, the capacity of the capacitor 12 may be about 0.1 μF to 50 μF. This value is the minimum limit value obtained from the capacity of the motor inductance, the maximum variation allowed for the inverter input voltage, and the maximum value of the current flowing through the motor.

  That is, the energy held by the motor when the maximum current flows through the motor is obtained from the inductance capacity. And the capacity | capacitance of the said capacitor | condenser is determined based on to what extent the raise of the terminal voltage of the capacitor | condenser which generate | occur | produces when the energy is given to a capacitor | condenser as a motor regenerative current.

  Specifically, assuming that the maximum current flowing through the motor is Im, the inductance inside the motor is Lm, and the allowable increase in the capacitor terminal voltage is Vm, the capacitance Cm of the capacitor is Cm> Lm · Im · Im / Vm / Vm is determined.

Next, the operation will be described.
In the motor drive device 100e of the fifth embodiment, the inverter circuit 3 and the inverter control unit 4a operate in the same manner as in the first embodiment. Therefore, the operation different from that in the first embodiment will be described below.

  When the motor 2 is stopped or when the switching operation of the inverter circuit 3 is stopped, the current flowing through the motor 2 is regenerated to the input side of the inverter circuit 3. If the regenerative current is large, the input side voltage of the inverter circuit 3 becomes an excessive voltage, and the motor drive device may be damaged.

  In the motor drive device 100e of the fifth embodiment, since the capacitor 12 is added to the input side of the inverter circuit 3 as shown in FIG. 9, the regenerative current from the motor 2 is generated when the motor 2 is stopped. The capacitor 12 is charged, and an increase in the input side voltage of the inverter circuit 3 due to the regenerative current can be suppressed.

  As a result, the motor drive device can be prevented from being damaged by the motor regenerative current generated when the motor is stopped, and a safer motor control device can be realized.

  As described above, in the fifth embodiment, the inverter circuit 3 of the motor drive device 100a according to the first embodiment includes the capacitor that charges the regenerative current from the motor. Therefore, in addition to the effects of the first embodiment, Thus, an increase in the inverter input voltage that occurs when the motor is stopped or when the switching operation of the inverter circuit is stopped can be suppressed, and the elements and the like can be prevented from being destroyed.

  In the fifth embodiment, the capacitor that charges the regenerative current from the motor is added to the input side of the inverter circuit 3 of the motor driving device 100a of the first embodiment. The added motor drive device is not limited to that of the first embodiment, and may be any of the motor drive devices of the second to fourth embodiments.

(Embodiment 6)
FIG. 10 is a block diagram for explaining a motor drive apparatus according to a sixth embodiment of the present invention.
The motor drive device 100f according to the sixth embodiment is such that an inductor 13 is inserted between the inverter circuit 3 of the motor drive device 100a according to the first embodiment and the voltage source 1, and the inductor 13 is a voltage source. 1 and the inverter circuit 3 are connected in series.

  The other configuration of the motor drive device 100f of the sixth embodiment is the same as that of the motor drive device 100a of the first embodiment.

  Here, the capacitance of the inductor 13 may be set to a value that eliminates the switching current noise generated by the switching operation of the inverter circuit and does not distort the waveform of the output current of the voltage source. For example, when the motor drive device drives a motor of a compressor used in a home air conditioner, the capacity of the inductor 13 may be about 0.01 mH to 4.0 mH. This value is proportional to the reciprocal of the carrier frequency in the inverter circuit 3, and is determined so that the harmonics of the carrier component can be suppressed.

  Specifically, when the amount to be attenuated is −X [dB], the circularity is π, and the carrier frequency is f [Hz], the inductor value Lr is 10 × log (2 × π × f × Lr)> X is determined to satisfy the value.

Next, the operation will be described.
In the motor drive device 100f according to the sixth embodiment, the inverter circuit 3 and the inverter control unit 4a operate in the same manner as those in the first embodiment. Therefore, hereinafter, operations different from those in the first embodiment will be described.

The output current of the voltage source 1 is affected by the switching operation of the inverter circuit 3, and the switching current is superimposed as noise.
In the motor drive device 100f of the sixth embodiment, as shown in FIG. 10, the noise generated in the inverter circuit 3 is blocked by the inductor 13 inserted between the voltage source 1 and the inverter circuit 3. Thus, power supply switching noise superimposed on the output current of the voltage source is reduced. Thereby, the distortion of the waveform of the output current of the voltage source 1 is suppressed, and the power factor of the input current is improved.

  As described above, in the sixth embodiment, the inductor 13 for cutting off the noise generated in the inverter circuit 3 is inserted between the input of the inverter circuit 3 and the voltage source 1 of the motor drive device 100a of the first embodiment. Therefore, in addition to the effect of the first embodiment, the switching noise superimposed on the output of the voltage source 1 can be reduced, thereby increasing the power factor of the input current and improving the current waveform. is there.

  In the sixth embodiment, the inductor 13 that cuts off the noise generated in the inverter circuit 3 is inserted between the inverter circuit 3 and the voltage source 1 of the motor drive device 100a of the first embodiment. However, the motor drive device having such an inductor is not limited to that of the first embodiment, and may be any motor drive device of the second to fourth embodiments.

  Further, in the fifth embodiment, the motor driving device has a capacitor added to the input side of the inverter circuit that constitutes the motor driving device. In the sixth embodiment, the motor driving device constitutes the motor driving device. Although a capacitor is inserted between the inverter circuit and the voltage source, the motor drive device may include both the capacitor and the inductor.

  In this case, since a series connection circuit composed of an inductor and a capacitor is formed, a resonance phenomenon may occur. This resonance frequency is 1 / 2π√ (LC) as generally known, and is determined by the capacitances of the inductor and the capacitor. Therefore, if the capacitances of the inductor and the capacitor are determined so that the resonance frequency is higher than the frequency subject to harmonic regulation for the power supply, a motor control device with less generated noise can be provided.

  Furthermore, the motor drive device according to each embodiment of the present invention is not limited to one that drives and controls a motor of a compressor used in an air conditioner, and any motor drive device that uses an inverter circuit to drive and control the motor. The drive motor of any device may be controlled.

  For example, a device to which the motor driving device of each of the above embodiments can be applied is a refrigerator, an electric washing machine, an electric dryer, an electric vacuum cleaner, a blower, a heat pump hot water supply equipped with a motor and an inverter circuit that generates the driving current. There are equipment such as bowls. For any of the devices, the utility is immeasurable, for example, by reducing the size and weight of the inverter circuit and providing a device with a high degree of design freedom and low cost.

  Hereinafter, an air conditioner, a refrigerator, an electric washing machine, a blower, a vacuum cleaner, an electric dryer, and a heat pump water heater, which are devices using the motor and the motor driving device of the first embodiment, will be specifically described.

(Embodiment 7)
FIG. 12 is a block diagram illustrating an air conditioner according to Embodiment 7 of the present invention.
The air conditioner 250 according to the seventh embodiment includes an indoor unit 255 and an outdoor unit 256, and is an air conditioner that performs air conditioning.

  The air conditioner 250 includes a compressor 250a that circulates refrigerant between the indoor unit 255 and the outdoor unit 256, and a motor driving device 250b that receives the voltage source 1 and drives a motor of the compressor 250a. ing. Here, the voltage source 1, the motor of the compressor 250a, and the motor driving device 250b are the same as the voltage source 1, the brushless motor 2, and the motor driving device 100a of the first embodiment, respectively.

  The air conditioner 250 includes a four-way valve 254, a throttle device 253, an indoor heat exchanger 251 and an outdoor heat exchanger 252 that form a refrigerant circulation path. Here, the indoor heat exchanger 251 constitutes the indoor unit 255, and the expansion device 253, the outdoor heat exchanger 252, the compressor 250 a, the four-way valve 254, and the motor driving device 250 b constitute the outdoor unit 256. is doing.

  The indoor heat exchanger 251 includes a blower 251a for increasing the heat exchange capability, and a temperature sensor 251b for measuring the temperature of the heat exchanger 251 or the ambient temperature. The outdoor heat exchanger 252 includes a blower 252a for increasing the heat exchange capability, and a temperature sensor 252b for measuring the temperature of the heat exchanger 252 or the ambient temperature.

  In the seventh embodiment, the compressor 250a and the four-way valve 254 are arranged in the refrigerant path between the indoor heat exchanger 251 and the outdoor heat exchanger 252. That is, in this air conditioner 250, the refrigerant flows in the direction of arrow A, the refrigerant that has passed through the outdoor heat exchanger 252 is sucked into the compressor 250a, and the refrigerant discharged from the compressor 250a is the indoor heat exchanger. 251 and the refrigerant flowing in the direction of arrow B, the refrigerant that has passed through the indoor heat exchanger 251 is sucked into the compressor 250a, and the refrigerant discharged from the compressor 250a is the outdoor heat exchanger 252. The state supplied to is switched by the four-way valve 254.

  The throttle device 253 has both a throttle action for reducing the flow rate of the circulating refrigerant and a valve action for automatically adjusting the flow rate of the refrigerant. That is, the expansion device 253 expands the liquid refrigerant by reducing the flow rate of the liquid refrigerant sent from the condenser to the evaporator while the refrigerant is circulating in the refrigerant circulation path, and is also required for the evaporator. Supply a sufficient amount of refrigerant.

  The indoor heat exchanger 251 operates as a condenser in heating operation and as an evaporator in cooling operation, and the outdoor heat exchanger 252 serves as an evaporator in heating operation and a condenser in cooling operation. It works as. In the condenser, the high-temperature and high-pressure refrigerant gas flowing inside is gradually liquefied by taking heat away from the air that is sent, and becomes high-pressure liquid refrigerant in the vicinity of the outlet of the condenser. This is equivalent to the refrigerant dissipating heat into the atmosphere and liquefying. Further, the liquid refrigerant that has been cooled to low temperature and low pressure by the expansion device 253 flows into the evaporator. When room air is sent to the evaporator in this state, the liquid refrigerant takes a large amount of heat from the air and evaporates, and changes to a low-temperature and low-pressure gas refrigerant. Air deprived of a large amount of heat by the evaporator is discharged as cold air from the outlet of the air conditioner.

  In the air conditioner 250, the command rotational speed of the brushless motor is set based on the operating state of the air conditioner, that is, the target temperature set for the air conditioner, the actual room temperature, and the outside air temperature. The device 250b controls the rotational speed of the brushless motor of the compressor 250a based on the set command rotational speed as in the first embodiment.

Next, the operation will be described.
In the air conditioner 250 according to the seventh embodiment, when a driving voltage is applied from the motor driving device 250b to the compressor 250a, the refrigerant circulates in the refrigerant circulation path, and the heat exchanger 251 and the outdoor unit of the indoor unit 255 are circulated. Heat exchange is performed in 256 heat exchangers 252. In other words, in the air conditioner 250, the refrigerant sealed in the refrigerant circulation circuit is circulated by the compressor 250a, whereby a known heat pump cycle is formed in the refrigerant circulation circuit. Thereby, indoor heating or cooling is performed.

  For example, when performing the heating operation of the air conditioner 250, the four-way valve 254 is set so that the refrigerant flows in the direction indicated by the arrow A by a user operation. In this case, the indoor heat exchanger 251 operates as a condenser and releases heat by the circulation of the refrigerant in the refrigerant circulation path. This warms the room.

  Conversely, when the air conditioner 250 is in the cooling operation, the four-way valve 254 is set so that the refrigerant flows in the direction indicated by the arrow B by the user's operation. In this case, the indoor heat exchanger 251 operates as an evaporator and absorbs the heat of the surrounding air by the circulation of the refrigerant in the refrigerant circulation path. This cools the room.

  Here, in the air conditioner 250, the command rotational speed is determined based on the target temperature set for the air conditioner, the actual room temperature, and the outside air temperature, and based on the command rotational speed as in the first embodiment. Thus, the rotation speed of the brushless motor of the compressor 250a is controlled by the motor driving device 250b. Thereby, in the air conditioner 250, comfortable air conditioning is performed.

  As described above, in the air conditioner 250 according to the seventh embodiment, the brushless motor is used as the power source of the compressor 250a, and the advance value β of the current supplied to the brushless motor is set in the same manner as in the first embodiment. Since the deviation between the rotational speed fo and the actual rotational speed f is determined to be a minimum, even in a situation where the input voltage of the inverter fluctuates, simple and stable field-weakening control that only changes the current advance value allows The brushless motor can be stably driven up to high speed rotation. As a result, the air conditioner 250 equipped with the brushless motor and its driving device can be designed with a high degree of freedom in design.

(Embodiment 8)
FIG. 13 is a block diagram illustrating a refrigerator according to Embodiment 8 of the present invention.
The refrigerator 260 according to the eighth embodiment includes a compressor 260a, a motor driving device 260b, a condenser 261, a cold room evaporator 262, and a throttle device 263.

  Here, the compressor 260a, the condenser 261, the expansion device 263, and the refrigerator compartment evaporator 262 form a refrigerant circulation path, and the motor driving device 260b receives the voltage source 1 as an input, and the compressor 260a. It drives a brushless motor which is a driving source of the motor. The voltage source 1, the brushless motor of the compressor 260a and the motor driving device 260b are the same as the voltage source 1, the brushless motor 2 and the motor driving device 100a of the first embodiment, respectively.

  As with the expansion device 253 of the air conditioner 250 of the seventh embodiment, the expansion device 263 restricts the flow rate of the liquid refrigerant sent from the condenser 261 while the refrigerant is circulating in the refrigerant circulation path. While the liquid refrigerant is expanded, the required amount of refrigerant is supplied to the refrigerator compartment evaporator 262 without excess or deficiency.

  The condenser 261 condenses the high-temperature and high-pressure refrigerant gas flowing inside, and releases the heat of the refrigerant to the outside air. The refrigerant gas sent to the condenser 261 is deprived of heat by the outside air and gradually liquefies, and becomes a high-pressure liquid refrigerant near the outlet of the condenser.

  The refrigerator compartment evaporator 262 cools the refrigerator by evaporating a low-temperature refrigerant liquid. The refrigerator compartment evaporator 262 includes a blower 262a for increasing the efficiency of heat exchange and a temperature sensor 262b for detecting the temperature in the refrigerator.

  And in this refrigerator 260, instruction | command rotation speed is set based on the driving | running state of a refrigerator, ie, the target temperature set with respect to the refrigerator, and the temperature in a refrigerator, and the motor drive device 260b is the same as that of Embodiment 1. Based on the set command rotational speed, the rotational speed of the brushless motor of the compressor 260a is controlled.

Next, the operation will be described.
In the refrigerator 260 according to the eighth embodiment, when the driving voltage Vd is applied from the motor driving device 260b to the brushless motor of the compressor 260a, the compressor 260a is driven and the refrigerant flows in the direction of arrow C in the refrigerant circulation path. It circulates and heat exchange is performed in the condenser 261 and the refrigerator compartment evaporator 262. Thereby, the inside of a refrigerator is cooled.

  That is, the refrigerant liquefied in the condenser 261 expands when the flow rate is reduced by the expansion device 263 to become a low-temperature refrigerant liquid. When the low-temperature liquid refrigerant is sent to the refrigerator compartment evaporator 262, the low-temperature refrigerant liquid is evaporated in the refrigerator compartment evaporator 262, and the refrigerator is cooled. At this time, the air in the refrigerator compartment is forcibly sent to the refrigerator compartment evaporator 262 by the blower 262a, and the refrigerator compartment evaporator 262 performs heat exchange efficiently.

  Further, in the refrigerator 260 of the eighth embodiment, the command rotational speed is set according to the target temperature set for the refrigerator 260 and the room temperature in the refrigerator, and the motor driving device 260b is the same as that of the first embodiment. Similarly, the rotational speed of the brushless motor of the compressor 260a is controlled based on the set command rotational speed f0. Thereby, in the refrigerator 260, the temperature in the refrigerator is maintained at the target temperature.

  Thus, in the refrigerator 260 of the eighth embodiment, a brushless motor is used as the power source of the compressor 260a, and the advance value β of the current supplied to the brushless motor is set to the command rotational speed as in the first embodiment. Since it is determined that the deviation between fo and the actual rotational speed f is minimized, the brushless motor is controlled by simple and stable field weakening control that only changes the current advance value even in a situation where the input voltage of the inverter fluctuates. Can be driven stably up to high-speed rotation. Thereby, the refrigerator 260 equipped with the brushless motor and its driving device can be designed with a high degree of freedom in design.

(Embodiment 9)
FIG. 14 is a block diagram for explaining an electric washing machine according to Embodiment 9 of the present invention.
The electric washing machine 270 according to the ninth embodiment has a washing machine outer frame 271, and an outer tub 273 is suspended from the washing machine outer frame 271 by a hanging rod 22. A washing / dehydrating tub 24 is rotatably disposed in the outer tub 273, and a stirring blade 275 is rotatably attached to the bottom of the washing / dehydrating tub 274.

  A brushless motor 276 that rotates the washing / dehydrating tub 24 and the stirring blade 275 is disposed in the space below the outer tub 273 in the outer frame 271 of the washing machine. A motor driving device 277 that drives the brushless motor 276 with the voltage source 1 as an input is attached.

  Here, the voltage source 1, the brushless motor 276, and the motor driving device 277 have the same configuration as the voltage source 1, the brushless motor 2, and the motor driving device 100a of the first embodiment, respectively. The drive device 277 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (not shown) that controls the operation of the electric washing machine 270.

Next, the operation will be described.
In the electric washing machine 270 according to the ninth embodiment, when the user performs a predetermined operation, a command signal is input from the microcomputer to the motor driving device 277, and a driving voltage is applied from the motor driving device 277 to the brushless motor 276. The Then, by driving the brushless motor 276, the stirring blade 275 or the washing / dehydrating tub 274 rotates, and washing and dehydration of clothes and the like in the washing / dehydrating tub 274 are performed.

  At this time, in the electric washing machine 270 according to the ninth embodiment, the rotational speed of the brushless motor is controlled by the motor driving device 277 based on the command rotational speed indicated by the command signal from the microcomputer as in the first embodiment. . Thereby, in the electric washing machine 270, the operation | movement according to the quantity and dirt of the laundry is performed.

  As described above, in the electric washing machine 270 of the ninth embodiment, the brushless motor 276 is used as the power source, and the advance value β of the current supplied to the brushless motor is set to the command rotational speed fo as in the first embodiment. And the actual rotational speed f are determined to be the smallest, so even in a situation where the input voltage of the inverter fluctuates, the brushless motor can be controlled by simple and stable field weakening control that only changes the current advance value. It is possible to drive stably up to high-speed rotation. As a result, the electric washing machine 270 equipped with the brushless motor and its drive device can be designed with a high degree of freedom in design.

(Embodiment 10)
FIG. 15 is a block diagram illustrating a blower according to Embodiment 10 of the present invention.
The blower 280 of the tenth embodiment includes a fan 281, a brushless motor 282 that rotationally drives the fan 281, and a motor driving device 283 that receives the voltage source 1 and drives the brushless motor 282. .

  Here, the voltage source 1, the brushless motor 282, and the motor driving device 283 have the same configuration as the voltage source 1, the brushless motor 2 and the motor driving device 100a of the first embodiment, respectively. The drive device 283 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (hereinafter referred to as a microcomputer) that controls the operation of the blower 280.

Next, the operation will be described.
In the blower 280 of the tenth embodiment, when a user performs a predetermined operation, a command signal is input from the microcomputer to the motor driving device 283, and a driving voltage is applied from the motor driving device 283 to the brushless motor 282. Then, the fan 281 is rotated by driving the brushless motor 282 and air is blown.

  At this time, in the blower 280 of the tenth embodiment, the output of the brushless motor 282 is controlled by the motor driving device 283 based on the command signal from the microcomputer as in the first embodiment. Thereby, in the air blower 280, the amount of air flow and the strength of the wind are adjusted.

  Thus, in the blower 280 of the tenth embodiment, the brushless motor 282 is used as a power source, and the advance value β of the current supplied to the brushless motor 280 is set to the command rotational speed fo as in the first embodiment. Since the deviation from the actual rotational speed f is determined to be the minimum, even in situations where the input voltage of the inverter fluctuates, the brushless motor can be operated at high speed with simple and stable field weakening control that only changes the current advance value. It can be driven stably until rotation. As a result, the blower 280 equipped with the brushless motor and its driving device can be designed with a high degree of freedom in design.

(Embodiment 11)
FIG. 16 is a block diagram illustrating a vacuum cleaner according to Embodiment 11 of the present invention.
The vacuum cleaner 290 of the eleventh embodiment includes a floor suction tool 297 having a suction port formed on the bottom surface, a vacuum cleaner body 290a for sucking air, one end for the floor suction tool 297, and the other end for cleaning. A dust suction hose 296 connected to the machine body.

  The vacuum cleaner body 290a includes a dust collection chamber 295 having a dust suction hose 296 opened at a part of the front surface and an electric blower 291 disposed on the back side of the dust collection chamber 295.

  The electric blower 291 includes a fan 42 disposed so as to face the back of the dust collecting chamber 295, a brushless motor 293 that rotates the fan, and a motor driving device that receives the voltage source 1 and drives the brushless motor 293. 294, and blows air so that the air is sucked by the rotation of the fan 292.

  Here, the voltage source 1, the brushless motor 293, and the motor driving device 294 are the same as the voltage source 1, the brushless motor 2, and the motor driving device 100a of the first embodiment, respectively. A command signal indicating a command rotation number corresponding to a user operation is input from a microcomputer (hereinafter referred to as a microcomputer) that controls the operation of the electric vacuum cleaner 290.

Next, the operation will be described.
In the vacuum cleaner 290 of the eleventh embodiment, when a user performs a predetermined operation, a command signal is input from the microcomputer to the motor driving device 294, and a driving voltage is applied from the motor driving device 294 to the brushless motor 293. . Then, the fan 292 rotates by driving the brushless motor 293, and a suction force is generated in the cleaner body 290a. The suction force generated in the vacuum cleaner main body 290a acts on a suction port (not shown) provided on the bottom surface of the floor suction tool 297 via the hose 296, and from the suction port of the floor suction tool 47 to the surface to be cleaned. Dust is sucked and collected in the dust collection chamber 45 of the cleaner body 290a.

  At this time, in the vacuum cleaner 290 of the eleventh embodiment, the rotation speed of the brushless motor 293 is controlled by the motor driving device 294 based on the command signal from the microcomputer, as in the first embodiment. As a result, the vacuum cleaner 290 adjusts the strength of the suction force.

  Thus, in the vacuum cleaner 290 of the eleventh embodiment, the brushless motor 293 is used as a power source, and the advance value β of the current supplied to the brushless motor 293 is set to the command rotational speed as in the first embodiment. Since it is determined that the deviation between fo and the actual rotational speed f is minimized, the brushless motor is controlled by simple and stable field weakening control that only changes the current advance value even in a situation where the input voltage of the inverter fluctuates. Can be driven stably up to high-speed rotation. Thereby, the vacuum cleaner 290 equipped with the brushless motor and its driving device can be designed with a high degree of freedom in design.

(Embodiment 12)
FIG. 17 is a block diagram for explaining an electric dryer according to a twelfth embodiment of the present invention.
The electric dryer 360 according to the twelfth embodiment includes a compressor 360a, a motor driving device 360b, a condenser 361, an evaporator 362, and a squeezing device 363.

  Here, the compressor 360a, the condenser 361, the expansion device 363, and the evaporator 362 form a refrigerant circulation path, and the motor driving device 360b receives the voltage source 1 as an input, and drives the compressor 360a. A brushless motor as a source is driven. The voltage source 1, the brushless motor of the compressor 360a and the motor driving device 360b are the same as the voltage source 1, the brushless motor 2 and the motor driving device 100a of the first embodiment, respectively.

  As with the throttle device 253 of the air conditioner 250 of the seventh embodiment, the throttle device 363 throttles the flow rate of the liquid refrigerant sent from the condenser 361 while the refrigerant is circulating in the refrigerant circulation path. The liquid refrigerant is expanded and the required amount of refrigerant is supplied to the evaporator 362 without excess or deficiency.

  The condenser 361 condenses the high-temperature and high-pressure refrigerant gas flowing inside, and releases the heat of the refrigerant to the outside air. The refrigerant gas sent to the condenser 361 is deprived of heat by the outside air and gradually liquefies, and becomes a high-pressure liquid refrigerant near the outlet of the condenser.

The evaporator 362 performs dehumidification in the dryer by evaporating a low-temperature refrigerant liquid. The evaporator 362 has a blower 362a for increasing the efficiency of dehumidification.
In this dryer 362, the motor drive device 360b controls the output of the motor of the compressor 360a based on the operating state of the dryer, that is, the dehumidification set for the dryer and the humidity in the dryer. To do.

Next, the operation will be described.
In the electric dryer 360 of the twelfth embodiment, when the driving voltage Vd is applied from the motor driving device 360b to the brushless motor of the compressor 360a, the compressor 360a is driven and the refrigerant is indicated by the arrow E in the refrigerant circulation path. The heat is exchanged in the condenser 361 and the evaporator 362. Thereby, dehumidification in a dryer is performed.

  That is, in the electric dryer 360, the refrigerant that has become liquid in the condenser 361 expands when the flow rate is reduced by the expansion device 363, and becomes a low-temperature refrigerant liquid. When the low-temperature liquid refrigerant is sent to the evaporator 362, the low-temperature refrigerant liquid is evaporated in the evaporator 362, and dehumidification in the dryer is performed. Specifically, the humid air in the dryer is cooled to below the dew point temperature, and the air from which moisture has been removed as condensed water is reheated (reheated). At this time, the air in the dryer is forcibly sent to the evaporator by a blower, and the evaporator efficiently performs heat exchange and dehumidifies.

  As described above, in the electric dryer 360 of the twelfth embodiment, the brushless motor is used as the power source of the compressor 360a, and the advance value β of the current supplied to the brushless motor is set to the command as in the first embodiment. Since the deviation between the rotational speed fo and the actual rotational speed f is determined to be a minimum, even in a situation where the input voltage of the inverter fluctuates, simple and stable field-weakening control that only changes the current advance value allows The brushless motor can be stably driven up to high speed rotation. As a result, the electric dryer 360 equipped with the brushless motor and its drive device can be designed with a high degree of freedom in design.

(Embodiment 13)
FIG. 18 is a block diagram illustrating a heat pump water heater according to a thirteenth embodiment of the present invention.

  The heat pump water heater 380 of the thirteenth embodiment connects the refrigeration cycle apparatus 381a that heats the supplied water and discharges hot water, and the hot water storage tank 381b that stores the hot water discharged from the refrigeration cycle apparatus 381a. And water pipes 386a, 386b, 387a, and 387b.

  The refrigeration cycle apparatus 381a includes a compressor 380a that forms a refrigerant circulation path, an air heat exchanger 382, an expansion device 383, and a water heat exchanger 385, and the voltage source 1 as an input, and the motor of the compressor 380a Has a motor driving device 380b.

  Here, the voltage source 1, the motor of the compressor 380a, and the motor driving device 380b are the same as the voltage source 1, the brushless motor 2, and the motor driving device 100a of the first embodiment, respectively.

  As with the expansion device 253 of the air conditioner 250 of the seventh embodiment, the expansion device 383 expands the liquid refrigerant by reducing the flow rate of the liquid refrigerant sent from the water heat exchanger 385 to the air heat exchanger 382. It is something to be made.

  The water heat exchanger 385 is a condenser that heats the water supplied to the refrigeration cycle apparatus 381a, and includes a temperature sensor 385a that detects the temperature of the heated water. The air heat exchanger 382 is an evaporator that absorbs heat from the ambient atmosphere, and includes a blower 382a for increasing the heat exchange capability and a temperature sensor 382b for detecting the ambient temperature.

  In the figure, reference numeral 384 denotes a refrigerant pipe for circulating the refrigerant along a refrigerant circulation path formed by the compressor 380a, the water heat exchanger 385, the expansion device 383, and the air heat exchanger 382. The refrigerant pipe 384 is connected to a defrost bypass pipe 384a that bypasses the water heat exchanger 385 and the expansion device 383 and supplies the refrigerant discharged from the compressor 380a to the air heat exchanger 382. A defrosting bypass valve 384b is provided in a part of the bypass pipe 384a.

  The hot water storage tank 381b has a hot water storage tank 388 for storing water or hot water. A water supply pipe 388c for supplying water from the outside into the hot water storage tank 388 is connected to the water receiving port 388c1 of the hot water storage tank 388, and hot water from the hot water storage tank 388 to the bathtub is connected to the hot water outlet 388d1 of the hot water storage tank 388. A bathtub hot water supply pipe 388d to be supplied is connected. A hot water supply pipe 389 for supplying hot water stored in the tank 388 to the outside is connected to the water inlet / outlet port 388a of the hot water storage tank 388.

  The hot water storage tank 388 and the water heat exchanger 385 of the refrigeration cycle apparatus 381a are connected by pipes 386a, 386b, 387a, and 387b, and water is circulated between the hot water storage tank 388 and the water heat exchanger 385. A road is formed.

  Here, the water pipe 386b is a pipe for supplying water from the hot water storage tank 388 to the water heat exchanger 385, one end of which is connected to the water outlet 388b of the hot water storage tank 388, and the other end via the joint portion 387b1. The water heat exchanger 385 is connected to the water inlet side pipe 387b. Further, a drain valve 388b1 for discharging water in the hot water storage tank 388 or hot water is attached to one end side of the water pipe 386b. The water pipe 386a is a pipe for returning water from the water heat exchanger 385 to the hot water storage tank 388. One end of the water pipe 386a is connected to the water inlet / outlet 388a of the hot water storage tank 388, and the other end is connected to the water heat via the joint portion 387a1. It is connected to the discharge side pipe 387a of the exchanger 385.

  A pump 387 that circulates water in the water circulation path is provided in a part of the incoming water side pipe 387 b of the water heat exchanger 385.

  Furthermore, in this water heater 380, the operating state of the water heater, that is, the target temperature of hot water set for the water heater, the temperature of water supplied from the hot water storage layer 381b to the water heat exchanger 385a of the refrigeration cycle apparatus 381a, The command rotational speed of the brushless motor is determined based on the outside air temperature, and the motor driving device 380b determines the motor output required for the brushless motor of the compressor 380a based on the command rotational speed.

Next, the operation will be described.
When a driving voltage is applied from the motor driving device 380b to the brushless motor of the compressor 380a and the compressor 380a is driven, the high-temperature refrigerant compressed by the compressor 380a circulates in the direction indicated by the arrow E, that is, through the refrigerant pipe 384. And is supplied to the water heat exchanger 385. When the water circulation path pump 387 is driven, water is supplied from the hot water storage tank 388 to the water heat exchanger 385.

  Then, in the water heat exchanger 385, heat exchange is performed between the refrigerant and the water supplied from the hot water storage tank 388, and heat is transferred from the refrigerant to the water. That is, the supplied water is heated, and the heated water is supplied to the hot water storage tank 388. At this time, the temperature of the heated water is monitored by the condensation temperature sensor 385a.

  Further, in the water heat exchanger 385, the refrigerant is condensed by the heat exchange, and the condensed liquid refrigerant expands when the flow rate is throttled by the expansion device 383 and is sent to the air heat exchanger 382. In the water heater 380, the air heat exchanger 382 functions as an evaporator. That is, the air heat exchanger 382 absorbs heat from the outside air sent by the blower 382b and evaporates the low-temperature refrigerant liquid. At this time, the temperature of the ambient atmosphere of the air heat exchanger 382 is monitored by the temperature sensor 382b.

  Further, in the refrigeration cycle apparatus 381a, when the air heat exchanger 382 is frosted, the defrost bypass valve 384b is opened, and high-temperature refrigerant is supplied to the air heat exchanger 382 via the defrost bypass path 384a. . Thereby, defrosting of the air heat exchanger 382 is performed.

  On the other hand, hot water is supplied to the hot water storage tank 381b from the water heat exchanger 385 of the refrigeration cycle apparatus 381a via the pipes 387a and 386a, and the supplied hot water is stored in the hot water storage tank 388. Hot water in the hot water storage tank 388 is supplied to the outside through a hot water supply pipe 389 as necessary. In particular, when hot water is supplied to the bathtub, the hot water in the hot water storage tank is supplied to the bathtub through the hot water supply pipe 388d for the bathtub.

Further, when the amount of water or hot water stored in the hot water storage tank 388 becomes a certain amount or less, water is replenished from the outside through the water supply pipe 388c.
In the water heater 380 of the tenth embodiment, the motor drive device 380b changes the target temperature of hot water set for the water heater 380, the temperature of water supplied to the water heat exchanger 385a, and the outside air temperature. Based on the command rotational speed, the motor drive device 380b controls the brushless motor rotational speed of the compressor 380a based on the command rotational speed. Thereby, hot water supply 380 supplies hot water at the target temperature.

  As described above, in the heat pump water heater 380 of the thirteenth embodiment, the brushless motor is used as the power source of the compressor 380a, and the advance value β of the current supplied to the brushless motor is set in the same manner as in the first embodiment. Since the deviation between the rotational speed fo and the actual rotational speed f is determined to be a minimum, even in a situation where the input voltage of the inverter fluctuates, simple and stable field-weakening control that only changes the current advance value allows The brushless motor can be stably driven up to high speed rotation. Thereby, the heat pump water heater 380 equipped with the brushless motor and its driving device can be designed with a high degree of freedom in design.

(Embodiment 14)
FIG. 19 is a schematic diagram illustrating a hybrid vehicle according to the fourteenth embodiment of the present invention.
The hybrid vehicle 400 according to the fourteenth embodiment is a vehicle in which two power sources, i.e., an internal combustion engine and a motor, are combined, and travels by operating the power sources simultaneously or individually depending on the situation.

  That is, the hybrid vehicle 400 includes an internal combustion engine 410 that generates power Ep, a motor 402 that generates power according to input power and generates power according to power supplied from the outside, and the internal combustion engine 401. Or it has the drive mechanism 440 which generate | occur | produces the driving force of a motor vehicle with the motive power which was generated with the electric motor 402. FIG. The hybrid vehicle 400 divides the power Ep generated by the battery 401 and the generator 430 and the internal combustion engine 410 into two systems, and supplies the power Ep1 of the divided power generation system to the generator 430. A power split mechanism 420 for supplying the drive system power Ep2 to the electric motor 402, a motor drive device 400a for driving the electric motor 402 as a motor, using the output Bc of the battery 401 and the output Gc of the generator 403 as inputs. have.

  Here, the electric motor 402 has the same configuration as the brushless motor 2 of the first embodiment, and operates as a motor or a generator according to the traveling state of the automobile. That is, the electric motor 402 is rotationally driven by the split power Ep2 from the power split mechanism 420 or the braking force Bp of the drive mechanism 440, and generates a drive force by the drive current Dc from the motor drive device 400a. The drive mechanism 440 drives a pair of drive wheels 441, a drive shaft 442 connected to the drive wheels 441, and power Dp supplied from the electric motor 402 to the drive wheels 441 via the drive shaft 442. And a gear mechanism 443 that transmits the braking force Bp of the driving wheel 441 to the electric motor 402 via the driving shaft 442 as the driving force of the electric motor 402. Furthermore, the motor drive device 400a has the same circuit configuration as the motor drive device 100a of the first embodiment. Here, the input nodes 1a and 1b of the motor drive device 400a are connected to the output of the battery 401. The terminal and the output terminal of the generator 403 are connected.

Next, the operation will be described.
The hybrid vehicle 400 charges the battery 401 with the electric power generated by rotating the generator 430 by the internal combustion engine 410, and travels using the output of the battery 401 or the output of the generator 430 as travel energy.

  For example, when the traveling efficiency due to driving of the internal combustion engine 410 is low, the battery output Bc is supplied to the electric motor 402 by the motor driving device 400a, and the driving force Dp generated by the electric motor 402 is transmitted to the driving wheels 441. As a result, the hybrid vehicle 400 travels with a motor.

  Further, when the traveling speed exceeds a certain speed, the internal combustion engine 410 starts to be driven, and the power Ep generated by the internal combustion engine 410 is supplied to the electric motor 402 as the driving system power Ep2 through the power split mechanism 420. In 402, power is generated by the drive current Dc from the motor drive device 400a, and the power Ep2 supplied from the internal combustion engine and the power generated by the drive current are supplied to the drive mechanism 440 as the drive power Dp. Thereby, in the drive mechanism 440, the drive force Dp is transmitted to the drive wheels 441 via the gear mechanism 443 and the drive shaft 442.

  Further, in this hybrid vehicle 400, when the driving load of the driving wheels 441 becomes light, the power split mechanism 420 distributes a part of the power Ep generated by the internal combustion engine 410 to the generator 430 as the power Ep1 of the power generation system. Then, the electric power Gc generated by the generator 430 is supplied to the battery 401 as the charging electric power Cc via the motor driving device 400a, whereby the battery 401 is charged. In this state, the hybrid vehicle 400 travels while charging the battery 401.

  Further, in this hybrid vehicle 400, when a braking operation is performed at the time of deceleration or stopping, the braking force Bp of the driving wheel 441 is transmitted as the driving force to the electric motor 402 via the driving shaft 442 and the gear mechanism 443. . At this time, the electric motor 402 operates as a generator, and the regenerative electric power Rc generated by the braking force Bp is applied to the battery 401 via the motor driving device 400a, and the battery 401 is charged.

  Thus, in hybrid vehicle 400 of the fourteenth embodiment, brushless motor 402 is used as the power source, and the advance value β of the current supplied to the brushless motor is set to the command rotational speed fo as in the first embodiment. Since the deviation from the actual rotational speed f is determined to be the minimum, even in situations where the input voltage of the inverter fluctuates, the brushless motor can be operated at high speed with simple and stable field weakening control that only changes the current advance value. It can be driven stably until rotation. As a result, the hybrid vehicle 400 equipped with the brushless motor and its drive device can be designed with a high degree of freedom in design.

  In the fourteenth embodiment, the electric vehicle is the most general series / parallel hybrid electric vehicle. However, the electric vehicle according to the fourteenth embodiment is a series hybrid electric vehicle 500 shown in FIG. Alternatively, a parallel hybrid electric vehicle 600 shown in FIG. 21 may be used.

  For example, a series hybrid vehicle 500 shown in FIG. 20 includes a motor 402a instead of the electric motor 402 in the hybrid electric vehicle 400 shown in FIG. 19, drives a generator 430 by the power Ep of the internal combustion engine 410, and generates electric power Gc. The battery 401 is charged or the motor 402a is driven. Accordingly, this hybrid vehicle 500 does not have the power split mechanism 420 in the hybrid vehicle shown in FIG. 19, and does not directly drive the drive wheels 411 by the internal combustion engine, but drives the drive wheels 441 only by the motor. It is. This hybrid vehicle 500 is called a series system because an internal combustion engine and a motor, which are two power sources, are arranged in series.

  Further, the parallel hybrid electric vehicle 600 shown in FIG. 21 includes a transmission 450 that replaces the power split mechanism 420 in the hybrid electric vehicle 400 shown in FIG. 19, and the power Ep of the internal combustion engine 410 is supplied to the electric motor via the transmission 450. 402. Therefore, this hybrid vehicle 600 does not have the generator 430 shown in FIG.

  In this parallel hybrid vehicle 600, the internal combustion engine 410 is mainly used for traveling, and in some cases, the internal combustion engine 410 is used as a power source for charging the battery 401.

  For example, when starting or accelerating when a load is applied to the internal combustion engine, the electric motor 402 operates as a motor by the electric power Dc supplied from the motor driving device 400a. The electric motor 402 is generated by the electric power Ep generated by the internal combustion engine and the electric motor 402. The motive power is output to the drive mechanism as the drive force Dp. As a result, the driving of the drive wheels 441 is assisted by the power of the motor. Further, when the internal combustion engine has a low operating efficiency and a light load, the electric motor 402 operates as a generator, and the battery is charged and the driving wheels are driven by the power of the internal combustion engine. It is done. Further, in this hybrid vehicle 600, during braking or downhill, the energy use efficiency during traveling is enhanced by collecting electric power by regenerative braking of the electric vehicle and stopping the engine when the vehicle is stopped. The hybrid vehicle 600 is called a parallel system because driving by two power sources, that is, driving by an internal combustion engine and driving by an electric motor are performed in parallel.

  Furthermore, the electric vehicle of the fourteenth embodiment may be an electric vehicle that does not have an internal combustion engine and runs only with electric power from the battery. In this case, the same effect as in the fourteenth embodiment can be obtained. .

  In the seventh to fourteenth embodiments, the motor drive device for driving the brushless motor as the power source is the same as the motor drive device in the first embodiment, but the motor drive in the seventh to fourteenth embodiments is used. The apparatus may be the same as the motor drive apparatus according to any one of the second to sixth embodiments.

  The motor driving device according to the present invention performs a field weakening control of a brushless motor with a control amount such as a preset table value even when the voltage source is steep or has a large fluctuation periodically. This can be carried out stably without using it, and this makes it possible to increase the maximum rotational speed of the brushless motor, which is extremely useful.

It is a block diagram explaining the motor drive device 100a by Embodiment 1 of this invention. It is a figure explaining operation | movement of the advance value determination part 6a in the motor drive device 100a of Embodiment 1, and has shown the processing flow of the hill-climbing method which is an example of the determination method of the advance value (beta). It is a block diagram explaining the motor drive device 100b by Embodiment 2 of this invention. It is a wave form diagram explaining operation | movement of the motor drive device 100b of the said Embodiment 2, and has shown the waveform of the input voltage. It is a wave form diagram explaining operation | movement of the motor drive device 100b of the said Embodiment 2, and has shown the waveform of the output current when not controlling an advance value. It is a wave form diagram explaining operation | movement of the motor drive device 100b of the said Embodiment 2, and has shown the waveform of the output current at the time of controlling an advance value. It is a block diagram explaining the motor drive device 100c by Embodiment 3 of this invention. It is a figure explaining operation | movement of the advance value determination part in the motor drive device 100c of the said Embodiment 3, and has shown the processing flow of the mountain climbing method which is an example of the determination method of the advance value (beta). It is a block diagram explaining the motor drive device 100d by Embodiment 4 of this invention. It is a figure explaining operation | movement of the advance value determination part in the motor drive device 100d of the said Embodiment 4, and has shown the processing flow of the hill-climbing method which is an example of the determination method of the advance value (beta). It is a block diagram explaining the motor drive device 100e by Embodiment 5 of this invention. It is a block diagram explaining the motor drive device 100f by Embodiment 6 of this invention. It is a figure explaining the field weakening control of the motor which is a prior art, and has shown the motor equivalent circuit. It is a figure explaining the field weakening control of the motor which is a prior art, and has shown the field current and torque current which are used by the vector control of a motor. It is a schematic diagram explaining the air conditioner 250 by Embodiment 7 of this invention. It is a schematic diagram explaining the refrigerator 260 by Embodiment 8 of this invention. It is a schematic diagram explaining the electric washing machine 270 by Embodiment 9 of this invention. It is a schematic diagram explaining the air blower 280 by Embodiment 10 of this invention. It is a schematic diagram explaining the vacuum cleaner 290 by Embodiment 11 of this invention. It is a schematic diagram explaining the electric dryer 360 by Embodiment 12 of this invention. It is a schematic diagram explaining the heat pump water heater 380 by Embodiment 13 of this invention. It is a schematic diagram illustrating a hybrid vehicle 400 according to a fourteenth embodiment of the present invention. FIG. 22 is a schematic diagram illustrating a modification of hybrid vehicle 400 according to the fourteenth embodiment, and shows a power system of series hybrid vehicle 500. FIG. 22 is a schematic diagram for explaining another modification of hybrid vehicle 400 according to the fourteenth embodiment, and shows a power system of parallel hybrid vehicle 600.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Voltage source 1a, 1b Output node 2 Brushless motor 3 Inverter circuit 3a-3c Connection point 4a, 4b, 4c, 4d, 4e, 4f Inverter control part 5 Rotor position estimation part 6a, 6c, 6d Advance angle value determination part 7 Drive Signal generator 8b, 8d Command current waveform generator 9 PWM generator 12 Capacitor 13 Inductor 31-36 Switching element 41-46 Diode 100a, 100b, 100c, 100d, 100e, 100f, 277, 283, 294, 400a Motor drive device 250 Air conditioner 250a, 260a, 360a, 380a Compressor 250b, 260b, 270b, 360b, 380b Motor drive controller 251 Indoor heat exchangers 251a, 252a, 262a, 362a, 382a Blowers 251b, 252b, 26 b, 362b, 382b, 385a Temperature sensor 252 Outdoor heat exchanger 253, 263, 273, 363, 383 Throttle device 254 Four-way valve 255 Indoor unit 256 Outdoor unit 260 Refrigerator 261, 361 Condenser 262 Cold room evaporator 270 Electric washing Machine 272 Hanging rod 273 Outer tank 274 Washing and dewatering tank 275 Stirring blades 276, 282, 293 Brushless motor 280 Blower 281, 292 Fan 290 Vacuum cleaner 290a Vacuum cleaner body 291 Electric blower 295 Dust collection chamber 296 Hose 297 Floor suction Tool 360 Electric dryer 362 Evaporator 364 Drying chamber 380 Heat pump water heater 381a Refrigeration cycle apparatus 381b Hot water storage tank 382 Air heat exchanger 384 Refrigerant pipe 384a Defrost bypass pipe 384b Defrost bypass valve 385 Water heat exchange 386a, 386b, 387a, 387b Water pipe 387a1, 387b1 Joint part 387 Pump 388 Hot water storage tank 388a Water inlet / outlet 388b Water outlet 388b1 Drain valve 388c Water supply pipe 388c1 Water inlet 388d Bath hot water supply pipe 388d1 Hot water outlet 388d1 Motor vehicle 401 Battery 402 Electric motor 402a Motor 410 Internal combustion engine 420 Power split mechanism 430 Generator 440 Drive mechanism 441 Drive wheel 442 Drive shaft 443 Gear mechanism 450 Transmission A to C, E, F Direction of refrigerant flow Bc Battery output current Bp Braking force Cc Charging current Dc Driving current Dp Driving force Ep Engine output Ep1, Ep2 Divided engine output fo Command rotational speed Gc Power generation current I Actual current Io Command current Rc Regenerative current Sg Gate signal (drive signal)
β Lead angle value θ Rotor position

Claims (3)

A motor driving device for driving a brushless motor,
An inverter circuit that converts the output voltage of the voltage source into a drive voltage and outputs the converted voltage to the brushless motor;
A rotor position estimating unit for estimating a rotor position of the brushless motor;
An inverter control unit that controls the inverter circuit so that the brushless motor is driven by a current based on the estimated rotor position;
A rotational speed determination unit that determines a command rotational speed of the brushless motor;
An actual rotational speed detection unit for detecting the actual rotational speed of the brushless motor,
The inverter control unit
A rotor position which is above Symbol estimated increase or decrease the phase difference between the current supplied to the brushless motor, the actual rotation of the brushless motor according to the rotation speed of the change of the brushless motor caused by the adjustment of the previous phase difference The number is repeatedly adjusted so that it matches the target rotational speed that is the target value.
The motor drive device characterized by the above-mentioned. The motor drive device according to claim 1,
The inverter control unit
In a state where the amplitude value of the current supplied to the brushless motor is fixed to the maximum value, the rotation speed of the brushless motor is controlled by increasing or decreasing the phase difference.
The motor drive device characterized by the above-mentioned. In the motor drive device according to claim 2,
The maximum amplitude value of the current supplied to the brushless motor is the maximum current value permitted to be supplied to the brushless motor.
The motor drive device characterized by the above-mentioned.

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