JP4416486B2 - Motor control device - Google Patents

Description

  The present invention relates to a motor control device for controlling a brushless motor included in an air conditioner, a refrigerator, a washing machine, a blower or the like using an inverter circuit.

  FIG. 33 is a block diagram showing a configuration of a conventional motor control device for driving a brushless motor. In the following description, the conventional motor control device shown in FIG. 33, reference numeral 101 denotes an AC power source, reference numeral 102 denotes an inductor, reference numeral 103 denotes a rectifier diode, reference numeral 104 denotes a smoothing capacitor, reference numeral 106 denotes an inverter circuit, reference numeral 107 denotes a brushless motor, and reference numeral 108 denotes a position sensor. When the AC voltage from the AC power supply 101 is converted into a DC voltage using the rectifier diode 103 and the smoothing capacitor 104 in order to input DC power to the inverter circuit 106, the current from the AC power supply 101 is used for smoothing. It flows only when the voltage of the capacitor 104 is smaller than the input AC voltage. For this reason, the current from the AC power supply 101 is a current with a harmonic component. Therefore, in the first prior art, the inductor 102 is provided between the AC power supply 101 and the rectifier diode 103 in order to reduce the harmonic component and improve the power factor. As described above, in the first prior art, the rectifier circuit 105 uses the inductor 102 and the smoothing capacitor 104 in addition to the rectifier diode 103. Further, when the brushless motor 107 is driven by an inverter, information on the rotation angle of the rotor is necessary. For this reason, in the first prior art, the rotation angle is detected using the position sensor 108 (see, for example, Patent Document 1).

  Since the inductor 102 and the smoothing capacitor 104 of the rectifier circuit 105 used in the first prior art are often large components with large inductance or capacitance, the conventional motor control device is large and expensive. There were many things. In the field of motor control devices, from the viewpoint of miniaturization and cost reduction of devices, rectifier circuits that use small components such as inductors with low inductance or capacitors with low capacitance, or do not use these components The construction of was desired.

  Therefore, a motor control device that does not use an inductor and a smoothing capacitor as shown in FIG. 34 has been proposed as a second prior art. Since the smoothing capacitor is not used in the second prior art, the input voltage to the inverter circuit 106 is not a direct current but a voltage waveform having pulsation. When a voltage having such a pulsation is input to the inverter circuit 106, a desired voltage to be applied to the brushless motor 107 may not be formed in the inverter circuit 106 when the input voltage to the inverter circuit 106 is low. In the second prior art, when such a desired voltage cannot be obtained, the phase of the voltage applied to the brushless motor 107 is advanced. Since the so-called field weakening state can be achieved by advancing the phase of the applied voltage to the brushless motor 107 in this way, the applied voltage required for the brushless motor 107 can be reduced. Therefore, the second conventional technique is a technique capable of continuing to drive the brushless motor 107 even when the input voltage to the inverter circuit 106 is low. However, in the second prior art, the switching operation of the inverter circuit 106 is stopped when the input voltage to the inverter circuit 106 becomes equal to or lower than a predetermined value. This is because there is a limit to driving the motor in the field-weakening state. As described above, the second conventional technique is a technique in which no voltage is applied to the brushless motor 107 when the input voltage to the inverter circuit 106 is equal to or lower than a predetermined voltage value (for example, Patent Document 2). reference).

In addition, in the motor control device, a device that does not use a position sensor is desired from the viewpoint of wireless wiring and cost reduction. In view of this, a third conventional technique has been proposed in which the motor current is detected to estimate the rotor position of the brushless motor. The third prior art is a calculation formula for estimating a phase derived based on a voltage equation from a motor current, a voltage value applied to the brushless motor at that time, and a motor constant such as a resistance value and an inductance of the brushless motor. Thus, the rotor position of the motor has been estimated (for example, see Non-Patent Document 1).
JP-A-9-74790 (FIG. 1) Japanese Patent Laid-Open No. 10-150795 (page 3-5, FIG. 1) Takeshita, Ichikawa, Lee, Matsui, "Sensorless salient pole type brushless DC motor control based on speed electromotive force estimation", IEEJ Transactions D, 1997, Vol. 117, No. 1, p. 98-104

  As described above, the first prior art uses a position sensor to detect the rotor position of a brushless motor, and uses an inductor or a smoothing capacitor to convert the input voltage to the inverter circuit to a DC voltage. . Therefore, since the inductor and the smoothing capacitor are large components having large inductance or capacitance, it is difficult to reduce the size of the motor control device using these components.

The second prior art is a motor control device that detects the rotor position of a brushless motor using a position sensor, and does not use large parts such as an inductor or a smoothing capacitor. Therefore, the second prior art is an effective technique from the viewpoint of miniaturization and cost reduction. However, in the second prior art, since the input voltage to the inverter circuit pulsates, there is a problem that the application of the voltage to the brushless motor is stopped when the input voltage is low below a predetermined value.
Therefore, a position sensorless system that achieves a reduction in size and cost by combining the second conventional technique that does not use an inductor or a smoothing capacitor and the third conventional technique that is configured to drive a motor without a position sensor. When trying to construct a motor control apparatus, there are the following problems. In the motor control device having such a configuration, the position of the rotor cannot be estimated during the period in which the voltage application to the brushless motor is stopped, and therefore the brushless motor cannot be driven without a position sensor. That is, it is impossible to construct a motor control device in which the input voltage to the inverter circuit pulsates without a position sensor by simply combining the second conventional technique and the third conventional technique.

  An object of the present invention is to provide a small motor control device that can reduce the size of the rectifier circuit portion and can be adapted to either a configuration using a position sensor or a configuration without a position sensor. Another object of the present invention is to provide a motor control device that can be driven without a position sensor without stopping the application of voltage to the brushless motor even if the input voltage of the inverter circuit pulsates greatly. It is to be.

In order to achieve the above object, the motor control device of the present invention has a variable voltage as an input, converts the voltage into a desired voltage and outputs the voltage to a brushless motor, and an input voltage to the inverter circuit, A motor current that flows to the brushless motor and a motor current command value that indicates a value that should flow to the brushless motor are input to generate a three-phase sine wave voltage command value to be applied to the brushless motor, and the three-phase sine wave In a motor control device including a control unit having a PWM generation unit that outputs a PWM signal according to a voltage command value,
The PWM generation unit includes a line modulation unit that subtracts and outputs a minimum value in the three-phase sine wave voltage command value from the three-phase sine wave voltage command value,
Compare the maximum value of the output of the interline modulation unit and the input voltage to the inverter circuit,
As a result of the comparison, when the input voltage is larger than the maximum value, the PWM signal is generated according to the ratio of each output of the line modulation unit to the input voltage,
When the input voltage is less than or equal to the maximum value, the PWM signal is formed according to the ratio of each output of the line modulation unit to the maximum value,
A voltage is applied to the brushless motor while the phase is maintained . The motor control device of the present invention configured as described above can reduce the size of the rectifier circuit portion, and can correspond to either a configuration using a position sensor or a configuration without a position sensor. Further, the motor control device of the present invention configured as described above can be driven without a position sensor without stopping the application of the voltage to the brushless motor even if the input voltage of the inverter circuit pulsates greatly. it can.
A motor control device according to another aspect of the present invention includes an inverter circuit that receives a fluctuating voltage, converts the voltage into a desired voltage, and outputs the voltage to a brushless motor.
A control unit that receives an input voltage to the inverter circuit, a motor current that flows to the brushless motor, and a motor current command value that indicates a value that should flow to the brushless motor, and generates a motor applied voltage command value for the inverter circuit In a motor control device comprising:
The control unit further includes:
A PWM generator that receives the motor applied voltage command value and the input voltage and outputs a PWM signal corresponding to the motor applied voltage command value to the inverter circuit;
The PWM control unit
The motor applied voltage command value and the input voltage are input, a reference voltage is set from the motor applied voltage command value, the reference voltage and the input voltage are compared, and as a result of the comparison, the input voltage is the reference voltage When the voltage is smaller than the voltage, a value obtained by multiplying the motor applied voltage command value by the ratio of the input voltage to the reference voltage is output. When the input voltage is equal to or higher than the reference voltage, the motor applied voltage command value is output as it is. Ratio correction unit,
An inverse dq converter that generates a three-phase sine wave voltage command value from the output of the ratio correction unit;
A line modulation unit that subtracts and outputs the minimum value of the three-phase sine wave voltage command value from the three-phase sine wave voltage command value; and
A ratio generation unit that generates a PWM signal based on a ratio of the output of the line modulation unit to the input voltage is configured to apply a voltage to the brushless motor while maintaining a phase. The motor control device of the present invention configured as described above can continuously apply a voltage without stopping the voltage application to the brushless motor even when the DC side voltage of the inverter circuit is low. Further, the motor control device of the present invention configured as described above does not stop the voltage application to the brushless motor even when the sensorless drive is performed in a situation where the rotor phase information of the brushless motor cannot be obtained from the position sensor. A voltage can be applied continuously. Therefore, according to the configuration of the motor control device of the present invention, the phase of the brushless motor can always be estimated, so that it is possible to provide a motor control device that is driven without using a position sensor.

  In the motor control device of the present invention, the control unit may be configured to estimate the rotational phase of the brushless motor based on the motor current. With this configuration, even when performing sensorless driving in which the rotor phase information of the brushless motor cannot be obtained from the position sensor, voltage can be continuously applied without stopping the voltage application to the motor. It is possible to estimate the phase and drive without using a position sensor.

  In the motor control device of the present invention, the control unit may be configured to stop the integral control of the control unit when the voltage value at both ends of the inverter circuit is smaller than the voltage command value applied to the brushless motor. By configuring in this way, unnecessary errors do not have to be superimposed on the controller that performs current control, so that the motor current does not flow unnecessarily, and the position sensorless estimation accuracy can be improved. Provided is a motor control device capable of performing control stably.

  In the motor control device of the present invention, the control unit may be configured to calculate the voltage command value by a calculation formula having a non-interference term. As described above, since the motor control device of the present invention has a non-interference term in the feedback control, the independence of the current control system can be improved, the position sensorless estimation accuracy can be further improved, and more stably. Operate.

In the motor control device of the present invention, the control unit may be configured to detect the voltage of the inverter circuit, estimate the voltage of the inverter circuit applied in the next control cycle, and control the inverter circuit. . When the input voltage of the inverter circuit pulsates greatly, an error occurs between the detection result and the actual voltage especially when the control cycle of the inverter circuit is long. However, since the control unit is configured to estimate and control the voltage of the inverter circuit applied in the next control cycle based on the detected voltage of the inverter circuit, the input voltage of the inverter circuit is estimated with high accuracy. can do. As a result, according to the present invention, a more accurate voltage can be applied to the brushless motor, and a more favorable motor control device can be provided.
In the motor control device of the present invention, a capacitor having a small capacitance may be provided on the input side of the inverter circuit. In the motor control device of the present invention configured as described above, since the regenerative current from the motor side flows into the capacitor, the input side voltage of the inverter main circuit rises abnormally due to the regenerative current. This is a safe device that can be prevented and has a function to protect against overvoltage.

  In the motor control device of the present invention, an inductor having a small inductance may be provided on the input side of the inverter circuit. The motor control device of the present invention configured as described above can remove harmonic components because the current waveform becomes smooth, and the device has a higher power supply utilization rate.

The motor control device of the present invention further includes a booster circuit having an inductor, a diode, a switching element, and a capacitor, and a booster circuit controller that controls the booster circuit,
The booster circuit control unit may be configured to determine a duty value of the switching element based on a signal from the control unit. The motor control device of the present invention configured as described above is configured such that the input side voltage of the inverter circuit can be boosted in the booster circuit, so that the maximum rotational speed of the brushless motor is increased, and the operation is performed in a wider driving rotational speed range. It becomes a motor control device that can.

In the motor control device of the present invention, the booster circuit control unit is configured to receive the detected phase of the AC power supply and the AC current value, and based on the detected phase and a control signal from the control unit. An AC current command unit that outputs an AC current command value, and a PWM command creation unit that forms and outputs a PWM command value for driving the switching element based on the AC current command value and the detected AC current of the AC power supply You may comprise so that it may have. The motor control device of the present invention configured as described above is a device that does not adversely affect the power supply system.

In the motor control device of the present invention, an inductor to which a fluctuating voltage is input, a plurality of diodes constituting the rectifier circuit, a switching element connected to the rectifier circuit and performing an on / off operation, a capacitor for outputting a boosted voltage, And a booster circuit controller that controls the booster circuit. The motor control device of the present invention configured as described above can greatly expand the operation range with a simple configuration.

In the motor control device of the present invention, when the capacitance of the capacitor is C [F] and the maximum output power of the motor is P [W],
C ≦ 2 × 10 ⁻⁷ × P
It is preferable to constitute so that.

In the motor control device of the present invention, the inverter circuit includes an inductor having a small inductance, the inductance of the inductor is L [H], and the capacitance of the capacitor is C [F].
L ≦ 9 × 10 ⁻⁹ / C
It is preferable to constitute so that.

In the motor control device of the present invention, when the inductance of the inductor is L [H] and the maximum output power of the motor is P [W],
L ≦ P × 10 ⁻⁶
It is preferable to constitute so that.

  The motor control device of the present invention configured as described above can be used for a compressor, an air conditioner, a refrigerator, an electric washing machine, an electric dryer, a blower, an electric vacuum cleaner, and a heat pump water heater, and an inverter circuit Even when the DC side voltage at is low, it is possible to drive each device with high efficiency by continuously applying a desired voltage without stopping the voltage application to the drive source.

  The novel features of the invention are nonetheless specifically set forth in the appended claims, but the invention, both in terms of structure and content, should be read in conjunction with the drawings and in the detailed description that follows. Will be better understood and appreciated.

ADVANTAGE OF THE INVENTION According to this invention, while being able to miniaturize a rectifier circuit part, the small motor control apparatus which can respond to any structure of the structure using a position sensor and the structure of a position sensorless can be provided.
In addition, according to the present invention, there is provided a motor control device that can be driven without a position sensor without stopping the application of voltage to a brushless motor even if the input voltage to the inverter circuit pulsates greatly. be able to.
Further, according to the present invention, it is possible to provide a motor control device that can continuously apply a voltage without stopping the voltage application to the motor even when the DC side voltage to the inverter circuit is low.

Further, according to the present invention, even when performing sensorless driving in which the rotor phase information of the brushless motor cannot be obtained from the position sensor, the voltage can be continuously applied without stopping the voltage application to the motor. It is possible to provide a motor control device that can estimate the phase and drive without using a position sensor.
Further, according to the present invention, unnecessary errors do not have to be superimposed on a controller that performs current control, so that motor current does not flow unnecessarily, position sensorless estimation accuracy can be improved, and high accuracy A stable motor control device can be provided.

In addition, according to the present invention, it is possible to provide a motor control device that can significantly improve output torque in a motor control device that does not have a smoothing capacitor with a large capacitance in a rectifier circuit. In the motor control device of the present invention, when the input voltage of the inverter circuit pulsates and a desired voltage cannot be applied to the motor, the phase of the motor applied voltage can be maintained, so that unnecessary motor current is reduced, It is possible to reduce motor stoppage due to overcurrent.
In addition, since the motor control device of the present invention enables highly accurate phase estimation, the motor can be driven without a position sensor, and can be applied to a compressor used in an air conditioner, a refrigerator, or the like.

In addition, according to the present invention, the followability of the motor current can be improved, so that it is possible to provide a motor control device with high efficiency, low noise, and improved output torque.
Furthermore, according to the present invention, a motor control device can be provided that can be configured without using a power factor improving inductor, which is a large component, and a smoothing capacitor having a large capacitance among conventional motor control devices. A compressor including a motor control device equivalent to or smaller than that of a compressor can be provided, which can bring about great benefits in promoting global energy saving and preserving the global environment.

In addition, the motor control device of the present invention is configured to boost the input voltage of the inverter circuit when the output voltage of the single-phase AC power supply is low so that the voltage applied to the brushless motor is insufficient. For this reason, according to the present invention, it is possible to provide a motor control device capable of increasing the maximum rotational speed of the brushless motor and greatly expanding the operation range.
Further, according to the present invention, by operating the booster circuit and the booster circuit control unit, the current waveform flowing through the single-phase AC power supply becomes almost sinusoidal, so that the power supply power factor becomes almost 1, which adversely affects the power supply system. It is possible to provide a motor control device that does not reach the target.
In the motor control device of the present invention, since the capacitance of one capacitor in the voltage doubler rectifier booster circuit can be reduced, the size can be reduced as compared with the conventional voltage doubler rectifier circuit.

  Although the invention has been described in its preferred form with a certain degree of detail, the present disclosure of this preferred form should vary in the details of construction, and combinations of elements and changes in order may vary in the claimed invention. It can be realized without departing from the scope and spirit.

  Hereinafter, a motor control device according to a preferred embodiment of the present invention will be described with reference to FIGS.

Embodiment 1
FIG. 1 is a block diagram showing the configuration of the motor control apparatus according to the first embodiment of the present invention. In FIG. 1, AC power output from a single-phase AC power supply 5 is rectified into DC power having pulsation in a rectifier circuit 1 and applied to an inverter circuit 2. The inverter circuit 2 converts the rectified DC power into AC power and applies a desired voltage to the brushless motor 3. The control unit 4 detects the current flowing through the brushless motor 3 and controls the drive of the inverter circuit 2. The control unit 4 includes a dq conversion unit 6, a d-axis PI controller 7, a q-axis PI controller 8, a PWM generation unit 9, a subtraction unit, and the like.

Next, the operation of the control unit 4 in the first embodiment will be described.
The dq converter 6 calculates the d-axis current detection value Id and the q-axis current detection value Iq according to the following formula (1) using the current detection values Iu, Iv, Iw flowing through the three-phase coils of the brushless motor 3. The rotational phase θ used in this calculation is obtained as a result of estimating the position signal from the position sensor when the brushless motor 3 is provided with a position sensor, and estimating the rotor position when the position sensor is not provided. Use the estimated phase.

The d-axis PI controller 7 includes an error between the d-axis current command value Id * calculated based on an external rotation speed command, a torque command, and the like, and the d-axis current detection value Id that is the output of the dq conversion unit 6. Is entered. The error is PI-controlled by the d-axis PI controller 7 to generate a d-axis voltage command value Vd. Similarly to the d-axis PI controller 7, the q-axis PI controller 8 includes a q-axis current command value Iq * calculated based on an external rotation speed command, a torque command, and the like, and an output of the dq conversion unit 6. An error from the q-axis current detection value Iq is input. The error is PI-controlled by the q-axis PI controller 8 to generate a q-axis voltage command value Vq.
The PWM generator 9 outputs a PWM signal for driving the inverter circuit 2 from the d-axis voltage command value Vd, the q-axis voltage command value Vq, and the input voltage detection value Vpn to the inverter circuit 2.

FIG. 2 is a block diagram showing the configuration and operation of the PWM generator 9. As illustrated in FIG. 2, the PWM generation unit 9 includes an inverse dq conversion unit 10, an interline modulation unit 11, and a Vpn correction unit 12.
The inverse dq converter 10 calculates the three-phase sine wave voltage command values Vu, Vv, Vw from the d-axis voltage command value Vd and the q-axis voltage command value Vq according to the following equation (2). As the rotational phase θ used for this calculation, when the brushless motor 3 is provided with a position sensor, the position signal thereof is used, or when the brushless motor 3 is not provided with a position sensor, an estimated phase obtained as a result of estimating the rotor position is used.

The line modulation unit 11 detects the minimum value in the input three-phase sine wave voltage command values Vu, Vv, and Vw, and subtracts the detected minimum value from the three-phase sine wave voltage command value Vu ′, Vv. Output as ', Vw'. As a result, the sine wave voltage command value of at least one phase becomes 0, and the remaining two phases become positive values.
The Vpn correction unit 12 receives the outputs Vu ′, Vv ′, Vw ′ from the line modulation unit 11 and the input voltage detection value Vpn, and generates PWM output duty values Du, Dv, Dw. Here, the PWM output duty values Du, Dv, and Dw are obtained by Expression (3) or Expression (4) described later.

FIG. 3 is a flowchart showing a calculation method in the Vpn correction unit 12.
The maximum values of the output values Vu ′, Vv ′, Vw ′ of each phase from the interline modulation section 11 are detected, and the values are set as the applied voltage maximum value Vmax (step 31). Next, the magnitudes of the applied voltage maximum value Vmax and the input voltage detection value Vpn are compared (step 32). In step 32, when the detected input voltage value Vpn is larger than the maximum applied voltage value Vmax, a normal applied calculation is performed and a desired applied voltage command value is applied to the brushless motor 3. Therefore, the PWM output duty values of the U phase, V phase, and W phase are determined by the following equation (3) (step 33).

  On the other hand, if the input voltage detection value Vpn is smaller than the applied voltage maximum value Vmax, the desired applied voltage command value cannot be applied to the brushless motor 3, and the maximum that can be formed at that time without changing the phase of the applied voltage. Apply a voltage of. Therefore, U-phase, V-phase, and W-phase PWM output duty values are determined by the following equation (4) (step 34).

  When the calculation of the above formula (4) is performed, the ratio of the U phase, the V phase, and the W phase is the same as the ratio before the calculation of the formula (4). A voltage is applied to.

  FIG. 4A is a graph showing experimental results of motor current by a conventional motor control device. FIG. 4B is a graph showing the experimental results of the motor current according to the first embodiment when the equation (4) of the Vpn correction unit 12 is used. 4A and 4B, the input voltage detection value Vpn, the motor current, the motor current command value, and the motor applied voltage phase are shown in order from the top. In the experiment in which the result of FIG. 4A was obtained, the motor control device having the configuration of the first prior art described above was used as a conventional motor control device.

  In the conventional motor control device, when the input voltage detection value Vpn, which is the input side voltage to the inverter circuit, is small, a current greatly deviating from the target current flows through the brushless motor. Such a current causes a decrease in motor efficiency and an increase in noise. In addition, if a large current flows, the motor magnet is demagnetized, causing a failure. Furthermore, since the maximum value of the current increases as the load applied to the brushless motor increases, the rated current of the inverter circuit must be increased to drive the brushless motor with a predetermined load. It was necessary to use a configured inverter circuit. 4A, in the conventional motor control device, when the input voltage detection value Vpn to the inverter circuit is small, the phase of the motor applied voltage is disturbed, and the motor current greatly fluctuates. It can be seen.

On the other hand, when the motor control device according to the first embodiment of the present invention is used, the correct voltage phase is applied to the brushless motor 3 even when the input voltage detection value Vpn is small in order to maintain the phase of the motor applied voltage. Has been. And since the disturbance of the motor current at that time is small, the motor efficiency is increased and the noise is reduced.
From the above experimental results, in the conventional motor control device, since the motor current becomes larger than necessary, the inverter circuit is increased in size and cost, whereas the motor using the first embodiment according to the present invention is used. In the control device, the motor current is less disturbed and can be configured by an inverter circuit having a small current capacity.

  According to the motor control device of the first embodiment of the present invention, the rectifier circuit portion can be reduced in size, and any of a configuration using a position sensor and a configuration without a position sensor can be supported. is there. Further, the motor control device of the first embodiment can be driven without a position sensor without stopping the application of the voltage to the brushless motor even if the input voltage of the inverter circuit pulsates greatly.

<< Embodiment 2 >>
Next, a motor control device according to a second embodiment of the present invention will be described. FIG. 5 is a block diagram showing the operation of the PWM generation unit 90 in the motor control apparatus of the second embodiment. The configuration of the motor control device of the second embodiment is substantially the same as the configuration of the first embodiment except for the PWM generation unit 9 in the motor control device of the first embodiment described above. explain.

As illustrated in FIG. 5, the PWM generation unit 90 of the second embodiment includes a ratio correction unit 13, an inverse dq conversion unit 10, an interline modulation unit 11, and a ratio generation unit 14. In FIG. 5, the operations of the inverse dq conversion unit 10 and the interline modulation unit 11 are the same as those in the first embodiment.
The calculation method in the ratio correction unit 13 is shown in the flowchart of FIG. V1 is calculated from the d-axis voltage command value Vd and the q-axis voltage command value Vq using the following equation (5) (step 35). The magnitudes of V1 and the detected input voltage Vpn are compared (step 36).

If the input voltage detection value Vpn is smaller in step 36, the values of the d-axis voltage command value Vd and the q-axis voltage command value Vq are changed to Vd ′ and Vq ′, respectively, according to the following equation (6). (Step 37). When the input voltage detection value Vpn is larger, the d-axis voltage command value Vd and the q-axis voltage command value Vq are output as they are.
The ratio generation unit 14 performs the calculation of the above-described equation (3) to generate the PWM output duty values Du, Dv, and Dw.

As described above, the ratio correction unit 13 performs the calculation of Expression (6) and changes the values of the d-axis voltage command value Vd and the q-axis voltage command value Vq to Vd ′ and Vq ′. Although not applied to the motor 3, the phase of the applied voltage is maintained.
The PWM generation unit 9 in the motor control device of the first embodiment described above and the PWM generation unit 90 in the motor control device of the second embodiment only differ in the calculation method in the middle, and if the conditions are the same, The calculated PWM output duty values Du, Dv, and Dw are the same.

  According to the motor control device of the second embodiment of the present invention, voltage can be continuously applied without stopping the voltage application to the brushless motor 3 even when the DC side voltage of the inverter circuit is low. In the second embodiment, the voltage is continuously applied without stopping the voltage application to the brushless motor 3 even when the sensorless driving is performed in a situation where the rotor phase information of the brushless motor 3 cannot be obtained from the position sensor. Can be applied. Therefore, according to the configuration of the motor control device of the second embodiment, since the phase of the brushless motor 3 can be always estimated, a motor control device that is driven without using a position sensor can be provided.

<< Embodiment 3 >>
Next, a motor control apparatus according to Embodiment 3 of the present invention will be described. FIG. 7 is a block diagram showing the configuration of the motor control apparatus according to the third embodiment. In FIG. 7, the rectifier circuit 1, the inverter circuit 2, the brushless motor 3, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. A phase estimation unit 15 is provided in the control unit 4a in the motor control device of the third embodiment. The phase estimation unit 15 includes the d-axis current detection value Id and the q-axis current detection value Iq calculated by the dq conversion unit 6, and the d-axis voltage command value Vd ′ and the q-axis voltage command value output from the PWM generation unit 9a. The estimated phase θ is output from Vq ′. The calculation method of the estimated phase θ is as described above, IEEJ Transaction D, Vol. 117, No. 1, pp. 98-104, 1997, Takeshita, Ichikawa, Lee, Matsui “Based on Speed Electromotive Force Estimation Since it is described in detail in “Sensorless salient pole type brushless DC motor control”, it is omitted here. The calculated estimated phase θ is sent to the dq converter 6 and the PWM generator 9a for use.

  Here, a method of calculating the estimated phase θ described in the above-mentioned document “Sensorless salient pole type brushless DC motor control based on speed electromotive force estimation” will be briefly described with reference to FIG. The phase estimation unit 15 sets an estimated value of the rotor phase of the brushless motor 3 and sets an error from the actual rotor phase of the brushless motor 3. From the voltage equation of a general brushless motor, a voltage equation based on the estimated value of the rotor phase is created using the set error. The estimated rotational speed of the brushless motor is calculated from the equation. Feedback control is performed so that the calculation result becomes equal to the actual rotation speed of the brushless motor. By continuously performing the feedback control, the above error can be converged to 0, and the estimated phase θ matches the actual rotor phase. When creating the above voltage equation, motor constants such as a winding resistance value and an inductance value of the brushless motor 3 are used. In the voltage equation, the voltage value applied to the brushless motor 3 at that time and the current value flowing are also used. Thus, the phase of the brushless motor 3 can be estimated by using the applied voltage, current, and motor constant of the brushless motor 3. For this reason, position sensorless driving is possible. If the estimated phase θ is differentiated, the estimated rotational speed ω of the brushless motor 3 can also be calculated.

In the motor control apparatus of the third embodiment, the d-axis voltage command value Vd ′ and the q-axis voltage command value Vq ′ input to the phase estimation unit 15 are actually applied to the brushless motor 3 by the PWM generation unit 9a. By setting the shaft voltage command value Vd and the q-axis voltage command value Vq equal to each other, phase estimation can be performed correctly even when the DC voltage of the inverter circuit 2 pulsates, and position sensorless driving is possible. Become. For example, when the PWM generation unit 9a of the third embodiment is configured based on the above-described second embodiment, the d-axis voltage command value Vd ′ and the q-axis voltage command value that are the outputs of the ratio correction unit 13 of FIG. Vq ′ may be output to the phase estimation unit 15. Alternatively, when the PWM generation unit 9a is configured based on the above-described first embodiment, a three-phase sine wave is obtained from the PWM output duty values Du, Dv, Dw and the input voltage detection value Vpn from the Vpn correction unit 12 of FIG. The voltages Vu, Vv, and Vw are calculated again, and the d-axis voltage command value and the q-axis voltage command value obtained as a result of performing the dq conversion may be output to the phase estimation unit 15.
The input voltage detection value Vpn when the duty value is determined is different from the input voltage when the inverter circuit 2 is actually in PWM operation because the input voltage is pulsating. Therefore, rather than outputting the voltage command values Vd ′ and Vq ′ at the time of command to the phase estimation unit 15, the d-axis is used by using the value of the input voltage detection value Vpn when the inverter circuit 2 is actually performing PWM operation. The q-axis voltage command value may be calculated again and output to the phase estimation unit 15. Needless to say, the recalculation improves the accuracy of phase estimation.

(A) of FIG. 8 is a graph which shows the experimental result of the phase estimation by the conventional motor control apparatus. FIG. 8B is a graph showing a result of the phase estimation experiment by the motor control apparatus according to the third embodiment of the present invention. 8A and 8B, the upper waveform indicates the input voltage detection value Vpn, and the lower waveform indicates the waveform of the estimated phase. In the experiment of FIG. 8A, a motor control device having a configuration obtained by simply combining the second conventional technology and the third conventional technology was used as a conventional motor control device.
As shown in FIG. 8A, in the conventional motor control apparatus, when the input voltage detection value Vpn of the inverter circuit is small, the estimated phase is distorted, and the estimation result and the actual phase are shifted. As a result, the motor efficiency is reduced and the noise is increased. Further, when the load is large, the phase shift becomes larger, causing a serious problem that the motor steps out and stops. As a device for solving such a problem, the motor control device of the third embodiment can be provided. As shown in FIG. 8B, the motor control device of the third embodiment is linear with the estimated phase being the same as the actual phase. Therefore, the motor control apparatus according to the third embodiment can perform excellent motor control without causing a decrease in motor efficiency or an increase in noise even if the configuration is a position sensor-less configuration.

<< Embodiment 4 >>
Next, a motor control apparatus according to Embodiment 4 of the present invention will be described. FIG. 9 is a block diagram showing the configuration of the motor control apparatus according to the fourth embodiment. In FIG. 9, the rectifier circuit 1, the inverter circuit 2, the brushless motor 3, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. The control unit 4b according to the fourth embodiment includes a d-axis PI controller 7a, a q-axis PI controller 8a, a PWM generation unit 9b, a dq conversion unit 6, a subtracting unit, and the like.
The PWM generator 9b according to the fourth embodiment performs step 34 (formula (4)) as a result of the condition determination at step 32 (FIG. 3) in the calculation process of the Vpn correction unit (FIG. 2) shown in the first embodiment. The signal S is sent to the d-axis PI controller 7a and the q-axis PI controller 8a.

  The d-axis PI controller 7a that has received the signal S from the PWM generator 9b, when the PWM generator 9b executes step 34, that is, in step 34, the d-axis current command value Id * and the d-axis current detection value Id. When the d-axis voltage command value Vd is created from the error, the P (proportional) control is performed and the I (integral) control is not performed. On the other hand, the q-axis PI controller 8a performs the same operation as that of the d-axis PI controller 7a.

FIG. 10 is a graph showing experimental results of motor current according to the fourth embodiment. In FIG. 10, the input voltage detection value Vpn, the motor current, the motor current command value, and the motor applied voltage phase are shown in order from the top.
Comparing the experimental result of FIG. 10 with the experimental result shown in FIG. 4 (b) of the first embodiment, the frequency of the motor current increasing significantly more than the motor current command value is reduced, and the error Can be seen to be smaller. It can be seen that the motor current waveform circled in FIG. 10 is closer to the motor current command value than the motor current waveform circled in FIG. As described above, the motor control device of the fourth embodiment can improve the controllability of the motor current, the occurrence of overcurrent is reduced, and it has been confirmed by experiments that the maximum value of the output torque of the motor is increased. .

<< Embodiment 5 >>
Next, a motor control apparatus according to a fifth embodiment of the present invention will be described. FIG. 11 is a block diagram showing the configuration of the motor control apparatus of the fifth embodiment. In FIG. 11, the rectifier circuit 1, the inverter circuit 2, the brushless motor 3, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. The control unit 4c according to the fifth embodiment includes a dq conversion unit 6, a d-axis PI controller 7, a q-axis PI controller 8, a PWM generation unit 9, a d-axis multiplication unit 18, a q-axis multiplication unit 19, and a q-axis addition. Part 20. The dq conversion unit 6, the d-axis PI controller 7, the q-axis PI controller 8, and the PWM generation unit 9 have the same functions as those in the first embodiment. The d-axis multiplication unit 18 outputs a result obtained by multiplying the q-axis current detection value Iq, the rotational speed ω of the brushless motor 3 and the q-axis inductance Lq of the brushless motor 3, and the addition result with the d-axis PI controller 7 is d The shaft application voltage command value Vd is used. The q-axis multiplier 19 outputs a result obtained by multiplying the d-axis current detection value Id, the rotational speed ω, and the d-axis inductance Ld of the brushless motor 3. The q-axis adding unit 20 outputs a result obtained by multiplying the rotational speed ω by the induced voltage Ke of the brushless motor 3. A result obtained by adding the outputs of the q-axis multiplier 19, the q-axis adder 20, and the q-axis PI controller 8 is defined as a q-axis applied voltage command value Vq. These operations can be expressed by the following equation (7). Expression (7) is a calculation expression for calculating the values of the d-axis applied voltage command value Vd and the q-axis applied voltage command value Vq input to the PWM generator 9. In Equation (7), the determinant with the PI symbol of the second term on the right side added to the left represents the output values of the d-axis PI controller 7 and the q-axis PI controller 8.

In the fifth embodiment, the independence of the d-axis and the q-axis can be increased by adding the first non-interference term on the right side of Equation (7). FIG. 12 is a graph showing experimental results of motor current according to the fifth embodiment.
As shown in FIG. 12, the follow-up performance of the motor current is further improved as compared with the motor control device of the fourth embodiment shown in FIG. It can be seen that the motor current waveform circled in FIG. 12 is closer to the motor current command value than the motor current waveform circled in FIG. In the motor control apparatus according to the fifth embodiment, the occurrence of overcurrent is further reduced as compared with the case where the motor control apparatus according to the fourth embodiment is used, and it is tested that the maximum value of the motor output torque can be further increased. Confirmed by

FIG. 13 is an experimental result showing the relationship between the rotational speed of the motor and the limit torque when the motor control device of the present invention is used in comparison with the case where the conventional motor control device is used. The motor control device of the present invention used in the experiment shown in FIG. 13 is a device having a configuration combining the configurations of the first embodiment, the third embodiment, the fourth embodiment, and the fifth embodiment described above. . In addition, the conventional motor control device used as a comparative example at this time is a motor control device having a configuration in which the above-described second conventional technology and the third conventional technology are simply combined. In this experiment, the same experimental result was obtained even when the configuration of the motor control device of the second embodiment was used instead of the configuration of the motor control device of the first embodiment.
As is apparent from the graph of FIG. 13, when the motor control device of the present invention is used, the limit torque is significantly increased as compared with the case where the conventional motor control device is used. Therefore, by using the motor control device of the present invention, it was possible to sufficiently satisfy the torque required for a compressor used in an air conditioner or a refrigerator. In addition, by using the motor control device of the present invention, the specification is satisfactory as a motor control device for driving a motor used in an electric washing machine, an electric dryer, a vacuum cleaner, a blower or the like.

<< Embodiment 6 >>
Next, a motor control apparatus according to a sixth embodiment of the present invention will be described. The motor control apparatus according to the sixth embodiment is configured to estimate an input voltage detection value Vpn input to the inverter circuit from past data.
In the motor control apparatus according to the sixth embodiment, the input voltage detection value Vpn is detected at every control cycle because the fluctuation is large. If the input voltage detection value detected in the previous control cycle is Vpn [n-1] and the input voltage detection value detected in the previous control cycle is Vpn [n-2], it is used for the current control cycle. Rather than using Vpn [n-1] as the input voltage detection value, the amount of change between Vpn [n-1] and Vpn [n-2] is calculated, and the input voltage detection value Vpn [ n]. The calculation formula is shown as the following formula (8).

Equation (8) holds when it is assumed that the amount of change between the previous input voltage detection value Vpn [n-1] and the previous previous input voltage detection value Vpn [n-2] is equal to the current and previous change amount. It is. In the motor control device of the present invention, it is possible to output a highly accurate duty value by using the input voltage detection value Vpn [n] estimated using Expression (8).
The configuration of estimating the input voltage detection value Vpn [n] in the sixth embodiment can be incorporated in the configurations of the first to fifth embodiments described above, and outputs a duty value with higher accuracy. Highly efficient motor control can be performed.

<< Embodiment 7 >>
Next, a motor control device according to a seventh embodiment of the present invention will be described.
When the motor is stopped or when the switching operation of the inverter circuit is stopped, the current flowing in the motor is regenerated to the input side of the inverter circuit. When the regenerative current is large, the voltage on the input side of the inverter circuit increases, which may cause overvoltage and damage the motor control device. The motor control apparatus of the seventh embodiment has a mechanism that prevents such damage due to regenerative current.

FIG. 14 is a circuit diagram showing rectifier circuit 1, inverter circuit 2, brushless motor 3, single-phase AC power supply 5 and the like other than the control unit in the motor control device according to the seventh embodiment of the present invention, and the control unit is omitted. is doing. As shown in FIG. 14, a capacitor 16 having a small capacitance is provided between the rectifier circuit 1 and the inverter circuit 2. By providing the capacitor 16 between the rectifier circuit 1 and the inverter circuit 2 in this way, it is possible to prevent the motor control device from being damaged by the regenerative current, and a safer motor control device can be realized.
The capacitance of the capacitor 16 is set to a value at which the motor control device is not damaged by the regenerative current. For example, in the case of a motor control device used for a home air conditioner or a compressor of a heat pump water heater, it may be about 0.1 μF to 50 μF. In the case of a refrigerator, an electric washing machine, an electric dryer, or an electric vacuum cleaner, the magnitude of the regenerative current is smaller than that of an air conditioner, so that it may be about 0.1 μF to 20 μF.
In the seventh embodiment, the capacitor 16 is described as being provided between the rectifier circuit 1 and the inverter circuit 2. However, the capacitor 16 may be connected to the input side of the inverter circuit 2.
Here, the regenerative current means that the energy stored in the capacitor 16 is determined by the inductance L [H] of the winding of the brushless motor 3 and the current flowing in the winding immediately before the brushless motor 3 stops. The electric current which flows into the capacitor | condenser 16 from the brushless motor 3 when regenerating is shown. The maximum output P [W] of the brushless motor 3 depends on the allowable current value of the brushless motor 3, the inductance L of the brushless motor 3, and the like. In the seventh embodiment, the maximum output P [W] of the brushless motor 3 comprehensively includes the relationship between the above-described electrostatic capacitance C [F] and the output of the brushless motor 3 to be used, a value that does not damage the motor control device, and the like. Is taken into account, the relationship shown by the following equation (9) is satisfied.

  The configuration for preventing the motor control device from being damaged by the regenerative current in the seventh embodiment can be incorporated in the configurations of the first to sixth embodiments described above, and provides a more reliable motor control device. It becomes possible.

<< Embodiment 8 >>
Next, a motor control device according to an eighth embodiment of the present invention will be described. FIG. 15 is a circuit diagram showing the rectifier circuit 1, the inverter circuit 2, the brushless motor 3, the single-phase AC power source 5 and the like other than the control unit in the motor control apparatus according to the eighth embodiment of the present invention, and the control unit is omitted. is doing.

The input current of the rectifier circuit 1 is affected by the switching operation in the inverter circuit 2. In particular, when the carrier frequency of the switching operation is low, the waveform is distorted. In the motor control apparatus of the eighth embodiment, an inductor 17 having an inductance L is provided between the single-phase AC power supply 5 and the rectifier circuit 1 as shown in FIG. In the motor control apparatus according to the eighth embodiment, by providing the inductor 17 between the single-phase AC power supply 5 and the rectifier circuit 1, the power factor of the input current can be increased and the current waveform can be improved. The inductance L of the inductor 17 is set to a value that reduces current distortion. For example, in the case of a motor control device used for a home air conditioner or a compressor of a heat pump water heater, the inductance L may be about 0.1 mH to 2.0 mH. In the case of a refrigerator, an electric washing machine, an electric dryer, or an electric vacuum cleaner, the inductance L may be about 0.1 mH to 1.0 mH because the current is smaller than that of the air conditioner.
In the eighth embodiment, the configuration in which the inductor 17 is provided between the single-phase AC power supply 5 and the rectifier circuit 1 has been described. However, the inductor 17 may be connected to the input side of the inverter circuit 2.
The inductance L of the inductor 17 is related to the magnitude of the current and the switching frequency of the inverter circuit 2. In the case of household appliances such as the air conditioner, refrigerator, and electric washing machine described above, the switching frequency is not so different and is substantially several kHz to several tens of kHz. Therefore, it is considered that the appropriate inductance L in the eighth embodiment is substantially determined by the magnitude of the current. Since the voltage of the single-phase AC power supply 5 is a common voltage in the world from 200V to 230V, there is a correlation between the maximum output P [W] of the brushless motor 3 and the appropriate inductance L, and substantially the following equation: It has the relationship shown by (10).

  In the case of a motor control device provided with both the inductor 17 and the capacitor 16, a resonance phenomenon occurs. In order to prevent the resonance phenomenon from adversely affecting the AC power supply system, the relationship represented by the following equation (11) is established between the inductance L of the inductor 17 and the capacitance C of the capacitor 16.

  Note that a motor control device provided with an inductor may be further provided with a capacitor having a capacitance C for the purpose of preventing the motor control device from being damaged by a regenerative current as described in the seventh embodiment. Good. However, in this case, an inductor and a capacitor are connected in series, and a resonance phenomenon may occur. The resonance frequency is 1 / 2π√ (LC) as generally known, and is determined by the values of the inductor and the capacitor. Therefore, as an example, if the values of the inductor and the capacitor are designed so that the resonance frequency is higher than the frequency of the power supply harmonic regulation, a motor control device with less generated noise can be provided.

Embodiment 9
Next, a motor control device according to a ninth embodiment of the present invention will be described. FIG. 16A is a block diagram showing the configuration of the motor control apparatus according to the ninth embodiment of the present invention. In FIG. 16A, the inverter circuit 2, the brushless motor 3, the control unit 4, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. In the motor control device of the ninth embodiment, a booster circuit 21 is provided on the input side of the inverter circuit 2, and an inverter voltage is boosted (eg, AC100V) from the single-phase AC power supply 5 (eg, AC200V). 2 is configured to input.

  The booster circuit 21 includes an inductor 200 to which the input voltage V of the single-phase AC power supply 5 is applied, two switching elements 201 and 202 connected in series, two diodes 203 and 204 connected in series, and a capacitor 205. ing. One end of the single-phase AC power supply 5 is connected to the connection point of the two switching elements 201 and 202 via the inductor 200, and the other end of the single-phase AC power supply 5 is connected to the connection point of the two diodes 203 and 204. Yes. The series connection body of the switching elements 201 and 202, the series connection body of the two diodes 203 and 204, and the capacitor 205 are connected in parallel. Outputs from both ends of the capacitor 205 are input to the inverter circuit 2.

  Further, the motor control device of the ninth embodiment is provided with a booster circuit control unit 22 for controlling the on / off operation of the switching elements 201 and 202 in the booster circuit 21. In the following description, the switching element 201 on the upper side of the motor control device shown in FIG. 16A is referred to as an upper arm switching element 201, and the switching element 202 on the lower side is referred to as a lower arm switching element 202.

Next, an example of the operation of the booster circuit control unit 22 in the motor control device of the ninth embodiment will be described.
The booster circuit control unit 22 outputs a PWM command for controlling the upper arm switching element 201 and the lower arm switching element 202 provided in the booster circuit 21. The PWM command for one switching element alternately includes an on / off period in which the on / off operation is repeated in a predetermined time and an off period in which the off state is continued. Further, in an on / off period in which one switching element repeats an on / off operation in a predetermined time, the other switching element is an off period in which the off state is continued.

  In FIG. 17, the signal (a) is the control signal V1 for the upper arm switching element 201 output from the booster circuit control unit 22, and the signal (b) is for the lower arm switching element 202 output from the booster circuit control unit 22. The control signal V2 and the signal (c) is the output voltage V of the single-phase AC power supply 5. Each of the signals shown in FIG. 17 shows an example. As shown in FIG. 17, for example, it is assumed that the upper arm switching element 201 performs the on / off operation in the period A and the lower arm switching element 202 continues to be in the off state, and the lower arm switching element 202 is turned on / off in the period B. It is assumed that the upper arm switching element 201 continues to be turned off by operating.

  The state shown in the period A is a period in which the voltage on the side where the inductor 200 is not connected in the output voltage V of the single-phase AC power supply 5 is high. The state shown in period B is a period in which the voltage on the side to which inductor 200 is connected in the output voltage of single-phase AC power supply 5 is high. That is, the period A and the period B are alternately generated in synchronization with the power supply frequency of the single-phase AC power supply 5. The booster circuit control unit 22 outputs a PWM command to the booster circuit 21 so that the upper arm switching element 201 and the lower arm switching element 202 provided in the booster circuit 21 are turned on and off as described above.

Next, a method for determining the PWM output duty value of the PWM command in the ninth embodiment will be described.
The control unit 4 determines whether or not step 34 of FIG. 3 shown in the above-described third embodiment has been executed at every timing when the input voltage of the inverter circuit 2 becomes maximum. That is, the control unit 4 determines whether the U, V, and W phase PWM output duty values are determined by the equation (4) when the input voltage detection value Vpn is smaller than the applied voltage maximum value Vmax.

  When it is determined that step 34 has been executed, the control unit 4 outputs a control signal indicating that step 34 has been executed to the booster circuit control unit 22. The booster circuit controller 22 increases the PWM output duty value of the PWM command output to the booster circuit 21 when the control signal from the controller 4 is input. On the other hand, when the control signal is not input, the booster circuit control unit 22 decreases the PWM output duty value of the PWM command. Therefore, the PWM output duty value of the PWM command of the booster circuit control unit 22 is changed at every timing when the input voltage of the inverter circuit 2 becomes maximum. This timing is a timing at which the output voltage of the single-phase AC power supply 5 becomes maximum.

Next, a method for determining the operation state between period A and period B shown in FIG. 17 will be described.
When the brushless motor 3 is started, the capacitor 205 provided in the booster circuit 21 has a small capacity, so that the input voltage of the inverter circuit 2 is similar to the waveform when the capacitor 205 is not provided (for example, FIG. 4). (A) and the input voltage detection signal indicated by Vpn in FIG. 4 (b)). At this time, the lower arm switching element 202 is turned on and off at a predetermined PWM output duty value of a predetermined PWM command regardless of the control signal from the control unit 4. In this case, when the output voltage of the single-phase AC power supply 5 is higher on the side where the inductor 200 is connected, the voltage of the capacitor 205 is boosted than when the on / off operation is not performed. Therefore, the state at this time can be determined that the voltage phase of the single-phase AC power supply 5 is the period B. Conversely, when the output voltage of the single-phase AC power supply 5 is higher on the side where the inductor 200 is not connected, the voltage of the capacitor 205 is not boosted. Therefore, the state at this time can be determined that the voltage phase of the single-phase AC power supply 5 is the period A.

Since the voltage phase of the single-phase AC power supply 5 can be detected by detecting whether or not the voltage of the capacitor 205 has been boosted as described above, the motor control device of the ninth embodiment uses a voltage phase detection circuit. The period A or the period B can be determined without any problem.
FIG. 18 shows the waveform of the output voltage V of the single-phase AC power supply 5 and the pulse signal waveform changed based on the calculated PWM output duty value in the motor control apparatus of the ninth embodiment.

In the above-described ninth embodiment, the lower arm switching element 202 has been described as being configured to be turned on and off at a predetermined PWM output duty value of a predetermined PWM command. The upper arm switching element 201 may be used. In that case, it goes without saying that the period A is when the capacitor 205 is boosted and the period B is when the capacitor 205 is not boosted.
FIG. 16B is a circuit diagram showing a configuration of another booster circuit 21a in the motor control apparatus of the ninth embodiment. As shown in FIG. 16B, the booster circuit 21a according to the ninth embodiment can also be configured by one switching element, a plurality of diodes, and one capacitor. In such a configuration, it is not necessary to distinguish between the upper arm switching element and the lower arm switching element, and one switching element may be switched based on the PWM command.

  As described above, the motor control device described in the ninth embodiment has a configuration capable of boosting the input voltage of the inverter circuit 2 when the output voltage of the single-phase AC power supply 5 is low so that the voltage applied to the brushless motor 3 is insufficient. is there. For this reason, the motor control device of the ninth embodiment can increase the maximum number of revolutions of the brushless motor 3 and greatly expand the operating range. In particular, in the case of an air conditioner, the maximum number of revolutions can be increased, so that the variable range of the cooling / heating capacity is expanded, and the comfort is further improved. Moreover, in the apparatus using the motor control apparatus of Embodiment 9, the maximum capacity in heating operation is improved, and an air conditioner with a larger heating effect can be provided.

<< Embodiment 10 >>
Next, a motor control device according to a tenth embodiment of the present invention will be described. FIG. 19 is a block diagram showing the configuration of the motor control apparatus according to the tenth embodiment of the present invention. In the motor control device of the tenth embodiment shown in FIG. 19, the inverter circuit 2, the brushless motor 3, the control unit 4, and the single-phase AC power supply 5 have the same functions and configurations as those of the ninth embodiment.

In the motor control device of the tenth embodiment, the booster circuit control unit 22a includes an alternating current command creation unit 23 and a PWM command creation unit 24.
The alternating current command creating unit 23 of the booster circuit control unit 22a detects the voltage phase of the single-phase alternating current power supply 5, creates an alternating current command value having the same phase as the detected voltage phase, and generates a PWM command creating unit. To 24. The amplitude value of the alternating current command value is created based on a control signal from the control unit 4.
The control signal input from the control unit 4 to the alternating current command creation unit 23 is the same as the control signal described in the ninth embodiment. The alternating current command creation unit 23 increases the amplitude value of the alternating current command value when the control signal from the control unit 4 is input. On the other hand, when the control signal from the control unit 4 is not input, the amplitude value of the alternating current command value is decreased.

The PWM command creation unit 24 receives the AC current command value from the AC current command creation unit 23 and the detected value of the AC current from the single-phase AC power supply 5. The PWM command creating unit 24 amplifies the error so that the output current of the booster circuit 21 becomes an AC current command value, creates a PWM signal for driving the switching element of the booster circuit 21, and uses the PWM signal as the booster circuit 21. Output to. In the PWM command creating unit 24 in the tenth embodiment, PI control is used as feedback control used for error amplification. FIG. 20 is a block diagram showing a specific configuration of the booster circuit control unit 22a. However, the present invention is not limited to such a PI control configuration, and other commonly used feedback control can be used.
FIG. 21 shows the waveform of the output voltage V of the single-phase AC power supply 5, the calculated PWM output duty value, and the pulse signal waveform changed based on the PWM output duty value in the motor control device of the tenth embodiment. Show.

  It can be determined whether the upper or lower switching element in the booster circuit 21 is driven or controlled based on whether the alternating current command value is positive or negative. For example, if the alternating current command value is positive, the lower arm switching element is PWM-operated and the PWM command is output so that the upper arm switching element is turned off. On the other hand, if the AC current command value is negative, the upper arm switching element is subjected to PWM operation, and the PWM command is output so that the lower arm switching element is turned off. Alternatively, since the voltage phase is detected in the booster circuit control unit 22a, the detected voltage phase is input to the PWM command creating unit 24, and either one of the upper and lower switching elements based on the detected voltage phase. May be determined to be PWM driven. FIG. 22 is a block diagram showing a specific configuration of the booster circuit control unit 22b configured as described above.

Needless to say, the booster circuit 21 may be a booster circuit 21a configured by one switching element as shown in FIG. 16B in the ninth embodiment.
By operating the booster circuit 21 and the booster circuit control units 22a and 22b as described above, the current waveform flowing through the single-phase AC power supply 5 becomes almost sinusoidal, so that the power source power factor becomes almost 1, which adversely affects the power supply system. It is possible to provide a motor control device that does not affect the above.

<< Embodiment 11 >>
Next, a motor control apparatus according to an eleventh embodiment of the present invention will be described. FIG. 23A is a block diagram showing the configuration of the motor control apparatus according to the eleventh embodiment of the present invention. In the motor control device of the eleventh embodiment shown in FIG. 23 (a), the inverter circuit 2, the brushless motor 3, the control unit 4, and the single-phase AC power source 5 are the same as those in the ninth and tenth embodiments described above. It has the same function and configuration.

  In the motor control apparatus according to the eleventh embodiment, the difference from the tenth embodiment described above is that a voltage doubler rectification booster circuit 25 is provided instead of the booster circuit 21. The voltage doubler rectification booster circuit 25 includes an inductor 300, a switching element 301, diodes 302, 303, 304, and 305, a capacitor 306 having a large capacitance, and a capacitor 307 having a small capacitance. The step-up circuit control unit 22c includes an alternating current command creation unit 23 and a PWM command creation unit 24b. The operation of the AC current command creating unit 23 is substantially the same as that described in the ninth and tenth embodiments.

Hereinafter, the operation of the PWM command generating unit 24b and the operation of the voltage doubler rectification booster circuit 25 will be described with reference to FIG.
In the output voltage of the single-phase AC power supply 5, the current is supplied to the capacitor 306 during a period (hereinafter referred to as period C) where the side where the inductor 300 is connected is higher than the side where the inductor 300 is not connected. Inflow. On the other hand, in the output voltage of the single-phase AC power supply 5, current flows into the capacitor 307 during a period when the side where the inductor 300 is not connected is higher (hereinafter referred to as period D).
Therefore, in period C, a current similar to the current input to the conventional voltage doubler rectifier circuit flows from the single-phase AC power supply 5, so that the power supply power factor is reduced when the inductor 300 is downsized in this state. Therefore, in the eleventh embodiment, the PWM command generation unit 24b is configured to output a PWM signal for PWM driving the switching element of the voltage doubler rectification booster circuit 25 during the period C, so that the power source power factor does not decrease.

Note that in the period D, the power supply power factor does not decrease because the circuit has the same structure as that described in the seventh embodiment.
The difference between the PWM command creating unit 24b in the eleventh embodiment and the PWM command creating unit 24 in the tenth embodiment described above is that the PWM signal is not output to the voltage doubler rectifying booster circuit 25 during the period D.

In the conventional voltage doubler rectifier circuit, a capacitor having a large capacitance such as an aluminum electrolytic capacitor has been used in which the capacitances of the two capacitors are substantially the same value. In the motor control apparatus according to the eleventh embodiment of the present invention, one of the two capacitors has a small capacitance. As described above, in the motor control device according to the eleventh embodiment, the capacitance of one capacitor can be reduced, so that the size can be reduced as compared with the conventional voltage doubler rectifier circuit.
FIG. 23B is a circuit diagram showing a voltage doubler rectification booster circuit 25a having another configuration in the motor control device according to the present invention. Even if the voltage doubler rectifier booster circuit 25a shown in FIG. 23B is used instead of the voltage doubler rectifier booster circuit 25 shown in FIG.

<< Embodiment 12 >>
Next, a compressor using the motor control device shown in the first to eleventh embodiments will be described with reference to FIG. FIG. 25 is a block diagram showing the configuration of the compressor according to the twelfth embodiment of the present invention.
In FIG. 25, the compressor 41 connected to the single-phase AC power supply 5 has a motor control device 40 and a compression mechanism 42 driven by the brushless motor 3. In the twelfth embodiment, the brushless motor 3 and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40. The output of the motor control device 40 is connected to the brushless motor 3 disposed inside the compression mechanism 42, and the brushless motor 3 is driven to rotate by the motor control device 40. By the rotation operation of the brushless motor 3, the compression mechanism 42 compresses the sucked refrigerant gas and discharges the high-pressure gas.
As described above, the motor control device 40 of the present invention shown in the first to eleventh embodiments is smaller and lighter than the conventional motor control device. 12, it is possible to provide a small compressor 41 in which the compression mechanism 42 and the motor control device 40 are integrated.

<< Embodiment 13 >>
FIG. 26 is a block diagram showing a configuration of an air conditioner according to a thirteenth embodiment of the present invention.
The air conditioner 43 according to the thirteenth embodiment includes an indoor unit 44 and an outdoor unit 45, and performs indoor air conditioning. In the air conditioner 43, the compression mechanism 42 circulates the refrigerant between the indoor unit 44 and the outdoor unit 45. The motor control device 40 to which the single-phase AC power supply 5 is connected drives and controls a brushless motor disposed inside the compression mechanism 42. In the thirteenth embodiment, the brushless motor and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.
In the air conditioner 43 according to the thirteenth embodiment, the indoor unit 44 has an indoor heat exchanger 48, and the outdoor unit 45 has a four-way valve 46 that forms a refrigerant circulation path, an expansion device 47, and outdoor heat exchange. A container 49 is provided.

The indoor heat exchanger 48 includes a blower 48a for increasing the heat exchanging capacity and a temperature sensor 48b for measuring the temperature of the indoor heat exchanger 48 or its surrounding temperature. The outdoor heat exchanger 49 includes a blower 49a for increasing the heat exchange capability, and a temperature sensor 49b for measuring the temperature of the outdoor heat exchanger 49 or its surrounding temperature.
In the air conditioner 43 of the thirteenth embodiment, the compression mechanism 42 and the four-way valve 46 are disposed in the refrigerant circulation path that connects between the indoor side heat exchanger 48 and the outdoor side heat exchanger 49. In the air conditioner 43 of the thirteenth embodiment, the direction of the refrigerant flowing in the refrigerant circulation path is switched by the switching operation of the four-way valve 46. For example, in the refrigerant circulation path of the air conditioner 43, the refrigerant flows in the direction of arrow A, and the refrigerant that has passed through the outdoor heat exchanger 49 is sucked into the compression mechanism 42 via the four-way valve 46, and the compression mechanism 42 The discharged refrigerant is supplied to the indoor heat exchanger 48. On the other hand, due to the switching operation of the four-way valve 46, the refrigerant flows in the direction of arrow B, and the refrigerant that has passed through the indoor heat exchanger 48 is sucked into the compression mechanism 42 via the four-way valve 46 and discharged from the compression mechanism 42. The refrigerant is supplied to the outdoor heat exchanger 49. Thus, the direction in which the refrigerant flows is switched by the switching operation of the four-way valve 46.

A throttling device 47 provided in the refrigerant circulation path connecting the indoor heat exchanger 48 and the outdoor heat exchanger 49 has a throttling action for restricting the flow rate of the circulating refrigerant and a valve action for automatically adjusting the flow rate of the refrigerant. It also has. The expansion device 47 is necessary for the evaporator while the liquid refrigerant is expanded immediately after the flow rate of the liquid refrigerant sent from the condenser to the evaporator while the refrigerant is circulating in the refrigerant circulation path. The amount of refrigerant is supplied without excess or deficiency.
In the air conditioner 43, the indoor heat exchanger 48 operates as a condenser in the heating operation and as an evaporator in the cooling operation. The outdoor heat exchanger 49 operates as an evaporator in the heating operation and as a condenser in the cooling operation. In the condenser, the high-temperature and high-pressure refrigerant gas flowing inside is gradually liquefied by taking heat away from the air that is sent in, and in the vicinity of the outlet of the condenser, a high-pressure liquid or a mixed state of liquid and gas is formed. This is equivalent to the refrigerant dissipating heat into the atmosphere and liquefying. In addition, the liquid which has been cooled to low temperature and low pressure by the expansion device 47 or a mixed refrigerant of the liquid and gas flows into the evaporator. In this state, when room air is sent to the evaporator, the refrigerant takes a large amount of heat from the air and evaporates, and becomes a refrigerant with an increased amount of gas. Air deprived of a large amount of heat by the evaporator is discharged as cold air from the outlet of the air conditioner 43.
In the air conditioner 43, the command rotational speed of the brushless motor is set based on the operating state, that is, the target temperature set for the air conditioner 43, the actual room temperature, and the outside air temperature. The motor control device 40 controls the rotation speed of the brushless motor of the compression mechanism 42 based on the set command rotation speed, similarly to the motor control apparatus of the first embodiment described above.

A method for controlling the rotation speed of the brushless motor so as to become the set command rotation speed will be described.
The command rotational speed is ω *, and the actual rotational speed of the brushless motor is ω, where ω is obtained by differentiating the position sensor signal in the case of a brushless motor having a position sensor. In the case of a brushless motor having no position sensor, as shown in the third embodiment, the estimated rotational speed obtained by differentiating the estimated phase θ may be regarded as the actual rotational speed ω. An error between the command rotational speed ω * and the actual rotational speed ω is calculated, and a value obtained by performing PI control on the error is output as a total current command value I *. The d-axis current command value Id * and the q-axis current command Iq * are calculated according to the following equations (12) and (13) using the current phase command value β * held in the control unit 4. .

  The current phase command value β * is a value that determines the operating state of the brushless motor 3. This value may be a predetermined value or may be changed according to the operating state of the brushless motor. By adding the above-described function to the control unit 4, when the actual rotational speed is smaller than the command rotational speed, the d-axis current command value and the q-axis current command value are increased by the PI control. Output torque increases and accelerates. Since the control unit 4 operates in this way, the motor control device operates so as to achieve the set command rotational speed, and the brushless motor operates at the command rotational speed.

Next, the operation | movement in the air conditioner 43 of Embodiment 13 is demonstrated.
In the air conditioner 43 of the thirteenth embodiment, when a drive voltage is applied from the motor control device 40 to the compression mechanism 42, the refrigerant circulates in the refrigerant circulation path. At this time, heat exchange is performed in the heat exchanger 48 of the indoor unit 44 and the heat exchanger 49 of the outdoor unit 45. That is, in the air conditioner 43, the refrigerant sealed in the refrigerant circulation circuit is circulated by the compression mechanism 42, whereby a known heat pump cycle is formed in the refrigerant circulation circuit. Thereby, indoor heating or cooling is performed.
For example, when performing the heating operation of the air conditioner 43, the four-way valve 46 is set so that the refrigerant flows in the direction indicated by the arrow A by the user's operation. In this case, the indoor heat exchanger 48 operates as a condenser and releases heat by the circulation of the refrigerant in the refrigerant circulation path. This warms the room.
Conversely, when the air conditioner 43 is cooled, the four-way valve 46 is set so that the refrigerant flows in the direction indicated by the arrow B by the user's operation. In this case, the indoor heat exchanger 48 operates as an evaporator and absorbs the heat of the surrounding air by the circulation of the refrigerant in the refrigerant circulation path. This cools the room.

In the air conditioner 43 according to the thirteenth embodiment, the command rotational speed is determined based on the target temperature, the actual room temperature, and the outside air temperature set in the air conditioner 43, and is determined in the same manner as in the first embodiment. Based on the commanded rotational speed, the motor control device 40 controls the rotational speed of the brushless motor of the compression mechanism 42. As a result, the air conditioner 43 according to the thirteenth embodiment can perform comfortable air conditioning.
In the air conditioner 43 according to the thirteenth embodiment, since the motor control device 40 is smaller and lighter than the conventional motor control device, the degree of freedom of arrangement of the motor control device 40 in the outdoor unit 45 increases, and the manufacturer It becomes easy to design. Further, by downsizing the motor control device, it is possible to provide a small and lightweight outdoor unit 45, so that it has excellent effects such as easy installation by consumers.
In the air conditioner 43 according to the thirteenth embodiment, when brushless motors are used to drive the blower 48a of the indoor heat exchanger 48 and the blower 49a of the outdoor heat exchanger 49, the drive control of these brushless motors is performed. The motor control device used for this purpose may be configured by any of the motor control devices described in the first to eleventh embodiments.

  In the thirteenth embodiment, an air conditioner capable of both cooling and heating operations has been described. However, in the case of an air conditioner dedicated to cooling, the four-way valve 46 is omitted and the refrigerant flows in the direction of arrow B. What is necessary is just the air conditioner which was made to do.

<< Embodiment 14 >>
FIG. 27 is a block diagram showing the configuration of the refrigerator according to Embodiment 14 of the present invention.
The refrigerator 51 of the fourteenth embodiment includes a motor control device 40, a compression mechanism 42, a condenser 52, a refrigerator compartment evaporator 53, and a throttle device 54.
In the refrigerator 51 of the fourteenth embodiment, the compression mechanism 42, the condenser 52, the expansion device 54, and the refrigerator compartment evaporator 53 are disposed in the refrigerant circulation path. The motor control device 40 is connected to the single-phase AC power supply 5 as an input power supply, and drives and controls a brushless motor that is a drive source of the compression mechanism 42.
In the fourteenth embodiment, the brushless motor disposed inside the compression mechanism 42 and the single-phase AC power supply 5 that is the input source of the motor control device 40 have the same functions and configurations as in the first embodiment. . Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.

The throttle device 54 in the refrigerator 51 of the fourteenth embodiment is sent out from the condenser 52 in a state where the refrigerant is circulating in the refrigerant circulation path, like the throttle device 47 of the air conditioner 43 of the thirteenth embodiment. The refrigerant is expanded by reducing the flow rate of the refrigerant, and the required amount of refrigerant is supplied to the refrigerator compartment evaporator 53 without excess or deficiency.
The condenser 52 condenses the high-temperature and high-pressure refrigerant gas flowing inside, and releases the heat of the refrigerant to the outside air. The refrigerant gas sent to the condenser 52 is gradually liquefied by taking heat away from the outside air, and in the vicinity of the outlet of the condenser 52, a high-pressure liquid or a mixed state of liquid and gas is formed.
The refrigerator compartment evaporator 53 cools the refrigerator by evaporating a low-temperature refrigerant. The refrigerator compartment evaporator 53 has a blower 53a for increasing the efficiency of heat exchange, and a temperature sensor 53b for detecting the temperature inside the refrigerator.

Next, the operation | movement in the refrigerator 51 of Embodiment 14 is demonstrated.
In the refrigerator 51 of the fourteenth embodiment, when a drive voltage is applied from the motor control device 40 to the brushless motor of the compression mechanism 42, the compression mechanism 42 is driven and the refrigerant circulates in the refrigerant circulation path in the direction of arrow C. At this time, heat exchange is performed by the condenser 52 and the refrigerator compartment evaporator 53, and the inside of a refrigerator is cooled.
In other words, the refrigerant condensed in the condenser 52 expands when the flow rate is reduced by the expansion device 54 and becomes a low-temperature refrigerant. And if a low temperature refrigerant | coolant is sent into the refrigerator compartment evaporator 53, in a refrigerator compartment evaporator 53, a low temperature refrigerant | coolant will evaporate and the inside of a refrigerator will be cooled. At this time, the air in the refrigerator compartment is forcibly sent into the refrigerator compartment evaporator 53 by the blower 53a, and the refrigerator compartment evaporator 53 performs heat exchange efficiently.
Further, in the refrigerator 51 of the fourteenth embodiment, the command rotational speed is set according to the target temperature set in the refrigerator 51 and the room temperature in the refrigerator, and the motor control device 40 is similar to the thirteenth embodiment. Based on the set command rotational speed, the rotational speed of the brushless motor of the compression mechanism 42 is controlled. As a result, in the refrigerator 51, the temperature in the refrigerator is maintained at the target temperature.

As described above, in the refrigerator 51 of the fourteenth embodiment, since the motor control device 40 is configured to be small and light, the degree of freedom of arrangement of the motor control device in the refrigerator is increased as compared with the conventional motor control device. Moreover, it has the effect that the internal volume of the refrigerator 51 can be increased by increasing the degree of freedom of arrangement of the motor control device. Moreover, since a lightweight motor control apparatus can be provided, the weight of the refrigerator 51 can be reduced.
In the refrigerator 51 according to the fourteenth embodiment of the present invention, when the brushless motor 3 is used to drive the blower 53a, the motor control device 40 used for driving control of the brushless motor 3 is used in the first embodiment. To any of the motor control devices described in the eleventh embodiment.

<< Embodiment 15 >>
FIG. 28 is a block diagram showing the configuration of the electric washing machine according to the fifteenth embodiment of the present invention.
The electric washing machine 55 according to the fifteenth embodiment has a washing machine outer frame 56, and an outer tub 57 is suspended by a hanging rod 58 in the washing machine outer frame 56. In the outer tub 57, a washing and dewatering tub 59 is rotatably arranged. A stirring blade 60 is rotatably attached to the bottom of the washing and dewatering tank 59.
In the space below the outer tub 57 in the washing machine outer frame 56, the brushless motor 3 for rotating the washing / dehydrating tub 59 and the stirring blade 60 is disposed. The washing machine outer frame 56 is attached with a motor control device 40 that drives and controls the brushless motor 3 with the single-phase AC power supply 5 as an input.
In the fifteenth embodiment, the brushless motor disposed inside the washing machine outer frame 56 and the single-phase AC power source 5 that is the input source of the motor control device 40 have the same functions and configurations as those of the first embodiment. Have Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.
In the electric washing machine 55 according to the fifteenth embodiment, the motor control device 40 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (not shown) that controls the operation of the electric washing machine 55. Entered.

Next, the operation in the electric washing machine 55 of the fifteenth embodiment will be described.
In the electric washing machine 55 according to the fifteenth embodiment, when a user performs a predetermined operation, a command signal is input from the microcomputer to the motor control device 40 and a drive voltage is applied to the brushless motor 3. As a result, the brushless motor 3 is driven to rotate the stirring blade 60 or the washing / dehydrating tub 59, and washing and dehydration of clothes and the like in the washing / dehydrating tub 59 are performed. At this time, in the electric washing machine 55 according to the fifteenth embodiment, based on the command rotational speed indicated by the command signal from the microcomputer, the motor controller 40 controls the rotational speed of the brushless motor 3 as in the above-described thirteenth embodiment. Be controlled. As a result, in the electric washing machine 55, an appropriate operation according to the amount of laundry and dirt is executed.

As described above, the electric washing machine 55 according to the fifteenth embodiment uses the miniaturized motor control device 40, so that the capacity of the washing and dewatering tub can be increased with the same external dimensions as the conventional electric washing machine. Has an effect. Moreover, in the electric washing machine 55 which concerns on this invention, since the motor control apparatus 40 reduced in weight is used, it has the outstanding effect that the weight reduction as the whole washing machine can be achieved.
In the electric washing machine 55 according to the fifteenth embodiment of the present invention, the motor control device 40 used for driving control of the brushless motor 3 is any motor described in the first to eleventh embodiments. You may comprise with a control apparatus.

<< Embodiment 16 >>
FIG. 29 is a block diagram showing the configuration of the electric dryer according to the sixteenth embodiment of the present invention.
The electric dryer 61 of the sixteenth embodiment has a dryer outer frame 62, and a drum 63 provided rotatably is installed in the dryer outer frame 62. A brushless motor 3 is connected to the drum 63, and the drum 63 is configured to rotate by the brushless motor 3.
In the sixteenth embodiment, the brushless motor 3 and the motor control device 40 and the single-phase AC power supply 5 that are arranged inside the dryer outer frame 62 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.
In the electric dryer 61 of the sixteenth embodiment, the motor control device 40 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (not shown) that controls the operation of the electric dryer 61. Entered.

Next, the operation in the electric dryer 61 of the sixteenth embodiment will be described.
In the electric dryer 61 of the sixteenth embodiment, when a user performs a predetermined operation, a command signal is input from the microcomputer to the motor control device 40. Thereby, a drive voltage is applied to the brushless motor 3. As a result, the brushless motor 3 is driven, the drum 63 rotates, and clothes and the like in the drum 63 are dried.
At this time, in the electric dryer 61 of the sixteenth embodiment, based on the command rotational speed indicated by the command signal from the microcomputer, the motor controller 40 controls the rotational speed of the brushless motor 3 based on the command rotational speed described above. Be controlled. As a result, in the electric dryer 61 of the sixteenth embodiment, an appropriate operation according to the amount of dry matter and dirt is executed.

As described above, the electric dryer 61 according to the sixteenth embodiment uses the miniaturized motor control device 40, and therefore has the effect of achieving a large drum capacity with the same external dimensions as the conventional electric dryer. . Moreover, in the electric dryer which concerns on this invention, since the motor control apparatus 40 reduced in weight is used, it has the effect that the weight reduction as the whole dryer can be achieved.
In the electric dryer 61 according to the sixteenth embodiment of the present invention, the motor control device 40 used for the drive control of the brushless motor 3 is any motor described in the first to eleventh embodiments. You may comprise with a control apparatus.

<< Embodiment 17 >>
FIG. 30 is a block diagram showing the configuration of the blower according to the seventeenth embodiment of the present invention.
The blower 64 according to the seventeenth embodiment includes a fan 65, a brushless motor 3 that rotationally drives the fan 65, and a motor control device 40 that drives and controls the brushless motor 3. The motor control device 40 is connected to the single-phase AC power source 5 and configured to apply a single-phase AC voltage.

In the seventeenth embodiment, the brushless motor 3 and the motor control device 40 and the single-phase AC power supply 5 arranged in the blower 64 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.
In the blower 64 according to the seventeenth embodiment, the motor control device 40 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (not shown) that controls the operation of the blower 64.

Next, the operation in the blower 64 of the seventeenth embodiment will be described.
In the blower 64 of the seventeenth embodiment, when the user performs a predetermined operation, a command signal is input from the microcomputer to the motor control device 40. When a command signal is input to the motor control device 40, a drive voltage is applied from the motor control device 40 to the brushless motor 3. As a result, the brushless motor 3 is driven, the fan 65 rotates, and air is blown. At this time, in the blower 64 of the seventeenth embodiment, the output of the brushless motor 3 is controlled by the motor control device 40 based on the command signal from the microcomputer as in the thirteenth embodiment. As a result, the blower 64 adjusts the amount of blown air and the strength of the wind.

As described above, in the blower 64 of the seventeenth embodiment, the motor control device 40 that is reduced in size and weight is used, so that the blower itself can be reduced in size and weight as compared with the conventional blower. Therefore, according to the present invention, a highly portable blower can be provided.
In the blower 64 according to the seventeenth embodiment of the present invention, the motor control device 40 used for driving control of the brushless motor 3 is any motor control device described in the first to eleventh embodiments. You may comprise.

<< Embodiment 18 >>
FIG. 31 is a block diagram showing the configuration of the electric vacuum cleaner according to the eighteenth embodiment of the present invention.
The vacuum cleaner 66 according to the eighteenth embodiment includes a vacuum cleaner body 69, a floor suction tool 67 having a suction port formed on the bottom surface, one end connected to the floor suction tool 67, and the other end connected to the vacuum cleaner body 69. A dust suction hose 68.
The vacuum cleaner main body 69 of the eighteenth embodiment includes a dust collection chamber 71 to which the vacuum cleaner main body side end of the dust suction hose 68 is connected, and an electric blower 70 disposed on the blowing side of the dust collection chamber 71. ing. The electric blower 70 includes a fan 72 arranged to face the blowing side of the dust collection chamber 71, a brushless motor 3 that rotates the fan 72, and a motor control device 40 that drives and controls the brushless motor 3. Yes. The motor control device 40 is connected to the single-phase AC power source 5 and configured to apply a single-phase AC voltage. The fan 72 sucks air through the dust suction hose 68 and the dust collecting chamber 71 from the suction port on the bottom surface of the floor suction tool 67 by the rotation.

In the eighteenth embodiment, the brushless motor 3, the motor control device 40, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.
In the electric vacuum cleaner 66 according to the eighteenth embodiment, a motor control device 40 receives a command signal indicating a command rotational speed corresponding to a user operation from a microcomputer (not shown) that controls the operation of the fan 72. .

Next, the operation | movement in the vacuum cleaner 66 of Embodiment 18 is demonstrated.
In the vacuum cleaner 66 according to the eighteenth embodiment, a command signal is input from the microcomputer to the motor control device 40 when the user performs a predetermined operation. When a command signal is input to the motor control device 40, a drive voltage is applied from the motor control device 40 to the brushless motor 3, and the brushless motor 3 is driven. As a result, the fan 72 rotates and a suction force is generated in the cleaner body 69. The suction force generated in the vacuum cleaner main body 69 sucks air from the suction port provided on the bottom surface of the floor suction tool 67 connected via the dust suction hose 68. Thereby, dust on the surface to be cleaned is sucked together with air from the suction port of the floor suction tool 67 and collected in the dust collection chamber 71 of the cleaner body 69. At this time, in the electric vacuum cleaner 66 according to the eighteenth embodiment, the motor control device 40 controls the rotation speed of the brushless motor 3 based on the command signal from the microcomputer as in the thirteenth embodiment. Therefore, in the electric vacuum cleaner 66 according to the eighteenth embodiment, the rotation speed of the brushless motor 3 is controlled to adjust the strength of the suction force.

As described above, the electric vacuum cleaner 66 according to the eighteenth embodiment uses the motor control device 40 that is reduced in size and weight, so that the vacuum cleaner body 69 can be reduced in size and weight as compared with a conventional cleaner. Therefore, according to the present invention, it is possible to provide a vacuum cleaner that is highly portable and easy for the user to handle.
In the vacuum cleaner 66 according to the eighteenth embodiment of the present invention, the motor control device 40 used for driving control of the brushless motor 3 is any motor described in the first to eleventh embodiments. You may comprise with a control apparatus.

<< Embodiment 19 >>
FIG. 32 is a block diagram showing the configuration of the heat pump water heater of the nineteenth embodiment according to the present invention.
The heat pump water heater 72 of the nineteenth embodiment connects a refrigeration cycle device 73 that heats supplied water and discharges hot water, and a hot water storage tank 74 that stores hot water discharged from the refrigeration cycle device 73. It has water piping 74a, 74b, 75a and 75b.
The refrigeration cycle apparatus 73 includes a compression mechanism 42 that forms a refrigerant circulation path, an air heat exchanger 76, an expansion device 77, and a water heat exchanger 78. In addition, the refrigeration cycle apparatus 73 is provided with a motor control device 40 that is connected to the single-phase AC power supply 5 and to which a single-phase AC voltage is applied.
In the nineteenth embodiment, the brushless motor 3, the motor control device 40, and the single-phase AC power supply 5 have the same functions and configurations as those of the first embodiment. Further, the motor control device 40 shown in the first to eleventh embodiments is applied to the motor control device 40.

The expansion device 77 restricts the flow rate of the liquid refrigerant sent from the water heat exchanger 78 to the air heat exchanger 76, similarly to the expansion device 47 of the air conditioner 43 of the thirteenth embodiment shown in FIG. Immediately thereafter, the liquid refrigerant is expanded.
The water heat exchanger 78 is a condenser that heats the water supplied to the refrigeration cycle apparatus 73, and includes a temperature sensor 78a that detects the temperature of the heated water. The air heat exchanger 76 is an evaporator that absorbs heat from the ambient atmosphere, and includes a blower 76a for increasing the heat exchange capability and a temperature sensor 76b for detecting the ambient temperature.
The refrigerant pipe 79 connects the compression mechanism 42, the water heat exchanger 78, the expansion device 77, and the air heat exchanger 76 to form a refrigerant circulation path. The refrigerant circulates along a refrigerant circulation path formed by the compression mechanism 42, the water heat exchanger 78, the expansion device 77, and the air heat exchanger 76. The refrigerant pipe 79 is connected to a defrost bypass pipe 80 that bypasses the water heat exchanger 78 and the expansion device 77 and supplies the refrigerant discharged from the compression mechanism 42 to the air heat exchanger 76. . A defrost bypass valve 81 is provided in a part of the defrost bypass pipe 80.

The hot water storage tank 74 has a hot water storage tank 82 for storing water or hot water. A water supply pipe 83 for supplying water from the outside into the hot water storage tank 82 is connected to the water receiving port 82 c of the hot water storage tank 82. In addition, a hot water outlet 82 d of the hot water storage tank 82 is connected to a bathtub hot water supply pipe 84 for supplying hot water from the hot water storage tank 82 to the bathtub. A hot water supply pipe 85 that supplies hot water stored in the tank 82 to the outside is connected to the water inlet / outlet port 82 a of the hot water storage tank 82.
The water heat exchanger 78 and the hot water storage tank 82 of the refrigeration cycle apparatus 73 are connected by water pipes 74 a, 74 b, 75 a and 75 b, and a water circulation path is provided between the hot water storage tank 82 and the water heat exchanger 78. Is formed.

The water pipe 74 b is a pipe on the hot water storage tank side for supplying water from the hot water storage tank 82 to the water heat exchanger 78. One end of the water pipe 74b is connected to the water outlet 82b of the hot water storage tank 82, and the other end is connected to the water inlet side water pipe 75b of the water heat exchanger 78 via the joint portion 87b. Further, a drain valve 86 for discharging water in the hot water storage tank 82 or hot water is attached to one end side of the water pipe 74b.
The water pipe 74 a is a pipe on the hot water storage tank side that returns water from the water heat exchanger 78 to the hot water storage tank 82. One end of the water pipe 74a is connected to the water inlet / outlet port 82a of the hot water storage tank 82, and the other end is connected to the discharge side water pipe 75a of the water heat exchanger 78 via the joint portion 87a.
A water inlet side water pipe 75b connecting the water heat exchanger 78 and the joint portion 87b is provided with a pump 88 for circulating water in the water circulation path.

  In the heat pump water heater 72 of the nineteenth embodiment, the operating state of the heat pump water heater 72, that is, the target temperature of hot water set for the heat pump water heater 72, from the hot water storage tank 74 to the water heat exchanger 78 of the refrigeration cycle apparatus 73. The command rotational speed of the brushless motor 3 is determined based on the temperature of the supplied water and the outside air temperature. Then, the motor control device 40 according to the nineteenth embodiment determines the motor output required for the brushless motor 3 of the compression mechanism 42 based on the command rotational speed.

Next, the operation | movement in the heat pump water heater 72 of Embodiment 19 is demonstrated.
In the heat pump water heater 72 of the nineteenth embodiment, when the drive voltage Cd is applied from the motor control device 40 to the brushless motor of the compression mechanism 42 and the compression mechanism 42 is driven, the high-temperature refrigerant compressed by the compression mechanism 42 is changed to the arrow D. Cycle in the direction. Accordingly, the high-temperature refrigerant passes through the refrigerant pipe 79 from the compression mechanism 42 and is supplied to the water heat exchanger 78. Further, when the pump 88 of the water circulation path is driven, water is supplied from the hot water storage tank 82 to the water heat exchanger 78.
At this time, in the water heat exchanger 78, heat exchange is performed between the high-temperature refrigerant and the water supplied from the hot water storage tank 82, and heat is transferred from the refrigerant to the water. Therefore, the water supplied to the water heat exchanger 78 is heated, and the heated water is supplied to the hot water storage tank 82. At this time, the temperature of the heated water is monitored by the condensation temperature sensor 78a.
In the water heat exchanger 78, the refrigerant condenses by heat exchange. The flow rate of the condensed liquid refrigerant is throttled by the throttle device 77, expands, and is sent to the air heat exchanger 76.

In the heat pump water heater 72 of the nineteenth embodiment, the air heat exchanger 76 functions as an evaporator. The air heat exchanger 76 absorbs heat from the outside air sent by the blower 76a and evaporates the low-temperature refrigerant liquid. At this time, the temperature of the ambient atmosphere around the air heat exchanger 76 is monitored by the temperature sensor 76b.
In the refrigeration cycle apparatus 73, when the air heat exchanger 76 is frosted, the defrost bypass valve 81 is opened, and high-temperature refrigerant is supplied to the air heat exchanger 76 via the defrost bypass path 80. Thereby, defrosting of the air heat exchanger 76 is performed.
On the other hand, hot water is supplied to the hot water storage tank 74 from the water heat exchanger 78 of the refrigeration cycle apparatus 73 through the water pipes 74a and 75a. Hot water supplied to the hot water tank 74 is stored in the hot water storage tank 82. Hot water in the hot water storage tank 82 is supplied to the outside through the hot water supply pipe 85 as necessary. In particular, when hot water is supplied to the bathtub, the hot water in the hot water storage tank 82 is supplied to the bathtub through the hot water supply pipe 84 for the bathtub.
In addition, when the amount of water stored in the hot water storage tank 82 or the amount of hot water becomes a certain amount or less, water is replenished from the outside through the water supply pipe 83.

  In the heat pump water heater 72 of the nineteenth embodiment, based on the target temperature of hot water set for the heat pump water heater 72 by the motor control device 40, the temperature of water supplied to the water heat exchanger 78, and the outside air temperature. Thus, the command rotational speed of the brushless motor 3 is determined. In the heat pump water heater 72 of the nineteenth embodiment, the rotational speed of the brushless motor 3 of the compression mechanism 42 is controlled by the motor control device 40 based on the command rotational speed as in the thirteenth embodiment. Thereby, in the heat pump water heater 72 of the nineteenth embodiment, the hot water at the target temperature is reliably supplied.

As described above, the heat pump water heater 72 according to the nineteenth embodiment uses the motor control device 40 that is reduced in size and weight, so that the heat pump water heater 72 can be reduced in size and weight as compared with the conventional water heater. it can. Therefore, in the heat pump water heater of the present invention, the ease of installation due to miniaturization is improved, and the ease of installation due to weight reduction is also improved. Further, according to the present invention, since the cost can be significantly reduced as compared with the conventional water heater, the merit for the user is expanded.
In the heat pump water heater 72 according to the nineteenth embodiment of the present invention, the motor control device 40 used for driving control of the brushless motor 3 is any motor described in the first to eleventh embodiments. You may comprise with a control apparatus.

  Note that the present invention described in the first to nineteenth embodiments is not limited to being mounted on the products described in the above-described embodiments, and other than driving a brushless motor using an inverter circuit. Needless to say, the present invention can also be applied to the motor control apparatus. In any product, by reducing the size and weight of the motor control device, the degree of freedom in designing the corresponding product is improved, and an inexpensive product can be provided.

In particular, the utility of the air conditioner and the compressor used in the air conditioner will be described.
Most of the home air conditioners sold in Japan are converted into inverters, which are extremely energy-saving devices compared to air conditioners that are not converted into inverters. Therefore, the power consumption of air conditioners in Japan is about half that of air conditioners 10 years ago, and inverterization has permeated. However, from a global perspective, there are more air conditioners that have not been converted into inverters, and it is desirable to convert the world's air conditioners into inverters from the viewpoint of promoting energy saving and protecting the global environment.

In Japan, most air conditioners are in the form of products, but in countries other than Japan, they are often distributed as single compressor products. In such single compressor markets, the size of conventional compressors There is a need for a compressor of the same size or smaller. Therefore, as a result of adding the inverter circuit, if the size becomes larger than before, it is not accepted by the market, and it is difficult to promote energy saving by converting the compressors of the world into inverters. For this reason, a compressor including an inverter device having the same performance and the same shape or a small size is required.
As described above, according to the present invention, it is possible to provide a motor control device having a configuration that does not use a power factor improving inductor, which is a large component, and a capacitor having a large smoothing capacitance among conventional motor control devices. Therefore, according to the present invention, it is possible to provide a compressor including a motor control device that is equal to or smaller than that of a conventional compressor, to promote global energy saving and to bring great utility to the preservation of the global environment. Can do.

  In each of the above-described embodiments, an example has been described in which an AC power supply is used as an input, and this is rectified and input to the inverter circuit. However, the present invention is not limited to such a configuration. In the present invention, even if a fluctuating voltage is input to the inverter circuit, the inverter circuit is configured to convert it to a desired voltage and output it to the brushless motor. For example, when a plurality of loads are connected to a single DC power source as found in a vehicle-mounted brushless motor, the output voltage of the DC power source varies depending on the operating conditions of these loads. Even if a DC power supply that fluctuates in this way is input to the motor control device of the present invention, the inverter circuit can convert it to a desired voltage and drive the brushless motor with high accuracy.

  The motor control device of the present invention can also be applied to a compressor of an in-vehicle air conditioner that is driven by a brushless motor. The motor control device of the present invention is useful in a vehicle in which the engine is stopped while the vehicle is stopped and the engine is started when the vehicle starts, for example, an idling stop vehicle that stops idling of the engine when the vehicle is stopped. When the engine is started, an instantaneous drop in the power supply voltage occurs. However, when the motor control device of the present invention is mounted on the compressor of an in-vehicle air conditioner, the voltage applied to the brushless motor can be adjusted even when the power supply voltage that occurs when starting the engine is instantaneously reduced. However, the vehicle-mounted air conditioner can be continuously operated without stopping. As described above, the motor control device of the present invention is particularly effective for the vehicle and the like when the engine is stopped and the engine is started at the time of start, such as an idling stop vehicle.

  Further, in each of the above-described embodiments, as a method for detecting the phase by the current supplied to the brushless motor without using the position sensor, the IEEJ Transactions D, 117, published in 1997 (Heisei 9). No. 1, pp. 98-104, Takeshita, Ichikawa, Lee, Matsui “Sensorless salient pole type brushless DC motor control based on speed electromotive force estimation” has been described. The present invention is not limited to this method, and any method can be applied to the present invention as long as it is a method for detecting a phase with a current.

  The motor control device according to the present invention can drive each device with high efficiency by continuously applying a desired voltage without stopping the voltage application to the drive source even when the DC side voltage in the inverter circuit is low. It is useful as a motor control device for compressors, air conditioners, refrigerators, electric washing machines, electric dryers, blowers, vacuum cleaners, heat pump water heaters, and the like.

It is a block diagram which shows the structure of the motor control apparatus of Embodiment 1 which concerns on this invention. It is a block diagram which shows the structure of the PWM production | generation part in Embodiment 1 which concerns on this invention. It is a flowchart which shows operation | movement of the Vpn correction | amendment part in Embodiment 1 which concerns on this invention. (A) is a graph which shows the experimental result which measured the motor current etc. by the conventional motor control apparatus, (b) is a graph which shows the experimental result which measured the motor current etc. by the motor control apparatus of Embodiment 1. FIG. . It is a block diagram of the PWM production | generation part in the motor control apparatus of Embodiment 2 which concerns on this invention. It is a flowchart which shows operation | movement of the ratio correction | amendment part in Embodiment 2 which concerns on this invention. It is a block diagram which shows the structure of the motor control apparatus of Embodiment 3 which concerns on this invention. (A) is a graph which shows the experimental result which measured the motor current etc. by the conventional motor control apparatus, (b) is a graph which shows the experimental result which measured the motor current etc. by the motor control apparatus of Embodiment 3. . It is a block diagram which shows the structure of the motor control apparatus of Embodiment 4 which concerns on this invention. It is a graph which shows the experimental result which measured the motor current etc. by the motor control apparatus of Embodiment 4 which concerns on this invention. It is a block diagram which shows the structure of the motor control apparatus of Embodiment 5 which concerns on this invention. It is the experimental result which measured the motor current etc. by the motor control apparatus of Embodiment 5 which concerns on this invention. It is a graph which shows the experimental result which shows the limiting torque of the motor by the motor control apparatus of this invention, and the conventional motor control apparatus. It is a block diagram which shows the structure of the motor control apparatus of Embodiment 7 which concerns on this invention. It is a block diagram which shows the structure of the motor control apparatus of Embodiment 8 which concerns on this invention. (A) is a block diagram which shows the structure of the motor control apparatus of Embodiment 9 which concerns on this invention, (b) shows another structure of the step-up circuit in the motor control apparatus of Embodiment 9 which concerns on this invention. It is a circuit diagram. It is a wave form diagram which shows the input waveform to the voltage booster circuit in the motor control apparatus of Embodiment 9 which concerns on this invention. It is a wave form diagram which shows the operation | movement in the motor control apparatus of Embodiment 9 which concerns on this invention. It is a block diagram which shows the structure of the motor control apparatus of Embodiment 10 which concerns on this invention. It is a block diagram which shows the structure of the voltage booster circuit control part in the motor control apparatus of Embodiment 10 which concerns on this invention. It is a wave form diagram which shows the operation | movement in the motor control apparatus of Embodiment 10 which concerns on this invention. It is a block diagram which shows another structure of the pressure | voltage rise circuit control part in the motor control apparatus of Embodiment 10 which concerns on this invention. (A) is a block diagram showing a configuration of a motor control device according to an eleventh embodiment of the present invention, and (b) is a voltage doubler rectification booster of another configuration in the motor control device according to the eleventh embodiment of the present invention. It is a circuit diagram which shows a circuit. It is a wave form diagram which shows the operation | movement in the motor control apparatus of Embodiment 11 which concerns on this invention. It is a block diagram which shows the structure of the compressor of Embodiment 12 which concerns on this invention. It is a block diagram which shows the structure of the air conditioner of Embodiment 13 which concerns on this invention. It is a block diagram which shows the structure of the refrigerator of Embodiment 14 which concerns on this invention. It is a block diagram which shows the structure of the electric washing machine of Embodiment 15 which concerns on this invention. It is a block diagram which shows the structure of the electric dryer of Embodiment 16 which concerns on this invention. It is a block diagram which shows the structure of the air blower of Embodiment 17 which concerns on this invention. It is a block diagram which shows the structure of the vacuum cleaner of Embodiment 18 which concerns on this invention. It is a block diagram which shows the structure of the heat pump water heater of Embodiment 19 which concerns on this invention. It is a block diagram which shows the structure of the motor control apparatus of the 1st prior art. It is a block diagram which shows the structure of the motor control apparatus of the 2nd prior art.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Rectification circuit 2 Inverter circuit 3 Brushless motor 4 Control part 5 Single phase alternating current power supply 6 dq conversion part 7 d axis PI controller 8 q axis PI controller 9 PWM production | generation part 10 Inverse dq conversion part 11 Interline modulation part 12 Vpn correction | amendment Unit 13 Ratio correction unit 14 Ratio generation unit 15 Phase estimation unit 16 Capacitor 17 Inductor 18 d-axis multiplication unit 19 q-axis multiplication unit 20 q-axis addition unit 21 Booster circuit 22 Booster circuit control unit 23 AC current command creation unit 24 PWM command creation Unit 25 Voltage doubler rectification booster circuit 26 Capacitor 27 Capacitor 40 Motor controller 41 Compressor 43 Air conditioner 51 Refrigerator 55 Electric washing machine 61 Electric dryer 64 Blower 66 Electric vacuum cleaner 72 Heat pump water heater

Claims (22)

An inverter circuit that takes a fluctuating voltage as an input, converts the voltage to a desired voltage and outputs the voltage to a brushless motor, an input voltage to the inverter circuit, a motor current flowing through the brushless motor, and a brushless motor A PWM generator that receives a motor current command value indicating a value, generates a three-phase sine wave voltage command value to be applied to the brushless motor, and outputs a PWM signal corresponding to the three-phase sine wave voltage command value; In a motor control device comprising a control unit having
The PWM generation unit includes a line modulation unit that subtracts and outputs a minimum value in the three-phase sine wave voltage command value from the three-phase sine wave voltage command value,
Compare the maximum value of the output of the interline modulation unit and the input voltage to the inverter circuit,
As a result of the comparison, when the input voltage is larger than the maximum value, the PWM signal is generated according to the ratio of each output of the line modulation unit to the input voltage,
When the input voltage is less than or equal to the maximum value, the PWM signal is formed according to the ratio of each output of the line modulation unit to the maximum value, and the voltage is applied to the brushless motor while the phase is maintained Motor controller. An inverter circuit that takes a fluctuating voltage as an input, converts the voltage into a desired voltage, and outputs the voltage to a brushless motor; and
A control unit that receives an input voltage to the inverter circuit, a motor current that flows to the brushless motor, and a motor current command value that indicates a value that should flow to the brushless motor, and generates a motor applied voltage command value for the inverter circuit In a motor control device comprising:
The control unit further includes:
A PWM generator that receives the motor applied voltage command value and the input voltage and outputs a PWM signal corresponding to the motor applied voltage command value to the inverter circuit;
The PWM control unit
The motor applied voltage command value and the input voltage are input, a reference voltage is set from the motor applied voltage command value, the reference voltage and the input voltage are compared, and as a result of the comparison, the input voltage is the reference voltage When the voltage is smaller than the voltage, a value obtained by multiplying the motor applied voltage command value by the ratio of the input voltage to the reference voltage is output. When the input voltage is equal to or higher than the reference voltage, the motor applied voltage command value is output as it is. Ratio correction unit,
An inverse dq converter that generates a three-phase sine wave voltage command value from the output of the ratio correction unit;
A line modulation unit that subtracts and outputs the minimum value of the three-phase sine wave voltage command value from the three-phase sine wave voltage command value; and
A motor control device configured to apply a voltage to the brushless motor in a state in which a phase is maintained, and a ratio generator that generates a PWM signal based on a ratio of an output of the line modulation unit to the input voltage . Control unit, the motor control device according to claim 1 or 2 configured to estimate on the basis of the rotational phase of the brushless motor to the motor current. The control unit according to any one of claims 1 to 3 , wherein the control unit is configured to stop the integral control of the control unit when a voltage value at both ends of the inverter circuit is smaller than a voltage command value applied to the brushless motor. Motor control device. The motor control device according to any one of claims 1 to 4 , wherein the control unit is configured to calculate a voltage command value by a calculation formula having a non-interference term. Control unit detects the voltage of the inverter circuit, estimates a voltage of the inverter circuit to be applied to the next control cycle, any one of claims 1 to 5 configured to control the inverter circuit The motor control device described in 1. The motor control device according to any one of claims 1 to 6 , wherein the motor control device is configured to include a capacitor having a small electrostatic capacitance on an input side of the inverter circuit. The motor control device according to any one of claims 1, which is configured to have a small inductor inductance on the input side of the inverter circuit 7. A booster circuit including an inductor, a diode, a switching element, and a capacitor; and a booster circuit controller that controls the booster circuit;
The boosting circuit control unit, the motor control apparatus according to any one of claims 1 to 6, wherein the determining based on a signal from the controller the duty value of said switching element. The booster circuit control unit is configured to receive the detected AC power supply phase and AC current value, and outputs an AC current command value based on the detected phase and a control signal from the control unit. current command unit, and according to claim 9 having a PWM command generation section, which forms and outputs a PWM command value for driving the switching element based on the AC current of the AC current command value and the detected AC power supply Motor control device. A step-up circuit having an inductor to which a variable voltage is input; a plurality of diodes constituting the rectifier circuit; a switching element connected to the rectifier circuit; the motor control device according to any one of claims 1, characterized by further comprising a boosting circuit control section for controlling the circuit 6. If the capacitance of the capacitor is C [F] and the maximum output power of the motor is P [W],
C ≦ 2 × 10 ⁻⁷ × P
The motor control device according to claim 7 , wherein the motor control device is configured as follows. When an inductor having a small inductance is provided on the input side of the inverter circuit, the inductance of the inductor is L [H], and the capacitance of the capacitor is C [F].
L ≦ 9 × 10 ⁻⁹ / C
The motor control device according to claim 7 , wherein: If the inductance of the inductor is L [H] and the maximum output power of the motor is P [W],
L ≦ P × 10 ⁻⁶
The motor control device according to claim 8 , wherein the motor control device is configured as follows. The compressor which has a motor control device according to any one of claims 1 to 14 . An air conditioner having the motor control device according to any one of claims 1 to 14 . A refrigerator having the motor control device according to any one of claims 1 to 14 . An electric washing machine comprising the motor control device according to any one of claims 1 to 14 . The electric dryer which has the motor control apparatus as described in any one of Claim 1 to 14 . A blower comprising the motor control device according to any one of claims 1 to 14 . A vacuum cleaner comprising the motor control device according to any one of claims 1 to 14 . A heat pump water heater having the motor control device according to any one of claims 1 to 14 .

Images