CN112104283A - Open-winding motor drive device and refrigeration cycle device - Google Patents
Open-winding motor drive device and refrigeration cycle device Download PDFInfo
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- CN112104283A CN112104283A CN202010552527.0A CN202010552527A CN112104283A CN 112104283 A CN112104283 A CN 112104283A CN 202010552527 A CN202010552527 A CN 202010552527A CN 112104283 A CN112104283 A CN 112104283A
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- 238000004804 winding Methods 0.000 title claims abstract description 45
- 238000005057 refrigeration Methods 0.000 title claims abstract description 12
- 238000001514 detection method Methods 0.000 claims abstract description 21
- 238000012937 correction Methods 0.000 claims description 5
- 238000010586 diagram Methods 0.000 description 18
- 230000014509 gene expression Effects 0.000 description 12
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- 230000006835 compression Effects 0.000 description 9
- 238000007906 compression Methods 0.000 description 9
- 238000006243 chemical reaction Methods 0.000 description 7
- 230000007246 mechanism Effects 0.000 description 7
- 238000001816 cooling Methods 0.000 description 3
- 238000009499 grossing Methods 0.000 description 3
- 238000010438 heat treatment Methods 0.000 description 3
- 239000003507 refrigerant Substances 0.000 description 3
- 238000007664 blowing Methods 0.000 description 2
- 239000003990 capacitor Substances 0.000 description 2
- 230000006837 decompression Effects 0.000 description 2
- 230000020169 heat generation Effects 0.000 description 2
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- 238000000034 method Methods 0.000 description 2
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- 239000006096 absorbing agent Substances 0.000 description 1
- 238000004378 air conditioning Methods 0.000 description 1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/06—Rotor flux based control involving the use of rotor position or rotor speed sensors
- H02P21/08—Indirect field-oriented control; Rotor flux feed-forward control
- H02P21/09—Field phase angle calculation based on rotor voltage equation by adding slip frequency and speed proportional frequency
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
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Abstract
An open-winding motor drive device and a refrigeration cycle device, the open-winding motor drive device comprising: a primary side inverter and a secondary side inverter connected to the 3 winding terminals, respectively, in a motor having an open winding structure in which 3-phase windings are independent from each other and 6 winding terminals are provided; a converter for supplying a DC power obtained by converting a voltage of an AC power into a DC power to the primary-side and secondary-side inverters; a phase current detecting unit for detecting each phase current flowing through the motor; a zero-phase current detection unit that detects a zero-phase current flowing between the primary-side and secondary-side inverters; a speed detection unit for detecting a rotational speed of the motor; and a control unit that performs PWM control of the primary-side and secondary-side inverters based on the detected phase currents and the zero-phase current, and that adjusts the amount of the zero-phase current while driving the motor, wherein the control unit includes a phase advance compensation unit that calculates such that the phase of the detected zero-phase current advances in accordance with the rotation speed of the motor.
Description
Technical Field
Embodiments of the present invention relate to a device for driving a motor having an open-winding structure, and a refrigeration cycle device including the device.
Background
As a technique for improving efficiency of a system for driving a motor having an open-winding structure, for example, as shown in japanese patent No. 3352182, a technique for improving efficiency by suppressing a zero-phase current flowing between 2 inverters for driving the motor is known.
In a motor that generates a high induced voltage like the open-winding structure, the same torque can be generated with a smaller current, and therefore, the current consumption can be reduced and the efficiency can be improved. On the other hand, in the motor having the dc bus common type, since a zero-phase current flowing in the same direction is generated in 3 phases of the motor, there are problems such as a decrease in efficiency and heat generation of the element.
Further, the zero-phase current has a frequency 3 times higher than that of the current of U, V, W flowing for driving the motor, and the detection delay of the zero-phase current becomes large in the high rotation speed region. Therefore, in order to suppress the zero-phase current, it is necessary to shorten the period for controlling the motor, which causes a problem of heat generation of elements due to an increase in switching frequency or a problem of high cost of a control arithmetic device such as a microcomputer.
Disclosure of Invention
According to the following embodiments, an open-winding motor driving device and a refrigeration cycle device provided with the same are provided, which can suppress a zero-phase current even in a high rotation speed region without shortening a motor control cycle.
An open-winding motor driving device according to an embodiment includes:
a primary-side inverter connected to 3 winding terminals out of the 6 winding terminals of the open winding structure having 6 winding terminals, the 3-phase windings being independent from each other;
a secondary side inverter connected to the remaining 3 winding terminals of the motor;
a converter configured to supply a dc power source obtained by converting a voltage of an ac power source into a dc power to the primary-side inverter and the secondary-side inverter;
a phase current detection unit for detecting each phase current flowing through the motor;
a zero-phase current detection unit that detects a zero-phase current flowing between the primary-side inverter and the secondary-side inverter;
a speed detection unit that detects a rotational speed of the motor; and
a control unit that performs PWM (Pulse Width Modulation) control of the primary-side inverter and the secondary-side inverter based on the phase current of each phase detected by the phase current detection unit and the zero-phase current detected by the zero-phase current detection unit to drive the motor and adjust the amount of the zero-phase current,
the control unit includes a phase lead compensation unit that calculates the phase of the detected zero-phase current in advance of the rotational speed of the motor, and performs the PWM control based on the result of the calculation and the respective phase currents.
The refrigeration cycle device of the embodiment further includes:
the motor with open winding structure, 3-phase winding is independent respectively, and has 6 winding terminals; and
an open-winding motor drive device of an embodiment.
Drawings
Fig. 1 shows an embodiment, and is a diagram showing a circuit configuration of a motor drive system.
Fig. 2 is a functional block diagram showing an internal configuration of the control device.
Fig. 3 is a functional block diagram showing a detailed configuration of the zero-phase current control unit.
Fig. 4 is a diagram showing a plate line diagram corresponding to the characteristics of the phase advancing element portion.
Fig. 5 is a diagram showing a phase relationship between an actual zero-phase current and a zero-phase current detected in control.
Fig. 6 is a diagram showing a suppression state of the zero-phase current before and after the operation of the zero-phase current suppression control unit when the rotation speed is set to 40rps without operating the phase lead compensation unit.
Fig. 7 is a view corresponding to fig. 6 when the rotation speed is 50 rps.
Fig. 8 is a current waveform diagram in a state where the phase lead compensation unit 61 is operated and the zero-phase current suppression unit is not operated when the rotation speed is 50 rps.
Fig. 9 is a current waveform diagram in a state where the zero-phase current suppression unit is operated from the state of fig. 8.
Fig. 10 is a current waveform diagram showing the horizontal axis of fig. 8 reduced by 5 times.
Fig. 11 is a current waveform diagram showing the horizontal axis of fig. 9 reduced by 5 times.
Fig. 12 is a view corresponding to fig. 10 when the rotation speed is 70 rps.
Fig. 13 is a view corresponding to fig. 11 when the rotation speed is 70 rps.
Fig. 14 is a diagram schematically showing the structure of the air conditioner.
Detailed Description
Hereinafter, one embodiment will be described with reference to the drawings. In fig. 14, the compressor 2 constituting the heat pump refrigeration cycle apparatus 1 is configured such that the compression mechanism 3 and the motor 4 are housed in the same iron-made sealed container 5, and the rotor shaft of the motor 4 is coupled to the compression mechanism 3. As a result, the compression mechanism 3 is driven by the driving of the motor 4, and a compression operation is performed. Further, the compressor 2, the four-way valve 6, the indoor heat exchanger 7, the pressure reducer 8, and the outdoor heat exchanger 9 are connected by pipes as heat transfer medium flow paths to form a closed loop.
The compressor 2 is, for example, a rotary compressor, and the motor 4 is, for example, a 3-phase IPM (Interior Permanent Magnet) motor or a brushless DC motor. The amount of refrigerant discharged from the compression mechanism 3 changes according to a change in the rotation speed of the motor 4, and the output of the compressor 2 changes, whereby the capacity of the refrigeration cycle can be changed. The air conditioner E includes the heat pump refrigeration cycle device 1 described above.
During the heating operation of the air conditioner E, the four-way valve 6 is in a state shown by the solid line, and the high-temperature refrigerant compressed by the compression mechanism 3 of the compressor 2 is supplied from the four-way valve 6 to the indoor heat exchanger 7, condensed, decompressed by the decompression device 8, changed to a low temperature, flows to the outdoor heat exchanger 9, evaporated there, and returned to the compressor 2. On the other hand, during the cooling operation, the four-way valve 6 is switched to the state shown by the broken line. Therefore, the high-temperature refrigerant compressed by the compression section 3 of the compressor 2 is supplied from the four-way valve 6 to the outdoor heat exchanger 9, condensed, decompressed by the decompression device 8, changed to a low temperature, flows to the indoor heat exchanger 7, evaporated there, and returned to the compressor 2.
The outdoor heat exchanger 9 functions as an evaporator (heat absorber) during the heating operation, functions as a condenser (heat sink) during the cooling operation, and conversely, the indoor heat exchanger 7 functions as a condenser during the heating operation and functions as an evaporator during the cooling operation. Further, the air is blown by the fans 10 and 11 to the indoor and outdoor heat exchangers 7 and 9, respectively, and the heat exchange between the indoor air and the outdoor air is efficiently performed by the blown air in the heat exchangers 7 and 9.
The fan 11 for blowing air to the outdoor heat exchanger 9 is a propeller fan and is driven by a fan motor 12. Fan motor 12 is a brushless DC motor having high efficiency, for example, as in motor 4. The fan 10 for blowing air to the indoor heat exchanger 7 is a cross flow fan and is driven by a fan motor 13. The fan motor 13 is also preferably a brushless DC motor.
Fig. 1 is a diagram showing a circuit configuration of a motor drive system connected to a commercial 3-phase ac power supply 27. The 3-phase winding of the motor 4 that drives the compression mechanism unit 3 is formed in an open winding structure in which both terminals are disconnected without being connected to each other, and the motor 4 includes 6 winding terminals Ua, Va, Wa, Ub, Vb, Wb.
The primary-side inverter 21 and the secondary-side inverter 22 (hereinafter referred to as inverters 21 and 22) are each configured by 3-phase bridge connection of an IGBT23 as a switching element, and a flywheel diode 24 is connected in reverse parallel to each IGBT 23. For example, the inverters 21 and 22 can be each made of a module in which 6 IGBTs 23 and 6 freewheeling diodes 24 are all built in the same package. Each IGBT23 may be formed of a wide bandgap semiconductor such as SiC or GaN with high efficiency. The phase output terminals of the inverter 21 are connected to the winding terminals Ua, Va, and Wa of the motor 4, and the phase output terminals of the inverter 22 are connected to the winding terminals Ub, Vb, and Wb of the motor 4.
The inverters 21, 22 are connected in parallel with the converter 25. The converter 25 is a 3-phase full-wave rectifier circuit in which 6 diodes are bridged, and its 3-phase ac input terminal is connected to a 3-phase ac power supply 27 via a noise filter 26. A dc reactor 28 for power factor improvement is inserted in the positive power supply line between the converter 25 and the inverter 21. A smoothing capacitor 29 for smoothing a direct current is connected between the positive power supply line and the negative power supply line.
The current sensor 30(U, V, W) detects the phase current I of each phase of the motor 4u、Iv、IwIs provided between the 3-phase output line of the inverter 21 and the winding terminal of the motor 4. The current sensor 30(U, V, W) may be provided between the 3-phase output line of the inverter 22 and the winding terminal of the motor 4. The voltage sensor 31 detects a dc power supply voltage V as a terminal voltage of the smoothing capacitor 29DC。
The control device 33 is given a speed command value ω as a target rotation speed of the compression mechanism unit 3 from a higher-level control device in a system for driving the motor, for example, an air conditioning control unit of the air conditioner ErefSo that the detected motor speed ω and the speed command value ωrefControlled in a consistent manner. Control device 33 detects each phase current I based on current sensor 30u、Iv、IwAnd the DC voltage V detected by the voltage sensor 31DCSwitching signals are generated to be applied to the gates of the IGBTs 23 constituting the inverters 21 and 22. The control device 33 corresponds to a control unit.
Fig. 2 is a functional block diagram showing the internal configuration of the control device 33. The 3-phase/dq 0 converter 34 converts each phase current I detected via the current sensor 30u、Iv、IwCurrent I converted into current I of each axis coordinate of d, q and 0 used for vector controld、Iq、I0. With respect to zero phase current I0Can be adjusted by applying to each phase current Iu、Iv、IwAnd summed up to calculate. I.e. I0＝Iu+Iv+IwIn the second half, not shown, the signal is multiplied by 1/(√ 2) times and then output. The following is about zero phase current I0The coefficient 1/(√ 2) is omitted. The timing at which the 3-phase/dq 0 conversion unit 34 detects the current is set, for example, in synchronization with the carrier cycle in PWM control. Similarly, the current sensor 30 and the 3-phase/dq 0 conversion unit 34 correspond to a phase current detection unit. The 3-phase/dq 0 conversion unit 34 corresponds to a zero-phase current detection unit.
The speed/position estimating unit 35, which is an example of the speed detecting unit, estimates the speed ω and the motor current frequency ω from the voltage and the current of the motor 4eAnd a rotational position theta. The rotational position θ is input to the 3-phase/dq 0 converter 34 and the dq 0/3-phase converter 36. The speed control unit 37 receives an input speed command ωrefAnd the estimated speed ω, for example, by performing PI operation on the difference therebetween to generate and output a q-axis current command Iqref. The d-axis current command generating unit 38 generates the direct current voltage V from the direct current voltage VDCAnd the voltage amplitude V of the dq axisdqFor example, the d-axis current command value I is generated and output by performing PI operation on the difference between the two valuesdref。
The current control unit 39 responds to the q-axis current command IqrefAnd q-axis current IqTo generate a q-axis voltage command VqAnd according to the d-axis current command IdrefAnd d-axis current IdTo generate a d-axis voltage command Vd. Zero-phase current control unit40 according to the zero-phase current command I0refAnd a zero-phase current I inputted from the 3-phase/dq 0 conversion unit 340And a motor current frequency ω inputted from the speed/position estimating unit 35eGenerating and outputting zero-phase voltage command V0。
The dq0/3 phase conversion unit 36 instructs each axis voltage V by equation (1)q、Vd、V0Converted into 3-phase voltage command value V of 2 inverters 21 and 22u1、Vv1、Vw1、Vu2、Vv2、Vw2。
The modulation unit 42 generates and outputs switching signals applied to the gates of the IGBTs 23 constituting the inverters 21 and 22, PWM signals U1, V1, W1, X1, Y1, Z1, U2, V2, W2, X2, Y2, and Z2, based on the input voltage command value. The modulation unit 42 receives a dc voltage VDC。
Fig. 3 is a functional block diagram showing a detailed configuration of the zero-phase current control unit 40. The subtractor 43 obtains a zero-phase current command I0refAnd zero phase current I0And outputs the difference to the phase lead compensation unit 61. In the present embodiment, the zero-phase current command I0refIs set to zero in a normal state, thereby realizing zero phase current I0Inhibition of (3). The phase lead compensation unit 61 includes a phase lead element unit 62 and an amplifier 63. The phase advancing element 62 performs the following calculation. First, if the carrier frequency in PWM control is fcThe frequency corresponding to the rotational speed of the motor is represented by ωeThe signal delay of the circuitry is set to,
the detection delay phi of the zero-phase current is calculated by equation (2).
Further, the coefficients α and T are determined by expressions (3) and (4), respectively.
Further, when s is j ω, the phase lead element unit 62 multiplies the input zero-phase current signal by equation (5).
(1+αTs)/(1+Ts)…(5)
The amplifier 63 corresponding to the gain correction unit multiplies the current signal input from the phase lead element unit 62 by the gain G of the following expression. In addition, "#" represents a power.
An input terminal of the zero-phase current suppression unit 64 is connected to an output terminal of the amplifier 63. The amplifier 44 outputs the result of multiplying the input current signal by the proportional control gain Kp to the adder 46, and the amplifier 45 outputs the result of multiplying the current signal by the resonance control gain Kr to the subtractor 47. The output signal of the subtractor 47 is integrated by an integrator 48 and output to an adder 46 and a multiplier 49.
The multiplier 49 is inputted with the square of the value of 3 times of the motor current frequency ω e, the frequency (3 ω e)2Multiplied by the integration result of the integrator 48. The 3-time high-frequency component of the motor current frequency is equivalent to the zero-phase current I0. The multiplication result of the multiplier 49 is input to the subtractor 47 via the integrator 50.
The subtractor 47 subtracts the integration result of the integrator 50 from the output signal of the amplifier 45 and outputs the result to the integrator 48. In the above configuration, the parts other than the amplifier 44 and the adder 46 constitute the resonance control unit 51 that controls so as to improve the responsiveness to the 3 rd higher frequency of the current frequency. The addition result of the adder 46 becomes a zero-phase voltage V0And is output.
Next, the operation of the present embodiment will be described with reference to fig. 4 to 9. The control device 33 performs current detection and control calculation in synchronization with the carrier cycle in PWM control. The respective currents of the U-phase, V-phase, W-phase, and zero-phase are detected at the start of the carrier cycle, and motor control calculation and further zero-phase current suppression control calculation are executed based on the detected currents.
The specific content of the motor control operation is as follows: (1) current coordinate conversion processing by the 3-phase/dq 0 conversion unit 34, (2) speed and position estimation processing by the speed and position estimation unit 35, (3) speed control by the speed control unit 37, and (4) current control by the current control unit 39. Voltage command V generated based on current control by (4)q、VdAnd a zero-phase voltage V generated by a zero-phase current suppression control operation0The duty ratio in the PWM control is updated, and PWM signals U1, V1, W1, X1, Y1, Z1, U2, V2, W2, X2, Y2, and Z2 are generated and output.
Here, as shown in fig. 5, since a delay of 1 carrier cycle occurs in the detection of the zero-phase current, a phase difference occurs between the actual zero-phase current and the detected zero-phase current. Since the frequency of the zero-phase current is proportional to the rotation speed of the motor, the proportion of the detection delay with respect to the zero-phase current increases in the high rotation speed region and the phase difference increases. Thus, the zero-phase voltage command V for suppressing the zero-phase current0The phase difference from the actual zero-phase current becomes large. When the phase lead compensation unit 61 is not activated, for example, when the carrier frequency is 5kHz in a 6-pole motor, the zero-phase current can be suppressed when the rotation speed is 40rps as shown in fig. 6, but the zero-phase current increases when the rotation speed is 50rps as shown in fig. 7.
Therefore, in the present embodiment, the phase lead compensation unit 61 is caused to function to suppress the zero-phase current. Fig. 4 is a plate line diagram of the phase advancing element portion 62. From this figure, the angular frequency ω whose phase is the maximum is obtained by equation (7)m。
And, the maximum value of the phase phimThe result was obtained by equation (8). Further, the coefficient α is derived from expression (8) as in expression (3). The coefficient T is derived from expressions (7) and (3) as shown in expression (4). The current gain Gi [ dB ] of the phase lead element part 62]For example, the equation (9) and thus the ratio (output current)/(input current) is the equation (10).
Further, with respect to the relative angular frequency ωmA current gain Gi of, according to the panel diagram, is
Gi＝10log10α…(11)
. Therefore, the ratio (output current)/(input current) is expressed by the expression (12).
In equation (12), the current output from the phase lead element 62 is a numerical value multiplied by the right side of the input current. Therefore, the amplifier 63 performs correction by multiplying the gain G of expression (6). The amplifier 63 is an example of a gain correction unit.
When the control according to the present embodiment is applied to a 6-pole motor, which is an example of a conventional configuration, at a carrier frequency of 5kHz, the phase of the detected zero-phase current can be advanced to the phase of the actual zero-phase current by the phase advance compensation unit 61 at a rotation speed of 50rps, as shown in fig. 8. The zero-phase current suppression unit 64 is not operated. Fig. 9 shows a case where the zero-phase current suppression unit 64 is operated in comparison with the state shown in fig. 8, and it is understood that the zero-phase current is suppressed. Fig. 10 and 11 show the waveforms shown in fig. 8 and 9 with a time axis reduced by 5 times.
Fig. 12 and 13 are diagrams corresponding to fig. 10 and 11 when the rotation speed is 70rps, and it is understood that the zero-phase current is suppressed. From this, it is understood that the effect of the zero-phase current suppression control is expanded to a high rotation speed region.
As described above, according to the present embodiment, the primary-side inverter 21 is connected to the 3 winding terminals of the motor 4 having the open winding structure, and the secondary-side inverter 22 is connected to the remaining 3 winding terminals. The converter 25 supplies dc power obtained by converting the voltage of the ac power supply 27 into dc power to the inverters 21 and 22. The current sensor 30 detects each phase current I flowing through the motor 4u、Iv、IwThe 3-phase/dq 0 converter 34 detects a zero-phase current I flowing between the inverters 21 and 220。
The lead phase compensation unit 61 includes a phase lead element unit 62 and an amplifier 63, and the phase lead element unit 62 sets a detection delay phi of the zero-phase current by expression (2), determines coefficients alpha and T by expressions (3) and (4), and applies the coefficients to the input zero-phase current I0refAnd zero phase current I0The difference of (4) is calculated as expression (5). Further, the amplifier 63 multiplies the current input from the phase lead element 62 by the gain G of expression (6).
Thus, the zero-phase current suppression control can be speeded up without changing the carrier cycle and the motor control cycle, and the increase in the calculation load can be minimized.
Further, since the compressor 2 constituting the air conditioner E is driven by the motor 4, the air conditioner E can be configured at low cost.
(other embodiments)
The noise filter 26 may be set as desired.
The refrigeration cycle apparatus can be applied to apparatuses other than air conditioners such as heat pump water heaters and refrigerators.
The present invention can also be applied to devices other than refrigeration cycle devices.
The embodiments of the present invention have been described above, but the embodiments are presented only as examples and are not intended to limit the scope of the invention. The above-described new embodiments can be implemented in various other ways, and various omissions, substitutions, and changes can be made without departing from the spirit of the invention. The above-described embodiments and modifications thereof are included in the scope and gist of the invention, and are included in the invention described in the claims and the equivalent scope thereof.
Claims (3)
1. An open-winding motor driving device is provided with:
a primary-side inverter connected to 3 winding terminals out of 6 winding terminals in a motor having an open winding structure in which 3-phase windings are independent from each other and the motor has 6 winding terminals;
a secondary side inverter connected to the remaining 3 winding terminals of the motor;
a converter configured to supply a dc power source obtained by converting a voltage of an ac power source into a dc power to the primary-side inverter and the secondary-side inverter;
a phase current detection unit for detecting each phase current flowing through the motor;
a zero-phase current detection unit that detects a zero-phase current flowing between the primary-side inverter and the secondary-side inverter;
a speed detection unit that detects a rotational speed of the motor; and
a control unit that performs PWM control, i.e., pulse width modulation control, on the primary-side inverter and the secondary-side inverter based on the phase current detected by the phase current detection unit and the zero-phase current detected by the zero-phase current detection unit to adjust the zero-phase current amount while driving the motor,
the control unit includes a phase lead compensation unit that calculates the phase of the detected zero-phase current in advance of the rotational speed of the motor, and performs the PWM control based on the result of the calculation and the respective phase currents.
2. The open-winding motor driving device according to claim 1,
the phase lead compensation unit includes a phase lead element unit and a gain correction unit,
the phase lead element unit is configured such that when the detection delay of the zero-phase current is phi, the carrier frequency in the PWM control is fc, the frequency corresponding to the rotational speed of the motor is ω e, and the signal delay of the circuit system is ω e, the phase lead element unit detects the zero-phase current
φ＝3ωe/fc+，
The coefficients a and T are determined by the following equation,
α＝－(sinφ+1)/(sinφ－1)，T＝1/(3ωe√α)
when s is j ω, the following equation is performed for the zero-phase current input,
(1+αTs)/(1+Ts)
the gain correction part multiplies the current input from the phase advance element part by a gain G of the formula < u > A </u > denotes a power,
G＝1/{10＾(log10α/2)}。
3. a refrigeration cycle device is provided with:
the motor with open winding structure, 3-phase winding is independent respectively, and has 6 winding terminals; and
the open-winding motor driving device of claim 1 or 2.
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| JP2019112753A JP7237746B2 (en) | 2019-06-18 | 2019-06-18 | Open winding motor drive device and refrigeration cycle device |
| JP2019-112753 | 2019-06-18 |
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| CN112104283B CN112104283B (en) | 2023-11-28 |
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| JP2019062626A (en) * | 2017-09-26 | 2019-04-18 | 株式会社東芝 | Motor drive system |
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| CN104320027B (en) | 2014-09-25 | 2016-08-24 | 南京航空航天大学 | The control method of the open permanent-magnet electric generator system of parallel winding |
| JP2019062726A (en) | 2017-09-26 | 2019-04-18 | 株式会社東芝 | Motor drive system and wire connection changeover method for open winding structure motor |
| JP7074613B2 (en) | 2018-08-20 | 2022-05-24 | 株式会社東芝 | Open winding motor drive and refrigeration cycle equipment |
| JP7235588B2 (en) | 2019-05-14 | 2023-03-08 | 株式会社Soken | Rotating electric machine control device |
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| JP2008219956A (en) * | 2007-02-28 | 2008-09-18 | Mitsubishi Electric Corp | Motor driving controller and motor |
| JP2009273348A (en) * | 2008-04-07 | 2009-11-19 | Mitsubishi Electric Corp | Motor drive device, refrigerating air conditioner and motor drive method |
| WO2016125557A1 (en) * | 2015-02-06 | 2016-08-11 | 日立オートモティブシステムズ株式会社 | Motor drive device |
| JP2017077061A (en) * | 2015-10-13 | 2017-04-20 | 東洋電機製造株式会社 | Controller and ac motor driver |
| JP2017169251A (en) * | 2016-03-14 | 2017-09-21 | 株式会社明電舎 | Zero-phase current suppression controller of open winding induction machine |
| JP2019062626A (en) * | 2017-09-26 | 2019-04-18 | 株式会社東芝 | Motor drive system |
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| JP7237746B2 (en) | 2023-03-13 |
| CN112104283B (en) | 2023-11-28 |
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