JP4564288B2 - DC motor current control circuit and DC motor having this circuit - Google Patents
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Description
この発明は、直流モータの電流制御回路およびこの回路を具備する直流モータに関し、特に、ＰＷＭ駆動のＨブリッジ回路を採用してモータ駆動電流を精度良く検出し、直流モータを効率よく正転、逆転制御する直流モータの電流制御回路およびこの回路を具備する直流モータに関する。 The present invention relates to a current control circuit for a DC motor and a DC motor including the circuit, and in particular, employs a PWM-driven H-bridge circuit to detect a motor drive current with high accuracy and efficiently forward and reverse the DC motor. The present invention relates to a current control circuit for a direct current motor to be controlled and a direct current motor including the circuit.
直流モータの電流制御回路の従来例を図５を参照して説明する。
図５にＰＷＭ駆動のＨブリッジ回路を示す。Ｈブリッジ回路の第１アーム上側の素子をスイッチング素子Ａ、第１アーム下側の素子をスイッチング素子Ｂ、第２アーム上側の素子をスイッチング素子Ｃ、第２アーム下側の素子をスイッチング素子Ｄとする。第１アームから第２アームに向かって＋向きに通電するときはスイッチング素子Ａをオン、スイッチング素子ＤをＰＷＭ駆動することによりモータ印加電圧若しくはモータ駆動電流を制御し、第２アームから第１アームに向かって−向きに通電するときはスイッチング素子Ｂをオン、スイッチング素子ＣをＰＷＭ駆動することにより、直流モータＭに通電する電流の極性を切り替える構成としている。スイッチング素子Ａとスイッチング素子Ｂのなす第１アームと直流モータＭとの間にシャント抵抗ＲＳを挿入し、シャント抵抗ＲＳの両端に発生する電圧を増幅することにより、直流モータＭに流れるモータ駆動電流を検出している（特許文献１ 参照）。
FIG. 5 shows a PWM-driven H-bridge circuit. The element above the first arm of the H-bridge circuit is switching element A, the element below the first arm is switching element B, the element above the second arm is switching element C, and the element below the second arm is switching element D. To do. When energizing in the positive direction from the first arm toward the second arm, the switching element A is turned on and the switching element D is PWM-driven to control the motor applied voltage or the motor driving current. From the second arm to the first arm When the current is applied in the negative direction, the switching element B is turned on and the switching element C is PWM-driven to switch the polarity of the current supplied to the DC motor M. A motor driving current that flows through the DC motor M by inserting a shunt resistor RS between the first arm formed by the switching element A and the switching element B and the DC motor M and amplifying the voltage generated at both ends of the shunt resistor RS. Is detected (see Patent Document 1).
図５により図示説明される直流モータの電流制御回路は、シャント抵抗ＲＳの両端を差動増幅器ＯＰの両入力端に抵抗Ｒ１、Ｒ２を介して接続してモータ駆動電流を検出している。シャント抵抗ＲＳの両端間に生ずる微小な電圧差に基づいて発生する電流を検出するには、差動増幅器ＯＰに数十倍のゲインを持たせる必要がある。シャント抵抗ＲＳの両端から差動増幅器ＯＰに入力する場合、差動増幅器ＯＰの入力電圧範囲をモータ駆動電圧ＶＢと同程度にする必要があるが、モータ駆動電圧ＶＢを余り大きく設計することができない。 The current control circuit of the DC motor illustrated and described with reference to FIG. 5 detects the motor drive current by connecting both ends of the shunt resistor RS to both input ends of the differential amplifier OP via resistors R1 and R2. In order to detect a current generated based on a small voltage difference generated across the shunt resistor RS, the differential amplifier OP needs to have a gain of several tens of times. When inputting to the differential amplifier OP from both ends of the shunt resistor RS, the input voltage range of the differential amplifier OP needs to be approximately the same as the motor drive voltage VB, but the motor drive voltage VB cannot be designed to be too large. .
ここで、モータ駆動電流ＩＭは、右向き矢印のとき＋電流と称し、左向き矢印のとき−電流と称す。＋電流を流通せしめる場合、スイッチング素子Ｂ、Ｃは何れもオフの状態とし、スイッチング素子Ａをオンの状態とする。そして、スイッチング素子ＤをＰＷＭ駆動とすることにより、モータ駆動電流を＋電流に制御することができる。一方、−電流を流通せしめる場合は、スイッチング素子Ａ、Ｄを何れもオフの状態とし、スイッチング素子Ｂをオンの状態とする。そして、スイッチング素子ＣをＰＷＭ駆動とすることにより、モータ駆動電流を−電流に制御することができる。 Here, the motor drive current IM is referred to as + current when it is a right-pointing arrow, and is referred to as −current when it is a left-pointing arrow. When passing + current, the switching elements B and C are both turned off and the switching element A is turned on. The motor drive current can be controlled to a positive current by switching the switching element D to PWM drive. On the other hand, when the -current is allowed to flow, both the switching elements A and D are turned off and the switching element B is turned on. The motor driving current can be controlled to a negative current by switching the switching element C to PWM driving.
しかし、この制御の場合、微小なモータ駆動電流の制御は困難である。これを図６を参照して説明するに、スイッチング素子は一般にＦＥＴにより構成されるが、ＦＥＴの立ち上がり速度、立ち下がり速度は図６（ａ）に示される如く傾斜していて有限であることが微小なモータ駆動電流の制御を困難にしている。図６（ｂ）を参照するに、例えば＋方向に微小な電流を流通せしめようとする場合、ＰＷＭ駆動されるスイッチング素子Ｄは非常に小さなパルス幅で駆動されるところから、非常に小さな時間のパルス幅の間においてはパルスが正常な高さに迄立ち上がることができないので、結局、微小電流の制御は困難である。 However, in this control, it is difficult to control a minute motor drive current. This will be described with reference to FIG. 6. Although the switching element is generally composed of an FET, the rising speed and falling speed of the FET are inclined and finite as shown in FIG. This makes it difficult to control a minute motor drive current. Referring to FIG. 6B, for example, when a small current is to be circulated in the + direction, the switching element D that is driven by PWM is driven with a very small pulse width. Since the pulse cannot rise to a normal height during the pulse width, it is difficult to control the minute current.
そこで、この発明は、ＰＷＭ変調駆動のＨブリッジ回路を採用してモータ駆動電流を精度良く検出し、直流モータを効率よく正転、逆転制御する直流モータの電流制御回路およびこの回路を具備する直流モータを提供するものである。 Therefore, the present invention employs a PWM modulation drive H-bridge circuit to detect a motor drive current with high accuracy, and to efficiently control forward and reverse rotation of a DC motor, and a DC control circuit equipped with this circuit. A motor is provided.
請求項１：シャント抵抗ＲＳを用いてモータ電流を検出するパルス幅変調（ＰＷＭ）駆動方式のＨブリッジ回路を用いた直流モータの電流制御回路において、シャント抵抗ＲＳの両端を分圧回路より成る２個のアッテネータ２１ａ、２１ｂのそれぞれの一端に接続し、アッテネータ２１ａ、２１ｂの他端とシャント抵抗ＲＳの何れか一方の側との間にアッテネータ駆動回路２２を接続し、アッテネータ駆動回路２２をこれが接続されている側のアッテネータの分圧回路の中点の電圧が常にゼロとなるように構成し、２個のアッテネータ２１ａ、２１ｂの分圧回路それぞれの中点ａ、ｂの電圧を差動増幅器２３で増幅してモータ電流ＩＭを検出する直流モータの電流制御回路を構成した。 In a current control circuit of a direct current motor using a pulse width modulation (PWM) drive type H bridge circuit that detects a motor current using a shunt resistor RS, both ends of the shunt resistor RS are formed by voltage dividing circuits. number of attenuator 21a, and connected to one end of each of 21b, connect the attenuator driver circuit 22 between either side of the attenuator 21a, the other end of the 21b and the shunt resistor RS, which connects the attenuator driver circuit 22 The voltage at the midpoint of the voltage divider circuit of the attenuator on the side where the current is applied is always zero. A current control circuit for a DC motor that detects the motor current IM by amplification is configured.
また、請求項２：請求項１に記載される直流モータの電流制御回路を具備する直流モータを構成した。 Also, according to claim 2 constituted a DC motor having a current control circuit for a DC motor as claimed in claim 1.
この発明によれば、差動増幅器に入力する電圧に含まれる矩形波成分が減少して、同相信号除去比が高い部分を使用することができるので、精度の良い電流検出をすることができる。そして、アッテネータがシャント抵抗と差動増幅器との間に接続されるところからシャント抵抗両端の電圧を小さくし、このことに基づいてモータ駆動電圧を大きく設計することができる。 According to the present invention, the rectangular wave component included in the voltage input to the differential amplifier is reduced, and a portion having a high in-phase signal rejection ratio can be used, so that accurate current detection can be performed. . The voltage across the shunt resistor can be reduced from where the attenuator is connected between the shunt resistor and the differential amplifier, and based on this, the motor drive voltage can be designed to be large.
発明を実施するための最良の形態を図１を参照して説明する。
図１において、１はモータ駆動部を示し、Ｈブリッジ回路１１，ＰＷＭ駆動回路１２、制御器１３より成る。
このＨブリッジ回路１１は、第１アーム上側の素子をスイッチング素子Ａとし、第１アーム下側の素子をスイッチング素子Ｂとし、第２アーム上側の素子をスイッチング素子Ｃとし、第２アーム下側の素子をスイッチング素子Ｄとしている。スイッチング素子Ａ、Ｂ、Ｃ、Ｄは電界効果トランジスタＦＥＴにより構成している。そして、第１アームの上側のスイッチング素子Ａと下側スイッチング素子Ｂの相互接続点と、第２アームの上側のスイッチング素子Ｃと下側スイッチング素子Ｄの相互接続点との間に、シャント抵抗ＲＳと直流モータＭの直列接続経路を接続している。＋ＶＢは第１アームと第２アームの上側相互接続点に供給されるモータ駆動電圧を示す。第１アームと第２アームの下側相互接続点は接地している。
The best mode for carrying out the invention will be described with reference to FIG.
In FIG. 1, reference numeral 1 denotes a motor drive unit, which includes an H bridge circuit 11, a PWM drive circuit 12, and a controller 13.
The H bridge circuit 11 has an element on the upper side of the first arm as a switching element A, an element on the lower side of the first arm as a switching element B, an element on the upper side of the second arm as a switching element C, and an element on the lower side of the second arm. The element is a switching element D. The switching elements A, B, C, and D are composed of field effect transistors FET. The shunt resistor RS is connected between the interconnection point of the upper switching element A and the lower switching element B of the first arm and the interconnection point of the upper switching element C and the lower switching element D of the second arm. And a series connection path of the DC motor M are connected. + VB represents a motor drive voltage supplied to the upper interconnection point of the first arm and the second arm. The lower interconnection point of the first arm and the second arm is grounded.
ＰＷＭ駆動回路１２は、スイッチング素子Ａ、Ｂ、Ｃ、Ｄそれぞれの制御電極に接続する出力端子＊A 、＊B 、＊C 、＊D を有している。
制御器１３は、後で説明されるモータ駆動電流検出部２の出力する検出電流と指令値とにより決まる制御信号に基づいて、ＰＷＭ駆動回路１２の出力を制御し、スイッチング素子Ａ、Ｂ、Ｃ、Ｄの制御電極に対する出力を決定している。
モータ駆動電流検出部２は、分圧回路より成る２個のアッテネータ２１ａ、２１ｂと、演算増幅器より成るアッテネータ駆動回路２２と、差動増幅器２３とより成る。アッテネータ２１ａは、２個の抵抗Ｒ１、Ｒ２を直列接続した第１分圧回路より成り、アッテネータ２１ｂは２個の抵抗Ｒ３、Ｒ４を直列接続した第２分圧回路より成る。第１分圧回路の一方の端子はシャント抵抗ＲＳの端子の第１アーム側に接続すると共に、第２分圧回路の一方の端子はシャント抵抗ＲＳの端子の直流モータ側に接続している。第１分圧回路と第２分圧回路の他方の端子は相互接続してアッテネータ駆動回路２２の出力の点ｃに接続している。ここで、アッテネータ駆動回路２２の入力はシャント抵抗ＲＳの端子の第１アーム側に接続している。第１分圧回路の２個の抵抗Ｒ１、Ｒ２の中点ａと第２分圧回路の２個の抵抗Ｒ３、Ｒ４の中点ｂは、差動増幅器２３の各別の入力に接続している。差動増幅器２３の出力は加算器３の−端子に供給される。加算器３の＋端子には指令値が供給される。加算器３の計算結果はモータ駆動部１の制御器１３に入力される。
The PWM drive circuit 12 has output terminals * A , * B , * C , and * D that are connected to the control electrodes of the switching elements A, B, C, and D, respectively.
The controller 13 controls the output of the PWM drive circuit 12 based on a control signal determined by a detected current output from the motor drive current detector 2 and a command value, which will be described later, and switching elements A, B, C , D are determined for the control electrodes.
The motor drive current detection unit 2 includes two attenuators 21 a and 21 b formed of a voltage dividing circuit, an attenuator drive circuit 22 formed of an operational amplifier, and a differential amplifier 23. The attenuator 21a is composed of a first voltage dividing circuit in which two resistors R1 and R2 are connected in series, and the attenuator 21b is composed of a second voltage dividing circuit in which two resistors R3 and R4 are connected in series. One terminal of the first voltage dividing circuit is connected to the first arm side of the terminal of the shunt resistor RS, and one terminal of the second voltage dividing circuit is connected to the DC motor side of the terminal of the shunt resistor RS. The other terminals of the first voltage dividing circuit and the second voltage dividing circuit are connected to each other and connected to the output point c of the attenuator driving circuit 22. Here, the input of the attenuator driving circuit 22 is connected to the first arm side of the terminal of the shunt resistor RS. The middle point a of the two resistors R1 and R2 of the first voltage dividing circuit and the middle point b of the two resistors R3 and R4 of the second voltage dividing circuit are connected to respective different inputs of the differential amplifier 23. Yes. The output of the differential amplifier 23 is supplied to the minus terminal of the
実施例においては、スイッチング素子Ａとスイッチング素子Ｄとを一方の素子対とし、スイッチング素子Ｂとスイッチング素子Ｃとを他方の素子対とする。これにより、対をなすスイッチング素子は同時にオン、オフすることになる。即ち、スイッチング素子Ａがオンである場合、スイッチング素子Ｄもオンとなる。スイッチング素子Ａ、Ｂ、Ｃ、Ｄのオン、オフ、デューティの関係を示すと図２の如くになる。ここで、図示されないスイッチング素子Ａ、Ｄのオン時間と、スイッチング素子Ｂ、Ｃのオン時間とが等しいとき、即ち、デューティ５０％のときは、モータ駆動電流ＩＭ＝０となる。そして、スイッチング素子Ａ、Ｄのオン時間が、スイッチング素子Ｂ、Ｃのオン時間と比較して長いとき、即ち、デューティが５０％より大きい図２（ａ）、（ｂ）のときはモータ駆動電流ＩＭの向きは＋となる。逆に、スイッチング素子Ａ、Ｄのオン時間が、スイッチング素子Ｂ、Ｃのオン時間と比較して短いとき、即ち、デューティが５０％より小さい図２（ｃ）ときはモータ駆動電流ＩＭの向きは−となる。 In the embodiment, the switching element A and the switching element D are set as one element pair, and the switching element B and the switching element C are set as the other element pair. As a result, the paired switching elements are simultaneously turned on and off. That is, when the switching element A is on, the switching element D is also on. FIG. 2 shows the relationship between on, off, and duty of the switching elements A, B, C, and D. Here, when the ON times of the switching elements A and D (not shown) and the ON times of the switching elements B and C are equal, that is, when the duty is 50%, the motor drive current IM = 0. When the ON times of the switching elements A and D are longer than the ON times of the switching elements B and C, that is, when the duty is greater than 50% in FIGS. The direction of IM is +. Conversely, when the on-time of the switching elements A and D is shorter than the on-time of the switching elements B and C, that is, when the duty is smaller than 50% in FIG. -.
スイッチング素子ＡとＢ、或いはスイッチング素子ＣとＤが同時にオンとなると、モータ電源が短絡されるところから、スイッチング素子Ａ、Ｂ、Ｃ、Ｄを構成する電界効果トランジスタＦＥＴには、スイッチング素子ＡとＢとの間、或いはスイッチング素子ＣとＤとの間には必ず同時にオフの時間、即ち、デッドタイムが設定される。この様な駆動パターンでＨブリッジを駆動するアッテネータ駆動回路を説明する。
直流モータＭに大きな駆動力を発生させようとする場合、直流モータＭの発生する駆動力は流通する電流に比例するので、直流モータＭに大きな電流を流通する必要がある。直流モータＭに流れる電流ＩＭは、当該モータに印加されるモータ駆動電圧ＶＢで決まるところから、結局、大きなモータ駆動電圧ＶＢを必要とすることになる。この様な事情から、差動増幅器２３の入力電圧範囲より大きな電圧で直流モータＭを駆動したいという必要に迫られる場合もある。しかし、この様な過大な電圧で直流モータＭを駆動した場合、シャント抵抗ＲＳの両端に直接に差動増幅器２３を接続すると当然に差動増幅器２３は損傷する。そこで、図１の実施例においては、シャント抵抗ＲＳの両端と差動増幅器２３の入力との間に２個のアッテネータ２１ａ、２１ｂを挿入接続することで、差動増幅器２３の入力電圧範囲より大きな電圧で直流モータＭを駆動する構成を採用している。
When the switching elements A and B or the switching elements C and D are simultaneously turned on, the motor power supply is short-circuited, so that the field effect transistor FET constituting the switching elements A, B, C, and D includes the switching element A and An OFF time, that is, a dead time is always set between B and the switching elements C and D. An attenuator drive circuit for driving the H bridge with such a drive pattern will be described.
When a large driving force is to be generated in the DC motor M, the driving force generated by the DC motor M is proportional to the flowing current, so that a large current needs to flow through the DC motor M. Since the current IM flowing through the DC motor M is determined by the motor drive voltage VB applied to the motor, a large motor drive voltage VB is eventually required. Under such circumstances, there is a case where it is necessary to drive the DC motor M with a voltage larger than the input voltage range of the differential amplifier 23. However, when the DC motor M is driven with such an excessive voltage, if the differential amplifier 23 is directly connected to both ends of the shunt resistor RS, the differential amplifier 23 is naturally damaged. Therefore, in the embodiment of FIG. 1, two attenuators 21 a and 21 b are inserted and connected between both ends of the shunt resistor RS and the input of the differential amplifier 23, so that the input voltage range of the differential amplifier 23 is larger. A configuration in which the DC motor M is driven by voltage is adopted.
ところで、図１においてアッテネータ駆動回路２２の出力ｃ点をＧＮＤとしたときの、差動増幅器２３の入力ａ点およびｂ点の波形を示すと、図３（ｂ）、（ｃ）に示される如くになる。なお、図３（ａ）は直流モータＭの両端の電圧を示す。即ち、差動増幅器２３の入力ａ点およびｂ点の電圧は、アッテネータ２１により、下記の通りになる。
Ｖａ＝ＶS１・ＲＢ／（ＲＡ＋ＲＢ）
Ｖｂ＝ＶS２・ＲＢ／（ＲＡ＋ＲＢ）
但し、ＲＡ＝Ｒ１＝Ｒ３、ＲＢ＝Ｒ２＝Ｒ４
この両電圧Ｖａ、Ｖｂを差動増幅器２３に入力すると、電圧Ｖａ、Ｖｂは矩形波であるところから、高い周波数成分を含んでおり、同相信号除去比が悪化して正常な差動増幅結果は得られない。
By the way, when the output point c of the attenuator driving circuit 22 in FIG. 1 is set to GND, the waveforms at the points a and b of the differential amplifier 23 are shown as shown in FIGS. 3B and 3C. become. FIG. 3A shows the voltage across the DC motor M. That is, the voltages at the points a and b of the differential amplifier 23 are as follows by the
Va = V S 1 · RB / (RA + RB)
Vb = V S 2 · RB / (RA + RB)
However, RA = R1 = R3, RB = R2 = R4
When these voltages Va and Vb are input to the differential amplifier 23, the voltages Va and Vb are rectangular waves, and therefore contain high frequency components, and the common-mode signal rejection ratio deteriorates and normal differential amplification results are obtained. Cannot be obtained.
そこで、アッテネータ駆動回路２２の出力ｃ点にアッテネータ２１ｂを接続する。そして、アッテネータ駆動回路２２を反転増幅器とし、ゲイン＝−ＲＢ／ＲＡに設定する。図４を参照するに、この通りに設定することにより、ａ点の電圧Ｖａは図４（ｂ）に示される如く常に０とし、ｂ点の電圧Ｖｂを図４（ｃ）に示される如くＩＭ・ＲＳとすることができる。これにより、差動増幅器２３に入力される電圧に含まれる矩形波成分が減少するところから、高い周波数成分は減少する。従って、同相信号除去比が高い部分を使用することができるので、精度の良い電流検出をすることができ、リニアリティが保たれる。そして、直流モータの電流制御回路の以上の実施例は、アッテネータ２１ａ、２１ｂがシャント抵抗ＲＳと差動増幅器２３との間に接続されるところからシャント抵抗の両端の電圧は小さくなり、これに基づいてモータ駆動電圧ＶＢを大きく設計することができる。これにより、電気的時定数の大きな直流モータＭでも応答速度を上げることができる。 Therefore, the attenuator 21b is connected to the output c point of the attenuator driving circuit 22. Then, the attenuator driving circuit 22 is an inverting amplifier, and gain = −RB / RA is set. Referring to FIG. 4, by setting in this way, the voltage Va at the point a is always 0 as shown in FIG. 4B, and the voltage Vb at the point b is IM as shown in FIG. 4C. -It can be RS. Thereby, since the rectangular wave component contained in the voltage input to the differential amplifier 23 decreases, the high frequency component decreases. Therefore, a portion having a high in-phase signal rejection ratio can be used, so that accurate current detection can be performed and linearity is maintained. The above embodiment of the current control circuit of the DC motor is based on the fact that the voltage across the shunt resistor is reduced since the attenuators 21a and 21b are connected between the shunt resistor RS and the differential amplifier 23. Thus, the motor drive voltage VB can be designed large. As a result, the response speed can be increased even with a DC motor M having a large electrical time constant.
１ モータ駆動部 １１ Ｈブリッジ回路
１２ ＰＷＭ駆動回路 １３ 制御器
Ａ、Ｂ、Ｃ、Ｄ スイッチング素子 ＲＳ シャント抵抗
Ｍ 直流モータ ＶＢ モータ駆動電圧
＊A 、＊B 、＊C 、＊D 出力端子 ２ モータ駆動電流検出部
２１ アッテネータ ２２ アッテネータ駆動回路
２３ 差動増幅器 ３ 加算器
ａ 第１分圧回路の２個の抵抗Ｒ１、Ｒ２の中点
ｂ 第２分圧回路の２個の抵抗Ｒ３、Ｒ４の中点
ＩＭ モータ駆動電流
DESCRIPTION OF SYMBOLS 1 Motor drive part 11 H bridge circuit 12 PWM drive circuit 13 Controller A, B, C, D Switching element RS Shunt resistance M DC motor VB Motor drive voltage * A , * B , * C , * D output terminal 2 Motor drive
Claims (2)
シャント抵抗の両端を分圧回路より成る２個のアッテネータのそれぞれの一端に接続し、
２個のアッテネータのそれぞれの他端とシャント抵抗の何れか一方の側の間にアッテネータ駆動回路を接続し、当該アッテネータ駆動回路をこれが接続されている側のアッテネータの分圧回路の中点の電圧が常にゼロとなるように構成し、
２個のアッテネータの分圧回路それぞれの中点の電圧を差動増幅器で増幅してモータ電流を検出する、
ことを特徴とする直流モータの電流制御回路。 In a current control circuit for a DC motor using an H-bridge circuit of a pulse width modulation (PWM) drive system that detects a motor current using a shunt resistor,
Connect both ends of the shunt resistor to one end of each of the two attenuators consisting of a voltage divider,
Connect the attenuator driver circuit between the two respective other end either side of the shunt resistor of the attenuator, the voltage divider circuit of the midpoint voltage of the side of the attenuator the attenuator driver circuit which is connected Is always set to zero ,
The motor voltage is detected by amplifying the midpoint voltage of each of the voltage divider circuits of the two attenuators using a differential amplifier.
A current control circuit for a direct current motor.
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| JP2004183401A JP4564288B2 (en) | 2004-06-22 | 2004-06-22 | DC motor current control circuit and DC motor having this circuit |
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| JP2004183401A JP4564288B2 (en) | 2004-06-22 | 2004-06-22 | DC motor current control circuit and DC motor having this circuit |
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| JP4564288B2 true JP4564288B2 (en) | 2010-10-20 |
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| JP4607075B2 (en) * | 2006-09-05 | 2011-01-05 | 三菱電機株式会社 | DC motor current detection device and galvano scanner system |
| JP2008271628A (en) * | 2007-04-16 | 2008-11-06 | Jtekt Corp | Current sensing circuit |
| US7477082B2 (en) * | 2007-05-15 | 2009-01-13 | Freescale Semiconductor, Inc. | Method and circuit for driving H-bridge that reduces switching noise |
| JP2016164490A (en) * | 2015-03-06 | 2016-09-08 | キヤノン株式会社 | Current detector, driving device, and industrial machine |
| JP6570671B2 (en) | 2018-02-01 | 2019-09-04 | 油研工業株式会社 | Bipolar current control drive circuit for inductive load |
| CN110971159B (en) * | 2019-11-13 | 2022-02-08 | 齐鲁工业大学 | High-power speed regulation and protection circuit system of H-bridge direct-current motor |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62115905A (en) * | 1985-11-15 | 1987-05-27 | Hitachi Micro Comput Eng Ltd | Electronic switch |
| JP2002051540A (en) * | 2000-07-27 | 2002-02-15 | Fdk Corp | Non-insulating step-down dc-dc converter |
| JP2002238290A (en) * | 2001-02-13 | 2002-08-23 | Mitsubishi Electric Corp | Motor drive control apparatus |
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Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62115905A (en) * | 1985-11-15 | 1987-05-27 | Hitachi Micro Comput Eng Ltd | Electronic switch |
| JP2002051540A (en) * | 2000-07-27 | 2002-02-15 | Fdk Corp | Non-insulating step-down dc-dc converter |
| JP2002238290A (en) * | 2001-02-13 | 2002-08-23 | Mitsubishi Electric Corp | Motor drive control apparatus |
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