JP3732176B2 - Multiplexer - Google Patents

Description

【００１８】
【数２】

【００１９】
前述の（２）式より、第１のサーキュレータ（ＣＩＲ１）の第２の端子Ｔ_２１３、並びに、第２のサーキュレータ（ＣＩＲ２）の第２の端子Ｔ_２２３には、それぞれ（−ｊＥ_ｉｉ／√２）の電圧が出力され、これらの電圧は、電力合成器（ＴＱ_２３）で合成されて端子Ｔ_２３から出力される。
この端子Ｔ_２３から出力される電圧は、下記（３）で求めることができ、端子Ｔ_２３からは、（−Ｅ_ｉｉ）の電圧が出力される。即ち、図５に示す端子Ｔ_２２に電圧を加えた時に、同じ電圧が、端子Ｔ_２３から出力される。
【００２０】
【数３】

【００２１】
図５に示す端子Ｔ_２１に入力される電圧は、第１の電力分配器（ＴＱ_２１）で２分配され、第１のサーキュレータ（ＣＩＲ１）の第１の端子Ｔ_２１１、並びに、第２のサーキュレータ（ＣＩＲ２）の第１の端子Ｔ_２２１に入力され、それぞれ第１のサーキュレータ（ＣＩＲ１）の第２の端子Ｔ_２１２、並びに、第２のサーキュレータ（ＣＩＲ２）の第２の端子Ｔ_２２２から出力される。
この出力電圧は、第２の電力分配器（ＴＱ_２２）で合成された後、第２群の帯域通過フィルタ（Ｂ２，Ｂ４，…，Ｂｎ−１）で反射され、再度第２の電力分配器（ＴＱ_２２）に入力され、前述と同様にして、端子Ｔ_２３から出力される。
即ち、図５に示す端子Ｔ_２１に電圧を加えた時に、同じ電圧（あるいは、電流）が、端子Ｔ_２３から出力される。
接続ケーブルの長さ、および、Ｑ変成器型の電力分配器（ＴＱ_２１，ＴＱ_２２）と電力合成器（ＴＱ_２３）の特性が同一特性であれば、図５に示すサーキュレータ（ＣＩＲ１，ＣＩＲ２）の並列運転は、１個のサーキュレータと等価になる。
【００２２】
しかしながら、図５に示すサーキュレータ（ＣＩＲ１，ＣＩＲ２）に入力される送信波の電圧（あるいは、電流）は、１／√２にすることができるので、各サーキュレータ（ＣＩＲ１，ＣＩＲ２）を通過する送信波の電力を、１／２にすることができる。
このことは、電力容量が２倍になること意味するので、相互変調波（ＩＭ３）が発生するレベルを、３ｄＢ増加させたことになる。
即ち、図１に示す合波器において、相互変調波（ＩＭ３）が発生する送信波の電力レベルをＰ（Ｗ）とすると、本実施の形態では、相互変調波（ＩＭ３）が発生する送信波の電力レベルを、２×Ｐ（Ｗ）とすることができ、入力される送信波の電力が大きい場合でも、相互変調波（ＩＭ３）の発生を低減することが可能となる。
入力される送信波の電力が、より大電力の場合には、並列運転させるサーキュレータの数を、３，４，…，ｎと成し、それに合わせて、第１の電力分配器（ＴＱ_２１）と第２の電力分配器（ＴＱ_２２）での分配数、および電力合成器（ＴＱ_２３）での合波数を設定すればよい。
【００２３】
本発明の実施の形態において、並列運転させるサーキュレータの数を４とした場合の、サーキュレータ（ＣＲ１〜ＣＲＩ４）、第１の電力分配器（ＴＱ_４１）、第２の電力分配器（ＴＱ_４２）、および電力合成器（ＴＱ_４３）の構成を図６に示す。
図６に示す合波器では、電力容量が４倍になるので、相互変調波（ＩＭ３）が発生するレベルを、６ｄＢ増加させることができる。
また、分配数がｎの場合の、電力分配器（ＴＱ_４１，ＴＱ_４２）、および電力合成器（ＴＱ_４３）の〔Ｓ〕マトリクス（〔Ｓｎ〕）を下記（４）式に示す。
【００２４】
【数４】

【００２５】
以上、本発明者によってなされた発明を、前記実施の形態に基づき具体的に説明したが、本発明は、前記実施の形態に限定されるものではなく、その要旨を逸脱しない範囲において種々変更可能であることは勿論である。
【００２６】
【発明の効果】
本願において開示される発明のうち代表的なものによって得られる効果を簡単に説明すれば、下記の通りである。
本発明によれば、従来の合波器に比して、小型化を図り、コストを低減するとともに、良好な電気的特性が得られる合波器を提供することが可能となる。
【図面の簡単な説明】
【図１】本発明の基本となる合波器の概略構成を示すブロック図である。
【図２】図１に示す第２群の帯域通過フィルタ（Ｂ２，Ｂ４，Ｂ６）の減衰特性と、反射減衰量を示すグラフである。
【図３】図１に示す第１群の帯域通過フィルタ（Ｂ１，Ｂ３，…，Ｂｎ）の減衰特性を示すグラフである。
【図４】図１に示す各入力端子（Ｔ_１〜Ｔ_ｎ）と、図１に示す出力端子（Ｔ_００）との間の伝送特性を示すグラフである。
【図５】本発明の実施の形態の合波器の概略構成を示すブロック図である。
【図６】本発明の実施の形態において、並列運転させるサーキュレータの数を４とした場合の、サーキュレータ、第１の電力分配器、第２の電力分配器、および電力合成器の構成を示すブロック図である。
【図７】従来のＣＩＢ型合波器の概略構成を示すブロック図である。
【図８】従来のスターポイント型合波器の概略構成を示すブロック図である。
【符号の説明】
Ｈ１１，Ｈ１２，Ｈ２１，Ｈ２２，Ｈｎ１，Ｈｎ２…ハイブリッド回路、ＣＩＲ，ＣＲＩ１〜ＣＲＩ４…サーキュレータ、ＴＱ_２１，ＴＱ_２２，ＴＱ_４１，ＴＱ_４２…電力分配器、ＴＱ_２３，ＴＱ_４３…電力合成器、Ｂ１〜Ｂｎ，ＢＦ１１、ＢＦ１２，ＢＦ２１，ＢＦ２２，ＢＦｎ１，ＢＦｎ２…帯域通過フィルタ、Ｒ…無反射終端器。[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a multiplexer, and more particularly to a multiplexer that is used when multiplexing transmission power in a mobile communication field such as terrestrial digital television and WCDMA.
[0002]
[Prior art]
A CIB type multiplexer shown in FIG. 7 is known as a conventionally used multiplexer (also referred to as an antenna sharing device).
As shown in FIG. 7, in the conventional CIB type multiplexer, the fourth terminal (T ₄ ) and the first terminal (T ₁ ) of each adjacent second hybrid circuit (H12, H22,..., Hn2). Are connected to each other, the first terminal (T ₁ ) of one second hybrid circuit (H12) at both ends is connected to the non-reflective terminator (R), and the other second hybrid at both ends is connected The fourth terminal (T ₄ ) of the circuit (Hn2) serves as an output end and is connected to, for example, an antenna (not shown).
Further, each of the second hybrid circuit (H12, H22, ..., Hn2 ) and a second terminal of the _{(T 2),} the first hybrid circuit (H11, H21, ..., Hn1 ) a second terminal of the _(T 2) Are connected to band-pass filters (BF11, BF21,..., BFn1) that pass transmission waves of the respective channels, and third terminals of the respective second hybrid circuits (H12, H22,..., Hn2). _{(T 3)} and the first hybrid circuit (H11, H21, ..., Hn1 ) between the third terminal of _{(T 3),} band pass filter for passing a transmission wave of each channel, respectively (BF12, BF22 , BFn2) are connected.
Furthermore, the first terminal (T ₁ ) of each first hybrid circuit (H11, H21,..., Hn1) is connected to a transmitter that outputs a transmission wave of each channel, and each first hybrid circuit (H11, The fourth terminals (T ₄ ) of H21,..., Hn1) are connected to the non-reflecting terminator (R), respectively.
Here, each of the first and second hybrid circuits and each bandpass filter constitutes a constant impedance bandpass filter that passes the transmission wave of each channel.
[0003]
Hereinafter, the operation of the CIB multiplexer shown in FIG. 7 will be briefly described.
The transmission wave of the channel CH1 input from the first terminal (T ₁ ) of the first hybrid circuit (H11) passes through the bandpass filters (BF11, BF12) and is input to the second hybrid circuit (H12). , And output from the fourth terminal (T ₄ ) of the second hybrid circuit (H12).
The transmission wave of the channel CH1 output from the second hybrid circuit (H12) is input to the second hybrid circuit (H22) and totally reflected by the bandpass filters (BF21, BF22), and then the second hybrid circuit ( H22) from the fourth terminal (T ₄ ). Thereafter, similarly, the signal is output from the fourth terminal (T ₄ ) of the second hybrid circuit (Hn2).
As a conventionally used multiplexer (also referred to as an antenna sharing device), a star point type multiplexer shown in FIG. 8 is known.
As shown in FIG. 8, the conventional star point type multiplexer is configured by connecting, in parallel, band pass filters (B1, B2,..., Bn) that pass the transmission waves of the respective channels to the output terminal To. The
[0004]
The prior art document information related to the present invention includes the following.
[Patent Document 1]
Japanese Patent Application No. 2001-186833 [0005]
[Problems to be solved by the invention]
The above-described CIB type multiplexer shown in FIG. 7 requires n sets (n × 2) of high-performance band-pass filters (that is, high selectivity type band-pass filters) and hybrid circuits. There are problems that the overall size of the waver increases and the product cost increases.
On the other hand, since the star point type multiplexer shown in FIG. 8 may have n band pass filters, the overall size of the multiplexer can be reduced as compared with the CIB type multiplexer shown in FIG. In addition, the product cost can be reduced.
However, when combining adjacent channel signals, even if a high-performance band-pass filter is used, there is a problem that inter-circuit interference occurs due to a small guard band, and good electrical characteristics cannot be obtained. is there.
[0006]
The present invention has been made to solve the above-described problems of the prior art, and the object of the present invention is to achieve downsizing, cost reduction, and good performance as compared with a conventional multiplexer. An object of the present invention is to provide a multiplexer that can obtain electrical characteristics.
The above and other objects and novel features of the present invention will become apparent from the description of this specification and the accompanying drawings.
[0007]
[Means for Solving the Problems]
Of the inventions disclosed in this application, the outline of typical ones will be briefly described as follows.
That is, the present invention includes a circulator that outputs the power input to the first terminal from the second terminal and outputs the power input to the second terminal from the third terminal, and the circulator includes the circulator. the first terminal, and connect the odd-number or first group of m passing the transmission waves of every other channel of one number even numbered (m ≧ 2) pieces of the band-pass filter, and said second Basically, a second group of n (n ≧ 2) band-pass filters that allow every other channel transmission wave of the odd-numbered or even-numbered number to pass through are connected to the two terminals.
In this basic multiplexer, a high selectivity type bandpass filter is used as the second group of n (n ≧ 2) bandpass filters, so that m (m ≧ m ≧ 1) of the first group is used. 2) A low-selectivity type (passband having a wide bandwidth) can be used as each bandpass filter.
[0008]
Therefore, according to this basic multiplexer, the m (m ≧ 2) band-pass filters of the first group and the n (n ≧ 2) band-pass filters of the second group are the same. For example, when m = n, since n / 2 high-cost band-pass filters with high cost may be used, the size can be reduced compared to the CIB multiplexer shown in FIG. It is possible to reduce costs.
In addition, each of the m (m ≧ 2) band-pass filters of the first group and the n (n ≧ 2) band-pass filters of the second group, every other odd number or even number. Since the transmission waves of the two channels are allowed to pass through, no inter-circuit interference occurs between adjacent channels as in the conventional star point type multiplexer, so that good electrical characteristics can be obtained.
[0009]
However, in this basic multiplexer, when the input power is large, the intermodulation wave (IM3) is combined with the synthesized transmission wave output from the third terminal of the circulator due to the minute non-linearity of the circulator. ) Occurs.
Therefore, in the multiplexer according to the present invention, k (k ≧ 2) circulators are used, and the outputs of the m (m ≧ 2) band-pass filters of the first group are k-distributed to obtain the k pieces. Input to the first terminals of the circulators of the second group, distribute the outputs of the n (n ≧ 2) band-pass filters of the second group into k, and input to the second terminals of the k circulators, Further, the output from the third terminal is synthesized and output.
That is, the multiplexer of the present invention is characterized in that k circulators are operated in parallel.
In general, since the intermodulation wave is proportional to the square of the input power, in the above-described basic multiplexer, when the input power is doubled, the intermodulation wave is quadrupled. Then, even if the input power is doubled by operating two circulators in parallel, the power input to each circulator is (1/2). It becomes the same as when
DETAILED DESCRIPTION OF THE INVENTION
Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.
Note that components having the same function are denoted by the same reference symbols throughout the drawings for describing the embodiment, and the repetitive description thereof will be omitted.
[Configuration of a multiplexer serving as a basis of the present invention]
FIG. 1 is a block diagram showing a schematic configuration of a multiplexer which is the basis of the present invention. Incidentally, in FIG. 1, CH1 through CHn indicates the channel number of consecutive television _signals, f 1 ~f _n indicates the center frequency of each bandpass filter.
In the figure, the circulator (CIR) outputs the power input to the first terminal (T ₀₁ ) to the second terminal (T ₀₂ ) and the power input to the second terminal (T ₀₂ ). Output to the third terminal (T ₀₀ ).
The first terminal (T ₀₁ ) is connected to a first group of band-pass filters (B 1, B 3,..., Bn) connected in a star-point form, and the second terminal (T ₀₂ ) is connected to the first terminal (T ₀₁ ). A second group of bandpass filters (B2, B4,..., Bn-1) connected in a star point type are connected.
Each of the bandpass filters (B1, B3,..., Bn) of the first group of bandpass filters passes the transmission wave of the odd-numbered channel, so that between adjacent channels (for example, between channel CH1 and channel CH3) Inter-circuit interference does not occur.
[0011]
Each of the band-pass filters (B2, B4,..., Bn-1) of the second group of band-pass filters passes the transmission wave of the even-numbered channel, so that it is between adjacent channels (for example, channel CH2 and channel CH4). Inter-circuit interference does not occur.
The first group of band-pass filters (B1, B3,..., Bn) pass the transmission waves of the even-numbered channels, and the second group of band-pass filters (B2, B4,..., Bn-1). The transmission wave of the odd-numbered channel may be passed.
In the multiplexer shown in FIG. 1, the transmission wave of each channel that has passed through the second group of bandpass filters (B2, B4,..., Bn-1) is transmitted to the second terminal (T ₀₂ ) of the circulator (CIR). And output from the third terminal (T ₀₀ ).
In addition, the transmission wave of each channel that has passed through the first group of bandpass filters (B1, B3,..., Bn) is input to the first terminal (T ₀₁ ) of the circulator (CIR), and the second terminal ( Although output from T _02), the second group of bandpass filters (B2, B4, ..., are reflected by Bn-1), is input again the second terminal _{(T 02),} the third terminal (T ₀₀ ).
[0012]
FIG. 2 is a graph showing attenuation characteristics and return loss of the second group of bandpass filters (B2, B4, B6) shown in FIG. The solid line in the figure shows the attenuation characteristic, and the two-dot chain line shows the return loss.
As can be seen from the attenuation characteristics of FIG. 2, the second group of bandpass filters (B2, B4, B6) have an attenuation characteristic in which the passband is narrower than the channel width and has a steep fall, that is, high selection. A degree-type bandpass filter is used.
In this embodiment, the channel width is 6 MHz, and the passband of the bandpass filter is 5.6 MHz.
A bandpass filter having such characteristics can be realized using a HE mode dielectric resonator, a TE _01δ mode dielectric resonator, a rectangular waveguide resonator, or a circular waveguide resonator. , The cost will be higher.
[0013]
FIG. 3 is a graph showing the attenuation characteristics of the first group of bandpass filters (B1, B3,..., Bn) shown in FIG.
As can be seen from the attenuation characteristic of FIG. 3, the first group of bandpass filters (B1, B3,..., Bn) has an attenuation characteristic in which the passband is wider than the channel width and the fall is gentle. A low selectivity type bandpass filter is used.
A bandpass filter having such characteristics can be realized by using a coaxial resonator or a TM _01δ mode dielectric resonator, and can be relatively small and manufactured at low cost.
The transmission wave of each channel that has passed through the first group of band-pass filters (B1, B3,..., Bn) is input to the first terminal (T ₀₁ ) of the circulator (CIR) and the second terminal (T ₀₂ ) And reflected by the second group of bandpass filters (B2, B4,..., Bn−1).
At this time, the transmission wave of each channel that has passed through the first group of bandpass filters (B1, B3,..., Bn) has the adjacent channel component in the second group of bands, according to the return loss characteristics shown in FIG. Absorbed by the pass filters (B2, B4,..., Bn-1).
[0014]
For example, the channel CH2 component in the transmission wave of the channel CH1 that has passed through the bandpass filter B1 is absorbed by the bandpass filter B2.
Similarly, the channel CH2 component in the channel CH3 transmission wave is absorbed by the bandpass filter B2, and the channel CH4 component in the channel CH3 transmission wave is absorbed by the bandpass filter B4.
Therefore, as shown in FIG. 4, the transmission wave of each channel that has passed through the first group of bandpass filters (B1, B3,..., Bn) output from the third terminal (T ₀₀ ) of the circulator is The pass band is narrower than the channel width, and has an attenuation characteristic with a sharp fall.
FIG. 4 is a graph showing the transmission characteristics of the multiplexer according to the present embodiment. The input terminals (T _{1 to} T _n ) shown in FIG. 1 and the output terminals (T ₀₀ ) shown in FIG. It is a graph which shows the transmission characteristic between.
In the present embodiment, the first group of band pass filters (B1, B3,..., Bn) having the attenuation characteristics shown in FIG.
However, as in the present embodiment, a bandpass filter with high selectivity can be obtained by using the first group of bandpass filters (B1, B3,..., Bn) having the attenuation characteristics shown in FIG. This embodiment is more advantageous in reducing the cost because the number of use can be halved.
[0015]
[Configuration of the multiplexer according to the embodiment of the present invention]
In the above-described multiplexer shown in FIG. 1, when the input power is large, the synthesized transmission output from the third terminal (T ₀₀ ) of the circulator (CIR) by the minute non-linearity of the circulator (CIR). An intermodulation wave (IM3) is generated in the wave.
In order to solve this problem, the multiplexer of the present invention is characterized by operating a plurality of circulators in parallel.
FIG. 5 is a block diagram showing a schematic configuration of the multiplexer according to the embodiment of the present invention.
The multiplexer according to the present embodiment includes a first power distributor (TQ ₂₁ ), a second power distributor (TQ ₂₂ ), a first circulator (CIR1), and a second circulator (CIR2). And a power combiner (TQ ₂₃ ), which is different from the multiplexer shown in FIG.
The first power divider (TQ ₂₁ ) branches the output of the first group of bandpass filters (B1, B3,..., Bn) into two branches, and the second power divider (TQ ₂₂ ) The output of the band pass filters (B2, B4,..., Bn-1) is branched into two.
First circulator (CIR1) is the first terminal _{(T 211),} power divider One output of _{(TQ 21)} is input, the power divider to the second terminal _{(T 212) (TQ 22)} One of the outputs is input.
[0016]
Second circulator (CIR2) is the first terminal _{(T 221),} power divider other output of _{(TQ 21)} is input, the power divider to the second terminal _{(T 222) (TQ 22)} The other output of is input.
The power combiner (TQ ₂₃ ) is transmitted from the third terminal (T ₂₁₃ ) of the first circulator (CIR 1) and from the third terminal (T ₂₂₃ ) of the second circulator (CIR 2). Combines the output transmission wave and outputs it.
Here, the first power distributor (TQ ₂₁ ), the second power distributor (TQ ₂₂ ), and the power combiner (TQ ₂₃ ) are configured by, for example, a λ / 4 type Q transformer.
The [S] matrix of the first power distributor (TQ ₂₁ ), the second power distributor (TQ ₂₂ ), and the power combiner (TQ ₂₃ ) is obtained by the following equation (1).
Further, when the input voltage E _ii is applied to the terminal T ₂₂ shown in FIG. 5, the output voltages (E ₁₁ , T ₂₂₃ ) output from the terminals (T ₂₁₃ , T ₂₂₃ ) of the second power distributor (TQ ₂₂ ). E ₁₂ ) can be obtained by the following equation (2).
[0017]
[Expression 1]

[0018]
[Expression 2]

[0019]
From the above equation (2), the second terminal T ₂₁₃ of the first circulator (CIR1) and the second terminal T ₂₂₃ of the second circulator (CIR2) are respectively (−jE _ii / √2 ), And these voltages are combined by the power combiner (TQ ₂₃ ) and output from the terminal T ₂₃ .
Voltage output from the terminal _{T 23} may be determined by the following (3), from the terminal _{T 23,} - voltage _{(E ii)} is outputted. That is, when the voltage plus the terminal T ₂₂ shown in FIG. 5, the same voltage is output from the terminal T _23.
[0020]
[Equation 3]

[0021]
The voltage input to the terminal T ₂₁ shown in FIG. 5 is divided into two by the first power distributor (TQ ₂₁ ), the first terminal T ₂₁₁ of the first circulator (CIR1), and the second circulator. (CIR2) is input to the first terminal _{T 221} of the second terminal _{T 212} of each of the first circulator (CIR1), and is outputted from the second second terminal _{T 222} of the circulator (CIR2) .
This output voltage is synthesized by the second power divider (TQ ₂₂ ), then reflected by the second group of bandpass filters (B2, B4,..., Bn−1), and again the second power divider. (TQ ₂₂ ) and output from the terminal T ₂₃ in the same manner as described above.
That is, when the voltage plus the terminal T ₂₁ shown in FIG. 5, the same voltage (or current) is output from the terminal T _23.
If the length of the connection cable and the characteristics of the Q transformer type power distributor (TQ ₂₁ , TQ ₂₂ ) and the power combiner (TQ ₂₃ ) are the same, the circulators (CIR1, CIR2) shown in FIG. The parallel operation is equivalent to one circulator.
[0022]
However, since the voltage (or current) of the transmission wave input to the circulators (CIR1, CIR2) shown in FIG. 5 can be 1 / √2, the transmission wave passing through each circulator (CIR1, CIR2). Can be halved.
This means that the power capacity is doubled, so the level at which the intermodulation wave (IM3) is generated is increased by 3 dB.
That is, in the multiplexer shown in FIG. 1, when the power level of the transmission wave generated by the intermodulation wave (IM3) is P (W), in this embodiment, the transmission wave generated by the intermodulation wave (IM3). The power level can be 2 × P (W), and even when the power of the input transmission wave is large, the generation of the intermodulation wave (IM3) can be reduced.
When the power of the input transmission wave is larger, the number of circulators operated in parallel is 3, 4,..., N, and the first power distributor (TQ ₂₁ ) is accordingly adjusted. And the number of distributions in the second power distributor (TQ ₂₂ ) and the number of multiplexing in the power combiner (TQ ₂₃ ) may be set.
[0023]
In the embodiment of the present invention, when the number of circulators operated in parallel is four, the circulator (CR1 to CRI4), the first power distributor (TQ ₄₁ ), the second power distributor (TQ ₄₂ ), FIG. 6 shows the configuration of the power combiner (TQ ₄₃ ).
In the multiplexer shown in FIG. 6, since the power capacity is quadrupled, the level at which the intermodulation wave (IM3) is generated can be increased by 6 dB.
The [S] matrix ([Sn]) of the power distributors (TQ ₄₁ , TQ ₄₂ ) and the power combiner (TQ ₄₃ ) when the number of distributions is n is shown in the following formula (4).
[0024]
[Expression 4]

[0025]
Although the invention made by the present inventor has been specifically described based on the above-described embodiment, the present invention is not limited to the above-described embodiment, and various modifications can be made without departing from the scope of the invention. Of course.
[0026]
【The invention's effect】
The effects obtained by the representative ones of the inventions disclosed in the present application will be briefly described as follows.
According to the present invention, it is possible to provide a multiplexer that can be reduced in size, reduced in cost, and can have good electrical characteristics as compared with a conventional multiplexer.
[Brief description of the drawings]
FIG. 1 is a block diagram showing a schematic configuration of a multiplexer serving as a basis of the present invention.
FIG. 2 is a graph showing attenuation characteristics and return loss amounts of the second group of bandpass filters (B2, B4, B6) shown in FIG.
FIG. 3 is a graph showing attenuation characteristics of the first group of bandpass filters (B1, B3,..., Bn) shown in FIG.
4 is a graph showing transmission characteristics between each input terminal (T _{1 to} T _n ) shown in FIG. 1 and an output terminal (T ₀₀ ) shown in FIG. 1;
FIG. 5 is a block diagram showing a schematic configuration of a multiplexer according to an embodiment of the present invention.
FIG. 6 is a block diagram showing the configuration of a circulator, a first power distributor, a second power distributor, and a power combiner when the number of circulators operated in parallel is four in the embodiment of the present invention. FIG.
FIG. 7 is a block diagram showing a schematic configuration of a conventional CIB multiplexer.
FIG. 8 is a block diagram showing a schematic configuration of a conventional star point multiplexer.
[Explanation of symbols]
H11, H12, H21, H22, Hn1, Hn2 ... hybrid circuit, CIR, CRI1~CRI4 ... _{circulator, TQ 21, TQ 22, TQ} 41, TQ 42 ... power _{distributor, TQ 23, TQ 43 ...} power synthesizer, B1 ~ Bn, BF11, BF12, BF21, BF22, BFn1, BFn2 ... band pass filter, R ... non-reflection terminator.

Claims (3)

A first power distributor that has an input terminal and k (k ≧ 2) output terminals, distributes the power input to the input terminal k, and outputs the power from the k output terminals;
A first group of m (m ≧ 2) bands that are connected in parallel to the input terminals of the first power distributor and allow transmission waves of every other channel of odd number or even number to pass through. A pass filter,
A second power distributor that has an input terminal and k output terminals, distributes the power input to the input terminals k, and outputs the power from the k output terminals;
A second group of n (n ≧ 2) bands that are connected in parallel to the input terminal of the second power distributor and allow transmission waves of every other channel of odd number or other number to pass through. A pass filter,
A first terminal; a second terminal; and a third terminal, wherein the first terminal is connected to each output terminal of the first power distributor, and the second power distributor. K circulators to which the second terminals are connected to the output terminals, respectively,
k input terminals and output terminals, the k input terminals are respectively connected to the third terminals of the circulators, and the power input to the k input terminals is synthesized, A multiplexer comprising a power combiner that outputs from an output terminal,
Each of the circulators outputs the power input to the first terminal from the second terminal, and outputs the power input to the second terminal from the third terminal. Multiplexer. 2. The multiplexer according to claim 1, wherein the first and second power distributors and the power combiner are configured by λ / 4 type Q transformers. Each bandpass filter of the first group is composed of a low-selectivity type bandpass filter,
3. The multiplexer according to claim 1, wherein each band-pass filter of the second group is configured by a highly selective band-pass filter. 4.

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