JP3214463B2 - Wireless communication device - Google Patents
Wireless communication deviceInfo
- Publication number
- JP3214463B2 JP3214463B2 JP29953798A JP29953798A JP3214463B2 JP 3214463 B2 JP3214463 B2 JP 3214463B2 JP 29953798 A JP29953798 A JP 29953798A JP 29953798 A JP29953798 A JP 29953798A JP 3214463 B2 JP3214463 B2 JP 3214463B2
- Authority
- JP
- Japan
- Prior art keywords
- signal
- phase
- variable gain
- gain amplifier
- gain
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
- 238000004891 communication Methods 0.000 title claims description 20
- 230000005540 biological transmission Effects 0.000 claims description 30
- 238000000034 method Methods 0.000 claims description 7
- 238000006243 chemical reaction Methods 0.000 claims description 6
- 238000010586 diagram Methods 0.000 description 15
- 238000001514 detection method Methods 0.000 description 9
- 230000001360 synchronised effect Effects 0.000 description 8
- 230000003247 decreasing effect Effects 0.000 description 3
- 230000010363 phase shift Effects 0.000 description 3
- 230000005236 sound signal Effects 0.000 description 2
- 230000002093 peripheral effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/32—Modifications of amplifiers to reduce non-linear distortion
- H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
- H03F1/3247—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits using feedback acting on predistortion circuits
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G3/00—Gain control in amplifiers or frequency changers
- H03G3/20—Automatic control
- H03G3/30—Automatic control in amplifiers having semiconductor devices
Landscapes
- Physics & Mathematics (AREA)
- Nonlinear Science (AREA)
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
- Control Of Amplification And Gain Control (AREA)
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、無線通信装置に関
し、特に受信信号または送信信号を増幅する可変利得増
幅器を有する無線通信装置に関するものである。The present invention relates to a radio communication device, and more particularly to a radio communication device having a variable gain amplifier for amplifying a received signal or a transmitted signal.
【０００２】[0002]
【従来の技術】従来、ＣＤＭＡ（Code Division Multip
le Access）無線方式などのディジタル無線通信システ
ムで用いられる位相偏移変調方式では、データを搬送波
の各位相に対応させて伝送する方式である。例えば、Ｑ
ＰＳＫ（Quadripahse Phase Shift Keying：４位相偏移
変調）方式では、図６（ａ）に示すように、Ｉ−Ｑ平面
上のシンボルとして、π／４相にデータ「００」、３π
／４相にデータ「１０」、５π／４相にデータ「１
１」、７π／４相にデータ「０１」が割り当てられて伝
送される。2. Description of the Related Art Conventionally, CDMA (Code Division Multip
Le Access) A phase shift keying method used in a digital wireless communication system such as a wireless method is a method of transmitting data corresponding to each phase of a carrier wave. For example, Q
In the PSK (Quadripahse Phase Shift Keying) system, as shown in FIG. 6A, as a symbol on the IQ plane, data “00” and 3π in π / 4 phase are used.
Data “10” for / 4 phase, data “1” for 5π / 4 phase
Data “01” is allocated to the 1 ”and 7π / 4 phases and transmitted.
【０００３】この場合、各データは互いにπ／４ずつ位
相がずれており、各シンボル間の位相差を保持したま
ま、図６（ｂ）に示すように全体の位相すなわち基準位
相をφだけ回転させることもできる。例えば、このよう
な位相偏移変調方式で用いられる内相同期検波では、主
信号に設けられたスロットごとに基準位相を回転させる
とともに、そのスロット内の各データごとに基準位相を
回転させるものとなっている。In this case, each data is shifted in phase by π / 4 from each other, and the entire phase, that is, the reference phase is rotated by φ as shown in FIG. It can also be done. For example, in the internal phase synchronous detection used in such a phase shift keying system, the reference phase is rotated for each slot provided in the main signal, and the reference phase is rotated for each data in the slot. Has become.
【０００４】図７は内挿同期検波方式による信号フォー
マット例を示す説明図、図８は内挿同期検波方式の位相
変化を示す説明図である。図７において、各スロットに
はそれぞれのスロットの基準位相を示すパイロット（Ｐ
ＩＬＯＴ）部と伝送するデータを示すデータ部が設けら
れている。このような信号を検波する場合、まず各スロ
ットのパイロット部からそのスロットにおける基準位
相、ここではデータ「１１」の位相を検出する。FIG. 7 is an explanatory diagram showing an example of a signal format according to the interpolation synchronous detection method, and FIG. 8 is an explanatory diagram showing a phase change in the interpolation synchronous detection method. In FIG. 7, each slot has a pilot (P) indicating the reference phase of the slot.
An ILOT) section and a data section indicating data to be transmitted are provided. When detecting such a signal, first, a reference phase in this slot, that is, a phase of data "11" is detected from a pilot portion of each slot.
【０００５】例えば、図７のスロットＳ１では、そのパ
イロット部Ｐ１にはＰ１１〜Ｐ１４の４つのパイロット
データ「１１」が格納されており、これらのシンボル位
置の平均値から図８（ａ）に示すスロットＳ１の基準位
相Ｐ１０が検出される。同様にして、スロットＳ２の基
準位相Ｐ２０が検出され、このＰ２０から直前スロット
の基準位相Ｐ１０までを、図８（ｂ）に示すように、そ
のスロット内のデータ数で分割し、各データごとに徐々
に位相をずらすことにより同期が得られる。For example, in slot S1 of FIG. 7, four pilot data "11" of P11 to P14 are stored in the pilot portion P1, and an average value of these symbol positions is shown in FIG. The reference phase P10 of the slot S1 is detected. Similarly, the reference phase P20 of the slot S2 is detected, and from P20 to the reference phase P10 of the immediately preceding slot is divided by the number of data in the slot as shown in FIG. Synchronization is obtained by gradually shifting the phase.
【０００６】[0006]
【発明が解決しようとする課題】しかしながら、このよ
うな従来の無線通信装置では、変調部または復調部のア
ナログ回路部分に可変利得増幅器を有する場合、その可
変利得増幅器のダイナミックな利得変化により生じる位
相変化のために、パイロット信号に基づく基準位相の検
出に誤差が生じ、利得の切替単位となるスロットごとに
検波誤りを生じるという問題があった。その理由は、可
変利得増幅器の位相変化量が利得により異なり、利得変
化を生じた時に可変利得増幅器の入力信号と出力信号と
の間で位相の相対関係が崩れるためである。However, in such a conventional wireless communication apparatus, when a variable gain amplifier is provided in an analog circuit portion of a modulation section or a demodulation section, a phase generated by a dynamic gain change of the variable gain amplifier. Due to the change, an error occurs in the detection of the reference phase based on the pilot signal, and there has been a problem that a detection error occurs in each slot serving as a gain switching unit. The reason is that the amount of phase change of the variable gain amplifier differs depending on the gain, and when a gain change occurs, the relative relationship of the phase between the input signal and the output signal of the variable gain amplifier is broken.
【０００７】本発明はこのような課題を解決するための
ものであり、利得変化に応じて可変利得増幅器で位相が
変化する場合でも、位相変化を低減して検波誤りを抑制
できる無線通信装置を提供することを目的としている。SUMMARY OF THE INVENTION The present invention has been made to solve such a problem, and a radio communication apparatus capable of reducing a phase change and suppressing a detection error even when a phase is changed by a variable gain amplifier according to a gain change. It is intended to provide.
【０００８】[0008]
【課題を解決するための手段】このような目的を達成す
るために、本発明による無線通信装置は、可変利得増幅
器の位相特性とは逆の位相特性を有する位相補正手段を
設け、可変利得増幅器の利得を制御する利得信号に基づ
いてＡ／Ｄ変換手段によりディジタル化されたＩ，Ｑ成
分を増減することにより、可変利得増幅器での位相変化
分だけ受信信号の位相補正を行うようにしたものであ
る。In order to achieve the above object, a wireless communication apparatus according to the present invention comprises a variable gain amplifier.
Phase correction means having a phase characteristic opposite to that of the
Based on a gain signal that controls the gain of the variable gain amplifier.
I and Q components digitized by the A / D conversion means.
Phase change in the variable gain amplifier by increasing or decreasing
The phase of the received signal is corrected by the minute .
【０００９】また、可変利得増幅器の位相特性とは逆の
位相特性を有する位相補正手段を設け、可変利得増幅器
の利得を制御する利得信号に基づいてＤ／Ａ変換手段に
入力されるディジタル値のＩ，Ｑ成分を増減することに
より、可変利得増幅器での位相変化分だけ送信信号の位
相補正を行うようにしたものである。 Further, the phase correction means having opposite phase characteristics provided from the phase characteristics of the variable gain amplifier, the digital value input to the D / A converting means based on the gain signal for controlling the gain of the variable gain amplifier By increasing or decreasing the I and Q components, the phase of the transmission signal is corrected by the amount of phase change in the variable gain amplifier.
【００１０】[0010]
【発明の実施の形態】次に、本発明について図面を参照
して説明する。図１は本発明の第１の実施の形態である
無線通信装置の要部を示すブロック図であり、特に受信
信号または送信信号を増幅する可変利得増幅器の周辺部
が示されている。同図（ａ）において、可変利得増幅器
１は無線通信装置のアナログ回路を構成する一素子であ
り、利得信号４に応じて利得を変化させることにより、
アナログの入力信号３Ａ、例えば受信信号や送信信号を
所定の大きさ（例えば振幅）の出力信号３Ｂに変換して
出力する。Next, the present invention will be described with reference to the drawings. FIG. 1 is a block diagram showing a main part of a wireless communication apparatus according to a first embodiment of the present invention, particularly showing a peripheral part of a variable gain amplifier for amplifying a reception signal or a transmission signal. In FIG. 1A, a variable gain amplifier 1 is one element constituting an analog circuit of a wireless communication device.
An analog input signal 3A, for example, a reception signal or a transmission signal is converted into an output signal 3B having a predetermined size (for example, amplitude) and output.
【００１１】この場合、入力信号３Ａの大きさに基づい
て利得信号４を制御することにより、ＡＧＣ（Auto Gai
n Control ）増幅器が構成される。例えば、小さな入力
信号３Ａが入力された場合は、高い利得を示す利得信号
４を可変利得増幅器１に供給し、大きな入力信号３Ａが
入力された場合は、低い利得を示す利得信号４を供給す
ることにより、可変利得増幅器１からほぼ一定の大きさ
の出力信号３Ｂが得られる。In this case, by controlling the gain signal 4 based on the magnitude of the input signal 3A, the AGC (Auto Gai
n Control) An amplifier is configured. For example, when a small input signal 3A is input, a gain signal 4 indicating a high gain is supplied to the variable gain amplifier 1, and when a large input signal 3A is input, a gain signal 4 indicating a low gain is supplied. Thus, the output signal 3B having a substantially constant magnitude is obtained from the variable gain amplifier 1.
【００１２】また、位相補正部２は、可変利得増幅器１
の利得が変化するのに伴って発生する出力信号３Ｂの位
相変化を、可変利得増幅器１とは逆方向の位相特性に基
づいて位相補正を行うものである。なお、図１（ａ）で
は位相補正部２は可変利得増幅器１の後段に配置されて
いるが、図１（ｂ）に示すように、その前段に配置する
こともできる。Further, the phase correction unit 2 includes a variable gain amplifier 1
Is to correct the phase change of the output signal 3B generated with the change of the gain based on the phase characteristic in the direction opposite to that of the variable gain amplifier 1. In FIG. 1A, the phase correction unit 2 is arranged at the subsequent stage of the variable gain amplifier 1, but as shown in FIG. 1B, it can be arranged at the preceding stage.
【００１３】図２は位相補正部の位相特性を示す説明図
である。可変利得増幅器１の出力信号３Ｂの位相変化
が、その入力信号に対して利得によらず一定であれば信
号位相の相対的な変化は起こらない。しかし、実際に
は、図２に示すように、可変利得増幅器１の利得に対し
て位相変化量は変化する。FIG. 2 is an explanatory diagram showing the phase characteristics of the phase correction unit. If the phase change of the output signal 3B of the variable gain amplifier 1 is constant regardless of the gain with respect to the input signal, no relative change in the signal phase occurs. However, in practice, as shown in FIG. 2, the phase change amount changes with respect to the gain of the variable gain amplifier 1.
【００１４】位相補正部２は、可変利得増幅器１の利得
に対する位相変化量すなわち位相特性８に対して、極性
が逆向きの変化量を有する位相特性９を有し、可変利得
増幅器１の出力信号の位相補正を行う。例えば、利得Ｇ
０、ＧＡ、ＧＢに対する可変利得増幅器１の位相変化量
が、それぞれΦ０，Φ０−ΦＡ，Φ０＋ΦＢの場合、位
相補正部２の位相補正量を各利得に対してそれぞれΦ
０，Φ０＋ΦＡ，Φ０−ΦＢとする。The phase correction unit 2 has a phase characteristic 9 having a change amount in which the polarity is opposite to a phase change amount with respect to the gain of the variable gain amplifier 1, that is, a phase characteristic 8. Is performed. For example, the gain G
When the phase change amounts of the variable gain amplifier 1 with respect to 0, GA, and GB are Φ0, Φ0−ΦA, and Φ0 + ΦB, respectively, the phase correction amount of the phase correction unit 2 is set to Φ0 for each gain.
0, Φ0 + ΦA, Φ0−ΦB.
【００１５】これにより、信号の位相変化量は、位相補
正部２からの出力信号３Ｃでは、常に２×Φ０に収束さ
せることができる。したがって、可変利得増幅器１の利
得がダイナミックに変化しても、可変利得増幅器１の入
力信号３Ａと、可変利得増幅器１の出力信号３Ｂとの間
で生じる位相の相対関係の変化が抑制された出力信号３
Ｃを得ることができる。Thus, the amount of phase change of the signal can always be converged to 2 × Φ0 in the output signal 3C from the phase correction unit 2. Therefore, even if the gain of the variable gain amplifier 1 dynamically changes, the output in which the change in the relative relationship of the phase generated between the input signal 3A of the variable gain amplifier 1 and the output signal 3B of the variable gain amplifier 1 is suppressed. Signal 3
C can be obtained.
【００１６】この場合、位相補正部２において、可変利
得増幅器１の利得信号４に対する位相特性９をテーブル
に用意しておき、ベースバンドでディジタル的に位相補
正を行うこともできる。また、位相特性９を回路または
演算式により関数化し、利得信号４を入力として位相補
正量を得るようにしてもよい。In this case, the phase correction section 2 can prepare a phase characteristic 9 for the gain signal 4 of the variable gain amplifier 1 in a table, and perform digital phase correction in baseband. Further, the phase characteristic 9 may be converted into a function by a circuit or an arithmetic expression, and the gain correction signal 4 may be input to obtain the phase correction amount.
【００１７】次に、図３を参照して、本発明の第２の実
施の形態として、多位相偏移変調方式の無線通信装置に
適用した場合について説明する。図３はＱＰＳＫ変調方
式の無線通信装置を示すブロック図である。前述したよ
うに、ＱＰＳＫ変調方式などの多位相偏移変調方式を用
いた無線通信システムでは、より正確な位相制御が求め
られることから、受信側復調器の前段や送信側変調器の
後段で利用される可変利得増幅器による位相変化を低減
する必要がある。Next, with reference to FIG. 3, a description will be given of a second embodiment of the present invention in which the present invention is applied to a multi-phase shift keying wireless communication apparatus. FIG. 3 is a block diagram showing a wireless communication device of the QPSK modulation system. As described above, in a wireless communication system using a multi-phase shift keying system such as a QPSK modulation system, more accurate phase control is required, so that a wireless communication system is used in a stage before a receiving-side demodulator or after a transmitting-side modulator. It is necessary to reduce the phase change caused by the variable gain amplifier.
【００１８】本実施の形態では、ディジタル化された後
の受信信号４２に対して位相補正する受信信号位相補正
部１４を設けて、可変利得増幅器１１による位相変化を
ディジタル信号処理により補正するようにしたものであ
る。また、アナログ化される前の送信信号５３に対して
位相補正する送信信号位相補正部２４を設けて、可変利
得増幅器２１による位相変化をディジタル信号処理によ
り補正するようにしたものである。In the present embodiment, the received signal phase corrector 14 for correcting the phase of the digitized received signal 42 is provided, and the phase change by the variable gain amplifier 11 is corrected by digital signal processing. It was done. Further, a transmission signal phase correction unit 24 that corrects the phase of the transmission signal 53 before being converted into an analog signal is provided, and the phase change by the variable gain amplifier 21 is corrected by digital signal processing.
【００１９】まず、受信側では、アンテナ（図示せず）
を介して受信した受信信号４１が可変利得増幅器１１に
より増幅された後、復調器１２により復調され、Ａ／Ｄ
変換器１３によりディジタル化されてＩ−Ｑ平面でのＩ
ｒ，Ｑｒ成分からなる受信信号４２が生成される。次
に、受信信号位相補正部１４では、後述する受信利得制
御部１５からの利得信号４５に基づいて、受信信号４２
のＩｒ，Ｑｒ成分をそれぞれ位相補正して、受信信号４
３すなわちＩｒ’，Ｑｒ’成分を生成し、ベースバンド
処理部３１に出力する。First, on the receiving side, an antenna (not shown)
The signal 41 received via the A / D is amplified by the variable gain amplifier 11 and then demodulated by the demodulator 12.
It is digitized by the converter 13 and I in the IQ plane
A received signal 42 composed of the r and Qr components is generated. Next, the reception signal phase correction unit 14 receives the reception signal 42 based on a gain signal 45 from the reception gain control unit 15 described later.
Are respectively phase-corrected for the Ir and Qr components of
3, that is, Ir ′ and Qr ′ components are generated and output to the baseband processing unit 31.
【００２０】これにより、ベースバンド処理部３１で
は、位相補正された受信信号４３に基づいて、前述した
図７の各スロットのパイロット部およびデータ部が認識
され、例えばデータ部に格納された音声情報については
音声信号に復号化された後、スピーカ３２に出力され
る。ここで、受信利得制御部１５は、この受信信号４２
から受信信号４１の大きさを検出し、その大きさが適切
となるように受信信号４１の各スロットごとに可変利得
増幅器１１の利得が算出される。Thus, the baseband processing section 31 recognizes the pilot section and the data section of each slot shown in FIG. 7 based on the phase-corrected received signal 43, for example, the audio information stored in the data section. Is decoded into an audio signal and then output to the speaker 32. Here, the reception gain control unit 15 outputs the received signal 42
, The magnitude of the received signal 41 is detected, and the gain of the variable gain amplifier 11 is calculated for each slot of the received signal 41 so that the magnitude becomes appropriate.
【００２１】そして、ベースバンド処理部３１からのタ
イミング信号４４に基づいて、可変利得増幅器１１の利
得が各スロットに同期するように、可変利得増幅器１１
の利得を示す利得信号４５がディジタル量で出力され
る。この利得信号４５はＤ／Ａ変換器１６でアナログ化
された後、可変利得増幅器１１に供給され、受信信号４
１が適切な大きさに増幅されて復調器１２に出力され
る。Then, based on the timing signal 44 from the baseband processing section 31, the variable gain amplifier 11 is controlled so that the gain of the variable gain amplifier 11 is synchronized with each slot.
Is output as a digital quantity. The gain signal 45 is converted into an analog signal by the D / A converter 16 and then supplied to the variable gain amplifier 11 to receive the received signal 4.
1 is amplified to an appropriate size and output to the demodulator 12.
【００２２】一方、受信利得制御部１５からの利得信号
４５は、受信信号位相補正部１４にも並列的に出力さ
れ、可変利得増幅器１１の利得変化に同期して、受信信
号４２に対して利得信号４５に応じた位相補正が行われ
る。これにより、可変利得増幅器１１での位相変化が各
スロットごとに受信信号位相補正部１４で補正され、ベ
ースバンド処理部３１に対して位相変化が抑制された受
信信号４３が供給される。On the other hand, the gain signal 45 from the reception gain control unit 15 is also output to the reception signal phase correction unit 14 in parallel, and the gain of the reception signal 42 is synchronized with the gain change of the variable gain amplifier 11. The phase correction according to the signal 45 is performed. Thereby, the phase change in the variable gain amplifier 11 is corrected by the received signal phase corrector 14 for each slot, and the received signal 43 in which the phase change is suppressed is supplied to the baseband processing unit 31.
【００２３】次に、送信側では、例えばマイク３３から
入力された音声信号がベースバンド処理部３１で符号化
されてスロットのデータ部に格納され、データ「１１」
などの固定的なパイロット信号から構成されるパイロッ
ト部とともに、Ｉ−Ｑ平面でのＩｔ，Ｑｔ成分からなる
送信信号５３に変換されて出力される。また、ベースバ
ンド処理部３１は、可変利得増幅器２１の利得が各スロ
ットに同期するように、可変利得増幅器２１の利得を示
す利得信号５５を出力する。Next, on the transmitting side, for example, the audio signal input from the microphone 33 is encoded by the baseband processing unit 31 and stored in the data part of the slot, and the data "11"
Along with a pilot section composed of a fixed pilot signal such as the above, it is converted into a transmission signal 53 composed of It and Qt components on the IQ plane and output. Further, the baseband processing unit 31 outputs a gain signal 55 indicating the gain of the variable gain amplifier 21 so that the gain of the variable gain amplifier 21 is synchronized with each slot.
【００２４】送信信号位相補正部２４では、送信信号５
３のＩｔ，Ｑｔ成分に対して利得信号５５に応じた分だ
け前もって位相補正を行うことにより、Ｉｔ’，Ｑｔ’
成分からなる位相補正後の送信信号５２を生成する。こ
の送信信号５２は、Ｄ／Ａ変換器２３によりアナログ化
された後、変調器２２で変調され、可変利得増幅器２１
でスロットごとの利得信号５５に基づき増幅され、送信
信号５１としてアンテナに出力される。The transmission signal phase correction section 24 outputs the transmission signal 5
By performing phase correction in advance for the It and Qt components of No. 3 by an amount corresponding to the gain signal 55, It 'and Qt'
A phase-corrected transmission signal 52 composed of components is generated. The transmission signal 52 is converted into an analog signal by the D / A converter 23, and then modulated by the modulator 22 to obtain a variable gain amplifier 21.
Is amplified based on the gain signal 55 for each slot, and output to the antenna as a transmission signal 51.
【００２５】これにより、可変利得増幅器２１での位相
変化が各スロットごとに送信信号位相補正部２４で予め
補正され、位相変化が抑制された適切な大きさの送信信
号５１が出力される。なお、送信信号の電力は、受信信
号４１の大きさや受信信号により基地局から指示された
情報に基づいてベースバンド処理部３１で決定される。As a result, the phase change in the variable gain amplifier 21 is corrected in advance by the transmission signal phase corrector 24 for each slot, and the transmission signal 51 of an appropriate magnitude with the phase change suppressed is output. The power of the transmission signal is determined by the baseband processing unit 31 based on the magnitude of the reception signal 41 and information specified by the base station based on the reception signal.
【００２６】例えば、ＣＤＭＡ無線方式などのディジタ
ル無線通信システムでは、移動局の送信電力を適切な値
に制御する方法として、基地局から送信された信号の受
信レベルに応じて移動局が単独で送信電力を決定するオ
ープンループ制御があり、基地局からの信号レベルによ
り基地局と移動局との距離を判断し、適切な送信電力を
決定するものといえる。For example, in a digital radio communication system such as a CDMA radio system, as a method of controlling the transmission power of a mobile station to an appropriate value, the mobile station transmits a signal alone according to the reception level of a signal transmitted from a base station. There is an open-loop control for determining the power, and it can be said that an appropriate transmission power is determined by determining the distance between the base station and the mobile station based on the signal level from the base station.
【００２７】これに対して、基地局からの指示に応じて
移動局が送信電力を決定するクローズドループ制御とが
あり、この場合は、移動局から送信された信号のレベル
を基地局が検出し、これが最適値となるまで移動局に対
して送信電力の増減を所定の情報により通知するもので
ある。On the other hand, there is a closed loop control in which the mobile station determines the transmission power in accordance with an instruction from the base station. In this case, the base station detects the level of the signal transmitted from the mobile station. Until this reaches an optimum value, the mobile station is notified of the increase or decrease of the transmission power using predetermined information.
【００２８】したがって、このような方法によりベース
バンド処理部３１で送信信号５１の大きさを決定し、可
変利得増幅器２１の利得を示す利得信号５５を生成する
ものとなる。図４は送信側位相補正動作を示す説明図、
図５は位相補正例を示す説明図である。例えば、スロッ
トＳ１の送信利得がＧ１の場合、これが利得信号５５に
より通知され、送信信号位相補正部２４において利得Ｇ
１に対応する位相補正量φ１が設定される。Accordingly, the size of the transmission signal 51 is determined by the baseband processing section 31 by such a method, and the gain signal 55 indicating the gain of the variable gain amplifier 21 is generated. FIG. 4 is an explanatory diagram showing a transmission-side phase correction operation,
FIG. 5 is an explanatory diagram showing an example of phase correction. For example, when the transmission gain of the slot S1 is G1, this is notified by a gain signal 55, and the transmission signal
The phase correction amount φ1 corresponding to 1 is set.
【００２９】これにより、可変利得増幅器２１の利得が
Ｇ１の場合の位相変化量が打ち消されるように、予め送
信位相補正部２４でφ１だけ位相補正が行われ、所望の
位相回転量φＴが得られるものとなる。この場合、送信
信号位相補正部２４では、図５に示すように、Ｉ−Ｑ平
面におけるデジタル値のＩｔ，Ｑｔ成分に対し、それぞ
れΔＩ，ΔＱだけ増減するだけで位相補正される。As a result, the transmission phase correction unit 24 performs phase correction by φ1 in advance so that the phase change amount when the gain of the variable gain amplifier 21 is G1 is canceled, and a desired phase rotation amount φT is obtained. It will be. In this case, as shown in FIG. 5, the transmission signal phase correction unit 24 corrects the phase by simply increasing or decreasing ΔI and ΔQ, respectively, with respect to the digital value It and Qt components on the IQ plane.
【００３０】このように、受信信号および送信信号がデ
ィジタル値として処理されている区間で位相補正するよ
うにしたので、アナログ信号の位相を補正する場合と比
較して容易に位相補正できる。なお、以上の説明におい
て、受信信号位相補正部１４および送信信号位相補正部
２４を設けて、ディジタル的に位相補正を行うようにし
たが、これらをベースバンド処理部３１内で行ってもよ
く、新たな回路部を設けることなく、可変利得増幅器の
利得変化に起因する位相変化を抑制できる。As described above, since the phase is corrected in the section where the received signal and the transmitted signal are processed as digital values, the phase can be corrected more easily as compared with the case where the phase of the analog signal is corrected. In the above description, the reception signal phase correction unit 14 and the transmission signal phase correction unit 24 are provided to perform digital phase correction. However, these may be performed in the baseband processing unit 31. A phase change due to a gain change of the variable gain amplifier can be suppressed without providing a new circuit unit.
【００３１】[0031]
【発明の効果】以上説明したように、本発明によれば、
可変利得増幅器の利得がダイナミックに変化する場合で
も、可変利得増幅器の利得変化に起因して発生する信号
の位相変化量を抑制でき、位相変化による検波誤りを抑
制できる。As described above, according to the present invention,
Even when the gain of the variable gain amplifier changes dynamically, the amount of phase change of the signal generated due to the change in gain of the variable gain amplifier can be suppressed, and the detection error due to the phase change can be suppressed.
【図１】 本発明の第１の実施の形態による無線通信装
置の要部を示すブロック図である。FIG. 1 is a block diagram illustrating a main part of a wireless communication device according to a first embodiment of the present invention.
【図２】 位相補正部の位相特性を示す説明図である。FIG. 2 is an explanatory diagram illustrating phase characteristics of a phase correction unit.
【図３】 本発明の第２の実施の形態による無線通信装
置を示すブロック図である。FIG. 3 is a block diagram showing a wireless communication device according to a second embodiment of the present invention.
【図４】 位相補正動作を示す説明図である。FIG. 4 is an explanatory diagram showing a phase correction operation.
【図５】 位相補正例を示す説明図である。FIG. 5 is an explanatory diagram showing an example of phase correction.
【図６】 ＱＰＳＫ変調方式の位相関係を示す説明図で
ある。FIG. 6 is an explanatory diagram showing a phase relationship of a QPSK modulation method.
【図７】 内挿同期検波方式による信号フォーマット例
を示す説明図である。FIG. 7 is an explanatory diagram illustrating an example of a signal format according to an interpolation synchronous detection method.
【図８】 内挿同期検波方式の位相変化を示す説明図で
ある。FIG. 8 is an explanatory diagram showing a phase change in an interpolation synchronous detection method.
１…可変利得増幅器、２…位相補正部、３Ａ…入力信
号、３Ｂ…可変利得増幅器の出力信号、３Ｃ…位相補正
部の出力信号、４…利得信号、８…可変利得増幅器の位
相特性、位相補正部の位相特性、１１，２１…可変利得
増幅器、１２…復調器、１３…Ａ／Ｄ変換器、１４…受
信信号位相補正部、１５…受信利得制御部、１６，２
３，２６…Ｄ／Ａ変換器、２２…変調器、２４…送信信
号位相補正部、３１…ベースバンド処理部、３２…スピ
ーカ、３３…マイク、４１…受信信号（アナログ）、４
２受信信号（ディジタル）、４３…受信信号（位相補正
後）、４４タイミング信号、４５，５５…利得信号、５
１…送信信号（アナログ）、５２…送信信号（位相補正
後）、５３…送信信号（ディジタル）。DESCRIPTION OF SYMBOLS 1 ... Variable gain amplifier, 2 ... Phase correction part, 3A ... Input signal, 3B ... Variable gain amplifier output signal, 3C ... Phase correction part output signal, 4 ... Gain signal, 8 ... Phase characteristic and phase of variable gain amplifier Phase characteristics of correction unit 11, 21, variable gain amplifier, 12 demodulator, 13 A / D converter, 14 reception signal phase correction unit, 15 reception gain control unit, 16, 2
3, 26 D / A converter, 22 modulator, 24 transmission signal phase correction unit, 31 baseband processing unit, 32 speaker, 33 microphone, 41 reception signal (analog), 4
2 Received signal (digital), 43: Received signal (after phase correction), 44 Timing signal, 45, 55: Gain signal, 5
1 ... transmission signal (analog), 52 ... transmission signal (after phase correction), 53 ... transmission signal (digital).
───────────────────────────────────────────────────── フロントページの続き (58)調査した分野(Int.Cl.7，ＤＢ名) H04L 27/00 - 27/38 ──────────────────────────────────────────────────続 き Continued on front page (58) Field surveyed (Int. Cl. 7 , DB name) H04L 27/00-27/38
Claims (2)
る可変利得増幅器を用いて受信信号を増幅する無線通信
装置において、 可変利得増幅器で増幅された受信信号をＩ−Ｑ平面の
Ｉ，Ｑ成分に復調する復調手段と、 この復調手段により復調されたＩ，Ｑ成分をディジタル
化するＡ／Ｄ変換手段と、 可変利得増幅器の位相特性とは逆の位相特性を有し、可
変利得増幅器の利得を制御する利得信号に基づいてＡ／
Ｄ変換手段によりディジタル化されたＩ，Ｑ成分を増減
することにより、可変利得増幅器での位相変化分だけ位
相補正を行う位相補正手段を備える ことを特徴とする無
線通信装置。 The gain can be changed based on a predetermined gain signal.
Communication Amplifying Received Signal Using Variable Gain Amplifier
In the device, the received signal amplified by the variable gain amplifier is
I, a demodulation means for demodulating the Q component, I demodulated by the demodulating means, the Q component digital
A / D conversion means and a variable gain amplifier have phase characteristics opposite to those of the variable gain amplifier.
A / A based on a gain signal controlling the gain of the variable gain amplifier
Increase / decrease I and Q components digitized by D conversion means
By doing so, only the phase change in the variable gain amplifier
A wireless communication device comprising a phase correction unit for performing phase correction .
る可変利得増幅器を用いて送信信号を増幅する無線通信
装置において、 ディジタル値で示されるＩ−Ｑ平面のＩ，Ｑ成分をそれ
ぞれアナログ化するＤ／Ａ変換手段と、 このＤ／Ａ変換手段によりアナログ化されたＩ，Ｑ成分
を送信信号に変調して可変利得増幅器に出力する変調手
段と、 可変利得増幅器の位相特性とは逆の位相特性を有し、可
変利得増幅器の利得を制御する利得信号に基づいてＤ／
Ａ変換手段に入力されるディジタル値のＩ，Ｑ成分を増
減することにより、可変利得増幅器での位相変化分だけ
位相補正を行う位相補正手段を備える ことを特徴とする
無線通信装置。2. The method according to claim 1 , wherein the gain can be changed based on a predetermined gain signal.
Communication Amplifying Transmission Signal Using Variable Gain Amplifier
In the device, the I and Q components of the IQ plane represented by digital values are
D / A conversion means for converting to analog, and I and Q components converted to analog by the D / A conversion means
Modulating the signal into a transmission signal and outputting it to the variable gain amplifier
Stage and the variable gain amplifier have phase characteristics opposite to those of the
Based on the gain signal controlling the gain of the variable gain amplifier, D /
Increase the I and Q components of the digital value input to the A conversion means
The amount of phase change in the variable gain amplifier
A wireless communication device comprising a phase correction unit for performing a phase correction .
Priority Applications (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP29953798A JP3214463B2 (en) | 1998-10-21 | 1998-10-21 | Wireless communication device |
| US09/421,851 US6721370B1 (en) | 1998-10-21 | 1999-10-20 | Phase correction circuit for radio communication apparatus |
| GB9924966A GB2345619B (en) | 1998-10-21 | 1999-10-21 | Phase correction circuit for radio communication apparatus |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP29953798A JP3214463B2 (en) | 1998-10-21 | 1998-10-21 | Wireless communication device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JP2000134273A JP2000134273A (en) | 2000-05-12 |
| JP3214463B2 true JP3214463B2 (en) | 2001-10-02 |
Family
ID=17873901
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP29953798A Expired - Fee Related JP3214463B2 (en) | 1998-10-21 | 1998-10-21 | Wireless communication device |
Country Status (3)
| Country | Link |
|---|---|
| US (1) | US6721370B1 (en) |
| JP (1) | JP3214463B2 (en) |
| GB (1) | GB2345619B (en) |
Families Citing this family (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7376206B1 (en) | 2000-11-06 | 2008-05-20 | Qualcomm Incorporated | Method and apparatus for adjusting the phase of a received signal |
| JP2002290254A (en) * | 2001-03-26 | 2002-10-04 | Nec Corp | Direct conversion receiver |
| US7058139B2 (en) * | 2001-11-16 | 2006-06-06 | Koninklijke Philips Electronics N.V. | Transmitter with transmitter chain phase adjustment on the basis of pre-stored phase information |
| US7024169B2 (en) * | 2002-01-25 | 2006-04-04 | Qualcomm Incorporated | AMPS receiver using a zero-IF architecture |
| US7085333B2 (en) * | 2002-04-15 | 2006-08-01 | General Dynamics Decision Systems, Inc. | Constant-phase, gain-controlled amplification circuit |
| US20060183451A1 (en) * | 2003-06-06 | 2006-08-17 | Interdigital Technology Corporation | Method and system for continuously compensating for phase variations introduced into a communication signal by automatic gain control adjustments |
| US7502601B2 (en) * | 2003-12-22 | 2009-03-10 | Black Sand Technologies, Inc. | Power amplifier with digital power control and associated methods |
| US7522892B2 (en) * | 2003-12-22 | 2009-04-21 | Black Sand Technologies, Inc. | Power amplifier with serial interface and associated methods |
| US7400864B2 (en) * | 2004-04-15 | 2008-07-15 | Interdigital Technology Corporation | Method and apparatus for compensating for phase variations caused by activation of an amplifier |
| DE102016119478A1 (en) * | 2016-10-12 | 2018-04-12 | Profil Verbindungstechnik Gmbh & Co. Kg | A rivet and an assembly part consisting of a rivet and a sheet metal part |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| GB559093A (en) | 1942-08-17 | 1944-02-03 | Siemens Electric Lamps & Suppl | Improvements relating to metal vapour electric discharge lamps |
| SU1022289A1 (en) * | 1982-01-07 | 1983-06-07 | Марийский Политехнический Институт Им.М.Горького | Device for automatic stabilization of frequency |
| US4700151A (en) * | 1985-03-20 | 1987-10-13 | Nec Corporation | Modulation system capable of improving a transmission system |
| JPH0771118B2 (en) * | 1989-12-27 | 1995-07-31 | 三菱電機株式会社 | Modulator |
| JPH03198512A (en) | 1989-12-27 | 1991-08-29 | Mitsubishi Electric Corp | High frequency amplifier |
| JPH03289220A (en) | 1990-04-04 | 1991-12-19 | Alpine Electron Inc | Radio receiver |
| US5065110A (en) | 1990-05-02 | 1991-11-12 | Teledyne Mec | Feed-forward amplifier including phase correction |
| JPH0758930B2 (en) | 1990-05-18 | 1995-06-21 | 富士通株式会社 | Automatic gain control amplifier |
| EP0839606A3 (en) | 1990-08-04 | 2000-09-27 | Toyo Co., Ltd. | A honing tool and super-high precision finishing method using said honing tool |
| JPH0575541A (en) | 1991-09-11 | 1993-03-26 | Nec Corp | Optical parallel signal receiver |
| JP3019569B2 (en) | 1991-12-30 | 2000-03-13 | 日本電気株式会社 | Automatic gain control circuit |
| JP2773524B2 (en) * | 1992-02-29 | 1998-07-09 | 日本電気株式会社 | Digital mobile radio receiver |
| US5509030A (en) * | 1992-03-04 | 1996-04-16 | Alcatel Network Systems, Inc. | RF receiver AGC incorporating time domain equalizer circuity |
| JPH0865352A (en) | 1994-08-24 | 1996-03-08 | Yuseisho Tsushin Sogo Kenkyusho | Digital modulator |
| JP2917828B2 (en) | 1994-09-30 | 1999-07-12 | 日本電気株式会社 | Transmitter |
| JPH08330868A (en) | 1995-05-31 | 1996-12-13 | Canon Inc | Variable gain circuit |
| US5742201A (en) | 1996-01-30 | 1998-04-21 | Spectrian | Polar envelope correction mechanism for enhancing linearity of RF/microwave power amplifier |
| JP3504800B2 (en) | 1996-03-01 | 2004-03-08 | 富士通株式会社 | Quadrature demodulator |
| US5787362A (en) * | 1996-07-08 | 1998-07-28 | Nokia Mobile Phones Limited | AM removal from FM signal generated by IQ modulator |
| JP3106996B2 (en) * | 1997-04-02 | 2000-11-06 | 日本電気株式会社 | Feed forward amplification circuit |
| KR100251561B1 (en) * | 1997-06-19 | 2000-04-15 | 윤종용 | Apparatus and method for linearizing tx signal in digital communication system |
| JP3570898B2 (en) * | 1998-08-24 | 2004-09-29 | 日本電気株式会社 | Pre-distortion circuit |
-
1998
- 1998-10-21 JP JP29953798A patent/JP3214463B2/en not_active Expired - Fee Related
-
1999
- 1999-10-20 US US09/421,851 patent/US6721370B1/en not_active Expired - Fee Related
- 1999-10-21 GB GB9924966A patent/GB2345619B/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| GB2345619A (en) | 2000-07-12 |
| GB9924966D0 (en) | 1999-12-22 |
| US6721370B1 (en) | 2004-04-13 |
| JP2000134273A (en) | 2000-05-12 |
| GB2345619B (en) | 2004-03-03 |
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