JP2579905B2 - Power conversion equipment for vehicles - Google Patents

Description

Description: TECHNICAL FIELD [0001] The present invention relates to a vehicular power conversion device including a DC voltage source that receives power supply from an AC power source and a load device thereof.

[Technical Background of the Invention] Load devices powered by a DC voltage source include a pulse width modulation control (PWM) inverter and an induction motor, or a DC chopper device and a DC motor. When using a battery as this DC voltage source, there is not much problem,
When a DC voltage is obtained from a commercial power supply via an AC power converter, a reactive power and a harmonic generated on the commercial power supply side have recently become a problem.

To solve this problem, as an AC / DC power converter,
A method in which a pulse width modulation control (PWM) converter is inserted between a commercial power supply and a DC voltage source (capacitor) (Japanese Patent Application No.
−171886).

FIG. 8 shows a configuration diagram of a conventional power conversion device using a PWM converter as an AC / DC power converter.

In the figure, SUP is a single-phase AC power supply, L _S is an AC reactor, CON
V is an AC / DC power converter, C _d is a DC smoothing capacitor, and LAD is a load device. Converter CONV
Element with a self-extinguishing capacity (for example, a gate turn-off thyristor) S ₁ ~S _4, wheeling diodes D ₁ to D ₄ and a DC reactor L _1, is composed of L ₂ the elements S ₁ to S ₄ are AC side voltage V _In order to control the value of _C , known pulse width modulation control is performed. That is, the converter CONV when viewed from the DC voltage source (capacitor) C _d, it becomes a pulse width modulation control (PWM) inverter, in which case the AC power source SUP side can be viewed as a type of load.

Voltage V _d of the conventional power converter the DC voltage source C _d
The current supplied from the AC power supply so that
Controls the I _S, 4-quadrant operation is possible in accordance with the power demand from the load device LAD.

The input current I _S is always controlled in phase with the source voltage V _S, the input power factor is 1.

The input current I _S is to be controlled sinusoidally, the harmonics becomes extremely small.

Is a feature.

 Hereinafter, the control operation of this device will be briefly described.

The following control circuits are prepared. CT _C
Is an AC current detector, R ₁ and R ₂ are voltage dividing resistors for detecting DC voltage, ISO is an isolation amplifier, VR is a DC voltage setting device, C ₁
-C ₃ comparators, G _V (S) is a voltage control compensation circuit, ML is the multiplier, OA inverting operational amplifier, G _I (S) is a current control compensation circuit, TRG carrier wave (triangular wave) generator, GC Is a gate control circuit.

First, the DC voltage V _d detected via the isolation amplifier ISO
And apply voltage command value V _d ^* from the voltage setting unit VR to the comparator C _1, a deviation ^{_{ε V = V d * -V d}} . The deviation epsilon _V is input to control compensation circuit G _V (S), integrating amplifier or proportionately amplified, the peak value command I _m of the input current I _S.

The peak value command I _m is input to a multiplier ML, is multiplied by the other input sin .omega.t. The input signal sinωt
Is a unit sine wave synchronized with the power supply voltage V _S = V _m · sin ωt,
It is determined by detecting the power supply voltage V _S and multiplying it by a constant (1 / V _m times).

The output signal I _S ^* of the multiplier ML gives a command value of the current to be supplied from the power supply, and is expressed by the following equation.

I _S ^* = I _m · sin ωt (1) The input current command value I _S ^* is inverted by the inverting amplifier OA,
It becomes the command value I _C ^* of the AC current I _C supplied from the converter CONV to the power supply SUP. Hereinafter, I _C ^* is referred to as a converter output current command value.

Converter output current I _C is inputted to the comparator C ₂ detected by the AC current detector CT _C. Comparator said command value by C ₂ I _C ^* and the detection value I _C are compared, the deviation ε _{I = I C} ^* -
I _C is required. The deviation ε _I is calculated by the following control compensation circuit G
_{The signal} is input to _I (S), is compared and amplified, and becomes a control input signal e _i for pulse width modulation control.

Pulse width modulation control is a well-known method, and the carrier generator TR
G, is carried out the control by a comparator C ₃ and a gate control circuit GC.

That is, the carrier generator TRG has a triangle e _{T with a} frequency of about 1 kHz.
The generated, the comparator C ₃ compares the triangular wave e _T and the input signal e _i, the gate control circuit in accordance with the deviation ε _{T =} e _i -e _T
From GC, giving on and off signals to the gate turn-off thyristors S ₁ to S _4.

When e _i> e _T, that is, when the deviation epsilon _T is positive, thyristor S ₁ and S ₄ is turned on (this time S _2, S ₃ is turned off) converter AC output voltage V _C of the + V _d.

When e _i <e _T , that is, when the deviation ε _T is negative, the thyristors S ₂ and S ₃ are turned on (at this time, S ₁ and S ₄ are turned off), and V _C = −V _d .

Moreover, e _i is greater in positive values on period of the S ₁ and S ₄ are longer, the ON period of S ₂ and S ₃ is shortened, the average value of V _C is proportional to the input signal e _i It takes a positive value with voltage. vice versa
e _i is the time of the negative value is prolonged towards the S ₂ and the ON period of the S ₃ than the ON period of the S ₁ and S _4, the average value of the converter output voltage V _C is proportional to the input signal e _i The value is negative.

That is, a value proportional to the input signal e _i, so that the output voltage V _C of the converter is controlled.

(Inverted value of the input current I _S supplied from the power supply) the output current I _C of the converter is controlled by adjusting the output voltage V _C of the converter.

And the supply voltage V _S to the AC inductor L _S, the difference voltage V _L = V _S -V _C between the output voltage V _C of the converter is applied.

When V _S > V _C , the power supply current I _S increases in the direction of the arrow in the figure. It said changing the converter output current I _C acts to decrease the direction indicated by the arrow in FIG. Conversely, when V _S <V _C , the converter output current I _C tends to increase in the direction of the arrow in the figure.

Actual current I _C with respect to converter output current command value I _C ^*
When the relation of I _C ^* > I _C is satisfied, the deviation ε _I = I _C ^* −I _C becomes a positive value, and the input signal e _i of the PWM control is increased via the control compensation circuit G _I (S). Therefore, converter output voltage V _C also increases in proportion to input signal e _i , and V _C > V _S , increasing converter output current I _C in the direction of the arrow in the figure. Conversely, I _C ^* <
When it becomes I _C , the deviation ε _I becomes a negative value and e _i, that is, V _C
Decrease. Therefore, the output current I _{C of the} converter is controlled to match the command value I _C ^* . If the command value I _C ^* is changed in a sinusoidal manner, the actual current I _C is also controlled in a sinusoidal manner.

The output current I _C of the converter is the inverted value of the input current I _S from the power supply, also the command value I _C ^* of the converter output current which is a command value I _S ^* of the inverted value of the input current from the power supply. Therefore, the input current _IS is controlled to follow the command value _IS ^* .

Next will be described a control operation of the voltage V _d of the DC capacitor C _d.

By the comparator C _1, the DC voltage detection value V _d and the command value V _d
Compare ^* . V _d ^*> V if the deviation epsilon _V of _d is a positive value, through the control compensating circuit G _V (S), the input current peak value I _m
Increase. The input current command value I _S ^* is given by a sine wave having the same phase as the power supply voltage as shown by the equation (1). Therefore,
Assuming that the actual input current I _S is controlled to be I _S = I _S ^* as described above, when the peak value _Im is a positive value, the active power P _S represented by the following equation becomes a single-phase power supply. It is supplied to the DC capacitor C _d via the converter CNV from SUP.

P _S = V _S × I _S = V _m · I _m · (sinωt) ² = V _m · I _m · (1-cos2ωt) / 2 (2) Therefore, the energy P _S · t is applied to the DC capacitor C _d . As a result, the DC voltage _Vd rises.

If a V _d ^{* <V} _d Conversely, the deviation epsilon _V takes a negative value, finally reduces the peak value I _m through control compensation circuit G _V (S) and I _m <0. Therefore, the effective power P _S becomes a negative value, in turn, the energy P _S t is regenerated to the power supply from the DC capacitor C _d. As a result, the DC voltage V _d decreases,
Finally, V _d is controlled to V _d ^* .

The load device LAD is, for example, a known PWM inverter-driven induction motor or the like, and includes a DC concentrator C _d serving as a DC voltage source.
To exchange power. If the load device LAD is by consuming power, although the DC voltage V _d is lowered by the control, always controlled to V _d ≒ V _d ^* and supplies active power P _S from the power supply. Conversely, when the power regeneration from the load device LAD (if the induction motor and regenerative operation) are performed, but V _d is temporarily increased, by regenerating the active power P _S in correspondingly supply SUP, also V _d ≒ V _d ^* . That is, the load device LAD
Depending on the power consumption or power regeneration is the power P _S is supplied from the power source SUP is adjusted automatically.

Since the input current I _S at this time is controlled to a sine wave of the supply voltage in phase or opposite phase (during regenerative), naturally input power factor =
At 1, the harmonic component has a very small value.

[Problems of the prior art]

Such a conventional power converter has the following problems.

That is, if the power supply voltage varies greatly, since it must be normal operation PWM converter at its maximum value, momentum, had to operation by increasing the value of the DC voltage V _d.

FIG. 9 shows a voltage-current vector diagram at the power receiving end of a conventional power converter (FIG. 8), where V _S is a power supply voltage, I _S is an input current, and _VL is applied to an AC reactor L _S. shows voltage, V _C is the converter on the AC side output voltage, respectively. The following relational expression holds between the vectors. _S = _L + _C (3) _L = Jω · L _S · (4) ω = 2π _S : Power supply angular frequency L _S : Inductance of AC reactor When the power supply voltage _S changes like _S ′, the same. To keep the input power _S flowing, the converter must generate a voltage of _C '.

If the DC voltage of the converter was V _d, the effective value of the AC side generated voltage V _C is Becomes Where k _C is the modulation rate of the PWM converter and k _C
It becomes 1.

Therefore, by changing the modulation rate k _C , the magnitude of the AC-side generated voltage V _C of the converter can be adjusted, but the modulation rate k _C is only 1 at most.

Thus when the power supply voltage V _S as FIG. 9 is increased, since the AC side voltage V _C of the converter must be increased as V _C ', a higher value of the DC voltage V _d in advance in anticipation of it It is necessary to keep.

When the DC voltage _Vd is increased, naturally, the GTO (gate turn-off thyristor) that forms the converter
It was necessary to increase the withstand voltage of the elements and the smoothing capacitor _Cd , and the configuration of the device was complicated, and it had to be expensive.

Beyond the capacity of the AC side generated voltage V _C of the PWM converter,
When the power supply voltage V _S increases, the PWM control becomes impossible, and the operation with the input power factor = 1 cannot be performed. In addition, the waveform distortion of the input current I _S increases, and higher harmonics (particularly, lower harmonics).
And the power supply system is adversely affected in various ways.

[Object of the invention]

The present invention has been made in view of the above problems, without increasing the DC voltage value of the converter in response to an increase in the power supply voltage, to continue the normal operation of the pulse width modulation control,
It is an object of the present invention to provide a vehicular power converter in which the capacity of the device is reduced and the fluctuation of the power supply voltage is not applied as a disturbance to a control system for controlling the input current of the converter.

[Summary of the Invention]

The present invention provides a transformer in which a primary winding is connected to a current collector to obtain a single-phase AC power supply from a secondary winding, and a single-phase PWM converter in which an AC terminal is connected to the secondary winding via an AC reactor. And a DC smoothing capacitor connected between the DC terminals of the single-phase PWM converter, and an inverter having a DC side connected to the DC terminal of the PWM converter and a vehicle drive motor connected to the AC side. In the converter, means for obtaining a unit sine wave signal and a unit cosine wave signal synchronized with the single-phase AC power supply, and a command value of an input current of the single-phase PWM converter, an effective current command value and a reactive current command value thereof. And a deviation signal between the command value and the detection value of the input current of the single-phase PWM converter multiplied by the detection value of the single-phase AC power supply voltage by a predetermined coefficient, and added. PWM control of PWM converter By the force signal, the variation of the single-phase AC power source is a vehicle power conversion apparatus that does not participate as a disturbance to the control system of the input current of the single-phase PWM converter.

(Example of the invention)

FIG. 1 is a block diagram showing an embodiment of the power converter of the present invention.

In the figure, SUP is single-phase AC power source, BUS is wire-out AC, L _F wear of the wire inductance, PAN is the current collector, TR is a power transformer, L _S is AC inductor, CONV is PWM converter, C _d is DC smoothing A capacitor, INV is an inverter, M is an AC motor, WH is a wheel, and VH surrounded by a broken line represents a vehicle unit.

Further, as the control circuit, the comparator C ₁ -C _3, a control compensation circuit
G _V (S), G _I (S), proportional amplifiers K _Q , K _C , multipliers ML ₁ , M
L ₂ , sine and cosine wave generators S / C, adders A ₁ and A ₂ , and a pulse width modulation control circuit PWM are provided.

The inverter INV supplies AC motors (for example, induction motors) with three-phase AC power of variable voltage and variable frequency.
The generated torque of the electric motor is controlled according to the train speed command. Hereinafter, this part will be omitted because it is known. That is, the inverter INV and the AC motor M
Is the descriptions merely loading device of the smoothing capacitor C _d is a DC voltage source.

First, the operation of the input current control will be described. Input current I _S is detected by the current transformer CT _S, it is input to the comparator C _3.
The comparator C ₃ is the input current command value I _S ^* and the input current detection value I _S
And outputs a deviation ε _I = I _S ^* −I _S. The deviation ε
_I is input to the next current control compensation circuit G _I (S), is proportionally amplified (K _I unit). The output signal K _I · ε _I of G _I (S) is input to the pulse width modulation control circuit PWM via the adder A _2. P
The operation of the WM control has been described with reference to the conventional device and will not be described. In brief, it may be considered that the voltage V _C proportional to the input signal e _i is controlled to be generated on the AC side of the converter CONV.

For I _S ^*> I _S, the deviation epsilon _I becomes a positive value, increasing the input signal e _i of the PWM control circuit increases the output voltage V _C of the converter CONV. Therefore, the input current I _S increases in the direction of the arrow in the drawing, and calms down as I _S ≒ I _S ^* .

Conversely in the case of I _S ^{* <I} _S, deviation epsilon _I reduces the input signal e _i of become PWM control circuit and a negative value, the input current to reduce the V _C
Reduce the I _S. Therefore, it is controlled so that I _S ≒ I _S ^* . If I _S ^* is changed sinusoidally, the input current I _S is also controlled sinusoidally.

Input current I _S can be controlled by increasing or decreasing an AC output voltage V _C of the converter. At this time, the power supply voltage V _S is applied as a kind of disturbance when viewed from the input current control system. This detects the instantaneous value of the supply voltage V _S to eliminate the influence of the disturbance, and input to the adder A ₂ through a linear amplifier K _C. For this reason, the input signal e _i of the PWM control is expressed as e _i = K _I · ε _I + K _C · V _S (6), thereby generating the AC output voltage V _C = K · e _i of the converter. .

That is, by setting K _C = 1 / K, Thus, the influence of the power supply voltage can be removed.

Next will be described a control operation of the DC voltage V _d.

First, the input terminal voltage V _d of the DC smoothing capacitor C _d to a comparator C ₂ detected via an isolation amplifier or the like. The comparator C ₂ has a DC voltage command value V _d ^*, the deviation compares the voltage detection value V _d epsilon
And it outputs a _V = _{V d} ^* -V _d.

The deviation ε _V is compared or integrated and amplified through the next voltage control compensation circuit G _V (S). Integrating amplifier is an effective means when the zero steady state error epsilon _V. For the sake of simplicity of explanation, treated as only a proportional amplification (K _V times).

Output K _V · ε _{V =} I _Pm of G _V (S) is input to the next multiplier ML _2. The signal I _Pm not provide a height command of the active current component of input current I _S, it is multiplied by the unit sine wave sinωt synchronized with the power supply voltage V _S.

The unit sine wave sinωt is the detected value of the power supply voltage V _S = V _Sm
It is obtained by multiplying sinωt by (1 / V _Sm ).

The multiplier ML ₂ is configured to output the effective current peak value command I _Pm and the unit sine wave described above.
multiplied by the sinωt, active current command I _P ^* I _Pm · sinωt
Generate.

The active current command I _P ^* is the input current command I _S ^* through the adder A _1. The adder A ₁ is added together with active current command I _P ^* and the reactive current command I _Q ^{* (described} below), the input current command I _S ^{* =} but is intended to make the I _P ^{* +} I _Q ^*, wherein in order to simplify the explanation, we as I _Q ^{* =} 0.

If a V _d ^*> V _d, the deviation ε _{V = V d} ^* -V _d is a positive value, increasing the active current command I _P ^*. The input current I _S is controlled so as to match the command value I _S ^* = I _P ^*, and the active power P _S represented by the following equation is supplied from the power supply.

P _S = V _S · I _S = V _Sm · sin ωt × I _Pm · sin ωt = (V _Sm · I _Pm / 2) · (1−cos 2ωt) (8) Therefore, the DC smoothing capacitor C _d has energy P _S・ T
= (1/2) C _d V _d ² is supplied to increase the DC voltage V _d .
Eventually, V _d ≒ V _d ^* and calms down.

If a V _d ^{* <V} _d Conversely, deviation epsilon _V is a negative value, reducing the DC voltage V _d by decreasing the effective current command I _P ^* _m. Again, control is performed so that V _d ≒ V _d .

 Next, the operation of the reactive current control will be described.

First, the AC voltage V _S is detected, and the peak value V _Sm is obtained via a rectifier circuit. The AC voltage peak value V _Sm is compared with the comparator C _1.
And compared with the set voltage value _VSO . Deviation ε _S = V _SO −
The V _Sm amplified by the following operational amplifier K _Q, reactive current peak value command I
_Qm .

On the other hand, from the sine and cosine wave generator S / C, the power supply voltage V _S = V _Sm
- to generate a unit cosine wave cosωt synchronized with sin .omega.t, multiplies the reactive current peak value command I _Qm by the multiplier ML _1.

Output I _Q of the multiplier ML ₁ ^{* =} I _Qm · cosωt is invalid current instruction value.

FIG. 2 shows a specific configuration example of the sine / cosine wave generator S / C of FIG. 1, where K _S is a proportional amplifier, SH is a Schmitt circuit, _OSC is a pulse oscillator, and CN is a counting circuit. And ROM represent a read-only memory, and D / A represents a digital-to-analog converter.

A unit sine wave sinωt is obtained by detecting the power supply voltage V _S and performing a multiple of K _S = 1 / V _Sm . This is input to the next Schmitt circuit SH, and if sinωt1, the SH output is set to “1”, and if sinωt <1, the SH output is set to “0”, which is a signal for switching the up / down count of the next counter CN. . Here, the counter CN is controlled so as to be an up counter when the SH output is “1” and a down counter when the SH output is “0”. When the SH output changes from "0" to "1", the counter CN is cleared.

Pulse oscillator O _SC is intended to send a clock signal to the counter, the oscillation frequency _C is chosen to be an integral multiple of the power frequency _S. Here, it is assumed that _C = 512 · _S.

In the next read-only memory ROM, the unit cosine wave cosωt is stored between addresses 0 and 255, and the stored content is read by inputting the count number of the counter CN as an address. . The value is converted to an analog amount via a D / A converter.

FIG. 3 is a time chart for explaining the operation of FIG.

By dividing the power supply voltage V _S by the peak value V _Sm , a unit sine wave sinωt is obtained.

FIG. 3B shows an output waveform of the Schmitt circuit SH. “1” at sinωt0 and “0” at sinωt <0.
(C) shows the count value of the counter.
It is cleared when it changes to “1”, and the count value becomes 0. While the output of SH is "1", the count is up, and the count value becomes 255 in a half cycle of the power supply frequency. +1 at address 0 in ROM
A unit cosine wave which becomes 0,..., 255 at address 127 is stored, and cosωt as shown in (d) is obtained as an output of the D / A converter.

When the SH output becomes “0”, it is counted down to 255.
From the count to 0, cosωt is continuously output.

Referring back to Figure 1, the reactive current command value I _Q ^* and the active current instruction value I _P of above ^* were combined added by an adder A _1, the input current command value I _S ^{* =} I _P ^{* +} I _Q ^* is given.

FIG. 4 is a diagram showing voltage and current vectors on the AC side of the apparatus shown in FIG. 1, where _S is a power supply voltage, _S is an input current,
_C is AC side output voltage of the converter, _L represents a voltage applied to the AC reactor L _S. Each vector has the following relationship. _S = _C + _L (9) _L = jωL _{S S} (10) The case where the power supply voltage _S rises to _S ′ will be described.

In FIG. 1, the detected value V _Sm of the _peak value of the power supply voltage is the set value V
_It becomes larger than _SO , and the deviation ε _S = V _SO −V _Sm becomes a negative value. As a result, the reactive current _peak value command I _Qm = K _Q · ε _S also becomes a negative value, and the reactive current command value _IQ ^* is given so that a delayed reactive current flows. Therefore, the input current I _S is the command value I _S ^*
= I _P ^* + I _Q ^* , so that _S ′
= _S + _Q = I _S ^* . Reactor voltage applied at this time is _{L '= jωL S S'} becomes, without changing the AC side output voltage _C of the converter, it is possible to control the input current I _S '.

Therefore, even when the power supply voltage V _S rises, without being fallen uncontrolled, it is possible to control the input current to a sine wave.

FIG. 5 is a voltage-current vector diagram on the AC side during the regenerative operation. Even if the power supply voltage V _S rises to V _S ′, the reactive current _IQ is delayed in accordance therewith, so that the reactor applied voltage is increased. _VL becomes _VL ', and the input current control can be continued without increasing the value of the converter AC side voltage _C.

When the power supply voltage V _S is decreased, the deviation ε _{S =} V _SO -V _Sm becomes a positive value, is controlled to include reactive current I _Q proceeds to the input current I _S.

Figure 6 is shows the voltage-current vector diagram of the electric wire BUS subtrees of FIG. 1, considering the voltage drop due to the inductance L _F of the feeder, with respect to the power supply voltage V _G, the input current I _S flows Accordingly, the voltage V _P of the collector _point, the _{P = G -jωL F S ... (} 11). The inclusion of the reactive current I _Q delay to the input current,
V _P decreases the voltage as V _P '.

Figure 7 is by taking the reactive current I _Q proceeds similarly shows that the voltage V _P of the collector points is increased.

Thus, in the control method of FIG. 1, the voltage of the current collector PAN point V _P
If There elevated serves to lower the V _P by taking a delay current, conversely V _P is to function to increase the V _P by taking the leading current when lowered. Therefore PA
This has the effect of suppressing fluctuations in the voltage at point N.

In some cases, it may be sufficient to prevent the PWM converter from becoming inoperable in response to a rise in power supply voltage.
Then, if the output I _Qm of the proportional amplifier K _Q is positive, I _Qm
A limiter may be provided so that = 0.

〔The invention's effect〕

As described above, according to the present invention, without increasing the DC voltage value of the PWM converter with respect to an increase in the power supply voltage,
Pulse width modulation control can be normally operated and maintained. As a result, the capacity of the device can be reduced, and an economical system can be provided.

Further, the present invention exerts an excellent effect that the voltage fluctuation of the feeder is not added as a disturbance to the current control system of the single-phase PWM converter.

[Brief description of the drawings]

FIG. 1 is a configuration diagram showing an embodiment of a power converter of the present invention,
FIG. 2 is a block diagram showing a specific example of a part of FIG. 1, FIG. 3 is a time chart for explaining the operation of FIG.
7 are diagrams showing a voltage-current vector diagram on the AC side of the device of FIG. 1, FIG. 8 is a configuration diagram of a conventional power converter, and FIG. 9 is an AC-side voltage for explaining the operation of FIG. It is a current vector diagram. SUP: Single-phase AC power supply, BUS: AC feeder, L _F ... Feeder inductance, PAN: Current collector, TR: Power transformer, L _S: AC reactor, CONV: Pulse width modulation control Converter, C _d …… DC smoothing capacitor, INV …… Inverter, M …… AC motor, VH …… Train, WH …… Wheel, C ₁ -C ₃ …… Comparator, A ₁ , A ₂ … Adder , G _V (S), G _I (S): Control compensation circuit, K _Q , K _C: Operational amplifier, ML ₁ , ML _2: Multiplier, S / C: Sine wave, cosine wave generator , PWM ...... pulse width modulation control circuit, CT _S ...... current transformer.

Claims (1)

(57) [Claims] A transformer having a primary winding connected to a current collector and obtaining a single-phase AC power supply from a secondary winding, and a single-phase transformer having an AC terminal connected to the secondary winding via an AC reactor. A PWM converter, a DC smoothing capacitor connected between the DC terminals of the single-phase PWM converter, and an inverter having a DC side connected to the DC terminal of the single-phase PWM converter and a vehicle drive motor connected to the AC side. Means for obtaining a unit sine wave signal synchronized with the single-phase AC power supply, and an output of a pulse oscillator and the unit sine wave signal are applied, and the unit sine wave signal is counted up every 180 degrees. Counting means for repeating the countdown, a means for deriving a unit cosine wave signal synchronized with the unit sine wave signal from the contents of the counting means, and a command value and a detection value of a voltage of the DC smoothing capacitor. Means for calculating an effective current command value from a difference and the unit sine wave signal, and means for calculating a reactive current command value from a deviation between a command value and a detection value of a peak value of the single-phase AC power supply and the unit cosine wave signal Means for calculating a command value of the input current of the single-phase PWM converter from the effective current command value and the reactive current command value, the single-phase PWM
Means for adding the detected value of the single-phase AC power supply voltage by a predetermined coefficient to a deviation signal between the command value and the detected value of the input current of the converter, and adding the added value to the PWM control of the single-phase PWM converter A power conversion device for a vehicle, wherein the power conversion device is an input signal.