JP2020005085A - Drive circuit for switching element - Google Patents

Drive circuit for switching element Download PDF

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JP2020005085A
JP2020005085A JP2018121898A JP2018121898A JP2020005085A JP 2020005085 A JP2020005085 A JP 2020005085A JP 2018121898 A JP2018121898 A JP 2018121898A JP 2018121898 A JP2018121898 A JP 2018121898A JP 2020005085 A JP2020005085 A JP 2020005085A
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current
constant
unit
switching element
current consumption
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JP6848936B2 (en
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大祐 松本
Daisuke Matsumoto
大祐 松本
矩彦 井上
Norihiko Inoue
矩彦 井上
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Denso Corp
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Denso Corp
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/04—Modifications for accelerating switching
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/567—Circuits characterised by the use of more than one type of semiconductor device, e.g. BIMOS, composite devices such as IGBT

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Power Conversion In General (AREA)
  • Electronic Switches (AREA)

Abstract

To provide a drive circuit for switching element, capable of optimally suppressing power consumption in executing constant-current and constant-voltage driving for a voltage-drive type switching element.SOLUTION: A drive circuit 1 includes: a constant-current control amplifier 11 and a constant-voltage control amplifier 12 and current consumption adjustment sections 18 and 19 for controlling power consumption thereof, respectively. A current control section 6 individually controls the current consumption adjustment sections 18 and 19 on the basis of a driving state of an IGBT 4.SELECTED DRAWING: Figure 1

Description

本発明は、電圧駆動型のスイッチング素子を駆動する回路に関する。   The present invention relates to a circuit for driving a voltage-driven switching element.

例えばＩＧＢＴ等のパワー系のスイッチング素子を駆動する回路として、例えば特許文献１には、以下のような構成が開示されている。定電流生成部３０から流れ込む定電流の大きさに応じたオン時間でスイッチング素子５０をオンするドライバ回路４０を備える。定電流生成部３０は、スイッチング素子５０がオンするオン時間に達するまで大きい定電流を流してスイッチング素子５０の立上がり速度を高速に維持する。オン時間が経過した後は、小さい定電流を流してドライバ回路４０の消費電流を低減する。   For example, Patent Document 1 discloses the following configuration as a circuit for driving a power switching element such as an IGBT. A driver circuit 40 that turns on the switching element 50 with an on-time corresponding to the magnitude of the constant current flowing from the constant current generation unit 30 is provided. The constant current generator 30 supplies a large constant current until the ON time when the switching element 50 is turned on, and maintains the rising speed of the switching element 50 at high speed. After the lapse of the on-time, a small constant current is passed to reduce the current consumption of the driver circuit 40.

特開２０１２−１２９９７１号公報JP 2012-129971 A

ここで、駆動回路に定電流アンプ及び定電圧アンプを備え、スイッチング素子を定電流定電圧駆動することを想定する。このように構成される駆動回路では、ＩＧＢＴのゲートに印加する電圧を立ち上げる初期の段階では、定電流アンプによりゲート電圧の立上り速度を制御し、立上りの後半では定電圧アンプによってゲート電圧を所定の電圧に制御することが考えられる。また、この構成では、２つのアンプを使用することで消費電流が多くなるという問題がある。   Here, it is assumed that the driving circuit includes a constant current amplifier and a constant voltage amplifier, and the switching element is driven at a constant current and a constant voltage. In the driving circuit configured as described above, the rising speed of the gate voltage is controlled by the constant current amplifier in the initial stage of raising the voltage applied to the gate of the IGBT, and the gate voltage is controlled by the constant voltage amplifier in the latter half of the rising. It is conceivable to control to a voltage of In addition, this configuration has a problem that current consumption increases by using two amplifiers.

本発明は上記事情に鑑みてなされたものであり、その目的は、電圧駆動型のスイッチング素子を定電流定電圧駆動する際に、消費電流を最適に低減できるスイッチング素子の駆動回路を提供することにある。   The present invention has been made in view of the above circumstances, and an object of the present invention is to provide a switching element drive circuit that can optimally reduce current consumption when driving a voltage-driven switching element at a constant current and a constant voltage. It is in.

請求項１記載のスイッチング素子の駆動回路によれば、スイッチング素子のゲートを定電流駆動する定電流駆動部，及び同ゲートを定電圧駆動する定電圧駆動部に、内部における消費電流を調整する消費電流調整部を備える。そして、電流制御部は、前記ゲートの駆動状態に基づき、定電流駆動部及び定電圧駆動部の消費電流調整部を個別に制御する。このように構成すれば、スイッチング素子のゲートを駆動する過程で、定電流駆動部，定電圧駆動部のそれぞれが動作する状況に応じて、それぞれの消費電流を最適に調整して低減することができる。   According to the driving circuit for a switching element according to the first aspect, the constant current driving section for driving the gate of the switching element with a constant current and the constant voltage driving section for driving the gate with a constant voltage adjust the consumption current inside. A current adjustment unit is provided. Then, the current control unit individually controls the current consumption adjusting units of the constant current driving unit and the constant voltage driving unit based on the driving state of the gate. With this configuration, in the process of driving the gate of the switching element, it is possible to optimally adjust and reduce the current consumption of each of the constant current driver and the constant voltage driver in accordance with the situation in which each operates. it can.

請求項２記載のスイッチング素子の駆動回路によれば、電流制御部は、駆動信号がオフレベルであれば定電流駆動部及び定電圧駆動部の消費電流を低減させ、駆動信号がオンレベルになった時点から第１期間までは定電圧駆動部のみに消費電流を低減させる。そして、第１期間に続く第２期間では定電流駆動部のみに消費電流を低減させ、第２期間が終了すると定電流駆動部及び定電圧駆動部の消費電流を低減させる。   According to the driving circuit of the switching element, the current control unit reduces the current consumption of the constant current driving unit and the constant voltage driving unit when the driving signal is at the off level, and the driving signal becomes the on level. From the point in time until the first period, the current consumption is reduced only in the constant voltage drive unit. Then, in the second period following the first period, the current consumption is reduced only in the constant current driver, and when the second period ends, the current consumption in the constant current driver and the constant voltage driver is reduced.

すなわち、スイッチング素子のターンオンを開始させた直後からの第１期間は、定電流駆動部による定電流駆動を行うため、定電圧駆動部の消費電流を低減させる。そして、第１期間に続く第２期間では、定電圧駆動部による定電圧駆動を行うので、定電流駆動部の消費電流を低減させる。このように構成すれば、スイッチング素子のターンオンを制御する形態に応じて消費電流を効率的に低減できる。   That is, in the first period immediately after the start of turning on of the switching element, the constant current drive is performed by the constant current driver, so that the current consumption of the constant voltage driver is reduced. In the second period following the first period, the constant voltage driving is performed by the constant voltage driver, so that the current consumption of the constant current driver is reduced. With this configuration, the current consumption can be efficiently reduced according to the mode of controlling the turn-on of the switching element.

第１実施形態であり、駆動回路の構成を示す図FIG. 2 is a diagram illustrating a configuration of a drive circuit according to the first embodiment. アンプ部の詳細構成を示す図Diagram showing the detailed configuration of the amplifier section 消費電流調整部の詳細構成を示す図Diagram showing the detailed configuration of the current consumption adjustment unit 動作タイミングチャートOperation timing chart 第２実施形態であり、駆動回路の構成を示す図FIG. 14 is a diagram illustrating a configuration of a drive circuit according to a second embodiment. 動作タイミングチャートOperation timing chart 第３実施形態であり、駆動回路の構成を示す図FIG. 13 is a diagram illustrating a configuration of a drive circuit according to a third embodiment. 動作タイミングチャートOperation timing chart 第４実施形態であり、消費電流調整部の詳細構成を示す図FIG. 14 is a diagram illustrating a detailed configuration of a current consumption adjusting unit according to a fourth embodiment. 動作タイミングチャート（その１）Operation timing chart (1) 動作タイミングチャート（その２）Operation timing chart (2) 第５実施形態であり、駆動回路の構成を示す図FIG. 15 is a diagram illustrating a configuration of a drive circuit according to a fifth embodiment. 第６実施形態であり、駆動回路の構成を示す図FIG. 14 is a diagram illustrating a configuration of a drive circuit according to a sixth embodiment.

（第１実施形態）
図１に示すように、本実施形態の駆動回路１は、バッファ２及び駆動制御部３を備えている。外部より入力されるゲート駆動信号は、バッファ２を介して駆動制御部３に与えられる。駆動制御部３は、スイッチング素子である例えばＩＧＢＴ（Insulated Gate Bipolar Transistor）４のゲートを駆動する。ＩＧＢＴ４は、コレクタ電流を検出するための電流検出用エミッタを有している。ＩＧＢＴ４は、例えばインバータ回路を構成する素子である。 (1st Embodiment)
As shown in FIG. 1, the drive circuit 1 according to the present embodiment includes a buffer 2 and a drive control unit 3. A gate drive signal input from the outside is given to the drive control unit 3 via the buffer 2. The drive control unit 3 drives a gate of a switching element, for example, an IGBT (Insulated Gate Bipolar Transistor) 4. The IGBT 4 has a current detecting emitter for detecting a collector current. The IGBT 4 is, for example, an element that forms an inverter circuit.

駆動制御部３は、アンプ部５及び電流制御部６を備えている。アンプ部５は、ＩＧＢＴ４のゲートを定電流・定電圧駆動する。駆動回路１の入力端子７は、外付けの抵抗素子８を介して電源ＶＤＤに接続されている。駆動回路１の出力端子９は、外付けの抵抗素子１０を介してＩＧＢＴ４のゲートに接続されている。尚、駆動回路１は、集積回路として構成されている。   The drive control unit 3 includes an amplifier unit 5 and a current control unit 6. The amplifier unit 5 drives the gate of the IGBT 4 with a constant current and a constant voltage. The input terminal 7 of the drive circuit 1 is connected to a power supply VDD via an external resistor 8. The output terminal 9 of the drive circuit 1 is connected to the gate of the IGBT 4 via an external resistor 10. The drive circuit 1 is configured as an integrated circuit.

図２に示すように、アンプ部５は、定電流制御アンプ１１及び定電圧制御アンプ１２の組み合わせで構成されている。尚、アンプとして周知の詳細構成に関する説明は省略する。入力端子７は、定電流制御アンプ１１の反転入力端子に接続されている。入力端子７と出力端子９との間には、ＰチャネルＭＯＳＦＥＴ１３が接続されている。定電流制御アンプ１１のもう１つの反転入力端子は、定電圧制御アンプ１２の出力端子に接続されている。定電流制御アンプ１１の非反転入力端子は、電圧源１４の負極に接続されている。電圧源１４の正極は、電源ＶＤＤに接続されている。定電流制御アンプ１１の出力端子は、ＦＥＴ１３のゲートに接続されている。   As shown in FIG. 2, the amplifier section 5 is configured by a combination of a constant current control amplifier 11 and a constant voltage control amplifier 12. A description of a detailed configuration known as an amplifier will be omitted. The input terminal 7 is connected to an inverting input terminal of the constant current control amplifier 11. A P-channel MOSFET 13 is connected between the input terminal 7 and the output terminal 9. Another inverting input terminal of the constant current control amplifier 11 is connected to an output terminal of the constant voltage control amplifier 12. The non-inverting input terminal of the constant current control amplifier 11 is connected to the negative electrode of the voltage source 14. The positive electrode of the voltage source 14 is connected to the power supply VDD. The output terminal of the constant current control amplifier 11 is connected to the gate of the FET 13.

定電圧制御アンプ１２の非反転入力端子は、電圧源１５の正極に接続されている。定電圧制御アンプ１２の反転入力端子は、抵抗素子１６を介してグランドに接続されていると共に、抵抗素子１７を介して出力端子９に接続されている。定電流制御アンプ１１は定電流駆動部に相当し、定電圧制御アンプ１２は定電圧駆動部に相当する。   The non-inverting input terminal of the constant voltage control amplifier 12 is connected to the positive terminal of the voltage source 15. The inverting input terminal of the constant voltage control amplifier 12 is connected to ground via a resistor 16 and to the output terminal 9 via a resistor 17. The constant current control amplifier 11 corresponds to a constant current driver, and the constant voltage control amplifier 12 corresponds to a constant voltage driver.

ここで、電圧源１４，１５の電圧をそれぞれＶｒｅｆ１，Ｖｒｅｆ２とし、抵抗素子８の抵抗値をＲｓｈｕｎｔ，抵抗素子８に流れる電流をＩｇとする。この場合、定電流制御アンプ１１の反転入力端子の電位は（ＶＤＤ−Ｖｒｅｆ１）となるから、電流Ｉｇは
Ｉｇ＝Ｖｒｅｆ１／Ｒｓｈｕｎｔ
となる。したがって、例えばＶｒｅｆ１＝１Ｖ，Ｒｓｈｕｎｔ＝１Ωに設定すればＩｇ＝１Ａとなり、ＦＥＴ１３を介してＩＧＢＴ４のゲートに１Ａの電流を流すことができる。
また、定電圧制御アンプ１２は、抵抗素子１７及び１６で分圧されたゲート電圧が、電圧Ｖｒｅｆ２に等しくなるように定電流制御アンプ１１を制御する。 Here, the voltages of the voltage sources 14 and 15 are Vref1 and Vref2, respectively, the resistance value of the resistance element 8 is Rshunt, and the current flowing through the resistance element 8 is Ig. In this case, since the potential of the inverting input terminal of the constant current control amplifier 11 becomes (VDD-Vref1), the current Ig becomes Ig = Vref1 / Rshunt.
Becomes Therefore, for example, if Vref1 = 1V and Rshunt = 1Ω, Ig = 1A, and a current of 1A can flow to the gate of the IGBT 4 via the FET 13.
The constant voltage control amplifier 12 controls the constant current control amplifier 11 so that the gate voltage divided by the resistance elements 17 and 16 becomes equal to the voltage Vref2.

図１に示すように、定電流制御アンプ１１及び定電圧制御アンプ１２は、それぞれ消費電流調整部１８及び１９を備えている。これらは、例えば図３に示すように、スイッチ２０及び電流源２１の直列回路を複数並列に接続して構成されている。スイッチ２０のオンオフ制御は、電流制御部６により行われる。電流制御部６は、カウンタ２２及び制御信号出力部２３を備え、カウンタ２２には、バッファ２を介してゲート駆動信号が入力されている。カウンタ２２は、ゲート駆動信号がハイレベルを示す期間にカウント動作を行う。制御信号出力部２３は、そのカウント値に応じて消費電流調整部１８及び１９を制御する。カウンタ２２は時間監視部に相当する。   As shown in FIG. 1, the constant current control amplifier 11 and the constant voltage control amplifier 12 include current consumption adjusters 18 and 19, respectively. These are configured by connecting a plurality of series circuits of a switch 20 and a current source 21 in parallel, for example, as shown in FIG. The on / off control of the switch 20 is performed by the current control unit 6. The current control unit 6 includes a counter 22 and a control signal output unit 23, and a gate drive signal is input to the counter 22 via the buffer 2. The counter 22 performs a counting operation during a period in which the gate drive signal indicates a high level. The control signal output unit 23 controls the current consumption adjusting units 18 and 19 according to the count value. The counter 22 corresponds to a time monitoring unit.

次に、本実施形態の作用について説明する。図４に示すように、ゲート駆動信号がオフレベルのローを示している期間は、カウンタ２２はゼロクリアされている。この期間はアンプ部５が動作しないので、制御信号出力部２３は、定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を低減するように、消費電流調整部１８及び１９を制御する。そして、ゲート駆動信号がオンレベルのハイに変化するとアンプ部５が動作を開始し、カウンタ２２がカウント動作を開始する。   Next, the operation of the present embodiment will be described. As shown in FIG. 4, the counter 22 is cleared to zero during the period when the gate drive signal indicates the low level of the off level. Since the amplifier unit 5 does not operate during this period, the control signal output unit 23 controls the current consumption adjusting units 18 and 19 so as to reduce the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12. When the gate drive signal changes to the high level of the ON level, the amplifier unit 5 starts operating, and the counter 22 starts counting.

制御信号出力部２３は、カウンタ２２のカウント値が変化し始めると、定電流制御アンプ１１の消費電流を増加させるように消費電流調整部１８，図４中のＩ＿CCAMPを制御する。これに伴い定電流制御アンプ１１が動作を開始して、ＩＧＢＴ４のゲートに一定の電流Ｉｇを流す。すると、ＩＧＢＴ４のゲート容量が充電されて、ゲート電圧は上昇を開始する。 When the count value of the counter 22 starts to change, the control signal output unit 23 controls the current consumption adjusting unit 18 and I_CCAMP in FIG. 4 so as to increase the current consumption of the constant current control amplifier 11. Accordingly, the constant current control amplifier 11 starts operating, and flows a constant current Ig to the gate of the IGBT 4. Then, the gate capacitance of the IGBT 4 is charged, and the gate voltage starts to increase.

ゲート電圧がミラー電圧を超えた後にカウンタ２２のカウント値が第１所定値に達すると、制御信号出力部２３は、定電流制御アンプ１１の消費電流を低減させるように消費電流調整部１８を制御する。同時に、制御信号出力部２３は、定電圧制御アンプ１２の消費電流を増加させるように消費電流調整部１９，図４中のＩ＿CVAMPを制御する。これに伴い定電圧制御アンプ１２が動作を開始して、ゲート電圧は電圧Ｖｒｅｆ２に応じた電圧となるように制御される。 When the count value of the counter 22 reaches the first predetermined value after the gate voltage exceeds the mirror voltage, the control signal output unit 23 controls the current consumption adjusting unit 18 to reduce the current consumption of the constant current control amplifier 11. I do. At the same time, the control signal output unit 23 controls the current consumption adjusting unit 19 and I_CVAMP in FIG. 4 so as to increase the current consumption of the constant voltage control amplifier 12. Accordingly, the constant voltage control amplifier 12 starts operating, and the gate voltage is controlled to be a voltage corresponding to the voltage Vref2.

そして、ゲート電圧が前記電圧に達してＩＧＢＴ４がフルオン状態になった後、カウンタ２２のカウント値が第２所定値に達すると、制御信号出力部２３は、定電圧制御アンプ１２の消費電流を低減するように消費電流調整部１９を制御する。この時点で、カウンタ２２はゼロクリアされる。尚、カウンタ２２のカウント値が第１所定値に達するまでの期間は第１期間に相当し、第１所定値に達してから第２所定値に達するまでの期間が第２期間に相当する。   When the count value of the counter 22 reaches the second predetermined value after the gate voltage reaches the voltage and the IGBT 4 is turned on, the control signal output unit 23 reduces the current consumption of the constant voltage control amplifier 12. The current consumption adjusting unit 19 is controlled so as to perform the operation. At this point, the counter 22 is cleared to zero. Note that a period until the count value of the counter 22 reaches the first predetermined value corresponds to a first period, and a period from when the counter value reaches the first predetermined value to when it reaches the second predetermined value corresponds to a second period.

以上のように本実施形態によれば、駆動回路１に、定電流制御アンプ１１及び定電圧制御アンプ１２，並びにそれらの消費電流をそれぞれ制御する消費電流調整部１８及び１９を備える。そして、電流制御部６は、ＩＧＢＴ４のゲートの駆動状態に基づき、消費電流調整部１８及び１９を個別に制御する。このように構成すれば、ＩＧＢＴ４のゲートを駆動する過程で、定電流制御アンプ１１，定電圧制御アンプ１２のそれぞれが動作する状況に応じて、それぞれの消費電流を最適に調整して低減することができる。   As described above, according to the present embodiment, the drive circuit 1 includes the constant current control amplifier 11 and the constant voltage control amplifier 12, and the current consumption adjusting units 18 and 19 that control the current consumption of the amplifiers. Then, the current control unit 6 individually controls the current consumption adjusting units 18 and 19 based on the driving state of the gate of the IGBT 4. With such a configuration, in the process of driving the gate of the IGBT 4, the current consumption of each of the constant current control amplifier 11 and the constant voltage control amplifier 12 is optimally adjusted and reduced in accordance with the situation in which each operates. Can be.

具体的には、ゲート駆動信号がオフレベルであれば定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を低減させ、ゲート駆動信号がオンレベルになった時点から第１期間までは定電圧制御アンプ１２のみに消費電流を低減させる。そして、第１期間に続く第２期間では定電流制御アンプ１１のみに消費電流を低減させ、第２期間が終了すると再び定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を低減させる。   More specifically, if the gate drive signal is at the off level, the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12 is reduced. Only the control amplifier 12 reduces the current consumption. Then, in the second period following the first period, the current consumption is reduced only to the constant current control amplifier 11, and when the second period ends, the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12 is reduced again.

すなわち、ＩＧＢＴ４のターンオンを開始させた直後からの第１期間は、定電流制御アンプ１１による定電流駆動を行うため、定電圧制御アンプ１２の消費電流を低減させる。そして、第１期間に続く第２期間では定電圧制御アンプ１２による定電圧駆動を行うので、定電流制御アンプ１１の消費電流を低減させる。このように構成すれば、ＩＧＢＴ４のターンオンを制御する形態に応じて消費電流を効率的に低減できる。   That is, in the first period immediately after the turn-on of the IGBT 4 is started, the constant current drive by the constant current control amplifier 11 is performed, so that the current consumption of the constant voltage control amplifier 12 is reduced. Then, in the second period following the first period, the constant voltage drive by the constant voltage control amplifier 12 is performed, so that the current consumption of the constant current control amplifier 11 is reduced. With this configuration, the current consumption can be efficiently reduced according to the mode of controlling the turn-on of the IGBT 4.

そして、電流制御部６は、ゲート駆動信号がオンレベルになった時点から、カウンタ２２のカウント値が第１所定値に達することで一定時間が経過すると、第１期間を終了して第２期間を開始する。そして、カウンタ２２のカウント値が第２所定値に達すると第２期間を終了する。これにより、カウンタ２２のカウント値に応じて、第１期間及び第２期間の長さを調整できる。また、消費電流調整１８及び１９を、スイッチ２０と電流源２１との直列回路で構成し、その直列回路を複数並列に接続して構成したので、簡単な構成で消費電流を調整できる。   The current control unit 6 terminates the first period and ends the second period when a certain period of time has elapsed since the count value of the counter 22 has reached the first predetermined value from the point in time when the gate drive signal has turned on. To start. Then, when the count value of the counter 22 reaches the second predetermined value, the second period ends. Thereby, the lengths of the first period and the second period can be adjusted according to the count value of the counter 22. In addition, since the current consumption adjustments 18 and 19 are configured by a series circuit of the switch 20 and the current source 21 and a plurality of the series circuits are connected in parallel, the current consumption can be adjusted with a simple configuration.

（第２実施形態）
以下、第１実施形態と同一部分には同一符号を付して説明を省略し、異なる部分について説明する。図５に示すように、第２実施形態の駆動回路３１は、駆動制御部３に替わる駆動制御部３２を備えている。駆動制御部３２は、電流制御部６に替わる電流制御部３３を備えている。電流制御部３３は、ゲート電圧モニタ部３４及び制御信号出力部３５を備えている。 (2nd Embodiment)
Hereinafter, the same portions as those of the first embodiment are denoted by the same reference numerals, and description thereof will be omitted. Only different portions will be described. As shown in FIG. 5, the drive circuit 31 according to the second embodiment includes a drive control unit 32 instead of the drive control unit 3. The drive control unit 32 includes a current control unit 33 replacing the current control unit 6. The current control unit 33 includes a gate voltage monitoring unit 34 and a control signal output unit 35.

ゲート電圧モニタ部３４には、駆動回路３１の入力端子３６を介してＩＧＢＴ４のゲート電圧が入力されている。ゲート電圧モニタ部３４は電圧監視部に相当する。ゲート電圧モニタ部３４は、ゲート電圧が閾値Ｖｔｈに達すると、制御信号出力部３５にトリガ信号を出力する。制御信号出力部３５には、バッファ２を介してゲート駆動信号が入力されている。   The gate voltage of the IGBT 4 is input to the gate voltage monitor 34 via the input terminal 36 of the drive circuit 31. The gate voltage monitor 34 corresponds to a voltage monitor. When the gate voltage reaches the threshold value Vth, the gate voltage monitoring unit outputs a trigger signal to the control signal output unit. The gate drive signal is input to the control signal output unit 35 via the buffer 2.

次に、第２実施形態の作用について説明する。図６に示すように、制御信号出力部３５は、ゲート駆動信号がローレベルの期間は第１実施形態と同様に、定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を低減するように消費電流調整部１８及び１９を制御する。ゲート駆動信号がハイレベルに変化するとアンプ部５が動作を開始するが、制御信号出力部３５は、アンプ部５がＩＧＢＴ４のゲート電圧の上昇を開始させる前に、定電流制御アンプ１１の消費電流を増加させるように消費電流調整部１８を制御する。そして、定電流制御アンプ１１による定電流駆動が行われる。   Next, the operation of the second embodiment will be described. As shown in FIG. 6, the control signal output unit 35 reduces the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12 during the period when the gate drive signal is at the low level, as in the first embodiment. It controls the current consumption adjusters 18 and 19. When the gate drive signal changes to the high level, the amplifier unit 5 starts operating. However, the control signal output unit 35 outputs the current consumption of the constant current control amplifier 11 before the amplifier unit 5 starts increasing the gate voltage of the IGBT 4. Is controlled to increase the current consumption. Then, constant current driving by the constant current control amplifier 11 is performed.

ゲート電圧がミラー電圧を超えた後閾値電圧Ｖｔｈに達すると、ゲート電圧モニタ部３４が制御信号出力部３５にトリガ信号を出力する。これにより第１期間が終了し、第２期間の開始となる。すると、制御信号出力部３５は、定電流制御アンプ１１の消費電流を低減させるように消費電流調整部１８を制御し、定電流駆動が終了する。また、制御信号出力部３５は、定電圧制御アンプ１２の消費電流を増加させるように消費電流調整部１９を制御し、これに伴い定電圧制御アンプ１２が動作を開始して定電圧駆動が行われる。   When the gate voltage reaches the threshold voltage Vth after exceeding the mirror voltage, the gate voltage monitoring unit outputs a trigger signal to the control signal output unit. This ends the first period and starts the second period. Then, the control signal output unit 35 controls the current consumption adjusting unit 18 so as to reduce the current consumption of the constant current control amplifier 11, and the constant current driving ends. Further, the control signal output unit 35 controls the current consumption adjusting unit 19 so as to increase the current consumption of the constant voltage control amplifier 12, and accordingly, the constant voltage control amplifier 12 starts operating to perform the constant voltage drive. Be done.

そして、制御信号出力部３５は、トリガ信号が与えられてからＩＧＢＴ４がフルオン状態になった後、一定時間が経過すると、定電圧制御アンプ１２の消費電流を低減するように消費電流調整部１９を制御する。これに伴い、定電圧駆動が終了する。   Then, the control signal output unit 35 controls the current consumption adjusting unit 19 so as to reduce the current consumption of the constant voltage control amplifier 12 when a certain period of time elapses after the IGBT 4 is fully turned on after the trigger signal is given. Control. Accordingly, the constant voltage driving ends.

以上のように第２実施形態によれば、電流制御部３３は、ＩＧＢＴ４のゲート電圧を監視するゲート電圧モニタ部３４を備え、ゲート電圧が閾値Ｖｔｈに達すると第２期間を開始する。これにより、ＩＧＢＴ４のゲート電圧の変化に応じて、定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を最適に低減することができる。   As described above, according to the second embodiment, the current control unit 33 includes the gate voltage monitoring unit 34 that monitors the gate voltage of the IGBT 4, and starts the second period when the gate voltage reaches the threshold Vth. Thus, the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12 can be optimally reduced according to the change in the gate voltage of the IGBT 4.

（第３実施形態）
図７に示すように、第３実施形態の駆動回路４１は、駆動制御部４２を備えている。駆動制御部４２は、電流制御部４３を備えている。電流制御部４３は、第２実施形態のゲート電圧モニタ部３４を電流モニタ部４４に置き換えたものである。電流モニタ部４４は、入力端子９とＩＧＢＴ４のゲートとの間に流れる電流を監視する。そして、電流モニタ部４４は、監視している電流値が減少する過程で閾値Ｉｔを下回ると、制御信号出力部３５にトリガ信号を出力する。電流モニタ部４４は電流監視部に相当する。 (Third embodiment)
As shown in FIG. 7, the drive circuit 41 according to the third embodiment includes a drive control unit 42. The drive control unit 42 includes a current control unit 43. The current control unit 43 is obtained by replacing the gate voltage monitoring unit 34 of the second embodiment with a current monitoring unit 44. The current monitor 44 monitors a current flowing between the input terminal 9 and the gate of the IGBT 4. Then, the current monitoring unit 44 outputs a trigger signal to the control signal output unit 35 when the current value being monitored falls below the threshold value It in the process of decreasing. The current monitor 44 corresponds to a current monitor.

次に、第３実施形態の作用について説明する。図８に示すように、制御信号出力部３５は、ゲート駆動信号がローレベルからハイレベルに変化すると、第２実施形態と同様に動作する。そして、ＩＧＢＴ４がフルオン状態に近付く直前にゲート電流Ｉｇが減少して閾値Ｉｔを下回ると、電流モニタ部４４は制御信号出力部３５にトリガ信号を出力する。これにより第１期間が終了し、第２期間の開始となる。すると、制御信号出力部３５は、定電流制御アンプ１１の消費電流を低減させるように消費電流調整部１８を制御し、定電流駆動が終了する。また、制御信号出力部３５は、定電圧制御アンプ１２の消費電流を増加させるように消費電流調整部１９を制御し、これに伴い定電圧制御アンプ１２が動作を開始して定電圧駆動が行われる。以降の動作は第２実施形態と同様である。   Next, the operation of the third embodiment will be described. As shown in FIG. 8, when the gate drive signal changes from a low level to a high level, the control signal output unit 35 operates in the same manner as in the second embodiment. Then, when the gate current Ig decreases and falls below the threshold value It just before the IGBT 4 approaches the full-on state, the current monitor unit 44 outputs a trigger signal to the control signal output unit 35. This ends the first period and starts the second period. Then, the control signal output unit 35 controls the current consumption adjusting unit 18 so as to reduce the current consumption of the constant current control amplifier 11, and the constant current driving ends. Further, the control signal output unit 35 controls the current consumption adjusting unit 19 so as to increase the current consumption of the constant voltage control amplifier 12, and accordingly, the constant voltage control amplifier 12 starts operating to perform the constant voltage drive. Be done. Subsequent operations are the same as in the second embodiment.

以上ように第３実施形態によれば、電流制御部４３は、ＩＧＢＴ４のゲート電流を監視する電流モニタ部４４を備え、ゲート電流が閾値Ｉｔｈを下回ると第２期間を開始する。これにより、ゲート電流の変化に応じて、定電流制御アンプ１１及び定電圧制御アンプ１２の消費電流を最適に低減することができる。   As described above, according to the third embodiment, the current control unit 43 includes the current monitoring unit 44 that monitors the gate current of the IGBT 4, and starts the second period when the gate current falls below the threshold value Ith. Thereby, the current consumption of the constant current control amplifier 11 and the constant voltage control amplifier 12 can be optimally reduced according to the change in the gate current.

その他、電源ＶＤＤとＦＥＴ１３のソースとの間に流れる電流を監視しても良い。また、ＩＧＢＴ４の電流検出用エミッタにシャント抵抗を接続し、電流モニタ部４４はシャント抵抗４５の端子電圧により電流を監視しても良い。また、電流センサを用いても良い。   In addition, the current flowing between the power supply VDD and the source of the FET 13 may be monitored. Further, a shunt resistor may be connected to the current detecting emitter of the IGBT 4, and the current monitor 44 may monitor the current by the terminal voltage of the shunt resistor 45. Further, a current sensor may be used.

（第４実施形態）
第４実施形態は、図９に示すように、消費電流調整部１８及び１９に替えて、消費電流調整部４５及び４６を備える。定電流制御アンプ１１及び定電圧制御アンプ１２とグランドとの間には、ＰチャネルＭＯＳＦＥＴ４７及び抵抗素子４８の直列回路が接続されており、ＦＥＴ４７のドレインは、オペアンプ４９の反転入力端子に接続されている。オペアンプ４９の非反転入力端子には、可変電圧源５０の電圧が与えられている。消費電流調整部４５及び４６は、電流制御アンプとして構成されている。 (Fourth embodiment)
As shown in FIG. 9, the fourth embodiment includes current consumption adjusting units 45 and 46 instead of the current consumption adjusting units 18 and 19. A series circuit of a P-channel MOSFET 47 and a resistance element 48 is connected between the constant current control amplifier 11 and the constant voltage control amplifier 12 and the ground, and the drain of the FET 47 is connected to the inverting input terminal of the operational amplifier 49. I have. The voltage of the variable voltage source 50 is supplied to a non-inverting input terminal of the operational amplifier 49. The current consumption adjusting units 45 and 46 are configured as current control amplifiers.

次に、第４実施形態の作用について説明する。例えば第１実施形態の構成において、電流制御部６に可変電圧源５０の電圧を制御させる。これにより、第１期間から第２期間に移行させる際に、消費電流調整部４５により消費電流をリニアに減少させ、消費電流調整部４６により消費電流をリニアに増加させる。   Next, the operation of the fourth embodiment will be described. For example, in the configuration of the first embodiment, the current control unit 6 controls the voltage of the variable voltage source 50. Thus, when shifting from the first period to the second period, the current consumption is linearly reduced by the current consumption adjusting unit 45 and the current consumption is linearly increased by the current consumption adjusting unit 46.

すなわち、第１実施形態のようにスイッチ２０のオンオフで制御すると消費電流の変化量が大きくなり、第１期間から第２期間に移行する過程でゲート電圧にリンギングが発生する可能性が有る。これに対して、図１０に示すように、消費電流の減少及び増加に一定の傾きを付与することで、ゲート電圧に与える影響を低減できる。   That is, when control is performed by turning on and off the switch 20 as in the first embodiment, the amount of change in current consumption increases, and ringing may occur in the gate voltage during the transition from the first period to the second period. On the other hand, as shown in FIG. 10, the influence on the gate voltage can be reduced by giving a constant slope to the decrease and increase in the current consumption.

また、第４実施形態の構成によれば、図１１に示すように、第１期間において消費電流調整部４６により消費電流を低減するレベルを、第１実施形態よりも若干上昇させる制御も可能になる。これにより、消費電流は若干増加するが、第１期間から第２期間に移行する際の電流変化量が小さくなるので、図１０のケースと同様の効果が得られる。尚、図１０に示す制御と併せて行っても良い。   In addition, according to the configuration of the fourth embodiment, as shown in FIG. 11, it is possible to control the level of reducing the current consumption by the current consumption adjusting unit 46 in the first period to slightly increase the level compared to the first embodiment. Become. As a result, although the current consumption is slightly increased, the amount of change in the current when shifting from the first period to the second period is reduced, so that the same effect as in the case of FIG. The control may be performed in combination with the control shown in FIG.

（第５実施形態）
図１２に示すように、第５実施形態では、第１実施形態の駆動回路１によりＩＧＢＴ４を駆動する際に、外付けのＮＰＮトランジスタ５１を追加してＩＧＢＴ４とダーリントン接続する。トランジスタ５１のコレクタは入力端子７に接続され、ベースは抵抗素子１０に接続されている。そして、トランジスタ５１のエミッタはＩＧＢＴ４のゲートに接続されている。すなわち、駆動回路１がトランジスタ５１を介してＩＧＢＴ４を駆動する。これにより、ＩＧＢＴ４のゲートには、トランジスタ５１を介して駆動電流が供給されるので、アンプ部５の消費電流を低減できる。 (Fifth embodiment)
As shown in FIG. 12, in the fifth embodiment, when the IGBT 4 is driven by the drive circuit 1 of the first embodiment, an external NPN transistor 51 is added to make a Darlington connection with the IGBT 4. The collector of the transistor 51 is connected to the input terminal 7, and the base is connected to the resistance element 10. The emitter of the transistor 51 is connected to the gate of the IGBT4. That is, the drive circuit 1 drives the IGBT 4 via the transistor 51. Thus, the drive current is supplied to the gate of the IGBT 4 via the transistor 51, so that the current consumption of the amplifier unit 5 can be reduced.

（第６実施形態）
図１３に示すように、第６実施形態の駆動回路１Ｄは、駆動制御部３Ｄが２つのＩＧＢＴ４Ａ，４Ｂを並列に駆動するように、第１実施形態の駆動制御部３に対応する構成を２組備えている。この場合、駆動される負荷の消費電流量に応じてＩＧＢＴ４Ａ及び４Ｂを同時にオンオフさせても良いし、何れか一方のみを駆動させても良い。後者のケースについては、駆動させない方のＩＧＢＴ４に対応する消費電流制御部１８及び１９の消費電流を低減した状態に維持するように、電流制御部６Ｄを調整する。 (Sixth embodiment)
As shown in FIG. 13, the drive circuit 1D of the sixth embodiment has a configuration corresponding to the drive control unit 3 of the first embodiment, such that the drive control unit 3D drives the two IGBTs 4A and 4B in parallel. Has a pair. In this case, the IGBTs 4A and 4B may be turned on and off simultaneously or only one of them may be driven according to the amount of current consumed by the load to be driven. In the latter case, the current control unit 6D is adjusted so that the current consumption of the current consumption control units 18 and 19 corresponding to the IGBT 4 not to be driven is maintained in a reduced state.

（その他の実施形態）
ＩＧＢＴ４は、電流検出用のエミッタを有しないものでも良い。
スイッチ２０及び電流源２１の直列回路を１組だけで消費電流調整部を構成しても良い。
スイッチング素子はＩＧＢＴ４に限ることなく、電圧駆動型の素子であれば良い。
第６実施形態の構成において、３素子以上を並列に駆動するように構成しても良い。
各実施形態を適宜組み合わせて実施しても良い。
本開示は、実施例に準拠して記述されたが、本開示は当該実施例や構造に限定されるものではないと理解される。本開示は、様々な変形例や均等範囲内の変形をも包含する。加えて、様々な組み合わせや形態、さらには、それらに一要素のみ、それ以上、あるいはそれ以下、を含む他の組み合わせや形態をも、本開示の範疇や思想範囲に入るものである。 (Other embodiments)
The IGBT 4 may not have an emitter for current detection.
The current consumption adjusting unit may be configured with only one set of the series circuit of the switch 20 and the current source 21.
The switching element is not limited to the IGBT 4 and may be a voltage-driven element.
In the configuration of the sixth embodiment, three or more elements may be driven in parallel.
The respective embodiments may be implemented in combination as appropriate.
Although the present disclosure has been described with reference to the embodiments, it is understood that the present disclosure is not limited to the embodiments and the structures. The present disclosure also encompasses various modifications and variations within an equivalent range. In addition, various combinations and forms, and other combinations and forms including only one element, more or less, are also included in the scope and spirit of the present disclosure.

図面中、１は駆動回路、３は駆動制御部、４はＩＧＢＴ、５はアンプ部、６は電流制御部、１１は定電流制御アンプ、１２は定電圧制御アンプ、１８及び１９は消費電流調整部、２０はスイッチ、２１は電流源、２２はカウンタ、２３は制御信号出力部である。   In the drawing, 1 is a drive circuit, 3 is a drive control unit, 4 is an IGBT, 5 is an amplifier unit, 6 is a current control unit, 11 is a constant current control amplifier, 12 is a constant voltage control amplifier, and 18 and 19 are current consumption adjustments. , 20 is a switch, 21 is a current source, 22 is a counter, and 23 is a control signal output unit.

Claims (11)

入力される駆動信号に応じて電圧駆動型のスイッチング素子（４）を駆動するもので、
前記スイッチング素子のゲートを定電流駆動するもので、内部における消費電流を調整する消費電流調整部（１８，４５）を有する定電流駆動部（１１）と、
前記ゲートを定電圧駆動するもので、内部における消費電流を調整する消費電流調整部（１９，４６）を有する定電圧駆動部（１２）と、
前記ゲートの駆動状態に基づいて、前記定電流駆動部及び前記定電圧駆動部の消費電流調整部を個別に制御する電流制御部（６，６Ｄ，３３，４３）とを備えるスイッチング素子の駆動回路。 A voltage-driven switching element (4) is driven according to an input drive signal.
A constant current drive section (11) for driving a gate of the switching element at a constant current and having a current consumption adjusting section (18, 45) for adjusting current consumption inside;
A constant voltage driving section (12) for driving the gate at a constant voltage and having a current consumption adjusting section (19, 46) for adjusting current consumption inside;
A drive circuit for a switching element, comprising: a current control unit (6, 6D, 33, 43) that individually controls the constant current drive unit and the current consumption adjustment unit of the constant voltage drive unit based on the drive state of the gate. . 前記電流制御部は、
前記駆動信号がオフレベルであれば、前記定電流駆動部及び前記定電圧駆動部に消費電流を低減させ、
前記駆動信号がオンレベルになった時点から第１期間までは、前記定電圧駆動部のみに消費電流を低減させ、
前記第１期間に続く第２期間では、前記定電流駆動部のみに消費電流を低減させ、
前記第２期間が終了すると、前記定電流駆動部及び前記定電圧駆動部に消費電流を低減させる請求項１記載のスイッチング素子の駆動回路。 The current controller,
If the drive signal is off level, reduce the current consumption in the constant current drive unit and the constant voltage drive unit,
From the time when the drive signal is turned on to the first period, the current consumption is reduced only to the constant voltage drive unit,
In the second period following the first period, the current consumption is reduced only in the constant current driver,
2. The switching element drive circuit according to claim 1, wherein when the second period ends, the constant current driver and the constant voltage driver reduce current consumption. 前記電流制御部（３３）は、前記ゲート電圧を監視する電圧監視部（３４）を備え、
前記ゲート電圧が閾値に達すると、前記第２期間を開始する請求項２記載のスイッチング素子の駆動回路。 The current control unit (33) includes a voltage monitoring unit (34) that monitors the gate voltage,
The driving circuit according to claim 2, wherein the second period starts when the gate voltage reaches a threshold value. 前記電流制御部（４３）は、前記定電流駆動部より供給される電流を監視する電流監視部（４４）を備え、
前記電流が閾値を下回ると、前記第２期間を開始する請求項２又は３記載のスイッチング素子の駆動回路。 The current control unit (43) includes a current monitoring unit (44) that monitors a current supplied from the constant current driving unit,
4. The switching element drive circuit according to claim 2, wherein the second period starts when the current falls below a threshold. 前記電流制御部（６）は、前記駆動信号がオンレベルになった時点から計時を行う時間監視部（２２）を備え、
前記計時時間が一定時間になると、前記第２期間を開始する請求項２から４の何れか一項に記載のスイッチング素子の駆動回路。 The current control unit (6) includes a time monitoring unit (22) that measures time from a time point when the drive signal is turned on,
The driving circuit for a switching element according to any one of claims 2 to 4, wherein the second period starts when the counted time reaches a predetermined time. 前記消費電流調整部（４６）は、前記第１期間において、前記定電流駆動部の消費電流を一定量流すように制御する請求項２から５の何れか一項に記載のスイッチング素子の駆動回路。   The driving circuit for a switching element according to any one of claims 2 to 5, wherein the current consumption adjusting unit (46) controls the constant current driving unit to flow a constant amount of current during the first period. . 前記消費電流調整部（１８，１９）は、電流源（２１）とスイッチ（２０）との直列回路で構成される請求項１から６の何れか一項に記載のスイッチング素子の駆動回路。   The driving circuit for a switching element according to any one of claims 1 to 6, wherein the current consumption adjusting unit (18, 19) is configured by a series circuit of a current source (21) and a switch (20). 前記消費電流調整部は、前記直列回路を複数備え、それらが並列に接続されて構成される請求項７記載のスイッチング素子の駆動回路。   The driving circuit for a switching element according to claim 7, wherein the current consumption adjusting unit includes a plurality of the series circuits, and the series circuits are connected in parallel. 前記消費電流調整部（４５，４６）は、電流制御アンプで構成される請求項１から６の何れか一項に記載のスイッチング素子の駆動回路。   The driving circuit for a switching element according to any one of claims 1 to 6, wherein the current consumption adjusting unit (45, 46) includes a current control amplifier. 本体が集積回路で構成され、前記集積回路の外部に、前記スイッチング素子に通電する電流量を増幅する電流増幅用素子（５１）を備える請求項１から９の何れか一項に記載のスイッチング素子の駆動回路。   The switching element according to any one of claims 1 to 9, wherein the main body is formed of an integrated circuit, and a current amplification element (51) for amplifying an amount of current flowing through the switching element is provided outside the integrated circuit. Drive circuit. 複数のスイッチング素子を並列に駆動可能に構成される請求項１から１０の何れか一項に記載のスイッチング素子の駆動回路。   The driving circuit for a switching element according to any one of claims 1 to 10, wherein a plurality of switching elements can be driven in parallel.
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