JP2013168812A - Signal generating method and signal generating system - Google Patents

Abstract

PROBLEM TO BE SOLVED: To generate a waveform with small memory and in a short time made by addition composition of a plurality of signal waveforms with different sampling rates.SOLUTION: A signal generating method includes the steps of: grouping communication standards which have a relation of their sampling rates being an integral multiple among communication standards of a wave composition target, and generating a preliminary composite waveform made by addition composition by coordinating sampling rates in advance per group (S1); generating a signal waveform in accordance with communication standards not belonging to any group as an outside group signal waveform (S2); storing those in a memory (S3); then, reading out the preliminary composite waveform and the outside group signal waveform from the memory (S4); getting all signals to have a common sampling rate by performing rate conversion processing using a digital filter (S5), and then performing addition wave composition (S6); and generating a high-frequency test signal orthogonally modulated by the wave composite signal waveform (S7).

Description

  The present invention relates to a system for testing a base station supporting a plurality of standards or a device used therefor, reducing the capacity of a waveform memory required for adding and transmitting waveforms having different sampling rates depending on the standards, The present invention relates to a technique for reducing the time required for waveform generation.

  Although the communication standards for mobile terminals are increasing year by year, the standards differ depending on the carrier providing the service, and a plurality of standards are mixed.

  In order to cope with such a situation, it is required that a single base station can support a so-called multi-standard that supports a plurality of standards, and even 3GPP has adopted TS-37.104 / 37.141 as a multi-radio standard to E- Transmission / reception test standards for UTRA (LTE), UTRA, and base stations that support a plurality of GSM (registered trademark) / EDGE standards or devices (power amplifiers, etc.) used therefor have been specified.

  In the test corresponding to the multi-standard, transmission / reception is performed by combining signals of different communication standards. FIG. 13 shows an example of a multicarrier signal in which all three of E-UTRA (LTE), UTRA (FDD / W-CDMA) and GSM (registered trademark) / EDGE having different frequency bands are combined.

  For this reason, it is necessary to combine waveforms of different signals. With regard to such a technique, Patent Document 1 discloses a technique for adding a signal and an interference wave to generate a new signal.

JP 2006-029862 A

  However, the technique disclosed in Patent Document 1 adds signals having the same sampling rate, whereas in the multi-standard described above, it is necessary to synthesize signal waveforms having different sampling rates depending on the communication standard.

  When generating such a waveform, it is relatively easy to create a signal combining E-UTRA (30.72 MHz) and UTRA (3.84 MHz) having a sampling rate of an integral multiple, but GSM ( (Registered trademark) / EDGE has a sampling rate of 270.833 kHz, which is significantly different from the other two, and has no integer multiple relationship.

  Therefore, in order to generate a signal that combines these three standards as one waveform pattern, it becomes difficult to match the sampling rate of E-UTRA, UTRA, and GSM (registered trademark) / EDGE with the period of the signal, There is a problem that the waveform size to be generated becomes large, it takes time to generate the waveform, and it does not fit in the memory provided in the signal generator.

  An object of the present invention is to solve this problem and to provide a signal generation method and a signal generation system that can generate a waveform obtained by adding and synthesizing a plurality of signal waveforms having different sampling rates in a short time with a small amount of memory.

In order to achieve the above object, the signal generation method of the present invention comprises:
Of three or more types of communication standards with different sampling rates, those with a sampling rate that is an integer multiple are grouped as preliminary synthesis target communication standards, and the one with the lower sampling rate in the group The signal waveform of the communication standard is combined with the signal waveform of the communication standard having a higher sampling rate by interpolation processing of the integral multiple, and then added and synthesized to generate a preliminary synthesized waveform for each group. Generating a signal waveform of a communication standard that does not belong to the group as a signal waveform outside the group and storing it in a memory (S1 to S3),
Reading the preliminary synthesized waveform and the out-of-group signal waveform stored in the memory in time series at respective sampling rates (S4);
Of the read pre-synthesis waveform and out-of-group signal waveform, at least the signal waveform having the lowest sampling rate is subjected to rate conversion processing using a digital filter, and the read out pre-synthesis waveform and out-of-group signal A step of making all the waveforms have a common sampling rate (S5);
Adding the pre-synthesis waveform and the out-of-group signal waveform having the common sampling rate (S6);
Generating a high-frequency test signal orthogonally modulated with the combined signal waveform obtained by the addition processing (S7).

Further, the signal generation system of the present invention includes:
Of three or more types of communication standards with different sampling rates, those with a sampling rate that is an integer multiple are grouped as preliminary synthesis target communication standards, and the one with the lower sampling rate in the group The signal waveform of the communication standard is combined with the signal waveform of the communication standard having a higher sampling rate by interpolation processing of the integral multiple, and then added and synthesized to generate a preliminary synthesized waveform for each group. A waveform data generation unit (21) that generates a signal waveform of a communication standard that does not belong to the group as a signal waveform outside the group;
A waveform data memory (31) for storing the pre-synthesis waveform and the out-of-group signal waveform generated by the waveform data generation unit;
The preliminary synthesized waveform and the out-of-group signal waveform stored in the memory are read in time series at the respective sampling rates, and at least the signal waveform having the lowest sampling rate is selected from the read out preliminary synthesized waveform and the out-of-group signal waveform. A rate conversion unit (32) that performs a rate conversion process using a digital filter and outputs all of the read pre-synthesis waveform and the out-of-group signal waveform at a common sampling rate;
An addition unit (45) for adding the pre-synthesis waveform and the out-of-group signal waveform output at a common sampling rate from the rate conversion unit;
A quadrature modulation unit (50) for generating a high-frequency test signal that is quadrature modulated with the combined signal waveform obtained by the addition unit.

  As described above, according to the present invention, communication standards having a sampling rate that is an integral multiple of the communication standards to be combined are grouped, and a pre-combined waveform is generated by adding and combining the sampling rates in advance for each group. At the same time, a signal waveform of a communication standard that does not belong to any group is generated as a signal waveform outside the group, and these are stored in the memory. Then, while reading the preliminary synthesized waveform and the out-of-group signal waveform from this memory, the rate conversion process using the digital filter is performed to make all the signals have a common sampling rate, and then the combined signal waveform is obtained. A high-frequency test signal that has been quadrature-modulated with is generated.

  Therefore, a waveform obtained by adding and synthesizing a plurality of signal waveforms having different sampling rates can be generated in a short time with a small amount of memory.

The flowchart which shows the procedure of the signal generation method of this invention Overall configuration diagram of the signal generation system of the present invention The figure which shows the structural example of the signal generator main body of a signal generation system Configuration diagram of rate converter Operation explanatory diagram of rate conversion processing of M / N = 4 of the embodiment Diagram showing filter coefficient storage example and reading order Timing chart of M / N = 4 rate conversion processing of embodiment Operation explanatory diagram of rate conversion processing of M / N = 4/3 of the embodiment Operation explanatory diagram of rate conversion processing of M / N = 4/3 of the embodiment Operation explanatory diagram of rate conversion processing of M / N = 4/3 of the embodiment Timing chart of rate conversion processing of M / N = 4/3 in the embodiment The figure which shows the modification of the principal part The figure which shows the allocation frequency band of three different communication standards

Hereinafter, embodiments of the present invention will be described with reference to the drawings.
First, the procedure of the signal generation method of the present invention will be described based on the flowchart of FIG.

  First, among three or more types of communication standards to be combined with different sampling rates, communication standards having a sampling rate that is an integer multiple are grouped as communication standards to be pre-combined. The signal waveform of the communication standard having the lower sampling rate is matched with the signal waveform of the communication standard having the higher sampling rate by the interpolation processing of the integral multiple, and then added and synthesized, and the preliminary synthesized waveforms G1, G2,. In addition to the generation (S1), signal waveforms of communication standards not belonging to any of the groups are generated as out-of-group signal waveforms E1, E2,... (S2), and stored in the memory (S3). The signal waveform referred to here is a two-line signal composed of baseband signals I and Q having two orthogonal phases.

  These signal waveforms are frequency offset by a predetermined amount. Referring to FIG. 13 as an example, among the signals to be output, the center frequency f1 of the GSM (registered trademark) signal waveform in the lowest frequency band and the center frequency f6 of the GSM (registered trademark) signal waveform in the highest frequency band. An intermediate frequency f0 is set as a reference frequency. The frequency difference between the reference frequency f0 and each signal waveform is used as the frequency offset value of each signal waveform, and the corresponding signal waveform is generated with the frequency offset corresponding to the frequency offset value. For example, since the center frequency of the E-UTRA (LTE) signal waveform is f4, the frequency offset value is (f4-f0).

  Here, as described above, the communication standards to be combined are E-UTRA (sampling rate 30.72 MHz), UTRA (sampling rate 3.84 MHz), GSM (registered trademark) / EDGE (sampling rate 270.833 kHz). If there are three types, the two communication standards E-UTRA and UTRA satisfying the relationship of the sampling rate of an integral multiple belong to one group.

  In this group, since the ratio of the sampling rates is 8, if the data of the timing for dividing the sample value of the signal waveform of the communication standard UTRA with the sampling rate of 3.84 MHz into 8 equal sections is interpolated, the sampling rate It becomes 30.72 MHz, and it is possible to add the signal waveform of the communication standard E-UTRA and every sample, and the addition result may be stored as the pre-synthesis waveform G1. For this interpolation processing, conventionally known interpolation methods such as linear interpolation between two samples and curve interpolation between three samples can be used.

  Further, since the communication standard GSM (registered trademark) / EDGE having a sampling rate of 270.833 kHz does not belong to the above group, the signal waveform E1 is generated as a non-group signal waveform and stored in the memory. Here, as the signal waveform E1 of GSM (registered trademark) / EDGE, a signal waveform oversampled at 12 times (3.25 MHz) of the standard sampling rate 270.833 kHz is used. The sampling rate of other communication standards does not have an integer multiple relationship.

  When the system hardware is composed of a personal computer (PC) and a signal generator main body, the signal generation processing (S1, S2) is generated according to the signal generation program installed in the PC, and the PC internal Are temporarily stored in the storage device (for example, hard disk), and when these are used, they are transferred from the PC to the memory in the signal generator main body (S3). In addition, as a hardware configuration of the system, it is possible to adopt a system in which a signal generator main body is provided with a function of executing the signal generation processing without using a PC.

  Next, the preliminary synthesized waveforms G1, G2,... And the out-of-group signal waveforms E1, E2,... Stored in the memory are read out in time series at the respective sampling rates (S4). Is converted to a common sampling rate by performing rate conversion processing using a digital filter on the signal waveform having the lowest (S5).

  Here, the case where the rate conversion process is performed on two types of signals G1 and E1 having different sampling rates as in the above example, the sampling rate ratio between them is 30720/3250 = 3072/325, and the integer M, It can be represented by the ratio M / N of N.

  Therefore, if interpolation data at every N timings among the M division timings between two consecutive sample values of the signal E1 having a low sampling rate is obtained and output in time series, the signal E1 is the original. A signal waveform can be obtained when sampling is performed at M / N times the sampling rate.

  In order to realize this, an FIR type digital filter and a filter coefficient switching process obtained from an impulse response are used.

  The details of this rate conversion processing will be described later, but (M × P) pieces of data necessary for data interpolation at each timing for dividing the data input interval to the digital filter having the number of shift stages P of the signal to be rate converted in advance. Filter coefficients are stored in advance for each timing, and interpolation data for M timings is output in time series every N times during a period in which N data is input to the digital filter. Then, a set of P filter coefficients are sequentially selected and given to the digital filter at a speed of M / N with respect to the input rate, thereby performing a rate conversion process with a speed ratio M / N.

  In this example, the two types of signals G1 and E1 have the same sampling rate (in this case, the sampling rate of the signal G1). However, even if there are three or more types to be combined, rate conversion can be performed in the same manner. it can. The common sampling rate is not necessarily set to be equal to the sampling rate of the original signal, and the rate conversion may be performed on all the read signals to obtain a common sampling rate.

  In this way, the signals converted to the common sampling rate are added (S6), and a high-frequency test signal that is orthogonally modulated by the addition result is generated (S7).

  As quadrature modulation processing, I / Q2 system signals obtained by addition processing are converted into analog signals by D / A conversion processing and input to analog quadrature modulators to directly generate high-frequency band test signals. And the addition-processed I and Q2 system signals are input to a digital quadrature modulator, the output is converted to an analog signal by D / A conversion processing, and then frequency converted to a high frequency band for high frequency There are methods for generating a test signal for a band, and any of them may be adopted.

Next, a configuration example of the signal generation system of the present invention will be described.
FIG. 2 shows an example of the configuration of the signal generation system 20 to which the present invention is applied. As described above, the hardware includes the waveform data generation unit 21 composed of a PC and the signal generator main body 30. Has been.

  The waveform data generation unit 21 includes an operation unit 22, a display unit 23, a waveform processing unit 24 that performs processing such as generation and synthesis of signal waveform data according to each communication standard according to a program stored in advance and an operator's operation. A waveform data storage unit 25 for storing waveform data and a waveform data transmission unit 26 for transmitting the stored waveform data to the signal generator main body 30 are provided.

  Here, as described above, the waveform data generation unit 21 selects a communication standard whose sampling rate is an integral multiple of three or more types of communication standards with different sampling rates. Grouped as a communication standard, and within that group, the signal waveform of the communication standard with the lower sampling rate is combined with the signal waveform of the communication standard with the higher sampling rate by interpolation processing of the integral multiple, and then added and synthesized. Has a function of generating pre-combined waveforms G1, G2,... For each group, and generating signal waveforms of communication standards not belonging to any of the groups as out-of-group signal waveforms E1, E2,. Each signal waveform is frequency offset by an amount specified in advance via the operation unit 22.

  .. And the out-of-group signal waveforms E1, E2,... Generated by the waveform data generation unit 21 are sent to the signal generator body 30 and stored in the waveform data memory 31.

  The pre-synthesis waveform G1, G2,... And the out-of-group signal waveforms E1, E2,... Stored in the waveform data memory 31 are read out in time series at the respective sampling rates by the rate conversion unit 32, and the common sampling rate is obtained. Is converted to

  The rate conversion unit 32 performs a rate conversion process using a digital filter on at least the signal waveform having the lowest sampling rate among the read pre-synthesis waveform and the out-of-group signal waveform, thereby converting all of the read signal waveforms. Output at a common sampling rate. This process will be described later.

  The preliminary synthesized waveforms G1 ′, G2 ′,... And the out-of-group signal waveforms E1 ′, E2 ′,... Output from the rate converter 32 at a common sampling rate are input to the adder 45, and each I component, Q component Addition processing is performed every time, and the addition results Iout and Qout are input to the quadrature modulation unit 50.

  The quadrature modulation unit 50 generates a high-frequency test signal S that is quadrature modulated with the addition results Iout and Qout.

  FIG. 3 shows a specific configuration of the signal generator body 30 when two types of the pre-synthesis waveform G1 and the out-of-group signal waveform E1 are input from the waveform data generation unit 21, and the waveform data memory Of the signal waveforms G1 and E1 read from the signal 31, the signal E1 having a low rate is input to the rate converter 33 of the rate converter 32 and converted to a rate equal to the signal G1. The signal G1 is output after being delayed by the delay units 41 and 42 by the processing time of the rate converter 33.

  The signals G1 ′ and E1 ′ output from the rate conversion unit 32 at the same sampling rate are added with each other by the two adders 46 and 47 of the adder 45, and the Q components are added. The addition results Iout and Qout Is input to the quadrature modulation unit 50.

  The quadrature modulation unit 50 converts the digital addition results Iout and Qout into analog signals i and q by D / A converters 51 and 52, respectively, and inputs the analog signals to the analog quadrature modulator 53.

  The quadrature modulator 53 includes a local signal generator 53a, a 90 ° phase shifter 53b, multipliers (mixers) 53c and 53d, and an adder 53e. The multiplier 53c multiplies one input signal i by the local signal La. Then, the other input signal q and the signal Lb obtained by phase-shifting the local signal La by 90 ° are multiplied by the multiplier 53d, and both multiplication results are added by the adder 53e, and the phase is determined according to the input signals i and q. A high-frequency test signal S whose amplitude changes is output.

  This test signal S includes signal components of each communication standard combined at a sampling rate that are combined in different frequency bands, so that it is possible to test a base station or terminal corresponding to the multi-standard. it can.

  Next, the configuration and operation of the rate converter 33 will be described. For ease of explanation, a case will be described in which the target signal for rate conversion is a signal E1 with a sampling rate of 3.25 MHz, and this is matched with the sampling rate of 30.72 MHz of the preliminary combined signal G1.

  In this case, there are two types of signals E1 and G1, and the rate conversion processing of the speed ratio 3072/325 is performed by the rate converter 33 for the signal E1.

FIG. 4 shows the configuration of the rate converter 33.
The rate converter 33 performs a product-sum operation on the latest P data in a data string input in two systems I and Q and a set of P filter coefficients, and sequentially outputs the calculation results. Type digital filters 34A and 34B and (M × P) filter coefficients necessary for data interpolation at each timing for dividing the data input interval to the digital filters 34A and 34B into M equal parts are stored in advance for each timing. The filter coefficient storage means 38 and the digital filters 34A and 34B so that interpolation data for M timings every N times is output in time series during a period in which N data is input. Filter coefficient cut-off that sequentially selects a set of P filter coefficients from the coefficient storage means 38 and gives them to the digital filters 34A and 34B at an input rate M / N speed. And a means 39.

The digital filters 34A and 34B having the same configuration include P-stage registers 35 _{1 to} 35 _P that sequentially shift to the subsequent stage while storing input data, outputs R _{1 to} R _P of the registers 35 _{1 to} 35 _P , and P pieces. Plural P multipliers 36 _{1 to} 36 _P for obtaining a product of a set of filter coefficients h (i, 1) to h (i, P), and an adder for obtaining a sum of outputs of the multipliers 36 _{1 to} 36 _P 37 is an FIR type digital filter having a tap number P and 37.

  The digital filters 34A and 34B are used for calculating data for interpolating between input data by calculation, and the sum of coefficients and data obtained from the impulse response F (X) = (sinX) / X is a function waveform. This utilizes the property of approximating the data value at the intermediate point (reference point). Instead of the impulse response equation, an equation of F (X) = [(sinX) / X] · W (X) using the window function W (X) may be used.

  In order to perform this data interpolation, the filter coefficient storage means 38 has (M × P) filter coefficients necessary for data interpolation at each timing for equally dividing the data input interval Ts (sampling period of the signal E1) into M. Are stored in advance for each timing.

  Further, the filter coefficient switching means 39 is arranged so that interpolation data for M timings every other N is output in time series during a period in which N data is input to the digital filters 34A and 34B. A set of P filter coefficients is sequentially selected from the storage means 38 and applied to the digital filters 34A and 34B at an M / N speed of the F input rate.

  The filter coefficient to be written in the filter coefficient storage means 38 is calculated in advance based on the sampling rate of each signal, the speed ratio M / N necessary for rate conversion, etc., for example, by the waveform data generation unit 21 having the above-described PC configuration. Just remember.

Next, the operation of the rate converter 33 will be described.
First, the case of P = 8, M = 4, and N = 1 (speed ratio 4) will be described so that the operation of each part can be easily understood. Hereinafter, the I component and Q component of the input data will be described without distinction.

A timing at which eight input data Din (1) to Din (8) are input to the digital filter 34 is set to a reference timing t = 0. At this time, the output _R 1 to R ₈ of each register ₃₅ 1-35 _8, as shown in FIG. 5 _{(a), R 1 = Din} (1), R 2 = Din (2), ......, R 8 = Din (8).

For input data that these eight consecutive rate initial timing of the conversion process, the output values R _{4 =} Din register close to the middle position of the number of taps (or the but register 35 ₅ in this case register 35 ₄₎ Assuming (4), the desired value for the interpolation process is the output value R ₄ (= Din (4)) itself, which is already known.

Therefore, in this case, as shown in FIG. 5B, only the filter coefficient h (1, 4) for multiplying the output value R ₄ is 1, and the other filter coefficients h (1, 1) to h ( 1, 3), h (1, 5) to h (1, 8) may be multiplied by a set of filter coefficients of 0, and the initial output value Dout (1) by the interpolation process is
Dout (1) = _{j = 1} Σ ⁸ h (1, j) · Rj = 1 × Rj
(The symbol _{j = 1} Σ ⁸ represents the sum of j = 1 to 8).

  Here, a set of filter coefficients that outputs the input data itself is used with emphasis on accuracy, but a coefficient corresponding to an impulse response used for interpolation data calculation described later may be used.

  In FIG. 5A, since the speed ratio M / N = 4, among the timings Q1 to Q3 for dividing Ts by 4 (= m) between the input data Din (4) and Din (5), Q1 It is necessary to obtain interpolation data at the timing.

Therefore, as shown in FIG. 5C, an impulse response F (X−ΔT) in which the waveform center is shifted by ΔT = Ts / m from the initial timing is used, and each of the shifted functions F (X−ΔT) in the shifted function F (X−ΔT) is used. If the values of the sampling timings (Ts intervals) of the eight data stored in the register are set in the digital filter 34 as the second set of filter coefficients h (2,1) to h (2,8), the timing Q1 Output value Dout (2),
Dout (2) = _{j = 1} Σ ⁸ h (2, j) · Rj
Is obtained.

Similarly, as shown in (d) of FIG. 5, the values of the sampling timings (Ts intervals) of the eight data stored in the registers in the impulse response F (X-2ΔT) further shifted by ΔT are set to the third set. If the digital filter 34 is set as the filter coefficients h (3, 1) to h (3, 8), the output value Dout (3) at the timing Q2,
Dout (3) = _{j = 1} Σ ⁸ h (3, j) · Rj
Is obtained.

Further, as shown in FIG. 5E, the values of the sampling timings (Ts intervals) of the eight data stored in the registers in the impulse response F (X-3ΔT) further shifted by ΔT are set to the fourth set. If the digital filter 34 is set as the filter coefficients h (4,1) to h (4,8), the output value Dout (4) at timing Q3,
Dout (4) = _{j = 1} Σ ⁸ h (4, j) · Rj
Is obtained.

  As a result, four data Dout (1) to Dout (4) including the input data Din (4) and interpolating between the next data Din (5) are obtained. The above processing is performed at an interval of Ts / M until the input data is updated, and when the new data Din (9) is input and updated, the latest data Din (2) ˜ By performing the same process as described above for Din (9) and continuously performing the process, a rate conversion process with a speed ratio M / N = 4 for data Din can be performed.

  Four sets of filter coefficients h (1,1) to h (1,8), h (2,1) to h (2,8), h (3,1) to h (3) necessary for processing in this example. , 8) and h (4,1) to h (4,8) are stored in the filter coefficient storage means 38 constituted by a memory such as a RAM in the order of addresses as shown in FIG. The digital filter 34 may be read out in order and cyclically every time the time of 4 elapses.

  FIG. 7 summarizes the above-described series of operations. As shown in FIG. 7B, the input data Din is updated by one (= N) as shown in FIG. The four sets (= M) of filter coefficients necessary for interpolating between the two data are sequentially and cyclically changed in time series at intervals of Ts / 4 = ΔT, and in synchronization therewith, FIG. As shown in (c), the data Dout is output at a sampling rate four times the input.

  As described above, each sampling of the eight data stored in each register in the impulse response F (X) is used as the first set of filter coefficients h (1,1) to h (1,8). The timing (Ts interval) value may be obtained as a set and set in the digital filter 34.

  The above example is an example where M = 4 and N = 1, and for each point that divides the input data into M, every time one input data is input, M interpolation data is obtained for each point. Although it was obtained and output in time series and was a simple rate conversion process with a speed ratio of 4, an operation with M = 4 and N = 3 will be described next.

  As shown in FIG. 8A, the eight sets of data Din (1) to Din (8) are stored in the respective registers of the digital filter 34, and the first set as shown in FIG. Filter coefficients h (1,1) to h (1,8) are selected, and initial data Dout (1) = R1 = Din (4) is output.

  In this case, since M = 4 in the same manner as described above, the first set of filter coefficients used for the initial timing of processing and the three sets of data necessary for data interpolation at timings Q1 to Q3 that equally divide the two input data are divided into M. Although the filter coefficient is the same as in the above example, the next sampling interval is every 3 (= N), that is, at a timing delayed by 3ΔT, so that it is delayed by 3ΔT from the initial timing as shown in FIG. In the impulse response F (X-3ΔT) having the waveform at the timing Q3, the fourth set of filter coefficients h in the above example in which the values of the sampling timings (Ts intervals) of the eight data stored in the registers are set. By selecting (4, 1) to h (4, 8), the second sample data Dout (2) corresponding to this timing Q3 is output.

The next sample data is the timing further delayed by 3ΔT, that is, the timing of Q2 ′ among the timings Q1 ′ to Q3 ′ for dividing the register data R5 and R6 into M in FIG. Before the sampling, the sampling period Ts of the input data elapses from the initial processing timing, and the output values R _{1 to} R ₈ of the registers 35 _{1 to} 35 ₈ are as shown in FIG. Data Din (2) to Din (9) are updated respectively.

Therefore, at the timing of t = Ts + 2ΔT that has reached the next sample target timing Q2 from this input data update timing, as shown in FIG. 9B, the third set of filter coefficients h (3, 1) to h (3 , 8) is selected, among the three timings Q1 to Q3 for equally dividing the data Din (5) and Din (6) of the registers 35 ₄ and 35 ₅ into the third, the third corresponding to the timing Q2 Sample data Dout (3) is output.

Further, the next sample is a timing further delayed by 3ΔT from the state of FIG. 9, that is, Q1 ′ of the timings Q1 ′ to Q3 ′ of dividing each of the register data R5 and R6 by M in FIG. Before the sampling, the time (2 · Ts) that is twice the sampling period Ts of the input data elapses from the initial timing of processing, and each register as shown in FIG. output values _R 1 to R ₈ of 35 _{1-35 8} is updated in each data Din (3) ~Din (10) .

Therefore, at the timing of t = 2Ts + ΔT reaching the next sample target timing Q1 from this input data update timing, as shown in FIG. 10B, the second set of filter coefficients h (2, 1) to h (2 , 8) is selected, among the three timings Q1-Q3 that equally divide the data Din (6), Din (7) of the registers 35 ₄ , 35 ₅ into M, the fourth corresponding to the timing Q1 Sample data Dout (4) is output.

The next sample is the timing further delayed by 3ΔT from the state of FIG. 10, that is, the output timing of the register data R5 in FIG. 10 (a). After 3 · Ts, the output values R _{1 to} R ₈ of the registers 35 _{1 to} 35 ₈ are updated to data Din (4) to Din (11), respectively.

This state is equivalent to the initial state of FIG. 8 except that the register data has been updated, and has returned to the initial state of processing. Therefore, in accordance with the input data update timing, Similarly to b), the fifth sample equal to the data Din (7) of the registers 35 ₄ and 35 ₅ is selected by selecting the first set of filter coefficients h (1,1) to h (1,8). Data Dout (5) is output.

In other words, in this interpolation process, the filter coefficient is calculated at a cycle 3/4 (= N / M) times the sampling cycle Ts of the input data.
h (1, j) → h (4, j) → h (3, j) → h (2, j)
By cyclically reading and switching in this order, sample processing with a speed ratio of 4/3 (= M / N) with respect to the input data Din is continuously performed.

  FIG. 11 is a timing chart showing the relationship between the input data, filter coefficient switching, and resample data in the above example. While the input data Din of the sampling period Ts in FIG. 11A is updated 3 (= N) times. In addition, as shown in FIG. 4B, four sets of filter coefficients are changed in the order at intervals of 3Ts · / 4 (= Ts · N / M), and sample data calculated by the changed filter coefficients. Is output as shown in FIG. If the period is converted into a speed, the filter coefficient switching speed and the resampling speed are M / N of the input rate.

  The simple example of P = 8, M = 4, and N = 3 has been described above, but the number of taps P of the digital filter 34 is sufficient to reduce the interpolation error due to asymmetry caused by shifting the impulse response. Any number can be used.

  The range of the integers M and N that determine the rate ratio M / N of the rate conversion is arbitrary. If the upper limit of M and N is set to about 1024, many digital modulation symbols that are currently used It is possible to correspond to a combination of rates.

  In this embodiment, the signal G1 is delayed by the delay unit 40 by the processing time necessary for rate conversion on the signal E1, but instead of the delay unit 40, a rate converter 43 is provided as shown in FIG. The filter coefficient of the rate converter 43 is set so that the center value is 1 and the others are 0, so that a delay corresponding to half the number of taps P can be given. Is variable, rate conversion can be performed on both of the input signals, and the degree of freedom is greater with respect to the limitation of the frequency domain on the hardware handled after the D / A conversion processing of the orthogonal modulation unit 50. Can be given.

  For example, when the frequency region allowed in the D / A conversion process is Fa ± ΔF and the output sampling rate does not fall within this frequency region, rate conversion is required for both input data.

In this case, the following conditions must be satisfied for the integers M, M ′, N, and N ′.
Fa−ΔF ≦ Fin1 · (M / N) = Fin2 · (M ′ / N ′) ≦ Fa + ΔF

  If integers M, M ′, N, and N ′ satisfying the above conditions are found, a rate conversion process with a speed ratio M / N is performed on one input data string, and a speed ratio is performed on the other input data string. By performing M '/ N' resample processing, the sampling rates of both input data can be matched within the allowable frequency range, and even if there are hardware limitations, various sampling rates can be obtained. Data strings can be combined, and extremely high versatility can be given.

  DESCRIPTION OF SYMBOLS 20 ... Signal generation system, 21 ... Waveform data generation part, 30 ... Signal generator main body, 31 ... Waveform data memory, 32 ... Rate conversion part, 33 ... Rate converter, 34A, 34B ... Digital Filter, 38... Filter coefficient storage means, 39... Filter coefficient switching means, 40... Delay section, 45.

Claims (2)

Of three or more types of communication standards with different sampling rates, those with a sampling rate that is an integer multiple are grouped as preliminary synthesis target communication standards, and the one with the lower sampling rate in the group The signal waveform of the communication standard is combined with the signal waveform of the communication standard having a higher sampling rate by interpolation processing of the integral multiple, and then added and synthesized to generate a preliminary synthesized waveform for each group. Generating a signal waveform of a communication standard that does not belong to the group as a signal waveform outside the group and storing it in a memory (S1 to S3),
Reading the preliminary synthesized waveform and the out-of-group signal waveform stored in the memory in time series at respective sampling rates (S4);
Of the read pre-synthesis waveform and out-of-group signal waveform, at least the signal waveform having the lowest sampling rate is subjected to rate conversion processing using a digital filter, and the read out pre-synthesis waveform and out-of-group signal A step of making all the waveforms have a common sampling rate (S5);
Adding the pre-synthesis waveform and the out-of-group signal waveform having the common sampling rate (S6);
Generating a high-frequency test signal orthogonally modulated with the combined signal waveform obtained by the addition process (S7). Of three or more types of communication standards with different sampling rates, those with a sampling rate that is an integer multiple are grouped as preliminary synthesis target communication standards, and the one with the lower sampling rate in the group The signal waveform of the communication standard is combined with the signal waveform of the communication standard having a higher sampling rate by interpolation processing of the integral multiple, and then added and synthesized to generate a preliminary synthesized waveform for each group. A waveform data generation unit (21) that generates a signal waveform of a communication standard that does not belong to the group as a signal waveform outside the group;
A waveform data memory (31) for storing the pre-synthesis waveform and the out-of-group signal waveform generated by the waveform data generation unit;
The preliminary synthesized waveform and the out-of-group signal waveform stored in the memory are read in time series at the respective sampling rates, and at least the signal waveform having the lowest sampling rate is selected from the read out preliminary synthesized waveform and the out-of-group signal waveform. A rate conversion unit (32) that performs a rate conversion process using a digital filter and outputs all of the read pre-synthesis waveform and the out-of-group signal waveform at a common sampling rate;
An addition unit (45) for adding the pre-synthesis waveform and the out-of-group signal waveform output at a common sampling rate from the rate conversion unit;
A signal generation system comprising: a quadrature modulation unit (50) that generates a high-frequency test signal that is quadrature modulated with the combined signal waveform obtained by the addition unit.

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