JP2010288178A - Semiconductor integrated circuit and method of processing received signal - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a semiconductor integrated circuit which can accurately find a Doppler frequency with a small circuit scale. <P>SOLUTION: An input selector 14 selects whether an inverse Fourier transform 15 inputs a pilot signal alone or inputs a transmission line response value of a data signal and the pilot signal. The inverse Fourier transform 15 performs an inverse Fourier transforming operation to them, and calculates first and second impulse responses for use in identification of a principal wave position. A phase difference corrector 20 corrects a phase difference of the first impulse response used for the identification of principal wave position owing to a difference in the frequency of the pilot signal between symbols on the basis of a delay between the principal wave position and a Fourier transform window position. A phase deviation calculator 21 and a Doppler frequency calculator 22 calculate a Doppler frequency using the first impulse response having the corrected phase difference. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to a semiconductor integrated circuit and a received signal processing method.

In digital terrestrial broadcasting, demodulation processing is performed in consideration of the influence of Doppler shift in which the carrier frequency shifts during mobile reception.
SP (Scattered Pilot) signals, which are pilot signals, are inserted at regular intervals in OFDM (Orthogonal Frequency Division Multiplexing) frames of the terrestrial digital broadcasting standard ISDB-T (Integrated Services Digital Broadcasting-Terrestrial). Conventionally, a technique for estimating a frequency (Doppler frequency) added to a carrier frequency by mobile reception using a pilot signal extracted from a received signal after Fourier transform is known.

JP 2004-274722 A JP 2005-286636 A

Mikakawa and two others, “Highly accurate Doppler frequency estimation method suitable for OFDM”, IEICE General Conference, 2004, B-5-77, P.A. 564

However, the conventional semiconductor integrated circuit has a problem that the Doppler frequency cannot be accurately obtained from the pilot signal with a small circuit scale.
In view of the above points, an object of the present invention is to provide a semiconductor integrated circuit and a received signal processing method capable of accurately obtaining a Doppler frequency with a small circuit scale.

In order to achieve the above object, the following semiconductor integrated circuit is provided.
The semiconductor integrated circuit calculates a first impulse response by performing inverse Fourier transform on the pilot signal when only a pilot signal is input from the received signal after Fourier transform, and a data signal of the received signal. An inverse Fourier transform unit that calculates a second impulse response by performing inverse Fourier transform on the transmission path response value and the pilot signal when the transmission path response value calculated from the pilot signal is input, and the inverse Fourier transform An input selection unit for selecting whether to input only the pilot signal, or to input the transmission line response value and the pilot signal, and a second impulse response or more based on the second impulse response. When a multipath determination unit that determines whether or not a multipath has occurred and occurrence of the multipath that is greater than or equal to the predetermined length are detected, A main wave position specifying unit for specifying the main wave position in the first impulse response by comparing the position of the maximum value of the first impulse response with the position of the maximum value of the second impulse response; Based on the difference in frequency of the pilot signal between symbols based on the delay amount between the main wave position and the Fourier transform window position, using the first impulse response specifying the main wave position A phase difference correction unit that corrects a phase difference of the first impulse response, a phase between the first impulse response corrected by the phase difference correction unit and the first impulse response in a different symbol. A phase deviation calculation unit that calculates a rotation amount; and a Doppler frequency calculation unit that calculates a Doppler frequency based on the phase rotation amount.

  According to the disclosed semiconductor integrated circuit and received signal processing method, the Doppler frequency can be accurately obtained with a small circuit scale.

It is a figure which shows the structure of the principal part of the semiconductor integrated circuit of this Embodiment. It is a figure which shows the structure of the OFDM frame in terrestrial digital broadcasting. It is a figure which shows the mode of switching of an OFDM frame. It is a figure which shows an example of an impulse response. It is a figure which shows an example of the phase difference of the impulse response between different symbols. It is a figure which shows the example of the calculated amount of phase rotations. It is a figure which shows a mode that a main wave position is specified. It is an example which shows the case where a main wave position cannot be specified. It is a figure which shows the comparative example of the semiconductor integrated circuit of this Embodiment. It is a flowchart which shows the received signal processing method by the semiconductor integrated circuit of this Embodiment. It is a figure which shows the schematic structure of the principal part of an OFDM receiving system.

DESCRIPTION OF THE PREFERRED EMBODIMENTS Embodiments as aspects of a semiconductor integrated circuit and a received signal processing method of the present invention will be described below with reference to the drawings.
FIG. 1 is a diagram showing a configuration of a main part of the semiconductor integrated circuit according to the present embodiment.

The semiconductor integrated circuit 10 is, for example, an LSI (Large Scale Integrated circuit) for demodulating an OFDM signal for digital terrestrial broadcasting.
The semiconductor integrated circuit 10 includes a pilot signal storage unit 11, a subcarrier group storage unit 12, a transmission line response value generation unit 13, an input selection unit 14, an inverse Fourier transform unit 15, impulse response holding units 16 and 17, and an impulse response delay unit. 18 and a maximum value position detector 19. The semiconductor integrated circuit 10 also includes a phase difference correction unit 20, a phase deviation calculation unit 21, a Doppler frequency calculation unit 22, a multipath determination unit 23, a main wave position specifying unit 24, and a preceding wave detection unit 25.

Hereinafter, details of each part and its operation will be described.
The pilot signal storage unit 11 holds a pilot signal among subcarrier groups included in a received signal after Fourier transform (for example, FFT (Fast Fourier Transform)).

FIG. 2 is a diagram showing a configuration of an OFDM frame in digital terrestrial broadcasting.
The horizontal axis is the subcarrier number and represents the frequency direction. The vertical axis is the symbol number and represents the time direction. In the figure, black circles are SP signals Ds that are pilot signals, and white circles are data signals Da.

  The SP signal Ds, which is a pilot signal used in terrestrial digital broadcasting, is inserted every 12 carriers in the frequency direction and every 4 symbols in the time direction.

  The subcarrier group storage unit 12 holds a subcarrier group including a pilot signal and a data signal included in the received signal after Fourier transform. The subcarrier group storage unit 12 may hold all subcarriers of each symbol or may hold subcarriers of some segments.

  The transmission line response value generation unit 13 tentatively determines a data signal in the subcarrier group, obtains a tentative determination value of the transmission signal point, and then divides the received data signal by the tentative determination value. A transmission line response value indicating the influence of the path is generated. In the temporary determination, for example, a temporary determination value is generated by hard-determining the data signal according to a modulation scheme such as QPSK (Quadrature Phase Shift Keying), 16QAM (Quadrature Amplitude Modulation), or 64QAM.

  The input selection unit 14 selects whether to input only the pilot signal held in the pilot signal storage unit 11 or the transmission path response value and pilot signal obtained from the data signal to the inverse Fourier transform unit 15. For example, the input selection unit 14 detects a symbol number and detects switching of OFDM frames. Then, the input selection unit 14 switches between inputting only the pilot signal to the inverse Fourier transform unit 15 or inputting the transmission line response value and the pilot signal obtained from the data signal to the inverse Fourier transform unit 15 for each frame.

FIG. 3 is a diagram illustrating how OFDM frames are switched.
The horizontal axis is time.
The OFDM frames fs1, fs2, fp1, and fp2 have 204 symbols having symbol numbers 0 to 203 per frame.

  For example, the input selection unit 14 inputs a transmission line response value and a pilot signal obtained from the data signals of the OFDM frames fs1 and fs2 to the inverse Fourier transform unit 15, and performs an inverse Fourier transform (for example, IFFT (Inverse FFT)). Make it. Further, the input selection unit 14 inputs only the pilot signals of the OFDM frames fp1 and fp2 to the inverse Fourier transform unit 15 to perform inverse Fourier transform.

  When only the pilot signal is input from the input selection unit 14, the inverse Fourier transform unit 15 calculates an impulse response by performing inverse Fourier transform on the pilot signal, and holds the impulse response in the impulse response holding unit 16. In addition, when a transmission line response value and a pilot signal are input from the input selection unit 14, the inverse Fourier transform unit 15 performs an inverse Fourier transform on these signals to calculate an impulse response, and the impulse response holding unit 17 Hold.

FIG. 4 is a diagram illustrating an example of an impulse response.
4A shows an example of an impulse response in the (n-2) th symbol, and FIG. 4 (B) shows an example of an impulse response in the nth symbol. In FIG. 4, the horizontal axis represents time, and the vertical axis represents power.

The impulse response obtained here is called a delay profile because it indicates the multipath response of the transmission path.
When mobile reception is performed, phase rotation occurs due to fading, and impulse responses obtained between different symbols have different values. The amount of phase rotation at this time is proportional to the Doppler frequency received by the carrier wave. Therefore, the Doppler frequency can be calculated from the phase rotation amount of the impulse response between symbols in a certain period.

FIG. 5 is a diagram illustrating an example of the phase difference of the impulse response between different symbols.
Here, the maximum value I _n-2 of the impulse response of (n-2) th symbol, indicates the phase difference between the maximum value I _n of the impulse response of the n th symbol. ΔΘ represents the amount of phase rotation due to fading. Furthermore, when the frequency of the SP signal is shifted for each symbol as shown in FIG. 2, a phase difference ΔΦ due to the difference in the frequency of the SP signal is added. Therefore, a maximum value I _n-2 of the impulse response, the phase difference between the maximum value I _n of the impulse response becomes .DELTA..theta + .DELTA..PHI. The phase difference ΔΦ varies depending on the position of the Fourier transform window that cuts out the OFDM symbol.

  The impulse response holding unit 16 is, for example, a memory, holds an impulse response calculated when a pilot signal is input to the inverse Fourier transform unit 15, and outputs the impulse response to the impulse response delay unit 18. Further, the impulse response holding unit 16 sends the impulse response to the maximum value position detecting unit 19, inputs the position of the maximum value of the impulse response detected by the maximum value position detecting unit 19, and sets the maximum value of the impulse response to the phase. Output to the deviation calculator 21.

  The impulse response holding unit 17 is, for example, a memory, holds an impulse response calculated by inputting a transmission line response value obtained from a data signal and a pilot signal to the inverse Fourier transform unit 15, and detects a maximum value position. To the unit 19.

  The impulse response delay unit 18 is, for example, a memory, and holds and delays the impulse response output from the impulse response holding unit 16. Further, the impulse response delay unit 18 acquires the position of the maximum value of the input impulse response from the maximum value position detection unit 19 and holds it.

  The maximum value position detection unit 19 detects the position of the maximum value (maximum power) of the impulse response held by the impulse response holding unit 16 and outputs it to the impulse response holding unit 16 and the impulse response delay unit 18. The one with the highest power is likely to be the main wave with the best C / N ratio (Carrier to Noise Ratio). Further, the maximum value position detection unit 19 detects the position of the maximum value of the impulse response held by the impulse response holding unit 17 and outputs it to the multipath determination unit 23 together with the information of the impulse response.

  The phase difference correction unit 20 corrects the phase difference ΔΦ due to the difference in the frequency of the SP signal between symbols as shown in FIG. 5 with respect to the impulse response output from the impulse response delay unit 18. The phase difference ΔΦ is a value corresponding to the delay amount between the position of the Fourier transform window for cutting out the OFDM symbol and the position of the main wave or the preceding wave.

The phase difference correction unit 20 calculates the phase difference ΔΦ corresponding to the delay amount or holds it as a table in advance, and calculates the delay amount from the position of the input main wave or preceding wave, for example. Then, the phase difference correcting unit 20, the inverse phase of the phase difference .DELTA..PHI corresponding to the delay amount ^- the (e .DELTA..PHI), to multiply the impulse response of the main wave or a preceding wave. As a result, the phase difference ΔΦ due to the difference in the frequency of the SP signal between symbols is canceled.

  The phase deviation calculation unit 21, for example, the main wave or the preceding wave of the impulse response of the current symbol held in the impulse response holding unit 16 and the main wave of the impulse response of the previous symbol corrected by the phase difference correction unit 20. Alternatively, the phase rotation amount ΔΘ is calculated from the preceding wave.

FIG. 6 is a diagram illustrating an example of the calculated phase rotation amount.
Here, the maximum value of the impulse response of (n-2) th symbol and (main wave) I _n-2 shown in FIG. 5, the maximum value of the impulse response of the n th symbol phase difference (main wave) I _n It shows how it is sought.

Since the phase difference ΔΦ due to the frequency difference between the SP signal symbols is canceled by the phase difference correction unit 20, the phase deviation calculation unit 21 calculates only the phase rotation amount ΔΘ due to fading. Phase deviation calculator 21, the phase rotation amount .DELTA..theta, or calculated by calculating the difference in the maximum value I _n-2 and the phase of the maximum value I _n, is calculated by using the inner product operation.

  The phase rotation amount ΔΘ obtained by the phase deviation calculation unit 21 is proportional to the Doppler frequency fd. Therefore, the Doppler frequency calculation unit 22 calculates the Doppler frequency fd by multiplying the phase rotation amount ΔΘ by a predetermined value.

  The multipath determination unit 23 determines whether or not a multipath of a predetermined length or more has occurred from the impulse response by the subcarrier group including the data signal and the position of the maximum value (main wave position). . Specifically, the multipath determination unit 23 determines the length of the multipath by detecting how far the preceding wave (delayed wave) is away from the main wave. Then, the multipath determination unit 23 has a multipath longer than a length that may cause a return (for example, a 1/24 symbol length or more when receiving an OFDM frame of the terrestrial digital broadcasting standard ISDB-T). It is determined whether or not there is. The multipath determination unit 23 outputs the determination result to the main wave position specifying unit 24.

  Further, when the multipath determination unit 23 detects a multipath of a predetermined length or longer, the multipath determination unit 23 determines the position of the maximum value of the impulse response by the subcarrier group including the data signal detected by the maximum value position detection unit 19 This is sent to the wave position specifying unit 24. The multipath determination unit 23 may send the impulse response data itself to the main wave position specifying unit 24. Further, the multipath determination unit 23 may invalidate the function of the main wave position specifying unit 24 when a multipath having a predetermined length or more is not detected.

  As shown in FIG. 2, in the OFDM frame of the digital terrestrial broadcasting standard ISDB-T, SP signals are inserted at intervals of 12 in each symbol. Therefore, when a multipath having a length of 1/24 symbol or more exists, there is a possibility that the impulse response obtained from only the pilot signal may be folded (details will be described later). If the main wave position is not specified in consideration of this aliasing, the phase difference correction unit 20 cannot obtain a correct delay amount for obtaining the phase difference ΔΦ. Therefore, the phase deviation calculation unit 21 cannot calculate an accurate phase rotation amount ΔΘ, and the Doppler frequency calculation unit 22 cannot calculate an accurate Doppler frequency fd.

  On the other hand, if the impulse response obtained from the subcarrier group including the data signal is a multipath having a delay amount within a ½ symbol length, signal folding does not occur. Therefore, the main wave position specifying unit 24 specifies the main wave position of the impulse response based on the pilot signal using the impulse response based on the subcarrier group including the data signal.

  Note that the impulse response obtained from the subcarrier group including the data signal does not return, but since the transmission line response value is obtained from the temporary determination value, it is desirable to estimate the Doppler frequency from this impulse response. Absent. This is because in the case of a high fading environment during high-speed movement and 64QAM in the 13seg system, the reliability of the provisional determination value is lowered and the transmission line response value is greatly deteriorated. Therefore, in the semiconductor integrated circuit 10 of the present embodiment, an impulse response using a pilot signal is used for estimating the Doppler frequency.

  When the main wave position specifying unit 24 receives a determination result indicating that a multipath of a predetermined length or more has been detected, the main wave position specifying unit 24 is based on the position of the maximum value of each impulse response detected by the maximum value position detecting unit 19. Next, the main wave position of the impulse response by the pilot signal is specified.

  The main wave position specifying unit 24 specifies the main wave position at the switching portion of the OFDM frame as shown in FIG. Specifically, the main wave position specifying unit 24 uses, for example, an impulse response obtained from the last symbol of the OFDM frames fs1 and fs2 and an impulse response obtained from the first symbol of the OFDM frames fp1 and fp2. Specify the main wave position.

FIG. 7 is a diagram illustrating how the main wave position is specified.
FIG. 7A shows an impulse response obtained from a subcarrier group including a data signal. The vertical axis is power, and the horizontal axis is X (time). The horizontal axis is actually represented by IFFT points.

  In FIG. 7A, the preceding wave, the main wave, and the delayed wave appear at positions A1x, A2x, and A3x, respectively. First, the main wave position specifying unit 24 performs conversion for matching the time axis (horizontal axis X) with the time axis (horizontal axis Y) of the impulse response obtained only from the pilot signal, as shown in FIG. As shown in the upper diagram, a main wave position A2y indicating the maximum power is obtained. Thereby, it is possible to compare with the impulse response obtained only from the pilot signal.

  For example, when the OFDM standard of 1 seg and Mode 3 is used, the conversion formula is as follows. In the following formula, for example, the number of IFFT points of impulse response obtained from a subcarrier group including a data signal is 256, and the number of IFFT points of impulse response obtained only from a pilot signal is 64.

Ay = (Ax-256 / 2) × 3-64 / 2
Here, Ax-256 / 2 represents the deviation (number of points) of the main wave from the FFT window position. Since the FFT shift is performed, the FFT window position is assumed to be 256/2.

  When the 13seg, Mode3 OFDM standard is used, the conversion formula is as follows. In the following formula, for example, the number of IFFT points of impulse response obtained from the subcarrier group including the data signal is 256, and the number of IFFT points of impulse response obtained from the pilot signal alone is also 256.

Ay = (Ax−256 / 2) × 12−256 / 2
The example in the lower diagram of FIG. 7B shows an example of the impulse response obtained only from the pilot signal. Impulse responses appear at positions B1, B2, and B3, respectively. The impulse response at position B1 is the result of turning back the impulse response at position B4, and the impulse response at position B2 is folded from the impulse response at position B5. It is a return.

  The main wave position specifying unit 24 specifies the position of the maximum value as the main wave position when the maximum value of the impulse response by the pilot signal exists at a position substantially equal to the position A2y in the upper diagram of FIG. 7B. . Specifically, as shown in FIG. 7B, the main wave position specifying unit 24 determines whether or not the maximum value of the impulse response obtained from only the pilot signal is within a predetermined range (± α) from the position Ay. To detect. α is, for example, about 10 points or less in IFFT points. In the example of FIG. 7B, an impulse response indicating the maximum value at the position B1 is within the above range. Therefore, the main wave position specifying unit 24 specifies the impulse response existing at the position B1 as the main wave. Thereby, the folded main wave can be specified.

When the main wave position can be specified, the main wave position specifying unit 24 notifies the phase difference correcting unit 20 of the position of the specified main wave.
When the main wave position can be identified, the phase difference correction unit 20 sets the phase difference ΔΦ according to the delay amount d1 between the Fourier transform window position and the position B4 from which the identified main wave position B2 is folded. Ask. Then, the phase difference correction unit 20 multiplies the value of the main wave of the impulse response by the opposite phase (e ⁻ ΔΦ) of the phase difference ΔΦ. As a result, the phase difference ΔΦ due to the difference in the frequency of the SP signal between symbols is correctly canceled.

  Thereafter, the phase deviation calculation unit 21 calculates the amount of phase rotation from the maximum value of the impulse response of the current symbol from the impulse response holding unit 16 and the maximum value of the impulse response of the previous symbol corrected by the phase difference correction unit 20. ΔΘ is calculated. Then, the Doppler frequency calculation unit 22 calculates the Doppler frequency fd based on the phase rotation amount ΔΘ.

By the way, the main wave position specifying unit 24 cannot specify the main wave position in the following cases.
FIG. 8 is an example showing a case where the main wave position cannot be specified.
The upper diagram of FIG. 8 shows the position A2y after converting the time axis of the maximum value of the impulse response obtained from the subcarrier group including the data signal, similarly to the upper diagram of FIG. 7B.

  In the lower diagram of FIG. 8, the power of the impulse response at position B2, which is a folded delayed wave, is greater than the impulse response at position B1, which is the folded main wave. Since the main wave position specifying unit 24 of the present embodiment specifies the main wave position by comparing the maximum values of impulse responses between different frames as described above, such a phenomenon may occur.

That is, when time elapses between frames, the magnitude of the power of the main wave and the delayed wave may be reversed as shown in FIG. In this case, the main wave position specifying unit 24 cannot specify the main wave position.
For example, when the OFDM frames fs1, fs2, fp1, and fp2 are processed according to the flow shown in FIG. 3, the Doppler frequency is updated at the last symbol of the OFDM frames fp1 and fp2 in which only the pilot signal is inverse Fourier transformed. Done. Therefore, for example, if the main wave position cannot be specified at the switching part between the OFDM frames fs1 and fp1, even if the main wave position is successfully specified at the switching part between the next OFDM frames fs2 and fp2, the minimum period is four frame periods. The Doppler frequency cannot be updated.

Therefore, in the semiconductor integrated circuit 10 of the present embodiment, when the main wave position cannot be specified by the main wave position specifying unit 24, the Doppler frequency is calculated using the preceding wave.
First, when the main wave position cannot be specified, the main wave position specifying unit 24 notifies the phase difference correcting unit 20, the phase deviation calculating unit 21, and the preceding wave detecting unit 25 to that effect.

  The preceding wave detection unit 25 detects a preceding wave existing in the vicinity of the Fourier transform window position from the impulse response held in the impulse response holding unit 16 or the impulse response stored in the impulse response delay unit 18. For example, the preceding wave detection unit 25 detects an impulse response closest to the Fourier transform window position as a preceding wave with an impulse response having a magnitude equal to or greater than a certain power. Then, the preceding wave detection unit 25 notifies the impulse response holding unit 16, the impulse response delay unit 18, and the phase difference correction unit 20 of the position of the preceding wave.

For example, when the preceding wave position B3 is identified in the impulse response as shown in FIG. 8, the phase difference correction unit 20 determines the delay amount between the Fourier transform window position and the identified preceding wave position B3. A phase difference ΔΦ is obtained according to d2. Then, the phase difference correction unit 20 multiplies the value of the preceding wave of the impulse response by the opposite phase (e ⁻ ΔΦ) of the phase difference ΔΦ. As a result, the phase difference ΔΦ due to the difference in the frequency of the SP signal between symbols is correctly canceled.

  Further, the phase deviation calculating unit 21 calculates the phase rotation amount from the preceding wave of the impulse response of the current symbol from the impulse response holding unit 16 and the preceding wave of the impulse response of the previous symbol corrected by the phase difference correcting unit 20. ΔΘ is calculated. Then, the Doppler frequency calculation unit 22 calculates the Doppler frequency fd based on the phase rotation amount ΔΘ.

  As described above, the semiconductor integrated circuit 10 calculates an impulse response that is not affected by signal folding using a subcarrier group including a data signal and a pilot signal, and corrects the main response based on the position of the maximum value. The wave position is specified. As a result, the Doppler frequency can be accurately obtained even when a multipath having a predetermined length or more that may cause a return of the impulse response occurs.

Further, since the semiconductor integrated circuit 10 can calculate the Doppler frequency using the preceding wave even when the main wave position cannot be specified, the OFDM frames fs1, fs2, fp1, as shown in FIG. In fp2, the Doppler frequency can be updated at intervals of two frames.
(Comparative example)
FIG. 9 is a diagram showing a comparative example of the semiconductor integrated circuit of the present embodiment.

FIG. 9 shows a configuration of a semiconductor integrated circuit proposed by the inventors of the present application in Japanese Patent Application No. 2009-118550.
Components similar to those of the semiconductor integrated circuit 10 shown in FIG.

  In the semiconductor integrated circuit 10a of the comparative example, an inverse Fourier transform unit 15a that performs inverse Fourier transform on only the pilot signal, and an inverse Fourier transform unit 15b that performs inverse Fourier transform on the transmission path response value obtained from the data signal and the pilot signal are provided. ing. As a result, the inverse Fourier transform using only the pilot signal and the inverse Fourier transform using the transmission path response value and the pilot signal are performed in parallel. Two maximum value position detectors 19a and 19b are also provided.

In such a semiconductor integrated circuit 10a, the Doppler frequency can be updated for each frame, but the circuit scale is large.
On the other hand, in the semiconductor integrated circuit 10 of the present embodiment shown in FIG. 1, the input selection unit 14 is provided, and only the pilot signal is input to the inverse Fourier transform unit 15 or the transmission path obtained from the data signal It is selected whether to input the response value and pilot signal. Thereby, the number of inverse Fourier transform units 15 can be reduced to one, and the circuit scale can be greatly reduced to about ½.

Hereinafter, the flow of reception signal processing by the semiconductor integrated circuit 10 of the above-described embodiment will be summarized with a flowchart.
FIG. 10 is a flowchart showing a received signal processing method by the semiconductor integrated circuit of the present embodiment.

  The input selection unit 14 inputs only the pilot signal out of the received signal after Fourier transform to the inverse Fourier transform unit 15 or performs inverse Fourier transform on the transmission line response value and the pilot signal obtained from the data signal of the received signal. Whether to input to the unit 15 is selected (step S1).

  The inverse Fourier transform unit 15 performs inverse Fourier transform on only the pilot signal or the transmission path response value and the pilot signal obtained from the data signal, and calculates respective impulse responses (step S2). The maximum value position detector 19 detects the position of the maximum value of the impulse response based only on the pilot signal (step S3). Then, the impulse response delay unit 18 holds and delays the impulse response output from the impulse response holding unit 16 (step S4).

  Further, the maximum value position detector 19 detects the position (main wave position) of the transmission line response value obtained from the data signal and the maximum value of the impulse response by the pilot signal (step S5). Then, the multipath determination unit 23 determines whether or not a multipath of a predetermined length or more has occurred from the transmission path response value obtained from the data signal and the impulse response by the pilot signal (steps S6 and S7). . When there is a multipath longer than a predetermined length, the main wave position specifying unit 24 compares the position of the transmission line response value and the maximum value of the impulse response based on the pilot signal with the position of the maximum value of the impulse response based only on the pilot signal. To do. As a result, the main wave position specifying unit 24 specifies the main wave position in the impulse response using only the pilot signal (steps S8 and S9).

When the main wave position cannot be specified, the preceding wave detection unit 25 sets the position of the preceding wave of the impulse response based only on the pilot signal in the phase difference correction unit 20 (step S10).
If there is no multipath longer than the predetermined length, the main wave position is specified, or the preceding wave position is set, a phase difference correction process by the phase difference correction unit 20 is performed (step S11).

  When there is no multipath longer than the predetermined length, the phase difference correction unit 20 determines between the position (main wave position) of the maximum value of the impulse response output from the impulse response delay unit 18 and the Fourier transform window position. Find the amount of delay.

  On the other hand, when there is a multipath having a predetermined length or more, the phase difference correction unit 20 returns the main wave position and the Fourier transform window position of the folded main wave position specified by the main wave position specifying unit 24. The amount of delay between is calculated.

When the main wave position cannot be specified, the phase difference correction unit 20 obtains a delay amount between the position of the preceding wave detected by the preceding wave detection unit 25 and the Fourier transform window position.
Then, the phase difference correction unit 20 obtains the phase difference ΔΦ according to the delay amount between the main wave position or the position of the preceding wave and the Fourier transform window position, and obtains the opposite phase (e ⁻ ΔΦ) of the phase difference ΔΦ. Multiply the value of the main wave or preceding wave of the impulse response. As a result, the phase difference ΔΦ due to the difference in the frequency of the SP signal between symbols is canceled.

  Thereafter, the phase deviation calculating unit 21 calculates the phase rotation amount ΔΘ from the main wave or preceding wave of the impulse response of the current symbol and the main wave or preceding wave of the impulse response of the previous symbol corrected by the phase difference correcting unit 20. Is calculated (step S12). Then, the Doppler frequency calculation unit 22 calculates the Doppler frequency fd based on the phase rotation amount ΔΘ (step S13).

  Thus, in the received signal processing method of this embodiment, an impulse response that is not affected by signal folding is calculated using a subcarrier group including a data signal and a pilot signal, and the position of the maximum value is obtained. In addition, the correct main wave position is specified. As a result, the Doppler frequency can be accurately obtained even when a multipath that may cause aliasing occurs.

  In addition, the input selection unit 14 selects whether to calculate the impulse response based only on the pilot signal or to calculate the impulse response based on the transmission line response value and the pilot signal obtained from the data signal. It can be one. As a result, the circuit scale is greatly reduced.

  Even when the main wave position cannot be specified, the phase difference correction unit 20 corrects the phase difference ΔΦ using the preceding wave, so that the Doppler frequency cannot be updated for a long time. it can.

The semiconductor integrated circuit 10 and the reception signal processing method as described above are applied to the following OFDM reception system, for example.
FIG. 11 is a diagram illustrating a schematic configuration of a main part of the OFDM reception system.

  The OFDM reception system 30 includes a tuner 31, an orthogonal demodulation unit 32, a Fourier transform unit 33, a symbol number generation unit 34, a Doppler frequency estimation unit 35, a transmission path equalization unit 36, a demapping unit 37, An error correction unit 38 is provided. The OFDM receiving system 30 includes an MPEG-2 (Moving Picture Experts Group phase 2) decoder (or H.264 decoder) 39 and an output unit 40.

The tuner 31 receives a selected RF (Radio Frequency) signal via the antenna 31a.
The orthogonal demodulator 32 performs orthogonal demodulation on the received modulated wave.

The Fourier transform unit 33 performs Fourier transform (for example, FFT) on the orthogonally demodulated reception signal to convert it into a frequency domain signal.
The symbol number generation unit 34 generates a symbol number using a TMCC (Transmission and Multiplexing Configuration Control) signal included in a subcarrier group after Fourier transform, for example.

  The TMCC is included in a specific position (specified by the standard) of each symbol data of the received signal. Since differential modulation is used for TMCC transmission, the symbol number generation unit 34 demodulates the differentially modulated TMCC, generates a symbol number, and the Doppler frequency estimation unit 35 described above. Input to the input selection unit 14.

The Doppler frequency estimation unit 35 includes the components shown in FIG. 1 and calculates a Doppler frequency from the received signal that has been subjected to Fourier transform.
The transmission path equalization unit 36 equalizes the received signal subjected to the Fourier transform according to the Doppler frequency calculated by the Doppler frequency estimation unit 35. Thereby, the transmission signal from which disturbance due to the transmission path is removed is reproduced. Specifically, when equalizing the received signal, the transmission path equalization unit 36 obtains a transmission path estimation value from the pilot signal, and changes the filter coefficient used at this time according to the Doppler frequency. Since the Doppler frequency is proportional to the moving speed of the receiver, by changing the filter coefficient according to the Doppler frequency, it is possible to obtain a transmission path estimation value according to the moving speed, and the transmission signal can be accurately reproduced. .

The demapping unit 37 determines the signal point position of the transmission signal from which the disturbance has been removed, and derives the bit pattern of the transmission signal.
The error correction unit 38 corrects the data error using, for example, a Reed-Solomon code or a convolutional code with respect to the output of the demapping unit 37.

The MPEG-2 decoder 39 decodes the data encoded in the MPEG-2 format output from the error correction unit 38.
The output unit 40 is, for example, a display or a speaker, and outputs decoded video data or audio data.

  In the OFDM receiving system 30 as described above, for example, each configuration from the orthogonal demodulation unit 32 to the error correction unit 38 is provided as the semiconductor integrated circuit 50. The semiconductor integrated circuit 50 may include an MPEG-2 decoder 39.

  Such an OFDM receiving system 30 can be applied to, for example, a terrestrial digital broadcast receiving apparatus or a portable terminal capable of viewing terrestrial digital broadcasts. As described above, the semiconductor integrated circuit of this embodiment can calculate the Doppler frequency accurately with a small circuit scale, and thus is particularly useful for application in a portable terminal.

  As described above, one aspect of the semiconductor integrated circuit and the received signal processing method of the present invention has been described based on the embodiments. However, these are merely examples, and the present invention is not limited to the above description.

DESCRIPTION OF SYMBOLS 10 Semiconductor integrated circuit 11 Pilot signal memory | storage part 12 Subcarrier group memory | storage part 13 Transmission path response value production | generation part 14 Input selection part 15 Inverse Fourier-transform part 16, 17 Impulse response holding part 18 Impulse response delay part 19 Maximum value position detection part 20 Phase difference correction unit 21 Phase deviation calculation unit 22 Doppler frequency calculation unit 23 Multipath determination unit 24 Main wave position specification unit 25 Precedence wave detection unit

Claims (4)

When only the pilot signal is input from the received signal after the Fourier transform, the first impulse response is calculated by performing inverse Fourier transform on the pilot signal, and the transmission path response obtained from the data signal of the received signal When the value and the pilot signal are input, an inverse Fourier transform unit that calculates a second impulse response by performing an inverse Fourier transform on the transmission line response value and the pilot signal;
An input selection unit that selects whether to input only the pilot signal, or to input the transmission line response value and the pilot signal, to the inverse Fourier transform unit;
A multipath determination unit that determines whether or not a multipath of a predetermined length or more has occurred based on the second impulse response;
When the occurrence of the multipath of the predetermined length or more is detected, comparing the position of the maximum value of the first impulse response with the position of the maximum value of the second impulse response, A main wave position specifying unit for specifying the main wave position in the first impulse response;
Due to the difference in the frequency of the pilot signal between symbols based on the delay amount between the main wave position and the Fourier transform window position, using the first impulse response specifying the main wave position A phase difference correction unit for correcting a phase difference of the first impulse response;
A phase deviation calculation unit that calculates a phase rotation amount between the first impulse response corrected by the phase difference correction unit and the first impulse response in a different symbol;
Based on the amount of phase rotation, a Doppler frequency calculation unit that calculates a Doppler frequency;
A semiconductor integrated circuit comprising: Based on the first impulse response, it has a preceding wave detection unit for detecting a preceding wave,
In the case where the main wave position cannot be specified by the main wave position specifying unit, the phase difference correction unit determines the symbol based on the delay amount between the position of the preceding wave and the Fourier transform window position. The semiconductor integrated circuit according to claim 1, wherein a phase difference of the first impulse response due to a difference in frequency of the pilot signal between the first and second impulse responses is corrected.   2. The input selection unit detects symbol numbers and switches between input of only the pilot signal or input of the transmission line response value and the pilot signal for each OFDM frame. Semiconductor integrated circuit. The input selection unit inputs only the pilot signal of the received signal after Fourier transform to the inverse Fourier transform unit, or the transmission line response value obtained from the data signal of the received signal and the pilot signal as the inverse Fourier Select whether to input to the converter,
When only the pilot signal is input, the inverse Fourier transform unit calculates the first impulse response by performing inverse Fourier transform on the pilot signal, and when the transmission line response value and the pilot signal are input, A second impulse response is calculated by inverse Fourier transforming the transmission line response value and the pilot signal,
The multipath determination unit determines whether or not a multipath of a predetermined length or more has occurred based on the second impulse response,
When the main wave position specifying unit detects the occurrence of the multipath longer than the predetermined length, the position of the maximum value of the first impulse response and the position of the maximum value of the second impulse response To identify the main wave position in the first impulse response,
A phase difference correction unit uses the first impulse response specifying the main wave position, and based on the delay amount between the main wave position and the Fourier transform window position, the pilot signal between symbols Correcting the phase difference of the first impulse response due to the difference in frequency,
A phase deviation calculator calculates a phase rotation amount between the first impulse response corrected by the phase difference correction unit and the first impulse response in a different symbol;
A received signal processing method, wherein the Doppler frequency calculation unit calculates a Doppler frequency based on the phase rotation amount.

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