JP2010284004A - Quick charging device - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To quickly charge a battery of a vehicle and a large capacitance capacitor. <P>SOLUTION: A slow charger part 4 includes two pairs of DC parts where power supplies of secondary Δ winding 41 and secondary Y winding 42 with a phase difference of 30° between them are respectively rectified with diode bridges 43 and 53 through a transformer 40 from an AC power supply 3. At each DC part, capacitors 44 and 54 of small capacitance are connected in parallel to the diode bridges 43 and 53. A step-up chopper is connected to the diode bridges and small-capacitance capacitors through current detectors 45 and 55. Each step-up chopper includes reactors 46 and 56, IGBTs 47 and 57, and diodes 48 and 58. Output sides of the diodes 48 and 58 of the step-up chopper of each pair are connected to a rechargeable battery 5 to constitute the slow charger part 4. Capacitors 49 and 59 are those for suppressing surge, and are connected to output sides of the diodes 48 and 58 and emitter sides of the IGBTs 47 and 57. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to a rapid charging apparatus that rapidly charges a battery such as an automobile or a large-capacity capacitor.

  As a quick charging device that rapidly charges a battery such as an electric vehicle or a large-capacity capacitor, a battery that is charged over a relatively long period of time and a rapid charging device that quickly charges a power source battery such as an electric vehicle from the battery. The thing provided with the charging part is known (for example, refer patent document 1).

  FIG. 13 is an overall view of the configuration of this rapid charging apparatus. In FIG. 13, reference numeral 1 denotes an electric vehicle that moves an axle with a motor, and reference numeral 2 denotes a power source battery that supplies electric power to the motor. Reference numeral 3 denotes an AC power source that supplies power of about several tens of kVA, and 4 denotes a low-speed charging unit that is connected to the AC power source 3 and is charged over a relatively long time. Reference numeral 5 denotes a battery that is constantly charged by the low-speed charging unit 4. Reference numeral 6 denotes a quick charging unit that is supplied with electric power from the battery and charges the power source battery 2. In this rapid charging apparatus, the battery 5 is slowly charged with a small current from the AC power source 3 through the low-speed charging unit 4, and the power source battery 2 of the electric vehicle 1 is connected from the battery 5 through the rapid charging unit 6. To charge quickly.

  FIG. 14 shows a battery quick charging device for an electric vehicle currently used, and an outline of the configuration and operation will be described. A step-up converter with a power factor of approximately 1 is constituted by the three-phase PWM converter 20 from the AC power source 3 through the breaker 10, the current detectors 15 and 16, and the reactors 17 to 19. The capacitor 21 is charged while controlling the AC side current of the step-up converter in a sine wave shape with a high power factor. The AC side filter capacitors 12 to 14 are for supplying a high frequency current by PWM control.

  The voltage of the capacitor 21 is converted into a high frequency voltage (about 10 kHz to 20 kHz) by the PWM inverter bridge 22 and supplied to the primary side of the high frequency transformer 23. The secondary side of the high-frequency transformer 23 is converted into direct current by the diode bridge 24, the ripple caused by the PWM is reduced by the filter effect of the reactor 25 and the capacitor 27, and the current is detected by the current detector 26 to control the charging current. . The contactor 28 is a load non-current switching device.

  The current quick charger output is charged at 400V, 100A for 15 minutes. For this reason, about 50 kVA is required for AC power. However, in an electric vehicle, there is an opinion that 15 minutes of charging time is too long from comparison with the conventional gasoline refueling time, and a charging time of about 5 minutes is desired. In the past, charging for such a short time was impossible due to the characteristics of the battery. Recently, a lithium ion battery (trade name: SCiB (registered trademark)) using an oxide-based electrode material was announced in 5 minutes. Charging has become a reality.

  If such an improved lithium ion battery is used and charged at 400 V and 300 A, charging in 5 minutes becomes possible. Therefore, when considering a quick charging apparatus that realizes this, for example, a circuit as shown in FIG. 15 can be considered. That is, charging is performed at 400 V and 300 A, and considering the efficiency at 120 kW in that case, for the direct charging method (FIG. 14), AC power is required to be about 150 kVA, and considerable power receiving equipment is required. Therefore, the power receiving facility becomes expensive. In view of this, the circuit shown in FIG. 15 can be considered which can charge for 5 minutes at an output of 120 kW with a power receiving capacity of about 15 kVA.

  The circuit of FIG. 15 is provided with a step-down converter comprising an IGBT 33, a reactor 32, a diode 34, and a current detector 31 from the voltage of the capacitor 21 instead of the PWM inverter bridge of the circuit of FIG. The battery 5 is slowly charged. The charged battery 5 voltage is applied to the high-frequency transformer 23 via the high-frequency conversion inverter 22 to boost the voltage, and then the vehicle-side battery 2 is rapidly charged via the diode bridge 24.

JP-A-6-253461

For such a quick charger,
(1) Low AC input capacity
(2) AC side has high power factor
(3) The problem of high efficiency is required.

  However, in the invention of Patent Document 1, the basic concept of the quick charging device is shown, but no specific circuit is presented. In addition, since there is no insulation between the AC power source and the car battery, there is a problem of electric shock. Furthermore, in order to increase the efficiency of the charging device, the AC power source side needs to be highly efficient, but this point is not suggested.

  The circuits shown in FIGS. 14 and 15 have been proposed in order to solve the problems (1) to (3). However, the circuit shown in FIG. It was unsuitable for rapid charging. On the other hand, although the circuit of FIG. 15 can reduce the AC input capacity, there is a problem in that the number of times of passing through the semiconductor from the AC power source to the charging unit terminal is large and the efficiency is lowered.

  14 and 15 use a three-phase PWM converter. However, since this three-phase PWM converter requires a large number of high-speed semiconductor switching elements, the switching loss is large. For example, the number of elements through which the current of one phase of three phases passes is converted into a high-speed semiconductor switching element, and the number of times of passing through the semiconductor is two times in the PWM converter 20 part and once in the IGBT 33 of the step-down converter. It becomes. Further, in the quick charging unit, the total number of times is four, two times by the high-frequency inverter 22 and two times by the high-frequency diode bridge 24. As described above, the circuits of FIGS. 14 and 15 have a drawback that the efficiency is poor because the high-speed semiconductor switching element has many passes.

  In order to solve the above problems, it is conceivable to use a DC diode bridge instead of the step-up converter including the three-phase PWM converter 20 used in the circuits of FIGS. Certainly, in the case of a DC diode bridge, since there is no high-speed semiconductor switching element like the IGBT 33, the switching loss in that portion is reduced and the efficiency is improved. On the other hand, in the DC diode bridge, a circuit having a power factor of about 1 as in the three-phase PWM converter 20 cannot be configured, and there is a problem that the power factor is reduced on the AC side.

  The present invention is for solving the above-mentioned problems, and its purpose is to prevent a decrease in efficiency due to switching loss and a decrease in power factor associated with the use of a DC diode bridge while having a small AC input capacity. The aim is to provide a high-efficiency, high power factor rapid charging device.

  In order to achieve the above object, the rapid charging apparatus of the present invention is a means for obtaining a three-phase power source having a phase difference of 30 ° from an AC power source through a transformer, and a three-phase diode bridge from the two sets of three-phase power sources. Means for obtaining a rectified direct current, connecting a small-capacitance capacitor to the two sets of direct-current output sections, and charging a battery in the charging section or a large-capacity capacitor from the direct current section via a step-up chopper or a step-down chopper; Alternatively, the battery or the large-capacitance capacitor in the rapid charging unit is rapidly charged by means of charging the load battery or the large-capacity capacitor from the large-capacity capacitor by a two-phase step-up chopper or step-down chopper.

  According to the present invention, by using a three-phase diode bridge, the number of high-speed semiconductor switching elements used can be reduced, and the switching loss of the entire device can be reduced. Also, by obtaining two sets of power with a phase difference of 30 ° from a three-phase AC power source via a transformer and connecting them to a battery or a large-capacity capacitor in parallel via two sets of step-up choppers or step-down choppers. In addition, the ripple of the charging current flowing in the battery or the large-capacity capacitor can be reduced. Further, when two sets of power supplies having a phase difference of 30 ° are obtained from a three-phase AC power source via a transformer, the output current of the three-phase diode bridge is controlled to a flat waveform, so that the AC power source side, that is, the transformer The current waveform on the primary side of the device can be made close to a sine wave waveform, and a high-rate current can be obtained.

1 is a circuit diagram of a low speed charging unit in Embodiment 1 of the present invention. The block diagram and input-output waveform figure of the IGBT drive circuit part in Example 1 of this invention. The circuit diagram of the low-speed charge part in the modification of Example 1 of this invention. The block diagram and input-output waveform figure of the IGBT drive circuit part in the modification of Example 1 of this invention. The circuit diagram of the quick charge part in Example 1 of this invention. The circuit diagram of the quick charge part in the modification of Example 1 of this invention. The wave form diagram of the transformer primary side current in Example 1 of the present invention. The block diagram of the transformer part explaining the reason for which the current waveform of FIG. 7 is obtained, and the waveform diagram of an input-output current. The current waveform figure in each part of the quick charge part of FIG. The current waveform figure in each part of the quick charge part of FIG. Operation explanation diagram Comparison table between the conventional method and this plan The circuit diagram of the high-speed charge part in Example 2 of this invention. FIG. 6 is a block diagram of an IGBT drive circuit portion in Embodiment 2. The block diagram which shows the basic composition of the conventional quick charge apparatus for electric vehicles. The circuit diagram which shows an example of the conventional quick charge apparatus. The circuit diagram which shows the other example of the conventional quick charge apparatus.

  Embodiments of a quick charging apparatus according to the present invention will be described below with reference to the drawings. Constituent parts that are the same or similar in the prior art and each embodiment are denoted by common reference numerals, and redundant description is omitted.

[1-1. Constitution]
FIG. 1 is a configuration diagram of the low-speed charging unit 4 according to the first embodiment. The low-speed charging unit 4 supplies the power of the secondary side Δ winding 41 and the secondary side Y winding 42 having a phase difference of 30 degrees from the AC power source 3 through the transformer 40 with the diode bridges 43 and 53, respectively. It has two rectified DC parts. In each DC section, small capacitors 44 and 54 are connected in parallel to the diode bridges 43 and 53, respectively. A boost chopper is connected to the diode bridge and the small-capacitance capacitor via current detectors 45 and 55. The step-up chopper includes reactors 46 and 56, IGBTs 47 and 57, and diodes 48 and 58, respectively. The output side of the diodes 48 and 58 of each set of step-up choppers is connected to the charging battery 5 to constitute a charging unit. Capacitors 49 and 59 are capacitors for suppressing surges, and are connected to the output side of the diodes 48 and 58 and the emitter side of the IGBTs 47 and 57.

FIG. 2A shows a control circuit of the IGBT 47 constituting the step-up chopper. Since the control circuit of the IGBT 57 has the same configuration, the description thereof is omitted. The control circuit includes a PID amplifier 471 which receives the output _{I 1} of the current reference ^{I *} and the current detector 45, the PWM circuit 472 to the output of the PID amplifier 471 to the PWM signal. The IGBT47 through the IGBT drive circuit 473 by a PWM signal from the PWM circuit 472 and PWM control, and controls so that the output current _{I 12} from the step-up chopper the same waveform as the 3-phase bridge output voltage. Therefore, a current having a constant value as shown in FIG. 2B is supplied as the current reference I ^* .

  FIG. 3 shows a modification of the first embodiment shown in FIG. The low-speed charging unit 4 in FIG. 2 is obtained by changing the step-up chopper part in FIG. 1 to a step-down chopper. That is, the step-up chopper portion of FIG. 1 includes a first step-down chopper composed of an IGBT 47, a diode 48, a reactor 46, and a current detector 45, and a second step-down chopper composed of an IGBT 57, a diode 58, a reactor 56, and a current detector 55. It consists of choppers.

FIG. 4A shows a control circuit of the IGBT 47 constituting the step-down chopper of FIG. Since the control circuit of the IGBT 57 has the same configuration, the description thereof is omitted. The control circuit includes a PID amplifier 474 which receives the output _{I 1} of the current reference ^{I *} and the current detector 45, the PWM circuit 475 to the output of the PID amplifier 474 to the PWM signal. The IGBT47 through the IGBT drive circuit 476 and PWM control by the PWM signal from the PWM circuit 475, to control the input current _{I 11} from the step-down chopper at a constant value. Therefore, as the current reference I ^*, and supplies the three-phase current bridge output voltage waveform having the same shape of the waveform shown in FIG. 4 (B).

  Next, an example of the quick charging unit 6 will be described with reference to FIG. The A terminal in FIG. 5 is connected to the a terminal in FIG. 1 or 3 and the B terminal is connected to the b terminal. The rapid charging unit 6 includes a first boost chopper including a reactor 61, an IGBT 62, and a diode 63 via a current detector 60, and a second booster including a reactor 71, IGBT 72, and a diode 73 via a current detector 70. The output side of the boost chopper is shared. A filter capacitor 64 is connected to the output side of these boost choppers, and a load battery 2 is connected. The filter capacitor 64 may be omitted when the allowable charge ripple value is large.

  FIG. 6 is a modification of the quick charging unit 6. In the quick charging unit 6, the connection method of the terminals A and B for connecting to the low speed charging unit of FIG. 1 or FIG. 3 is the same as that of FIG. 6 includes a first step-down chopper that includes an IGBT 62, a diode 63, a reactor 64, and a current detector 65, and a second step-down chopper that includes an IGBT 72, a diode 73, a reactor 74, and a current detector 75. . The output sides of these two sets of step-down choppers are connected in parallel and connected to the load battery 2. The capacitor 66 connected between the terminals A and B is for absorbing the surge of the IGBTs 62 and 72.

[1-2. Action]
The operation of the first embodiment having such a configuration will be described with reference to FIGS. As shown in FIG. 2A, the current reference I ^* and the output I of the current detector 45 are amplified by a PID amplifier 471 and converted into a PWM signal by a PWM circuit 472. Through the IGBT drive circuit 473 by the PWM signal, the IGBT47 to PWM control, controls the current _{I 1} constant. The actual current I ₁ includes a PWM ripple of the carrier frequency. By smoothing this ripple with the capacitor 44, the output current I ₁₁ of the diode bridge 43 is as shown in FIG. It becomes a constant value.

On the other hand, the output current I ₁₂ of boost chopper includes, as shown in FIG. 2 (B), the same waveform as the 3-phase bridge output voltage. The reason is that the step-up chopper input voltage has a three-phase bridge output voltage waveform and its output current is flat, so that the chopper input power has a three-phase bridge output voltage waveform. Voltage of chopper output for input power = output power for a constant value in the voltage of the battery 5, the output current I ₁₂ is a 3-phase bridge voltage wave shape.

In FIG. 1, since two sets of such chopper circuit outputs are arranged in parallel, the carrier of the PMW is set to a difference of 180 °. As a result, two-phase control is achieved and the output current ripple is extremely reduced. Thus, the diode bridge output current I ₁₁ is controlled to a flat waveform, if the AC power supply side to have a 30 ° phase difference, as shown in FIG. 1, the AC power supply side current waveform, FIG. 7 As shown, the current waveform has less harmonics and high power factor operation is possible.

This point will be specifically described with reference to FIG. 8A, 3 is an AC power source, 40 is a transformer, 41 is a secondary side Δ winding, 42 is a secondary side Y winding, and 43 and 53 are diode bridges. IAC is the primary current of the transformer 40, I _acb is the output current from the secondary Δ winding 41, I _acb is the output current from the secondary Y winding 42, and I _11a is the output current of the diode bridge 43. , I _11b is an output current of the diode bridge 53. In this case, current _{I AC} at the primary side of the transformer 40, the _{I 411} determined by the output current _{I acb} from secondary △ windings 41, determined by the output current _{I acb} from the secondary side Y winding 42 I _{421 is} the combined waveform.

Therefore, as shown in FIG. 8B, when the output currents I _11a and I _11b of the diode bridges 43 and 53 are controlled to be constant, the primary current I _{411 of the} secondary Δ winding 41 and the secondary side The primary current I ₄₂₁ of the Y winding 42 is as shown in FIG. Therefore, a composite waveform _{I AC} transformer primary winding current _{I 411} and _{I 421} becomes the high power factor current approaching sinusoidal waveform as shown in FIG. 8 (C).

Next, the operation of the circuits of FIGS. 3 and 4 which are modifications of the first embodiment shown in FIGS. 1 and 2 will be described. As shown in FIG. 4A, a current having a three-phase full-wave rectified waveform as shown in FIG. 4B is supplied as the current reference I ^* , and this is compared with the output I ₁ of the current detector 45. Then, it is amplified by the PID amplifier 474. The output from the PID amplifier 474 is converted into a PWM signal by the PWM circuit 475, and the IGBT 47 is driven via the IGBT drive circuit 476. Current reference I ^* and the current detector output current I ₁ is substantially the same shape. However, the current detector output current I _1, the ripple is riding heavy by PWM carrier. Therefore, the power flowing into the battery 5, the battery voltage constant, the inflow current I ₁₂ is three-phase full-wave rectification wave shape. Output current I ₁₁ of the diode bridge 43, since the divided waveform battery input power voltage, the output current I ₁₁ becomes flat constant current.

  Also in the low-speed charging circuit 4 using the step-down chopper shown in FIGS. 3 and 4, the AC power supply current has a waveform close to a sine wave as shown in FIG. 7, and has a high power factor.

On the other hand, in the quick charging unit 6 using the two sets of step-up choppers of FIG. 5, the outputs I ₁ and I ₂ of the current detectors 60 and 70 are controlled to turn on and off the IGBTs 62 and 72. The drive circuits for the IGBTs 62 and 72 can be the same as those shown in FIGS. When the boost chopper is controlled in two phases in this way and the input currents I ₁ and I ₂ of the boost chopper are turned on / off, the output current currents i ₁ and i ₂ from the boost chopper of each phase are as shown in FIG. The intermittent current is out of phase.

That is, in FIG. 9, turning on IGBT 62 between times t1 to t2, from the battery 5 between terminals AB reactor 61 → IGBT 62 circuit is short-circuit current flows, the current _{I 1} is increased. When the IGBT 62 is turned off between the times t2 and t3, the energy stored in the reactor 61 passes through the diode 63 and charges the battery 2. This current is _{i 1.} On the other hand, the IGBT 72 is turned on between t2 and t3 and turned off between t3 and t4. The IGBT 62 and the IGBT 72 are switched with a phase difference of 180 °. Thus, since the rapid charging currents output from the respective boost choppers are i ₁ and i ₂ , the battery charging current as a combined current thereof is i ₁ + i ₂ , which is compared with the input current of the boost chopper. The ripple current is reduced. Further, by filtering the ripple current by the capacitor 64 provided on the output side of the two sets of boost choppers, the current of the load battery is further smoothed.

  FIG. 9 shows a waveform when the PWM duty by the PWM control circuit of the IGBTs 62 and 72 is 50%. That is, the ripple when the duty is 50% in FIG. 9 has the smallest ripple, but the ripple increases when the duty is not 50% in the PWM control. In this case, as described above, the capacitor 64 has a filter effect so that the ripple flowing in the battery 2 is equal to or less than a specified value.

Next, FIG. 10 shows waveforms when two-phase current control is performed using two sets of the step-down choppers of FIG. FIG. 10 also shows a case where the PWM duty is 50%. In the circuit of FIG. 6, by controlling the IGBTs 62 and 72 by the output currents I ₁ and I ₂ of the step-down chopper detected by the current detectors 65 and 75, the 180 ° phase as shown in FIG. A current with a shifted waveform is obtained. By synthesizing the outputs of the two-phase step-down choppers, the ripple of the output current i _{1 and} the ripple of the output current i ₂ of the two step-down choppers cancel each other, and the ripple of the current i ₁ + i ₂ flowing through the load battery 2 becomes zero. In this circuit, even if the duty is other than 50%, the ripple is very small.

[1-3. effect]
A comparison of the effects of the first embodiment and the prior art as described above is as follows.

(1) Power Factor and Efficiency of Low-Speed Charging Unit The conventional low-speed charging unit shown in FIG. 15 is compared with FIG. 1 or FIG. In the prior art, since a sine wave converter with a power factor ≈ 1 is used, the power factor is very good. In the first embodiment, the power factor is slightly low due to the waveform of FIG. 7, but since the waveform is close to a sine wave, the power factor is not extremely reduced, and a power factor close to that of a sine wave converter can be obtained.

  When the number of times of passing through the semiconductor is converted into a high-speed semiconductor switching element and compared, the prior art is 3 times, whereas in this embodiment, the diode bridges 43 and 53 pass the low-speed diode twice. This low-speed diode has a voltage drop of 1 / 1.5 compared to the high-speed diode, and since there is no loss due to switching, the loss can be regarded as 1/2. Therefore, since the diode bridges 43 and 53 can be regarded as one time when converted to a high-speed element, the entire low-speed charging unit requires two high-speed semiconductor switching elements, and thus the first embodiment is advantageous. Considering these, the efficiency of Example 1 is higher.

(2) Transformer part In the comparison of the transformer part, in the conventional technology in which a transformer is arranged in the quick charge part 6, a transformer with a rating of 150 kVA for 5 minutes is used to charge for 5 minutes at 400V, 300A. Necessary. Since the size of the transformer is substantially proportional to 1 / √f, for example, when an inverter transformer of f = 15 kHz is used, f≈10 to 15 kHz, which is smaller than the first embodiment using a commercial AC power supply of 50 Hz. is there. In Example 1, although it becomes a transformer of about 15 kVA, since frequency becomes 50 Hz, Example 1 is somewhat disadvantageous in terms of size. However, in consideration of the loss of the transformer section, the first embodiment that requires only a small-capacity 15 kVA transformer is much superior to the conventional technique of 150 kVA.

(3) Rapid charging unit In comparison with the rapid charging unit 6, the number of times that the high-speed semiconductor switching element passes is 4 in the conventional technology. On the other hand, in the first embodiment, as shown in FIG. 5 or FIG. 6, the number of times the high-speed semiconductor switching element passes is one, the first embodiment is significantly more advantageous, and the efficiency of the first embodiment is also higher. very good.
(4) Whole system Compared with the whole system, Example 1 is advantageous in terms of efficiency. Further, the rapid charging unit can significantly reduce the output ripple by performing two-phase current control as shown in FIGS. 5, 6, 9, and 10, and can extend the life of the load battery.

  FIG. 11 is a configuration diagram of the high-speed power unit 6 according to the second embodiment of the present invention. In the second embodiment, two chopper circuits are connected in parallel to the input terminals A and B from the battery 5, and the battery 2 is charged via these chopper circuits. That is, the first chopper circuit includes a step-down chopper composed of an IGBT 62, a diode 63, a reactor 64, and a current detector 65, and a step-up chopper composed of an IGBT 621, a diode 631, a filter capacitor 641, a reactor 64, and a current detector 65. Provide. The second chopper circuit is also provided with a step-down chopper composed of an IGBT 72, a diode 73, a reactor 74, and a current detector 75, and a step-up chopper composed of an IGBT 721, a diode 731, and a capacitor 642.

In the second embodiment, as shown in FIG. 12, current control is performed by the PID amplifier 100 in which 65 is input to the current reference I ^* and the detected current from the current detector 65. That is, when the output V of the PID amplifier 100 becomes 50% or more, the first PWM circuit 101 operates. PMW control is performed so that the IGBT 621 is turned on / off by the first PWM circuit 101, and the second PWM circuit 102 operates when the output V is 50% or less to drive the IGBT 62. When the output V that is being PWM controlled by the IGBT 62 is low, the IGBT 621 remains off and operates as a step-down chopper. In this case, since the current stops flowing when the voltage of the battery 2 becomes higher than the voltage between the terminals AB, the second PWM circuit 102 turns on the IGBT 62, the output V increases, and the first PWM circuit 101 is operated. As a result, the IGBT 621 is turned on and off to operate as a boost chopper.

  In the second embodiment having such a configuration, two sets of step-up / step-down choppers can be controlled in two phases to reduce charging current ripple. In addition, since the step-up / step-down chopper is used, when the voltage of the load battery 2 changes significantly, for example, it is suitable for an electric double layer capacitor or the like instead of the battery.

DESCRIPTION OF SYMBOLS 1 ... Electric vehicle 2 ... Power source battery 3 ... AC power supply 4 ... Low-speed charging part 5 ... Battery 6 ... Rapid charging part 10 ... Breakers 12, 13, 14 ... Capacitors 15, 16 ... Current detectors 17, 18, 19 ... Reactor 20 ... IGBT bridge 21 ... Capacitor 22 ... IGBT bridge 23 ... High frequency transformer 24 ... Diode bridge 25 ... Reactor 26 ... Current detector 27 ... Capacitor 28 ... Contactor 31 ... Current detector 32 ... Reactor 33 ... IGBT
34 ... Diode 40 ... Transformer 41 ... Secondary side Δ winding 42 ... Secondary side Y winding 43, 53 ... Diode bridge 44, 54 ... Capacitors 45, 55 ... Current detectors 46, 56, IGBT
47, 57, ... reactors 48, 58 ... diodes 49, 59 ... capacitors 471, 474 ... PID amplifiers 472, 475 ... PWM circuits 473, 476 ... IGBT drive circuits 60, 70 ... current detectors 61, 71 ... reactors 62, 72 ... IGBT
63, 73 ... Diodes 64, 66, 641, 642 ... Capacitors

Claims (6)

A fast charging unit comprising a low-speed charging unit for charging a battery or a large-capacitance capacitor inside the quick-charging device from an AC power source, and a quick-charging unit for rapidly charging a load battery or a large-capacity capacitor from the battery or the large-capacity capacitor with a large amount of power. In the device
Two sets of the low-speed charging unit including two sets of AC power supplies extracted at a phase difference of 30 ° on the secondary side of the transformer connected to the AC power supply, and three-phase diode bridges connected to the AC power supplies, respectively. And two sets of step-down chopper circuits or step-up chopper circuits connected to the output side of the DC unit,
A rapid charging device, wherein each set of chopper circuits is connected in parallel to an input side of a battery or a large-capacitance capacitor in the device.   The chopper circuit includes a current detector that detects a current flowing through the chopper circuit, and the internal battery that outputs from the chopper circuit by PWM control based on the current of the chopper circuit and the current reference by the current detector. Alternatively, the rapid charging apparatus according to claim 1, wherein the charging current waveform to the large-capacitance capacitor is controlled to a three-phase full-wave shape. The two sets of chopper circuits are provided with a current detector for detecting a current flowing through the chopper circuit, and output from the chopper circuit by PWM control based on the current of the chopper circuit by the current detector and a flat current reference. To control the charging current waveform to the battery or large-capacitance capacitor inside the device to a three-phase full-wave shape,
2. The rapid charging apparatus according to claim 1, wherein the ripple of the charging current is smoothed by setting a phase difference between the ripples of the charging current in a three-phase full-wave waveform output from the two sets of chopper circuits to 180 °.   Each set of chopper circuits includes a current detector that detects a current flowing through the chopper circuit. The current and the current reference of the chopper circuit by the current detector are set to a three-phase full-wave rectified waveform, and the three-phase full-wave PWM control of the chopper circuit based on the current of the chopper circuit having the rectified waveform and the current reference makes the phase difference of the ripple of the charging current waveform to the battery or the large-capacitance capacitor output from the chopper circuit 180 °. The rapid charging apparatus according to claim 1, wherein the charging current has a flat waveform.   The low-speed charging unit controls the output current of the two sets of three-phase diode bridges connected to the two sets of AC power supplies taken out with a phase difference of 30 ° to the secondary side of the transformer. The current of the primary winding of the transformer determined by the two secondary windings of the transformer corresponding to the output current of the two sets of three-phase diode bridges has a waveform close to a sine wave. The rapid charging apparatus according to claim 1 or 2. The quick charging unit is configured to load a load through any one of a chopper circuit having a two-phase step-up chopper, a chopper circuit having a two-phase step-down chopper, or a two-phase chopper circuit combining a step-up chopper and a step-down chopper. Connected to a battery or a large capacitor,
The rapid ripple according to any one of claims 1 to 5, wherein a ripple of an output from the two-phase chopper circuit rapidly charges the battery or the large-capacity capacitor of the load with a phase difference of 180 °. Charging device.

Images