JP2009171829A - Insulating-type switching power supply - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide an insulating-type switching power supply whose circuit scale is small, and whose switching element can transfer energy from a primary side to a secondary side regardless of ON cycle and OFF cycle. <P>SOLUTION: The system is configured to complementarily perform ON/OFF control a first switching element Q1 and a second switching element Q2, transfer the energy from the primary side to the secondary side with a second primary winding ni and a second secondary winding no in Q1 ON cycle, transfer the energy with a first primary winding np and a first secondary winding ns in Q2 ON cycle, connect the ns and no directly, insert the inductors into the no in series, and allow output current to flow through the inductors. <P>COPYRIGHT: (C)2009,JPO&INPIT

Description

  The present invention relates to an isolated switching power supply apparatus in which there is substantially no period during which energy transfer between primary and secondary of a transformer is not performed.

  Conventionally, forward converters, flyback converters, and the like are known as typical isolated switching power supply devices. Each of these isolated switching power supply devices accumulates energy in the transformer or the inductor during the period when the main switch element is on, and the primary while the primary side main switch element is on or off. The operation of transmitting energy from the side to the secondary side is performed, and there is a period in which energy transmission from the primary side to the secondary side is not performed in any period of ON / OFF of the main switch.

  On the other hand, a two-transformer type having two transformers as an insulating switching power supply device that performs energy transmission from the primary side to the secondary side in both the on-period and the off-period of the primary-side main switch element A DC-DC converter is known. The following patent document 1 is shown as an example.

  As shown in FIG. 1, the following Patent Document 1 discloses that a primary circuit includes a primary circuit W1 of a transformer T1, a primary coil W4 of a transformer T2, and a main switch Q1. 2 at connection points 10 and 20.

  Further, between the connection point between the primary coil W4 of the transformer T2 and the main switch Q1, and the connection point 20 between the negative end of the input DC power supply 2 and the main switch Q1, the primary coil W5 of the transformer T2 and the transformer T1 A series circuit composed of a primary coil W2 and a capacitor C1 is connected.

  Further, a series circuit including a capacitor C2 and a sub switch element Q2 is provided between a connection point between the primary coil W4 of the transformer T2 and the main switch element Q1 and a connection point between the primary coil W2 of the transformer T1 and the capacitor C1. It is connected.

  In addition, as the secondary side circuit, a load is applied so that a series circuit composed of the secondary coil W3 of the transformer T1 and the output switch Q4 and a series circuit composed of the output switch Q3 and the secondary coil W6 of the transformer T2 are parallel to each other. The so-called center tap type full-wave rectifier circuit is configured by connecting the both ends of the system 3 and the output switches Q3 and Q4 acting as synchronous rectifier elements. A capacitor C3 is connected to both ends of the load system 3 as a smoothing capacitor.

  In this way, during the period in which the main switch element Q1 is on, the sub switch element Q2 is off, and on the primary side, current flows through the primary coil W1 of the transformer T1 and the primary coil W4 of the transformer T2. On the next side, the output switch Q3 is turned on, Q4 is turned off, a current flows through the secondary coil W6 of the transformer T2, and an output voltage is supplied to the load system 3.

Further, during the period in which the main switch element Q1 is off, the sub switch element Q2 is on, and on the primary side, current flows through the primary coil W2 of the transformer T1 and the primary coil W5 of the transformer T2, and on the secondary side, The output switch Q3 is turned off, Q4 is turned on, a current flows through the secondary coil W3 of the transformer T1, and an output voltage is supplied to the load system 3.
JP 2005-51994 A

  However, the isolated switching power supply device disclosed in Patent Document 1 is characterized in that the use of two transformers eliminates the need for a secondary side choke coil. Two were required, and there was a problem that the circuit was enlarged.

  The advantage that the choke coil is unnecessary is effective in the sense that energy can be transmitted from the primary side to the secondary side while the primary side main switching element Q1 is on and off, but the secondary side If the side choke coil is not required, the output ripple becomes large due to the switching noise generated during the ON / OFF switching period of the primary side main switching element Q1, and the smoothing capacitor C3 is enlarged. There was a problem to do.

  Further, since a voltage obtained by adding the voltage across the capacitor C2 to the input voltage Vin is applied between the drain and source of the main switch element Q1, a high breakdown voltage switch element is required. Since the on-resistance which is a resistance component is large, the conduction loss in the switch element increases. For this reason, there existed a problem that efficiency fell and cost increased.

  Accordingly, an object of the present invention is to solve the above-described problem, and can transmit energy from the primary side to the secondary side of the transformer regardless of the on / off period of the main switch element. An object of the present invention is to provide an insulating switching power supply apparatus that can suppress the generation of switching noise that occurs in the off-switching period and can simultaneously reduce output ripple and that can use a low-breakdown-voltage switch element.

The present invention is configured as follows to solve the above-described problems.
(1) a DC power input unit to which a DC input voltage Vi is input;
A transformer T including a first primary winding np, a first secondary winding ns, and a second secondary winding no, which is composed of one magnetic component and is magnetically coupled; ,
A first inductor Lr connected in series to the first primary winding np;
A first rectifying element Ds that rectifies a sum of currents generated in the first secondary winding ns and the second secondary winding no, and generated in the second secondary winding no. A rectifier circuit comprising a second rectifier element Df for rectifying current;
A first switching circuit S1 including a parallel circuit of a first switching element Q1, a first capacitor C1, and a first diode D1,
A second switching circuit S2 composed of a parallel circuit of a second switching element Q2, a second capacitor C2, and a second diode D2,
A third capacitor Cr;
A first series circuit connected to both ends of the DC power supply input unit, wherein the first primary winding np and the first switch circuit S1 are connected in series;
A second switch circuit is connected to both ends of the first switch circuit S1 or both ends of the first primary winding np, and the second switch circuit S2 and the third capacitor Cr are connected in series. A series circuit,
The first switch circuit S1 and the second switch circuit S2 are insulated switching power supply devices configured to operate so as to repeat ON / OFF complementarily with a period in which both are OFF. And
The transformer T is synchronized with complementary ON / OFF operations of the first switch circuit S1 and the second switch circuit S2, and the first secondary winding ns or the second secondary winding. The wire no is complementarily wound so that energy transfer is performed from the primary side to the secondary side in a complementary manner,
In the first secondary winding ns and the second secondary winding no, the magnetic polarities of the windings are opposite to each other,
The output voltage Vo is output to the secondary side via the second inductor Lro.
(2)
A DC power supply input unit to which a DC input voltage Vi is input;
The first primary winding np, the first secondary winding ns, the second primary winding ni, and the second secondary winding no, which are composed of one magnetic component and are magnetically coupled. And a transformer T comprising:
A first inductance Lr connected in series to the first primary winding np;
A third inductor Lri connected in series to the second primary winding ni;
A second inductor Lro connected in series to the first secondary winding no;
A first rectifying element Ds that rectifies a sum of currents generated in the first secondary winding ns and the second secondary winding no, and generated in the second secondary winding no. A rectifier circuit comprising a second rectifier element Df for rectifying current, a first switching element Q1, a first capacitor C1, and a first switch circuit S1 comprising a parallel circuit of a first diode D1,
A second switching circuit S2 composed of a parallel circuit of a second switching element Q2, a second capacitor C2, and a second diode D2,
A third capacitor Cr;
A first series connected to both ends of the DC power supply input unit, wherein the first primary winding np or the second primary winding ni and the first switch circuit S1 are connected in series. Circuit,
The second switch circuit S2 and the third capacitor Cr are connected to both ends of the first switch circuit S1, or both ends of the first primary winding np or the second primary winding ni. A second series circuit connected in series;
A fourth capacitor Ce connected in parallel to the first series circuit,
The first switch circuit S1 and the second switch circuit S2 are insulated switching power supply devices configured to operate so as to repeat ON / OFF complementarily with a period in which both are OFF. And
The transformer T is synchronized with complementary ON / OFF operations of the first switch circuit S1 and the second switch circuit S2, and the first secondary winding ns or the second secondary winding. The wire no is complementarily wound so that energy transfer is performed from the primary side to the secondary side in a complementary manner,
In the first secondary winding ns and the second secondary winding no, the magnetic polarities of the windings are opposite to each other,
The output voltage Vo is output to the secondary side via the second inductor Lro.
(3)
The transformer T includes a first transformer T1 composed of the first primary winding np and the first secondary winding ns, the second primary winding ni and the second secondary. It is characterized by comprising a second transformer T2 composed of a winding no.
(4)
A primary leakage magnetic flux of the transformer T is used as the first inductor Lr.
(5)
As the second inductor Lro, a secondary leakage magnetic flux of the transformer T is used.
(6)
As the third inductor Lri, a primary leakage magnetic flux of the transformer T is used.
(7)
In the transformer T, the first primary winding np or the second primary winding ni is arranged in a direction to cancel the DC magnetic flux generated in the common magnetic core due to the current flowing through the second secondary winding no. The first secondary winding ns has a magnetic polarity opposite to that of the second secondary winding no, and the number of turns is larger than the number of turns of the second secondary winding no. It is characterized by that.
(8)
The first primary winding np and the second primary winding with respect to the direction of the current that flows when the first switch circuit S1 is conductive or the second switch circuit S2 is conductive. The line ni has the same magnetic polarity, and the first secondary winding ns and the second secondary winding no have opposite magnetic polarities.
(9)
The first transformer T1 is characterized in that the degree of magnetic coupling is smaller than that of the second transformer T2.
(10)
The first switch circuit S1 or the second switch circuit S2 is a field effect transistor.
(11)
The first switch circuit S1 or the second switch circuit S2 is driven by a zero voltage switching operation in which the switching element is turned on after the voltage across the switch circuit is reduced to 0V or near 0V. Features.
(12)
The rectifier circuit includes a third diode that rectifies a current flowing through the first secondary winding ns during a period in which energy transfer is performed from the primary side to the secondary side by the first secondary winding ns. Ds and a fourth diode Df for rectifying a current flowing through the second secondary winding no in a period in which energy transfer is performed from the primary side to the secondary side by the second secondary winding no It is comprised from these.
(13)
The third diode Ds or the fourth diode Df is constituted by a synchronous rectifier circuit in which a field effect transistor is replaced.
(14)
A turns ratio between the number of turns of the first secondary winding ns and the number of turns of the second secondary winding no.
ns: no = 2: 1
It is characterized by that.
(15)
In the transformer T, the magnetic coupling degree between at least the first primary winding np and the first secondary winding ns is relatively large, and the second secondary winding no and other windings The magnetic coupling degree with the line is relatively small.
(16)
The first primary winding np and the first secondary winding ns are composed of laminated windings, and the first secondary winding ns and the second secondary winding no, or the first secondary winding ns Of the primary winding np and the second secondary winding no, at least one of the primary winding np and the second secondary winding no is configured by split winding.
(17)
The transformer T has a plurality of leg cores, and the first primary winding np and the first secondary winding ns are wound around the same leg core, and at least the second secondary winding The winding no is configured to be wound around another leg core.
(18)
The first primary winding np and the first secondary winding ns are composed of laminated windings, and the first secondary winding ns and the second secondary winding no, or the first secondary winding ns Of the primary winding np and the second secondary winding no, at least one of the primary winding np and the second secondary winding no is configured by split winding.
(19)
The first switch circuit S1 and the second switch circuit S2 are controlled to stabilize the output voltage Vo by PWM control.
(20)
The third capacitor Cr is connected between the first primary winding ni and the first switch circuit S1.
(21)
When one of the first switch circuit S1 and the second switch circuit S2 has a time ratio (= on time / switching cycle) as Da,
0 ≦ Da ≦ 0.5
Drive only in the range of
0.5 ≦ Da ≦ 1
It is characterized by being driven only in the range.
(22)
The voltage conversion rate represented by the ratio of the output voltage Vo to the input voltage Vi of the power supply input unit is M (= Vo / Vi), and the first primary winding np and the first secondary winding When the turn ratio of ns is n (= np / ns),
M = D (1-D) / n
It is represented by.

According to this invention,
(A) Regardless of whether the switching element is in the on period or the off period, energy can be transmitted from the primary side to the secondary side, and the power conversion efficiency is excellent.
(B) By using one composite transformer composed of a leakage flux transformer, all the inductance elements required for circuit operation can be replaced by the leakage flux of the transformer, and the entire circuit scale can be greatly reduced. Is possible.
(C) In energy transmission from the primary side to the secondary side, energy is not accumulated in the inductance element, and the transformer can be miniaturized.
(D) Since the maximum magnetic flux density of the transformer can be sufficiently reduced even under heavy loads, the transformer can be designed with a margin against magnetic saturation, etc., compared to the conventional case, so that the transformer can be reduced in size and weight. Become.
(E) Current fluctuation when the energy transmission path is switched from magnetic coupling between one primary winding ni and secondary winding no to magnetic coupling between the other primary winding np and secondary winding ns. Since filter inductors for suppression are provided on the primary side and the secondary side, output ripple noise can be greatly reduced, and the smoothing capacitor can be reduced in size.
(F) Since the filter inductor Lro on the output side is replaced with the leakage flux of the transformer, the number of parts can be reduced and the circuit scale can be greatly reduced.
(G) Since the operating voltage of the first switching element Q1 is lowered to the same voltage as the input voltage, it is possible to use a low breakdown voltage semiconductor component for the switching element, and since the on-resistance is low, the switching loss can be reduced. Low cost and high efficiency can be realized.
(H) By driving the first switching element Q1 and the second switching element Q2 with zero voltage switching (ZVS), switching loss can be further reduced, and high efficiency can be achieved.
(I) By replacing the primary-side inductance element necessary for zero voltage switching (ZVS) drive with a leakage flux of the transformer, the number of parts can be reduced, and the circuit scale can be greatly reduced.
(J) Since the switching element Q2 functions as a voltage clamp circuit, it is possible to prevent a switching surge voltage from being applied to the switching element Q1, and thus a low-voltage semiconductor component can be used for the switching element. By using a low on-resistance element, conduction loss can be reduced and high efficiency can be realized.
Thus, the circuit scale can be simplified and a highly efficient isolated switching power supply device can be configured.

<< First Embodiment >>
FIG. 2 is a circuit diagram of the isolated switching power supply device according to the first embodiment.

  As shown in FIG. 2, the insulated switching power supply device includes a first inductor Lri and a second of the composite transformer T with respect to the + side terminal and the − side terminal of the power input unit to which the DC voltage Vi is supplied. A series circuit composed of the primary winding ni, the third capacitor Cr, and the first switch circuit S1 is connected, and the second primary winding ni of the composite transformer T and the third capacitor Cr are connected. A series circuit composed of the first primary winding np of the composite transformer T, the second inductor Lr, and the fourth capacitor Ce is connected between the point and the negative terminal of the power input unit. The second switch circuit S2 is connected between the connection point of the third capacitor Cr and the first switch circuit S1 and the connection point of the second inductor Lr and the fourth capacitor Ce.

  The first switch circuit S1 and the second switch circuit S2 are short-circuited when both are turned on at the same time. Therefore, the first switch circuit S1 and the second switch circuit S2 are configured to be complementarily turned on / off with a minimum dead time. Is done.

  The first switch circuit S1 includes a parallel connection circuit of a first switching element Q1, a first diode D1, and a first capacitor C1, and the second switch circuit S2 includes a second switch circuit S2. A switching circuit Q2, a second diode D2, and a second capacitor C2 are connected in parallel.

  By configuring the first switching element Q1 and the second switching element Q2 with field effect transistors such as MOSFETs, the parasitic diodes are the first diode D1 and the second diode D2, and the parasitic capacitor is the first capacitor. It can be used as C1 and the second capacitor C2. As a result, the mounting as these individual components can be omitted, and the number of components can be reduced.

  Further, on the secondary side of the composite transformer T, a first secondary winding ns mainly coupled to the first primary winding, and a second mainly coupled to the second primary winding ni. Secondary winding no, the first primary winding np and the second primary winding ns are of opposite polarity, the second primary winding ni and the second secondary winding no Are wound to have the same polarity.

  In the composite transformer T, the anode of the third diode Ds is connected to one end of the first secondary winding ns, and the anode of the fourth diode Df is connected to the other end of the first secondary winding ns. The cathode of the fourth diode Df is connected to the cathode of the third diode Ds. One end of the second secondary winding no is connected to a connection point between the cathode of the third diode Ds and the cathode of the fourth diode Df, and the other end of the second secondary winding no is 3 is connected to one end of the inductor Lro. The other end of the third inductor Lro is connected to one end of the load Ro, and the other end of the load Ro is connected to the other end of the first secondary winding ns. A smoothing fifth capacitor Co is connected in parallel to both ends of the load Ro.

  With such a configuration, the first primary winding np and the first secondary winding ns in the composite transformer T are periods in which the first switching element Q1 is off and the second switching element Q2 is on. The polarity of the winding is set so as to operate as a flyback system that sends power to the output at the second primary winding ni and the second secondary winding no, the first switching element Q1 is on, In addition, since the polarity of the winding is set so as to operate as a forward system that sends power to the output during the period in which the second switching element Q2 is off, the first switching element Q1 is on and the second switching element Q2 Is off, a voltage is induced in the second secondary winding no, the fourth diode Df is turned on, an output current is passed through the third inductor Lro, and a direct current is applied to the load Ro. The power voltage is supplied.

  In addition, during the period in which the first switching element Q1 is off and the second switching element Q2 is on, a voltage is induced in the first secondary winding ns and the third diode Ds is turned on. The DC output voltage is supplied to the load Ro by flowing an output current through the inductor Lro.

  In this way, in the composite transformer T, energy transmission from the primary side to the secondary side can be realized in either the on period or the off period of the first switch circuit S1, so that the minimum dead time is necessary. Except for, energy transmission from the primary side to the secondary side is possible over substantially the entire region of the switching period. Further, in the dead time period, which is a short period during which the transmission path is switched, the current fluctuation can be suppressed by the filter inductor Lro which can be constituted by the leakage flux of the transformer, so that the output ripple noise can be greatly reduced, and the fifth smoothing The capacitor Co can be reduced in size.

  FIG. 18 is a waveform diagram of each part of the circuit of the isolated switching power supply device shown in FIG. The circuit operation will be described below with reference to FIGS. In FIG. 18, vgs1 and vgs2 are the gate-source voltages of the switching elements Q1 and Q2, respectively, and are waveforms substantially representing the on / off of the switching elements Q1 and Q2. Further, vds1 and vds2 are drain-source voltages of the switching elements Q1 and Q2, respectively, and are substantially voltage waveforms across the capacitors C1 and C2. Further, id1, id2, ii, ip, and iL are current waveforms of currents flowing through the switch circuits S1, S2, the second primary winding ni, the first primary winding np, and the third inductor Lro, respectively. .

  The operation in the rated operation of the insulated switching power supply device can be divided into six operation states from time t1 to time t7 in one switching cycle Ts. The circuit operation will be described below for each state.

(1) State 1 state1 [t1 to t2]
First, after the second switching element Q2 is turned off, the first diode D1 is turned on when the drain-source voltage Vds1 of the first switching element Q1 approaches zero voltage. At this timing, the first switching element Q1 is turned on, and a zero voltage switching (ZVS) operation is performed.

(2) State 2 state2 [t2 to t3]
When the first switching element Q1 is turned on, a current flows through the first primary winding np and the second primary winding ni, and the current id1 and the first current flowing through the first switching element Q1 The current ip flowing through the primary winding np increases in a linear function. At this time, the first secondary winding ns mainly magnetically coupled to the first primary winding np operates as a flyback converter, and is mainly magnetically coupled to the second primary winding ni. Since the second secondary winding no that is coupled to is operated as a forward converter, current flows only through the second secondary winding no on the secondary side of the composite transformer T. The diode Ds is turned off, and the fourth diode Df is turned on. Therefore, the current flowing on the secondary side of the composite transformer T flows in the order of the fourth diode Df → the first secondary winding no → the third inductor Lro → the load Ro.

(3) State 3 state3 [t3 to t4]
When the first switching element Q1 is turned off, the energy stored in the first inductor Lri and the second inductor Lr charges the first capacitor C1, and accordingly, between the drain and source of the first switching element Q1. The voltage Vds1 increases. At the same time, the second capacitor C2 is discharged, and accordingly, the drain-source voltage Vds2 of the second switching element Q2 drops.

(4) State 4 state4 [t4 to t5]
When the drain-source voltage Vds2 of the second switching element Q2 becomes close to zero voltage, the second diode D2 is turned on. At this timing, the second switching element Q2 is turned on, and a zero voltage switching (ZVS) operation is performed.

(5) State 5 state5 [t5 to t6]
When the second switching element Q2 is turned on, the first primary winding np and the second primary winding ni are excited in the direction opposite to that in [State 2], and the second primary winding np is excited. No current flows through the winding ni, and the first primary winding np increases in a linear function in the opposite direction to that in [State 2]. Further, the current id2 flowing through the second switching element Q2 also increases in a linear function. At this time, the first secondary winding ns mainly magnetically coupled to the first primary winding np operates as a flyback converter, and is mainly magnetically coupled to the second primary winding ni. Since the second secondary winding no coupled to the No. 2 operates as a forward converter, current flows only through the first secondary winding ns on the secondary side of the composite transformer T. The diode Ds is turned on, and the fourth diode Df is turned off. Therefore, the current flowing on the secondary side of the composite transformer T flows in the order of the first secondary winding ns → the third diode Ds → the second secondary winding no → the third inductor Lro → the load Ro. .

(6) State 6 state6 [t6 to t7]
When the second switching element Q2 is turned off, the energy stored in the second inductor Lr charges the second capacitor C2, and accordingly, the drain-source voltage Vds2 of the second switching element Q2 increases. At the same time, the first capacitor C1 is discharged, and accordingly, the drain-source voltage Vds1 of the first switching element Q1 drops. Thereafter, the operation returns to [State 1].

  The on / off timing of the first switching element Q1 and the second switching element Q2 has, for example, an output voltage detection circuit for detecting the output voltage, and a photo that exceeds a predetermined voltage is detected. Feedback is performed using an insulating feedback means such as a coupler, and on / off control is performed based on the feedback.

  In addition, when PWM (pulse width modulation) control is used as the on / off control, the switching frequency is constant, so that frequency components such as EMI noise generated by the switching operation are also concentrated on the constant frequency. There is an advantage that it is easy to take measures against noise.

  However, in the present invention, not only PWM control but also various control methods such as PAM (pulse amplitude modulation) control and PFM (pulse frequency modulation), and a control method combining them can be used.

  FIG. 19 is an external view of a composite transformer T used in the insulating switching power supply device according to the first embodiment.

  As shown in FIG. 19, the first secondary winding ns mainly magnetically coupled to the first primary winding np, and the second primary winding ni mainly mainly magnetically. The second secondary winding no to be coupled is configured as one composite transformer. The first secondary winding no is wound so that the degree of magnetic coupling with the other windings is the smallest and the leakage flux is increased. Specifically, as shown in FIGS. 19 and 21, the composite transformer T has a plurality of leg cores, and the first primary winding np and the first secondary winding ns are the same. It is wound around the leg core, and at least the second secondary winding no is wound around the other leg core. Alternatively, the first primary winding np and the first secondary winding ns may be configured by laminated winding, and the second secondary winding no may be configured by split winding with respect to them. This is a configuration for increasing the inductance value when the second inductance Lro is replaced by the leakage flux of the composite transformer T.

In one composite transformer T, the voltage induced in the first secondary winding ns is Vo1, the voltage induced in the second secondary winding no is Vo2, and the voltage output to the load Ro. Is Vo, when the turns ratio of the first secondary winding ns and the second secondary winding no is ns: no = 2: 1,
When the first switching element Q1 is on and the second switching element Q2 is off, the output voltage Vo is
Vo = Vo2
When the first switching element Q1 is off and the second switching element Q2 is on, the output voltage Vo is
Vo = Vo1-Vo2 = 2Vo2-Vo2 = Vo2
Thus, the ripple component of the output voltage Vo can be eliminated.

When ns: no = 1: 1,
The magnitude of magnetic flux generated in the core of the composite transformer T when the first switching element Q1 is on and the second switching element Q2 is off, the first switching element Q1 is off, and the second switching element Q2 is Since the magnitude of the magnetic flux generated in the core of the composite transformer T becomes equal when it is on, and the core of the transformer is most difficult to be magnetically saturated, a margin can be given to the design of the composite transformer.

  A transformer provided with a portion having a small degree of magnetic coupling so as to intentionally generate a leakage magnetic flux as shown in FIG. 19 is called a leakage magnetic flux type transformer. As the structure of such a leakage flux type transformer, for example, variations as shown in FIGS. 19 to 26 are conceivable. In either case, the degree of magnetic coupling between the second secondary winding no and the other windings is reduced, and the degree of magnetic coupling between the first primary winding np and the first secondary winding ns is increased. It has a structure like that. As illustrated, the core structure may be “EE type core”, “EI type core”, “ER type core”, “ERI type core”, “LL type core”, “UU type core”, or the like.

Further, in the first embodiment, when the number of turns of the first primary winding np and the second primary winding ni of the composite transformer T is made equal, for example, the time ratio of the switching element (= on time) / Switching cycle) is Da, and the turns ratio of the first primary winding np and the first secondary winding ns is n, the voltage conversion rate M (= Vo / Vi) is the third capacitor When the voltage at both ends of Cr is VCr, the voltage at both ends of the fourth capacitor Ce is VCe, the on time of the switching element is Ton, and the off time is Toff, Vi = VCe and D = Ton / (Ton + Toff).
(Vi−VCr) × Ton = − (Vi−VCe−VCr) × Toff
The following equation holds. Solving this,
VCr = D × Vi.
At the same time, Vo = {(no / ni) × (Vi−VCr) × D + ((no−ns) / np) × (−VCr) × (1−D)} × Vi
The following equation holds. Since ni = np, when solving this,
M = Da * (1-Da) / n
It becomes. Therefore, since the voltage conversion rate M draws a parabolic characteristic curve with a peak at Da = 0.5, the first switching element Q1 and the second switching element Q2 have Da = 0.5 as a boundary point. Symmetrical operation is possible. That is, one switching element has 0 ≦ Da ≦ 0.5.
The other switching element operates in the range of 0.5 ≦ Da ≦ 1.
Operates in the range. By doing so, it is possible to disperse the conduction loss of the switching element, and it is possible to reduce the size of the heat dissipation structure and hence the switching power supply device.

  The effects of the configuration of the insulated switching power supply device according to the first embodiment are as follows.

  (A) Regardless of whether the switching element is in the on period or the off period, energy can be transmitted from the primary side to the secondary side, and the power conversion efficiency is excellent.

  (B) By using one composite transformer composed of a leakage flux transformer, all the inductance elements required for circuit operation can be replaced by the leakage flux of the transformer, and the entire circuit scale can be greatly reduced. Is possible.

  (C) In energy transmission from the primary side to the secondary side, energy is not accumulated in the inductance element, and the transformer can be miniaturized.

  (D) Since the maximum magnetic flux density of the transformer can be sufficiently reduced even under heavy loads, the transformer can be designed with a margin against magnetic saturation, etc., compared to the conventional case, so that the transformer can be reduced in size and weight. Become.

  (E) Current fluctuation when the energy transmission path is switched from magnetic coupling between one primary winding ni and secondary winding no to magnetic coupling between the other primary winding np and secondary winding ns. Since filter inductors for suppression are provided on the primary side and the secondary side, output ripple noise can be reduced, and the smoothing capacitor can be reduced in size.

  (F) Since the filter inductor Lro on the output side is replaced with the leakage flux of the transformer, the number of parts can be reduced and the circuit scale can be greatly reduced.

  (G) Since the operating voltage of the first switching element Q1 is lowered to the same voltage as the input voltage, it is possible to use a low breakdown voltage semiconductor component for the switching element, and since the on-resistance is low, the switching loss can be reduced. Low cost and high efficiency can be realized.

  (H) By driving the first switching element Q1 and the second switching element Q2 with zero voltage switching (ZVS), switching loss can be further reduced, and high efficiency can be achieved.

  (I) By substituting the primary side inductance element necessary for zero voltage switching (ZVS) drive with the leakage flux of the transformer, the number of parts can be reduced and the size can be greatly reduced.

  (J) Since the switching element Q2 functions as a voltage clamp circuit, it is possible to prevent a switching surge voltage from being applied to the switching element Q1, and thus a low-voltage semiconductor component can be used for the switching element. By using a low on-resistance element, conduction loss can be reduced and high efficiency can be realized.

In the first embodiment, the first primary winding np and the first secondary winding ns are configured to have opposite polarities, and the second primary winding ni and the second 2 Although the secondary winding no is configured to have the same polarity, the first primary winding np and the first secondary winding ns have the same polarity, the second primary winding ni and the second 2 The next winding no may be wound so as to have a reverse polarity.
<< Second Embodiment >>
FIG. 3 is a circuit diagram of an isolated switching power supply device according to the second embodiment. What is different from the circuit shown in FIG. 2 is the connection position of the third diode Ds. That is, in FIG. 3, the third diode has the fourth diode Df and the anode connected to each other. Other configurations are the same as those shown in FIG.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the second embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (g), (h), (i), and (j).

<< Third Embodiment >>
FIG. 4 is a circuit diagram of an isolated switching power supply device according to the third embodiment. 2 is different from the circuit shown in FIG. 2 in that the first primary winding np and the first secondary winding ns operate as a forward system, and the second primary winding ni and the second secondary winding. The line no operates in a flyback manner. That is, in FIG. 4, while the first switching element Q1 is on and the second switching element Q2 is off, a voltage is induced in the first secondary winding ns and the third diode Ds is turned on. The DC output voltage is supplied to the load Ro by flowing an output current through the inductor Lro.
Further, while the first switching element Q1 is off and the second switching element Q2 is on, a voltage is induced in the second secondary winding no and the fourth diode Df is turned on, and the third inductor A direct current output voltage is supplied to the load Ro by passing an output current through Lro. Other configurations are the same as those shown in FIG.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the third embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (g), (h), (i), and (j).
<< Fourth Embodiment >>
FIG. 5 is a circuit diagram of an isolated switching power supply device according to the fourth embodiment, which is configured by omitting the second primary winding ni and the second secondary winding no from the first embodiment. It is an example. In the first embodiment, in order to make the transmission energy in the period in which the first switch circuit S1 is on equal to the transmission energy in the period in which the second switch circuit S2 is on, the first 1 The number of turns of the secondary winding np and the second primary winding ni needs to be equal. That is, a current flows through the second primary winding ni while the first switch circuit S1 is on, and the first primary winding when the second switch circuit S2 is on. Since a current flows through np, the second primary winding ni can be omitted, and the transformer T can be driven only by the first primary winding np. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Compared with the first embodiment, the fourth embodiment does not require the second primary winding ni in the transformer T, and can be further downsized.

The effects of the configuration of the insulated switching power supply according to the second embodiment are the effects (a), (b), (c), (d), (f) among the effects mentioned in the first embodiment. , (G), (h), (i), (j).
<< Fifth Embodiment >>
FIG. 6 is a circuit diagram of an isolated switching power supply device according to the fifth embodiment. The first transformer is composed of the first primary winding np and the first secondary winding ns in the first embodiment. This is an example in which the second transformer T2 is configured by the second primary winding ni and the second secondary winding no, which constitutes T1. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Compared to the first embodiment, the fifth embodiment is disadvantageous in terms of miniaturization because the transformer is separated into two, but the first transformer T1 and the second transformer T2 are Each one is small in size, and the degree of freedom of arrangement location can be expanded on the mounting surface.

The effects of the configuration of the insulated switching power supply according to the fifth embodiment are the effects (a), (c), (d), (e), and (f) among the effects mentioned in the first embodiment. , (G), (h), (i), (j).
<< Sixth Embodiment >>
FIG. 7 is a circuit diagram of an isolated switching power supply device according to the sixth embodiment. A difference from the circuit shown in FIG. 6 is that the third diode Ds on the secondary side is replaced with a sixth capacitor Cs. In FIG. 6, when the first switching element Q1 is on and the second switching element Q2 is off, the third diode Ds is off, the first switching element Q1 is off, and the second switching element When Q2 is on, the third diode Ds is on.

  On the other hand, the circuit in FIG. 7 constitutes a so-called voltage doubler rectifier circuit. When the first switching element Q1 is on and the second switching element Q2 is off, the sixth capacitor Cs has When the charge is charged, the first switching element Q1 is off, and the second switching element Q2 is on, the first secondary winding ns outputs a voltage twice that of the embodiment in FIG. Is done. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Compared to the first embodiment, the sixth embodiment has no third diode Ds. Therefore, when the load current is large, the loss due to the forward voltage drop can be eliminated and the efficiency can be improved. There is an advantage.

In the sixth embodiment, the turn ratio between the first secondary winding ns and the second secondary winding no in the composite transformer T is
ns: no = 1: 1
It is preferable that In this case, when the voltage induced in the first secondary winding ns is Vo1, the voltage induced in the second secondary winding no is Vo2, and the voltage output to the load Ro is Vo, the first When the switching element Q1 is on and the second switching element Q2 is off, the output voltage Vo is
Vo = Vo2
Thus, when the first switching element Q1 is off and the second switching element Q2 is on, a voltage doubler rectifier circuit including the sixth capacitor Cs and the fourth diode Df is formed, and therefore the output voltage Vo Is
Vo = 2Vo1-Vo2 = 2Vo2-Vo2 = Vo2
Thus, the ripple voltage of the output voltage Vo can be eliminated, and the core of the composite transformer T can be most hardly magnetically saturated.

The effects of the configuration of the insulated switching power supply according to the sixth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (g), (h), (i), and (j).
<< Seventh Embodiment >>
FIG. 8 is a circuit diagram of an isolated switching power supply device according to the seventh embodiment. What is different from the circuit shown in FIG. 6 is the connection position of the third capacitor Cr. That is, in FIG. 8, the third capacitor Cr is connected between the first primary winding np and the second primary winding ni. Other configurations are the same as those shown in FIG.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply device according to the seventh embodiment are the effects (a), (b), (c), (d), (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Eighth Embodiment >>
FIG. 9 is a circuit diagram of an isolated switching power supply device according to the eighth embodiment. What is different from the circuit shown in FIG. 7 is the connection position of the first capacitor Cr. That is, in FIG. 9, the third capacitor Cr is connected between the connection point between the second inductor Lr and the fourth capacitor Ce and the second switch element S2. Other configurations are the same as those shown in FIG.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

  Since the eighth embodiment does not have the third diode Ds as compared with the first embodiment, when the load current is large, the loss due to the forward voltage drop can be eliminated and the efficiency can be improved. There is an advantage.

In the eighth embodiment, in particular, in the composite transformer T, the turns ratio of the first secondary winding ns and the second secondary winding no is
ns: no = 1: 1
It is preferable that The reason is the same as that shown in the sixth embodiment.

The effects of the configuration of the insulated switching power supply according to the eighth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Ninth embodiment >>
FIG. 10 is a circuit diagram of an isolated switching power supply device according to the ninth embodiment.

  In the insulated switching power supply device shown in FIG. 10, the second primary winding ni is omitted from the insulated switching power supply device shown in FIG. 10, which is the eighth embodiment, as in the fourth embodiment. The transformer T is driven by only one primary winding np. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the ninth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Tenth Embodiment >>
FIG. 11 is a circuit diagram of an isolated switching power supply device according to the tenth embodiment.

  The insulated switching power supply device shown in FIG. 11 has the first inductor Lri and the second primary winding of the composite transformer T with respect to the + side terminal and the − side terminal of the power input unit to which the DC voltage Vi is supplied. A series circuit composed of the line ni and the first switch circuit S1 is connected, the connection point between the first primary winding ni of the composite transformer T and the first switch circuit S1, and the negative side of the power input section A series circuit composed of the first primary winding np of the composite transformer T, the second inductor Lr, and the fourth capacitor Ce, and the second switch circuit S2 and the third capacitor Cr between the terminals. Are connected in parallel to each other. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the tenth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Eleventh Embodiment >>
FIG. 12 is a circuit diagram of an isolated switching power supply device according to the eleventh embodiment.

  The insulated switching power supply device shown in FIG. 12 omits the second primary winding ni from the insulated switching power supply device shown in FIG. 11 which is the tenth embodiment, as in the fourth embodiment. The transformer T is driven by only one primary winding np. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the eleventh embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Twelfth Embodiment >>
FIG. 13 is a circuit diagram of an isolated switching power supply device according to the twelfth embodiment. The insulated switching power supply device shown in FIG. 13 has a configuration in which the third capacitor Cr in the seventh embodiment shown in FIG. 8 is divided into a seventh capacitor Cr1 and an eighth capacitor Cr2. That is, the first inductor Lri, the second primary winding ni of the composite transformer T, and the first switch circuit S1 with respect to the + side terminal and the − side terminal of the power supply input unit to which the DC voltage Vi is supplied. Is connected between the connection point of the second primary winding ni of the composite transformer T and the first switch circuit S1 and the negative side terminal of the power input section. A series circuit including a first primary winding np of T, a second inductor Lr, a seventh capacitor Cr1, and a fourth capacitor Ce, and a connection point between the seventh capacitor Cr1 and the fourth capacitor Ce And the second switch element S2 is connected between the second primary winding ni and the connection point of the first switch element S1, and the connection between the second inductance Lr and the seventh capacitor Cr1. Between the point and the negative terminal of the power input section, 8 of the capacitor Cr2 is connected. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the twelfth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Thirteenth embodiment >>
FIG. 14 is a circuit diagram of an isolated switching power supply device according to the thirteenth embodiment.

  The isolated switching power supply device shown in FIG. 14 includes a third diode Ds and a fourth diode Df, a third switching element Q3, a fifth diode D3, and a ninth diode compared to the first embodiment. Third switch circuit S3 configured by a parallel connection circuit of capacitor C3, and fourth switch circuit configured by a parallel connection circuit of fourth switching element Q4, sixth diode D4, and tenth capacitor C4 The difference is that a synchronous rectifier circuit is configured by replacing S4. The third switch circuit S3 and the fourth switch circuit S4 are preferably composed of field effect transistors. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the thirteenth embodiment are as follows: (a), (b), (c), (d), (e) among the effects mentioned in the first embodiment. , (F), (g), (h), (i), and (j).
<< Fourteenth embodiment >>
FIG. 15 is a circuit diagram of an isolated switching power supply device according to the fourteenth embodiment.

  In the insulated switching power supply device shown in FIG. 15, the first secondary winding ns is composed of a third secondary winding ns1 and a fourth secondary winding ns2 in the first embodiment. However, the third and second diodes Ds and Df are different from each other in that a center tap type full-wave rectifier circuit is configured. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the fourteenth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (g), (h), (i), and (j).
<< 15th Embodiment >>
FIG. 16 is a circuit diagram of an isolated switching power supply device according to the fifteenth embodiment.

  The insulation type switching power supply device shown in FIG. 16 is the same as the insulation type switching power supply device shown in FIG. 10 which is the ninth embodiment in the primary side circuit. The winding no is composed of a fifth secondary winding no1 and a sixth secondary winding no2. Each of the fifth secondary winding no1 and the sixth secondary winding no2 has one end at the first end. 1 is connected to both ends of one secondary winding ns, and the other ends are connected to each other via a fourth inductor Lro1 and a fifth inductor Lro2, and are connected to one end of a load Ro.

  Further, both ends of the first secondary winding ns are connected via a fifth diode D1 and a sixth diode D6, respectively, and the connection point is connected to the other end of the load Ro.

  By such connection, the secondary side circuit constitutes a so-called current doubler (double current rectification) circuit. Since other points are the same as those in the first embodiment, description thereof will be omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

The effects of the configuration of the insulated switching power supply according to the fifteenth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).
<< Sixteenth Embodiment >>
FIG. 17 is a circuit diagram of an isolated switching power supply device according to the sixteenth embodiment.

  The insulation type switching power supply device shown in FIG. 17 is the same as the insulation type switching power supply device shown in FIG. 16 which is the fifteenth embodiment with respect to the secondary side circuit, and the other points are the first embodiment. Since it is the same as that, the description is omitted.

  Even if it is such a structure, there exists an effect similar to the case of 1st Embodiment.

  The effects of the configuration of the insulated switching power supply according to the sixteenth embodiment are the effects (a), (b), (c), (d), and (e) among the effects mentioned in the first embodiment. , (F), (h), (i), (j).

FIG. 11 is a circuit diagram of an isolated switching power supply device disclosed in Patent Document 1. 1 is a circuit diagram of an insulated switching power supply device according to a first embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 2nd embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 3rd embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 4th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 5th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 6th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 7th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning an 8th embodiment. FIG. 10 is a circuit diagram of an isolated switching power supply device according to a ninth embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 10th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning an 11th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 12th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 13th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 14th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 15th embodiment. It is a circuit diagram of the insulation type switching power supply device concerning a 16th embodiment. FIG. 2 is a waveform diagram of the isolated switching power supply device according to the first embodiment. 2 is a structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment. 6 is another structural example of a transformer used in the insulated switching power supply device according to the first embodiment.

Explanation of symbols

T-complex transformer T1-first transformer T2-second transformer np-first primary winding ni-secondary primary winding ns-first secondary winding no-second 2 Secondary winding ns1-third secondary winding ns2-fourth secondary winding no1-fifth secondary winding no2-sixth secondary winding Lri-first inductor Lr-second Inductor Lro-third inductor Lro1-fourth inductor Lro2-fifth inductor C1-first capacitor C2-second capacitor Cr-third capacitor Ce-fourth capacitor Co-fifth capacitor Cs -6th capacitor Cr1- 7th capacitor Cr2- 8th capacitor C3- 9th capacitor C4- 10th capacitor D1- 1st diode D2- 2nd diode Ds- 3rd diode Df- 4 diode D3-fifth diode D4-sixth diode D5-seventh diode D6-eighth diode Q1-first switching element Q2-second switching element Q3-third switching element Q4- 4th switching element S1- 1st switch circuit S2- 2nd switch circuit S3- 3rd switch circuit S4- 4th switch circuit Ro- load Vo- output voltage Vi- input voltage of power supply input part Da- Time ratio of switching element M-voltage conversion ratio Ton-on time of switching element Toff-off time of switching element Vcr-voltage across third capacitor VCe-voltage across fourth capacitor

Claims (22)

A DC power supply input unit to which a DC input voltage Vi is input;
A transformer T including a first primary winding np, a first secondary winding ns, and a second secondary winding no, which is composed of one magnetic component and is magnetically coupled; ,
A first inductor Lr connected in series to the first primary winding np;
A first rectifying element Ds that rectifies a sum of voltages generated in the first secondary winding ns and the second secondary winding no, and generated in the second secondary winding no. A rectifier circuit comprising a second rectifier element Df for rectifying the voltage;
A first switching circuit S1 including a parallel circuit of a first switching element Q1, a first capacitor C1, and a first diode D1,
A second switching circuit S2 composed of a parallel circuit of a second switching element Q2, a second capacitor C2, and a second diode D2,
A third capacitor Cr;
A first series circuit connected to both ends of the DC power supply input unit, wherein the first primary winding np and the first switch circuit S1 are connected in series;
A second switch circuit is connected to both ends of the first switch circuit S1 or both ends of the first primary winding np, and the second switch circuit S2 and the third capacitor Cr are connected in series. A series circuit,
The first switch circuit S1 and the second switch circuit S2 are insulated switching power supply devices configured to operate so as to repeat ON / OFF complementarily with a period in which both are OFF. And
The transformer T is synchronized with complementary ON / OFF operations of the first switch circuit S1 and the second switch circuit S2, and the first secondary winding ns or the second secondary winding. The wire no is complementarily wound so that energy transfer is performed from the primary side to the secondary side in a complementary manner,
In the first secondary winding ns and the second secondary winding no, the magnetic polarities of the windings are opposite to each other,
An isolated switching power supply device characterized in that an output voltage Vo is output to the secondary side via the second inductor Lro. A DC power supply input unit to which a DC input voltage Vi is input;
The first primary winding np, the first secondary winding ns, the second primary winding ni, and the second secondary winding no, which are composed of one magnetic component and are magnetically coupled. And a transformer T comprising:
A first inductance Lr connected in series to the first primary winding np;
A third inductor Lri connected in series to the second primary winding ni;
A second inductor Lro connected in series to the first secondary winding no;
A first rectifying element Ds that rectifies a sum of voltages generated in the first secondary winding ns and the second secondary winding no, and generated in the second secondary winding no. A rectifier circuit comprising a second rectifier element Df for rectifying the voltage, a first switching element Q1, a first capacitor C1, and a first switch circuit S1 comprising a parallel circuit of a first diode D1,
A second switching circuit S2 composed of a parallel circuit of a second switching element Q2, a second capacitor C2, and a second diode D2,
A third capacitor Cr;
A first series connected to both ends of the DC power supply input unit, wherein the first primary winding np or the second primary winding ni and the first switch circuit S1 are connected in series. Circuit,
The second switch circuit S2 and the third capacitor Cr are connected to both ends of the first switch circuit S1, or both ends of the first primary winding np or the second primary winding ni. A second series circuit connected in series;
A fourth capacitor Ce connected in parallel to the first series circuit,
The first switch circuit S1 and the second switch circuit S2 are insulated switching power supply devices configured to operate so as to repeat ON / OFF complementarily with a period in which both are OFF. And
The transformer T is synchronized with complementary ON / OFF operations of the first switch circuit S1 and the second switch circuit S2, and the first secondary winding ns or the second secondary winding. The wire no is complementarily wound so that energy transfer is performed from the primary side to the secondary side in a complementary manner,
In the first secondary winding ns and the second secondary winding no, the magnetic polarities of the windings are opposite to each other,
An isolated switching power supply device characterized in that an output voltage Vo is output to the secondary side via the second inductor Lro.   The transformer T includes a first transformer T1 composed of the first primary winding np and the first secondary winding ns, the second primary winding ni and the second secondary. 3. The insulated switching power supply device according to claim 2, comprising a second transformer T2 composed of a winding no.   The insulated switching power supply device according to claim 1, wherein a primary leakage magnetic flux of the transformer T is used as the first inductor Lr.   The insulated switching power supply device according to any one of claims 1 to 4, wherein a secondary leakage magnetic flux of the transformer T is used as the second inductor Lro.   6. The insulated switching power supply device according to claim 2, wherein a primary leakage magnetic flux of the transformer T is used as the third inductor Lri.   In the transformer T, the first primary winding np or the second primary winding ni is arranged in a direction to cancel the DC magnetic flux generated in the common magnetic core due to the current flowing through the second secondary winding no. The first secondary winding ns has a magnetic polarity opposite to that of the second secondary winding no, and the number of turns is larger than the number of turns of the second secondary winding no. The insulation type switching power supply device according to any one of claims 2 to 6.   The first primary winding np and the second primary winding with respect to the direction of the current that flows when the first switch circuit S1 is conductive or the second switch circuit S2 is conductive. The insulated type according to claim 7, wherein the line ni has the same magnetic polarity, and the first secondary winding ns and the second secondary winding no have opposite magnetic polarities. Switching power supply.   9. The insulated switching power supply device according to claim 8, wherein the first transformer T1 has a magnetic coupling degree smaller than that of the second transformer T2.   10. The insulated switching power supply device according to claim 1, wherein the first switch circuit S1 or the second switch circuit S2 is a field effect transistor.   The first switch circuit S1 or the second switch circuit S2 is driven by a zero voltage switching operation in which the switching element is turned on after the voltage across the switch circuit is reduced to 0V or near 0V. The insulated switching power supply device according to claim 10, wherein:   The rectifier circuit includes a third diode that rectifies a current flowing through the first secondary winding ns during a period in which energy transfer is performed from the primary side to the secondary side by the first secondary winding ns. Ds and a fourth diode Df for rectifying a current flowing through the second secondary winding no in a period in which energy transfer is performed from the primary side to the secondary side by the second secondary winding no The insulated switching power supply device according to any one of claims 1 to 11, wherein   13. The isolated switching power supply device according to claim 12, wherein the third diode Ds or the fourth diode Df is configured by a synchronous rectifier circuit in which a field effect transistor is replaced. A turns ratio between the number of turns of the first secondary winding ns and the number of turns of the second secondary winding no.
ns: no = 2: 1
The insulated switching power supply device according to claim 1, wherein:   In the transformer T, the magnetic coupling degree between at least the first primary winding np and the first secondary winding ns is relatively large, and the second secondary winding no and other windings The insulated switching power supply device according to claim 1, wherein the degree of magnetic coupling with the wire is relatively small.   The first primary winding np and the first secondary winding ns are composed of laminated windings, and the first secondary winding ns and the second secondary winding no, or the first secondary winding ns The insulated switching power supply device according to claim 1, wherein at least one of the primary winding np and the second secondary winding no is configured by split winding.   The transformer T has a plurality of leg cores, and the first primary winding np and the first secondary winding ns are wound around the same leg core, and at least the second secondary winding The insulated switching power supply device according to any one of claims 1 to 16, wherein the winding no is wound around another leg core.   The first primary winding np and the first secondary winding ns are composed of laminated windings, and the first secondary winding ns and the second secondary winding no, or the first secondary winding ns 18. The insulated switching power supply device according to claim 17, wherein at least one of the primary winding np and the second secondary winding no is configured by split winding.   19. The isolated switching according to claim 1, wherein the first switch circuit S <b> 1 and the second switch circuit S <b> 2 are controlled to stabilize the output voltage Vo by PWM control. Power supply.   20. The insulation type according to claim 1, wherein the third capacitor Cr is connected between the first primary winding ni and the first switch circuit S1. Switching power supply. When one of the first switch circuit S1 and the second switch circuit S2 has a time ratio (= on time / switching cycle) as Da,
0 ≦ Da ≦ 0.5
Drive only in the range of
0.5 ≦ Da ≦ 1
21. The insulated switching power supply device according to claim 20, wherein the switching type power supply device is driven only within the range. The voltage conversion rate represented by the ratio of the output voltage Vo to the input voltage Vi of the power supply input unit is M (= Vo / Vi), and the first primary winding np and the first secondary winding When the turn ratio of ns is n (= np / ns),
M = D (1-D) / n
The insulated switching power supply device according to claim 21, wherein

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