JP2005311970A - High-frequency transmitting-receiving device and radar apparatus provided with it, radar apparatus mounting vehivle, and radar apparatus mounting small ship - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To increase an on/off ratio of a transmission output of a high-frequency transmitting-receiving device by a simple constitution. <P>SOLUTION: The transmitting-receiving device sets a line length between a branch device 2 and a pulse modulator 3 or the line length between the branch device 2 at a mixer 6 side and the pulse modulator 3 to be δ=(2N+1)π when a millimeter-wave signal to transmit the pulse modulator 3 in an off state is regarded as Wa<SB>2</SB>, the millimeter-wave signal to transmit to an output end 3b of the pulse modulator 3 from other output end 2c of the branch device 2 through the mixer 6 and a circulator 4 and to reflect at the output end 3b of the pulse modulator 3 is regarded as Wb<SB>2</SB>, and a phase difference in a central frequency of these Wa<SB>2</SB>and Wb<SB>2</SB>is regarded as δ. <P>COPYRIGHT: (C)2006,JPO&NCIPI

Description

  The present invention relates to a high-frequency transmitter / receiver used in a millimeter-wave radar module, a millimeter-wave wireless communication device, or the like as a radar device mounted on a vehicle or a small ship, for example, and transmits when the modulator is in an off state. The present invention relates to a high-frequency transmitter / receiver in which a part of a trusted high-frequency signal is transmitted as an unnecessary signal, and an adverse effect on the transmission / reception of the high-frequency signal is suppressed.

  The present invention also relates to a radar device including the high-frequency transmitter / receiver, a radar device-equipped vehicle including the radar device, and a radar device-equipped small vessel.

  Conventionally, for example, a pulse modulation method disclosed in Patent Document 1 has been proposed as a method of a high-frequency transceiver that is expected to be applied to a millimeter-wave radar module, a millimeter-wave wireless communication device, or the like.

  As shown in the schematic block circuit diagram of FIG. 10, the conventional high-frequency transmitter / receiver of this pulse modulation system is connected to, for example, a high-frequency oscillator 61 that generates a high-frequency signal and an output end side of the high-frequency oscillator 61. A branching device 62 that branches the high-frequency signal and outputs it to one output end 62b and the other output end 62c, and a part of the high-frequency signal connected to one output end 62b side of the branching device 62. It has a pulse modulator 63 that performs pulse modulation and outputs it as a high-frequency signal for transmission, and first, second, and third terminals 64a, 64b, and 64c. The first terminal is connected to the output terminal 63a of the pulse modulator 63. A circulator 64 to which the high frequency signal input from the first terminal 64a is connected to the second terminal 64b, and the high frequency signal input from the second terminal 64b is output to the third terminal 64c. , Connected to the second terminal 64b of the circulator 64 As the local signal LO output to the other output terminal 62c of the branching device 62 connected between the transmission / reception antenna 65 and the other output terminal 62c of the branching device 62 and the third terminal 64c of the circulator 64. The mixer 66 is configured to mix the high frequency signal and the high frequency signal RF received by the transmission / reception antenna 65 to output an intermediate frequency signal.

  In addition, examples of conventional high-frequency transceivers adopting such a pulse modulation method include those disclosed in Patent Documents 2 to 4.

An example of a conventional radar device and a vehicle equipped with the radar device is disclosed in Patent Document 5, for example.
JP 2000-258525 A JP-A-11-183613 JP 2000-171556 A JP 2001-74829 A JP 2003-35768 A

  However, in all the configurations disclosed in Patent Documents 1 to 4, as shown in FIG. 10, after a part of the local signal LO is reflected by the mixer 66, the third terminal 64 c of the circulator 64 is used. Leaked from the first terminal 64a to the first terminal 64a, and the leaked high-frequency signal is totally reflected by the pulse modulator 63 in the off state and transmitted from the transmission / reception antenna 65 as an unnecessary high-frequency signal. The on / off ratio, which is the ratio of the intensity of each transmitting high-frequency signal transmitted from the transmission / reception antenna 65, when the 63 is in the on state and the off state decreases, and transmission / reception performance deteriorates. was there. That is, when such an unnecessary high-frequency signal is transmitted, the unnecessary high-frequency signal is mixed into the high-frequency signal RF that should be received, and a part of the high-frequency signal RF that should be received cannot be received correctly. There was a problem.

  In a radar apparatus using such a high-frequency transmitter / receiver, a low-frequency high-frequency signal reflected by a far object to be detected is converted to a high-frequency signal that is noise that is transmitted when the pulse modulator 63 is in an off state. Due to being buried, there is a problem that the detection range is narrow, or detection of a detection target object may be delayed because erroneous detection is likely to occur.

  Further, in vehicles and small ships equipped with such a radar device, it is performed to detect an object to be detected by the radar device and take appropriate behavior such as avoidance and braking based on the information, Since the detection of the object to be detected is delayed, there is a problem that the vehicle or the small ship may be caused to suddenly behave after the detection.

  The present invention has been devised to solve the above-described problems that are desired to be improved in the prior art. The object of the present invention is to provide a high-frequency signal for transmission when the pulse modulator is in an off state with a simple configuration. To provide a high-performance high-frequency transmitter / receiver capable of improving transmission / reception performance by suppressing a part of a signal from being transmitted as an unnecessary signal and increasing an on / off ratio of a transmission output. is there.

  Another object of the present invention is to provide a radar apparatus equipped with such a high-performance high-frequency transmitter / receiver, a radar apparatus-equipped vehicle equipped with the radar apparatus, and a radar apparatus-equipped small ship.

  The present inventors have found that such a problem is likely to occur because the isolation between the two input terminals of the mixer tends to be usually smaller than the isolation of the modulator in the off state. It was. Even if the modulator and the mixer are characteristic in this way, the line length between the branching device and the modulator or between the branching device on the mixer side and the modulator or the branching ratio of the branching device should be set appropriately. It was found that such a problem can be solved easily. The reason why the isolation between the two input terminals of the mixer tends to be as described above is that the isolation between the two input terminals of the mixer depends on operating conditions such as a bias current flowing through the mixer. This is because the isolation characteristic between the two input terminals of the mixer is not necessarily the best under the operation condition of the mixer in which the reception characteristic of the mixer is the best.

A first high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, and a branching device that is connected to the high-frequency oscillator and branches the high-frequency signal and outputs it to one output end and the other output end. A modulator connected to the one output end and modulating a high-frequency signal branched to the one output end and outputting a transmission high-frequency signal; a first terminal around the magnetic body; A circulator in which the output of the modulator is input to the first terminal, and a high-frequency signal input from one terminal in this order is output from an adjacent next terminal. The transmitting / receiving antenna connected to the second terminal of the circulator and the other output terminal connected between the other output terminal of the branching device and the third terminal of the circulator are branched. High frequency signal A mixer that mixes a high-frequency signal received by the transmission / reception antenna and outputs an intermediate frequency signal; a line length between the branching device and the modulator or the branching device on the mixer side; The line length between the modulator and the high-frequency signal that passes through the modulator in the off state is Wa ₂ , and the output of the modulator passes through the mixer and the circulator from the other output end of the branching unit. transmitted to the end, a high-frequency signal reflected by the output of said modulator and Wb _2, the phase difference at the center frequency of these Wa ₂ and Wb ₂ is taken as δ, δ = (2N + 1 ) · π ( However, N is an integer.).

A second high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, and a branching device that is connected to the high-frequency oscillator and branches the high-frequency signal and outputs it to one output end and the other output end. A modulator connected to the one output end and modulating a high-frequency signal branched to the one output end and outputting a transmission high-frequency signal; a first terminal around the magnetic body; A circulator in which the output of the modulator is input to the first terminal, and a high-frequency signal input from one terminal in this order is output from an adjacent next terminal. The transmitting / receiving antenna connected to the second terminal of the circulator and the other output terminal connected between the other output terminal of the branching device and the third terminal of the circulator are branched. High frequency signal Has and a mixer for outputting the intermediate frequency signal by mixing the radio frequency signal received by the transmitting and receiving antenna, a high frequency signal to be output to the one output end of the divider Wa _1, the intensity Pa ₁ , the high-frequency signal output to the other output terminal of the branching unit is Wb ₁ , the intensity is Pb _1, and the branching ratio of the branching unit is R = Pb ₁ / Pa ₁ (where R is 0 or more) It is a real number), and the branching ratio R of the branching device is set to R <1.

The second high-frequency transmitter / receiver of the present invention, in the above-described configuration, has a transmission coefficient of a high-frequency signal that passes through the modulator in the off state as A ₁ and a high-frequency signal that passes between two input terminals of the mixer. B _{1 is} the transmission coefficient, B _{2 is} the transmission coefficient of the high-frequency signal transmitted between the third terminal and the first terminal of the circulator, and the reflection coefficient of the high-frequency signal is reflected at the output end of the modulator. the when the _{B 3,} is characterized in that setting the branching ratio R so that _{R = a 1 / (B 1} · B 2 · B 3).

The second high-frequency transmitter / receiver according to the present invention includes a line length between the one output terminal of the branching device and the modulator or the other output terminal of the branching device and the mixer in each of the above configurations. And the length of the line between the modulator that has passed through the circulator, the high-frequency signal that passes through the modulator in the off state, Wa ₂ , and the mixer and the circulator from the other output end of the branching device. transmitted to the output terminal of the modulator Te, the high-frequency signal reflected by the output of the modulator and Wb _2, when the phase difference was [delta] at the center frequency of these Wa ₂ and Wb _2, [delta] = (2N + 1) · π (where N is an integer).

  A third high-frequency transmitter / receiver according to the present invention has a first terminal, a second terminal, and a third terminal around a magnetic body, and adjacently receives a high-frequency signal input from one terminal in this order. First and second circulators that output from the first terminal, a high-frequency oscillator that generates a high-frequency signal connected to the first terminal of the first circulator, and the second terminal of the first circulator; The high-frequency signal connected to the first terminal of the second circulator is transmitted to the second circulator side for transmission according to a pulse signal or reflected to the first circulator side. A transmitting / receiving antenna connected to the second terminal of the second circulator, the third terminal of the first circulator, and the second circulator The high-frequency signal that is reflected by the modulator and input from the third terminal of the first circulator and received by the transmission / reception antenna and connected to the terminal of the second circulator A mixer that mixes a high-frequency signal input from the third terminal and outputs an intermediate-frequency signal, Wa is the high-frequency signal that passes through the modulator in the off state, and the first circulator A high-frequency signal transmitted from the third terminal to the output end of the modulator through the mixer and the second circulator and reflected from the output end of the modulator is defined as Wb, and Wa and Wb Is set such that δ = (2N + 1) · π (where N is an integer), where δ is the phase difference at the center frequency.

  The third high-frequency transmitter / receiver of the present invention is characterized in that, in the above configuration, an attenuator or a variable attenuator is provided between the first circulator and the mixer.

  A radar apparatus according to the present invention processes any one of the first, second, and third high-frequency transmitters / receivers of the present invention having the above-described configuration, and processes the intermediate frequency signal output from the high-frequency transmitter / receiver to detect the object. And a distance information detector for detecting distance information up to.

  The radar device-equipped vehicle of the present invention includes the radar device of the present invention having the above-described configuration, and is characterized in that this radar device is used for detection of an object to be detected.

  A small ship equipped with a radar apparatus according to the present invention includes the radar apparatus according to the present invention having the above-described configuration, and is characterized in that this radar apparatus is used for detection of a detection target.

According to the first high-frequency transceiver of the present invention, a high-frequency oscillator that generates a high-frequency signal and the high-frequency signal connected to the high-frequency oscillator are branched and output to one output end and the other output end. A branching device, a modulator connected to the one output end, modulating a high-frequency signal branched to the one output end, and outputting a high-frequency signal for transmission; a first terminal around the magnetic body; A circulator having a second terminal and a third terminal and outputting a high-frequency signal inputted from one terminal in this order from an adjacent next terminal, wherein the output of the modulator is inputted to the first terminal A transmitting / receiving antenna connected to the second terminal of the circulator, and the other output terminal connected between the other output terminal of the branching device and the third terminal of the circulator. Branched high lap A mixer that mixes a signal and a high-frequency signal received by the transmission / reception antenna and outputs an intermediate frequency signal, a line length between the branching device and the modulator, or the branching device on the mixer side The high-frequency signal that passes through the modulator in the off state is Wa ₂ , the line length between the modulator and the modulator is Wa ₂ , the other output end of the branching unit is passed through the mixer and the circulator, and the modulator transmitted to the output terminal, a high-frequency signal reflected by the output of said modulator and Wb _2, when the phase difference was [delta] at the center frequency of these Wa ₂ and _{Wb 2, δ = (2N +} 1) · [pi (however, N is the integers.) since the set such that, are multiplexed by these Wa ₂ and Wb ₂ and antiphase between the output terminal and the circulator of the modulator, hit each other High-performance high-frequency that can improve transmission and reception performance by suppressing the transmission of a part of the high-frequency signal for transmission as an unnecessary signal when the modulator is in the off state because it attenuates effectively It becomes a transceiver.

According to the second high-frequency transceiver of the present invention, a high-frequency oscillator that generates a high-frequency signal and the high-frequency signal connected to the high-frequency oscillator are branched and output to one output end and the other output end. A branching device, a modulator connected to the one output end, modulating a high-frequency signal branched to the one output end, and outputting a high-frequency signal for transmission; a first terminal around the magnetic body; A circulator having a second terminal and a third terminal and outputting a high-frequency signal inputted from one terminal in this order from an adjacent next terminal, wherein the output of the modulator is inputted to the first terminal A transmitting / receiving antenna connected to the second terminal of the circulator, and the other output terminal connected between the other output terminal of the branching device and the third terminal of the circulator. Branched high lap Signal has and a mixer for outputting the intermediate frequency signal by mixing the radio frequency signal received by the receiving antenna, Wa 1 a high-frequency signal to be output to the one output end of the _divider, the intensity Is Pa ₁ , the high-frequency signal output to the other output terminal of the branching unit is Wb ₁ , its intensity is Pb _1, and the branching ratio of the branching unit is R = Pb ₁ / Pa ₁ (where R is 0) Since the branching ratio R of the branching device is set to R <1, the isolation between the two input terminals of the mixer becomes the isolation of the modulator in the off state. Even if it is smaller, the branching unit outputs a high-frequency signal with a smaller intensity to the other output end side than the one output end side, and passes through the mixer and circulator to the output end of the modulator. The In order to make it small, the intensity of the high-frequency signal reflected from the mixer side through the circulator and reflected at the output end of the modulator can be reduced. Further, since the strength of the high-frequency signal can be made close to the strength of the high-frequency signal transmitted through the modulator in the off state, these high-frequency signals can be interfered with each other and attenuated. Since it operates in this way, it has a simple configuration and can improve the transmission / reception performance by suppressing the transmission of a part of the high-frequency signal for transmission as an unnecessary signal when the modulator is in the off state. It becomes a high frequency transceiver.

Further, according to the second high-frequency transceiver of the present invention, the transmission coefficient of the high-frequency signal transmitted through the modulator in the off state is A ₁ , and the transmission coefficient of the high-frequency signal transmitted between the two input terminals of the mixer B ₁ , B _{2 is} the transmission coefficient of the high-frequency signal transmitted between the third terminal and the first terminal of the circulator, and B is the reflection coefficient of the high-frequency signal reflected at the output end of the modulator. _{when 3} was, the branching ratio R when set to be _{R = a 1 / (B 1} · B 2 · B 3) high-frequency signal reflected at the output of the modulator from the mixer side through the circulator And the intensity of the high-frequency signal transmitted through the modulator in the off state can be made substantially the same, so that these high-frequency signals can be effectively interfered with each other to attenuate each other. Off In this state, the transmission / reception performance can be improved by further suppressing transmission of a part of the transmission high-frequency signal as an unnecessary signal.

According to the second high-frequency transmitter / receiver of the present invention, a line length between the one output end of the branching device and the modulator, or the other output end of the branching device, the mixer, and the circulator. The line length between the modulator and the modulator that has passed through is Wa ₂ , the high-frequency signal that passes through the modulator in the off state, Wa ₂ , and the modulation from the other output end of the splitter through the mixer and the circulator transmitted to the output end of the vessel, a high-frequency signal reflected by the output of said modulator and Wb _2, when the phase difference was [delta] at the center frequency of these Wa ₂ and _{Wb 2, δ = (2N +} 1 ) · Π (where N is an integer), Wa ₂ and Wb ₂ are combined in opposite phases between the output end of the modulator and the circulator. Since it is most effectively attenuated by canceling out, it is possible to further effectively prevent a part of the high-frequency signal for transmission from being transmitted as an unnecessary signal when the modulator is in the off state, thereby improving transmission / reception performance. It becomes a high-performance high-frequency transceiver that can

  According to the third high-frequency transceiver of the present invention, the first terminal, the second terminal, and the third terminal are provided around the magnetic body, and the high-frequency signals input from one terminal in this order are adjacent to each other. First and second circulators that output from other terminals, a high-frequency oscillator that generates a high-frequency signal connected to the first terminal of the first circulator, and the second circulator of the first circulator The high-frequency signal connected between the terminal and the first terminal of the second circulator is transmitted for transmission to the second circulator side in response to a pulse signal, or the first circulator side A modulator that reflects to the second circulator, a transmission / reception antenna connected to the second terminal of the second circulator, the third terminal of the first circulator, and the second circulator The second high frequency signal connected between the third terminal and reflected by the modulator and input from the third terminal of the first circulator is received by the transmission / reception antenna and received by the second antenna. A mixer that mixes a high-frequency signal input from the third terminal of the circulator and outputs an intermediate-frequency signal, wherein Wa is the high-frequency signal that passes through the modulator in the off state, and A high-frequency signal transmitted from the third terminal of the circulator to the output end of the modulator through the mixer and the second circulator and reflected at the output end of the modulator is defined as Wb. Since δ = (2N + 1) · π (where N is an integer), where δ is the phase difference at the center frequency with respect to Wb, the output terminal of the modulator These Wa and Wb are combined in antiphase with the second circulator, and these Wa and Wb cancel each other and effectively attenuate, so that when the modulator is in the OFF state, Transmission / reception performance can be improved by suppressing transmission of a part of the signal as an unnecessary signal. Further, since the first circulator and the modulator work together so that the local signal is not input to the mixer while the modulator outputs the transmission high-frequency signal, one of the transmission high-frequency signals is output. Even if the part leaks from the first terminal of the second circulator to the third terminal due to insufficient isolation of the second circulator, the mixer outputs almost no intermediate frequency signal corresponding to the leaked high frequency signal Thus, the reception performance can be increased. As described above, in addition to the improvement of the transmission system, the reception system is also improved and becomes a high-performance high-frequency transceiver.

  According to the third high-frequency transceiver of the present invention, when an attenuator or a variable attenuator is provided between the first circulator and the mixer, the isolation between the two input terminals of the mixer is turned off. In order to reduce the intensity of the high frequency signal that the attenuator or variable attenuator passes through the mixer and the second circulator to the output end of the modulator, even if it is smaller than the isolation of the modulator in the state, The intensity of the high-frequency signal reflected from the mixer side through the second circulator and reflected at the output end of the modulator can be reduced. Moreover, since the intensity of the high-frequency signal can be brought close to that of the high-frequency signal transmitted through the modulator in the off state, these high-frequency signals are more effectively caused to interfere with each other in the opposite phase and attenuate each other. be able to. Since it operates in this way, a high-performance high-frequency transmitter / receiver that can further suppress the transmission of a part of the high-frequency signal for transmission as an unnecessary signal when the modulator is in an off state and improve the transmission / reception performance. It becomes.

  As described above, according to the high frequency transmitter / receiver of the present invention, it is possible to suppress a part of the transmission high frequency signal from being transmitted as an unnecessary signal when the modulator is in the off state by the above-described configurations. Thus, the transmission / reception performance can be increased with a simple configuration, and therefore the on / off ratio of the transmission output can be increased.

  Further, according to the radar apparatus of the present invention, the first, second and third high frequency transmitter / receiver of the present invention having the above-described configuration and the intermediate frequency signal output from the high frequency transmitter / receiver are processed. And a distance information detector for detecting distance information to the detection target, so that the high-frequency transmitter / receiver transmits a good high-frequency signal with a high on / off ratio of the transmission output. And a radar apparatus capable of reliably detecting a detection object at a short distance or a long distance.

  Further, according to the vehicle equipped with the radar apparatus of the present invention, the radar apparatus of the present invention having the above-described configuration is provided, and this radar apparatus is used for detection of the detection object. Vehicle, obstacles, etc. can be detected, for example, without causing the vehicle to take a sudden action to avoid them, appropriate control of the vehicle and appropriate warning to the driver can be made The vehicle is equipped with a radar device.

  Further, according to the small ship equipped with the radar device of the present invention, the radar device of the present invention having the above-described configuration is provided, and the radar device is used for detection of the detection object. Since other small vessel obstacles can be detected, for example, appropriate control of small vessels and appropriate warnings to the operator are made without causing the small vessels to take a sudden action to avoid them. It becomes a small ship equipped with a radar device.

  First, the first, second, and third high-frequency transceivers of the present invention will be described in detail below with reference to the drawings, taking as an example a high-frequency transceiver that transmits and receives millimeter-wave band high-frequency signals.

  FIG. 1 and FIG. 2 are a schematic block circuit diagram and a plan view, respectively, showing an example of an embodiment of a first high-frequency transceiver according to the present invention. FIG. 3 is a schematic block circuit diagram showing an example of an embodiment of the second high-frequency transceiver of the present invention. FIGS. 4 and 5 are a schematic block circuit diagram and a plan view, respectively, showing an example of an embodiment of the third high-frequency transceiver according to the present invention.

  1 to 5, 1 is a millimeter wave oscillator as a high frequency oscillator, 2 is a branching device, 2 'is a first circulator, 3 is a pulse modulator as a modulator, and 4 is a circulator (FIGS. 4 and 5). (Second circulator in the example of the embodiment of the third high-frequency transmitter / receiver of the present invention) Output terminal, 3a is an input terminal, 3b is an output terminal, 2'a and 4a are first terminals, 2'b and 4b are second terminals, 2'c and 4c are third terminals, and 11 is a flat conductor. 14, 15 are ferrite plates, 16, 46 are first dielectric lines, 17, 47 are second dielectric lines, 18, 48 are third dielectric lines, and 19, 49 are fourth dielectric bodies. Lines 20 and 50 are fifth dielectric lines, 21 and 51 are sixth dielectric lines, 22 is a non-reflective terminator, 14a and 15a are first connection parts, 14 15b is a second connection portion, 14c and 15c are third connection portions, 30 is a substrate used for the non-radiative dielectric line type pulse modulator 3 or mixer 6, and 31 is formed on the surface of the substrate 30. A choke-type bias supply line, 32 is a connection terminal formed at an interrupted part of the choke-type bias supply line 31, 33 is a diode as a high-frequency modulation element, and 34 is a diode as a high-frequency detection element.

In the block circuit diagram shown in FIG. 4, I ₁ is one input terminal of the mixer 6, which is an input terminal for inputting the millimeter wave signal RF_S received by the transmission / reception antenna 5 (input on the RF side of the mixer 6). I ₂ is the other input terminal of the mixer 6, and is an input terminal for inputting the local signal LO (input terminal on the local side of the mixer 6). Here, the local signal LO is a millimeter wave signal that is output from the millimeter wave oscillator 1 and input to the mixer 6 inside the millimeter wave radar. The input terminal I ₁ side is the RF side, and the input terminal I ₂ side is the local (LO) side.

In the block circuit diagram shown in FIG. 4, RF_N is an unnecessary millimeter in which a part of the millimeter wave signal for transmission pulsed by the pulse modulator 3 is pulsed to one input terminal I ₁ side of the mixer 6. The millimeter wave signal when leaking as a wave signal is shown. RF_S is a millimeter wave signal to be received that is received by the transmission / reception antenna 5 or the reception antenna 10 and input to _one input terminal I ₁ of the mixer 6. Show.

LO represents a millimeter wave signal as a local signal output from the millimeter wave oscillator 1 and transmitted through the first circulator 2 ′ and input to the other input terminal I ₂ of the mixer 6.

IF_OUT is an intermediate frequency signal output from the output terminal of the mixer 6, and the millimeter wave signals (millimeter wave signals RF_S and RF_N) input to the input terminal I ₁ of the mixer 6 and the local input of the mixer 6. An intermediate frequency signal output from the output terminal of the mixer 6 by mixing the millimeter wave signal (local signal LO) input to the terminal I ₂ is shown.

An example of an embodiment of a first high-frequency transceiver according to the present invention includes a millimeter-wave oscillator 1 that generates a millimeter-wave signal and a millimeter-wave oscillator 1 connected to the millimeter-wave oscillator 1, as shown in a block circuit diagram of FIG. A branching device 2 that branches a millimeter wave signal and outputs it to one output end 2b and the other output end 2c, and a millimeter wave signal that is connected to one output end 2b and branched to this one output end 2b. And a first modulator 4a, a second terminal 4b, and a third terminal 4c around the magnetic body, in this order from one terminal to the other. The circulator 4 that outputs the input millimeter wave signal from the next adjacent terminal, the output of the pulse modulator 3 being input to the first terminal 4a, and the transmission / reception connected to the second terminal 4b of the circulator 4 Antenna 5 and other output terminal 2c of branching device 2 A mixer connected between the third terminal 4c of the circulator 4 and mixing the millimeter wave signal branched to the other output end 2c and the millimeter wave signal received by the transmission / reception antenna 5 to output an intermediate frequency signal. 6, and the line length between the branching device 2 and the pulse modulator 3 or the line length between the branching device 2 on the mixer 6 side and the pulse modulator 3 is turned off. 3 millimeter wave signal transmitted through the Wa _2, through the mixer 6 and the circulator 4 from the other output terminal 2c of the branching device 2 transmits to the output end 3b of the pulse modulator 3, at the output 3b of the pulse modulator 3 When the reflected millimeter wave signal is Wb ₂ and the phase difference at the center frequency between these Wa ₂ and Wb ₂ is δ, δ = (2N + 1) · π (where N is an integer). It is the configuration set to.

  The first high-frequency transmitter / receiver of the present invention shown in FIG. 1 is also referred to as a non-radiative dielectric line (hereinafter referred to as an NRD guide) as a high-frequency transmission line for connecting the above components. ) Is used. As shown in a partially broken perspective view in FIG. 6, the basic configuration of this non-radiative dielectric line is a dielectric having a rectangular cross section between flat conductors 11 and 12 arranged in parallel with a predetermined interval a. The line 13 is arranged such that the interval a is a ≦ λ / 2 with respect to the wavelength λ of the millimeter wave signal. This eliminates the intrusion of noise from the outside into the dielectric line 13 and eliminates the radiation of the millimeter wave signal to the outside, so that the millimeter wave signal can be propagated through the dielectric line 13 with almost no loss. The wavelength λ is the wavelength of the millimeter wave signal in the air (free space) at the operating frequency.

That is, the first high-frequency transmitter / receiver of the present invention shown in FIG. 1 is specifically arranged in parallel at an interval of 1/2 or less of the wavelength of the millimeter wave signal, as shown in a plan view in FIG. One end of the first dielectric line 16 is connected between the flat plate conductors 11 (the other flat plate conductor is not shown), and the millimeter wave signal output from the high frequency diode is frequency-modulated and the millimeter wave signal The millimeter wave oscillator 1 that propagates and outputs the first dielectric line 16 and the millimeter wave signal connected to the other end of the first dielectric line 16 to the input end 3a side according to the pulse signal. The pulse modulator 3 that reflects or transmits to the output end 3 b side, the second dielectric line 17 having one end connected to the output end 3 b of the pulse modulator 3, and the plate conductor 11 are arranged in parallel. On the periphery of the ferrite plate 15 are input / output terminals for millimeter wave signals. A first terminal 15a has a first terminal 15a, a second terminal 15b, and a third terminal 15c, and outputs a millimeter wave signal input from one terminal in this order from an adjacent next terminal. The circulator 4 connected to the other end of the second dielectric line 17 and the peripheral ends of the ferrite plate 15 of the circulator 4 are arranged radially, and one end of each of the second terminal 15b and the third terminal 15c has one end. The third dielectric line 18 and the fourth dielectric line 19 connected, the transmitting and receiving antenna 5 connected to the other end of the third dielectric line 18, and the middle of the first dielectric line 16 A fifth dielectric line 20 that branches and propagates a part of the millimeter-wave signal that propagates through the first dielectric line 16 that is close to or joined to the first dielectric line 16, and the millimeter-wave oscillator 1 of the fifth dielectric line 20 Non-reflective terminator 22 connected to one end of the side, the other end of the fourth dielectric line 19 and the The millimeter wave signal input from the fifth dielectric line 20 connected to the other end of the dielectric line 20 and the millimeter wave signal input from the circulator 4 received by the transmission / reception antenna 5 are mixed. And a mixer 6 for outputting an intermediate frequency signal, and a portion where the first dielectric line 16 and the fifth dielectric line 20 are close to each other or joined together (this part constitutes the branching device 2). To the other end of the first dielectric line 16 (corresponding to the line length between the branching device 2 and the pulse modulator 3) or the first dielectric line 16 and the fifth The line length from the part where the dielectric line 20 is adjacent or joined to the other end of the fifth dielectric line 20, the line length of the fourth dielectric line 19, and the line length of the second dielectric line 17 (Corresponding to the line length between the branching device 2 on the mixer 6 side and the pulse modulator 3). ) Is a millimeter wave signal that passes through the pulse modulator 3 in the off state Wa ₂ , and the fifth dielectric in a portion where the first dielectric line 16 and the fifth dielectric line 20 are close to or joined to each other. mixer 6 from line 20 through the fourth dielectric line 19 and the circulator 4 transmits the output terminal 3b of the pulse modulator 3, a millimeter-wave signal reflected at the output end 3b of the pulse modulator 3 and Wb _2, When the phase difference at the center frequency between Wa ₂ and Wb ₂ is δ, δ = (2N + 1) · π is set. As described above, the first dielectric line 16 and the fifth dielectric line 20 constitute the branching device 2 in the proximity portion or the junction portion thereof.

  In FIG. 2, the first terminal 15a, the second terminal 15b, and the third terminal 15c correspond to the first terminal 4a, the second terminal 4b, and the third terminal 4c in FIG. 1, respectively. Yes.

  In this configuration, as shown in a perspective view in FIG. 7, the pulse modulator 3 performs high-frequency modulation on the connection terminal 32 formed at an interrupted portion of the choke-type bias supply line 31 formed on the surface of the substrate 30. A pulse modulation unit connected with a diode 33 as an element is connected between the first dielectric line 16 and the second dielectric line 17 and a millimeter wave signal output from the first dielectric line 16 is a diode. It is inserted so that it is incident on 33. In this configuration, a PIN diode may be used as the diode 33 as the high frequency modulation element.

  Note that such a transmission type pulse modulator is suitable for the pulse modulator 3 in the high-frequency transceiver of the present invention. Further, instead of the transmission type pulse modulator, a switch such as a semiconductor switch or a MEMS (Micro Electro Mechanical System) switch that can transmit or reflect a high-frequency signal may be used.

  Further, as shown in a perspective view in FIG. 8, the mixer 6 performs high-frequency detection on a connection terminal 32 formed at an interrupted portion of the choke-type bias supply line 31 formed on the surface of each of the two substrates 30. A millimeter wave detection unit connected with a diode 34 as an element is connected to each of the fourth dielectric line 19 and the fifth dielectric line 20, and the fourth dielectric line 19 and the fifth dielectric line 20. The fourth dielectric line is connected so that the millimeter wave signals output from the respective diodes 34 are incident on each diode 34 and the fourth dielectric line 19 and the fifth dielectric line 20 are electromagnetically coupled. The middle of 19 and the middle of the fifth dielectric line 20 are brought close to each other or joined together. In this configuration, a Schottky barrier diode may be used as the diode 34 as the high frequency detection element.

  In order to set the phase difference δ to be δ = (2N + 1) · π (where N is an integer), the second dielectric line 16 is increased by the length of the second dielectric line 16. The line length of the dielectric line 17 may be shortened, or the line length of the second dielectric line 17 may be increased by the amount corresponding to the shortening of the line length of the first dielectric line 16. In this way, it is not necessary to change the arrangement of other circuit elements other than the pulse modulator 3, and this adjustment can be facilitated. In this case, the position of the portion where the first dielectric line 16 and the fifth dielectric line 20 are close to each other or joined (portion constituting the branching device 2) is not changed.

The first high frequency transmitter / receiver of the present invention shown in FIGS. 1 and 2 configured as described above operates in the same manner as a conventional high frequency transmitter / receiver. However, at that time, the line length between the branching device 2 and the pulse modulator 3 or the line length between the branching device 2 on the mixer 6 side and the pulse modulator 3 is transmitted through the pulse modulator 3 in the off state. The millimeter wave signal to be transmitted is transmitted from Wa ₂ , the other output end 2 c of the branching device 2 to the output end 3 b of the pulse modulator 3 through the mixer 6 and the circulator 4, and reflected by the output end 3 b of the pulse modulator 3. When the wave signal is Wb ₂ and the phase difference at the center frequency between these Wa ₂ and Wb ₂ is δ, δ = (2N + 1) · π is set, so that the output end 3b of the pulse modulator 3 Since these Wa ₂ and Wb ₂ are combined in anti-phase with the circulator 4 and cancel each other and effectively attenuate, a part of the millimeter wave signal for transmission is transmitted when the pulse modulator 3 is in the OFF state. Is unnecessary Transmission as a simple signal can be suppressed, the on / off ratio of the transmission output can be increased, and the transmission / reception performance can be increased.

Next, as shown in FIG. 3, an example of an embodiment of the second high-frequency transceiver according to the present invention includes a millimeter-wave oscillator 1 that generates a millimeter-wave signal and a millimeter-wave oscillator 1 connected to the millimeter-wave oscillator 1. A branching device 2 for branching a wave signal and outputting it to one output end 2b and the other output end 2c, and a millimeter wave signal branched to this one output end 2b connected to one output end 2b. A pulse modulator 3 that modulates and outputs a millimeter wave signal for transmission, and has a first terminal 4a, a second terminal 4b, and a third terminal 4c around the magnetic body, and inputs from one terminal in this order. The circulator 4 that outputs the output of the pulse modulator 3 to the first terminal 4a and the transmission / reception antenna connected to the second terminal 4b of the circulator 4 5 and the other output terminal 2c of the branching device 2 and the circular circuit. The millimeter wave signal connected to the third terminal 4c of the data 4 and branched to the other output terminal 2c and the millimeter wave signal received by the transmission / reception antenna 5 are mixed to output an intermediate frequency signal. The millimeter wave signal output to one output end 2b of the branching device 2 is Wa ₁ , its intensity is Pa ₁ (unit: watts), and the other output end 2c of the branching device 2 is provided. The output millimeter wave signal is Wb ₁ , the intensity is Pb ₁ (unit: watts), and the branching ratio of the branching device 2 is R = Pb ₁ / Pa ₁ (where R is a real number of 0 or more). The branching ratio R of the branching device 2 is set to R <1.

In the above configuration, preferably, the transmission coefficient of the millimeter wave signal that passes through the pulse modulator 3 in the off state is A ₁ , and the transmission coefficient of the millimeter wave signal that passes between the two input terminals of the mixer 6 is B _1. , B _{2 is} the transmission coefficient of the millimeter wave signal transmitted between the third terminal 4 c and the first terminal 4 a of the circulator 4, and B is the reflection coefficient of the millimeter wave signal reflected at the output end 3 b of the pulse modulator 3. When each is set to ₃ , the branching ratio R may be set to be R = A ₁ / (B ₁ · B ₂ · B ₃ ).

Further, in the above configuration, preferably, the line length between the branching device 2 and the pulse modulator 3 or the line length between the branching device 2 on the mixer 6 side and the pulse modulator 3 is set to pulse modulation in an off state. The millimeter wave signal transmitted through the modulator 3 is transmitted through Wa ₂ , the other output end 2 c of the branching device 2 through the mixer 6 and the circulator 4 to the output end 3 b of the pulse modulator 3, and the output end 3 b of the pulse modulator 3. Where Wb ₂ is the millimeter wave signal reflected at, and δ is the phase difference at the center frequency between these Wa ₂ and Wb ₂ , δ = (2N + 1) · π (where N is an integer). It is good to set as follows.

  Further, the second high-frequency transmitter / receiver of the present invention shown in FIG. 3 is a high-frequency for connecting the above-described components as in the example of the first high-frequency transmitter / receiver of the present invention shown in the plan view of FIG. A non-radiative dielectric line is used as a transmission line for use.

That is, in the second high frequency transceiver of the present invention shown in FIG. 3, the millimeter wave output to the other end of the first dielectric line 16 is compared with the first high frequency transceiver of the present invention shown in FIG. When the signal is Wa ₁ , the intensity is Pa ₁ (unit: watts), the millimeter wave signal output to the other end of the fifth dielectric line 20 is Wb ₁ , and the intensity is Pb ₁ (unit: watts) For example, if the distance D between the adjacent portions of the first dielectric line 16 and the fifth dielectric line 20 is set so that the ratio of Pb ₁ and Pa ₁ is Pb ₁ / Pa ₁ <1. Good. Furthermore, it may be set so that R = A ₁ / (B ₁ · B ₂ · B ₃ ).

The second high frequency transmitter / receiver of the present invention configured as described above operates in the same manner as a conventional high frequency transmitter / receiver. However, at that time, the millimeter wave signal output to one output terminal 2b of the branching device 2 is Wa ₁ , its intensity is Pa ₁ , and the millimeter wave signal output to the other output terminal 2c of the branching device 2 is Wb _1. When the strength is Pb ₁ and the branching ratio of the branching device 2 is R = Pb ₁ / Pa ₁ , the branching ratio R of the branching device 2 is R <1, so that the two input terminals of the mixer 6 are Even if the isolation is worse than the isolation in the OFF state of the pulse modulator 3, the branching device 2 is connected to the other output end 2c (the fifth output end 2b) rather than the one output end 2b (the first dielectric line 16) side. In order to reduce the intensity of the millimeter wave signal that is output to the output end 3b of the pulse modulator 3 through the mixer 6 and the circulator 4, the millimeter wave signal is output to the dielectric line 20) side. From the pulse modulator 3 The intensity of the millimeter wave signal reflected by 3b can be reduced. Further, since the intensity of the millimeter wave signal can be made close to the intensity of the millimeter wave signal transmitted through the pulse modulator 3 in the off state, these millimeter wave signals can be caused to interfere with each other to attenuate each other. it can. Since it operates in this way, with a simple configuration, when the pulse modulator 3 is in an OFF state, a part of the transmission millimeter wave signal is suppressed from being transmitted as an unnecessary signal, and the transmission output is turned on / off. The ratio can be increased, and the transmission / reception performance can be increased.

The reason why the branching ratio R is preferably R <1 is that Pa ₂ (unit: watts) that is the intensity of the millimeter wave signal Wa ₂ and Pb ₂ (unit: watts) that is the intensity of the millimeter wave signal Wb ₂ are made closer. The millimeter wave signal Wa ₂ and the millimeter wave signal Wb ₂ effectively interfere with each other, and significantly more than Pa ₂ + Pb ₂ that is the sum of the respective intensities of the millimeter wave signals Wa ₂ and Wb ₂ . This is because the intensity when the millimeter wave signals Wa ₂ and Wb ₂ are combined can be reduced. This follows the general theory of interference when two high-frequency signals are caused to interfere. On the other hand, when the branching ratio R is R = 1, as described above, usually, in most cases, Pa ₂ <Pb ₂ when the pulse modulator 3 is in the OFF state, and the branching ratio R is set to R>. 1 that the at will, the effect of Pb ₂ becomes that the Pb ₂ and Pa ₂ is even larger than the Pa ₂ becomes different significantly, the millimeter-wave signal _Wa 2, Wb ₂ weaken and interfere with each other Therefore, the intensity when the millimeter wave signals Wa ₂ and Wb ₂ are combined is not much different from Pa ₂ + Pb ₂ which is the sum of the respective intensities of the millimeter wave signals Wa ₂ and Wb ₂ . The output of the millimeter wave signal when 3 is in the off state cannot be reduced, and the on / off ratio cannot be increased.

In addition, the transmission coefficient of the millimeter wave signal that passes through the pulse modulator 3 in the off state is A ₁ , the transmission coefficient of the millimeter wave signal that passes between the two input terminals of the mixer 6 is B ₁ , and the third coefficient of the circulator 4. the transmission coefficient of the millimeter wave signal to pass between the terminals 4c and the first terminal 4a B _2, when the reflection coefficient of the millimeter-wave signal reflected was B ₃ at the output 3b of the pulse modulator 3, the branch When the ratio R is set to be R = A ₁ / (B ₁ · B ₂ · B ₃ ), the intensity of the millimeter wave signal incident from the mixer 6 side and reflected by the output end 3 b of the pulse modulator 3 is Since the intensity of the millimeter wave signals transmitted through the pulse modulator 3 in the off state can be made substantially the same, these millimeter wave signals can be effectively interfered with each other and attenuated to each other. For transmission when device 3 is off It is possible to further suppress the transmission of a part of the millimeter wave signal as an unnecessary signal, to increase the on / off ratio of the transmission output, and to improve the transmission / reception performance.

The reason why the branching ratio R is preferably R = A ₁ / (B ₁ · B ₂ · B ₃ ) is that Pa ₂ (unit: Watt) which is the intensity of the millimeter wave signal Wa _{2 and} the intensity of the millimeter wave signal Wb ₂ Pb ₂ (unit: watts) can be brought close to each other so that the millimeter wave signal Wa ₂ and the millimeter wave signal Wb ₂ interfere more effectively than when R <1. in Te, than _Pa 2 + Pb ₂ is the sum of respective intensities of these millimeter-wave signals _Wa 2, Wb _2, because it is possible to a millimeter-wave signals _Wa 2, Wb ₂ is to reduce the strength when multiplexing is there.

Actually, among these A ₁ , B ₁ , B ₂ , and B ₃ , B ₂ transmits a millimeter wave signal from the third terminal 4 c of the circulator 4 to the first terminal 4 a with almost no loss, B ₂ ≈ 1 and B ₃ is almost totally reflected at the output end 3b of the pulse modulator ₃ in which the millimeter wave signal is in an OFF state, and therefore B ₃ ≈1, so that substantially the ratio of A ₁ and B ₁ The branching ratio R may be determined. At that time, the A ₁ may be measured by turning the pulse modulator 3 off and measuring the transmission coefficient S ₂₁ between the input end 3a and the output end 3b of the pulse modulator 3 with a network analyzer for millimeter wave band. Further, B ₁ may be measured permeability coefficient S ₂₁ between the two input terminals of the mixer 6 with a network analyzer for the millimeter wave band in the state where the mixer 6 was flowed a predetermined bias current. In order to measure these, as will be described later, a metal plate for shielding electromagnetic waves is inserted between the first dielectric line 16 and the second dielectric line 17 in place of the millimeter wave modulation switch. If a metal plate for shielding electromagnetic waves is inserted between the first dielectric line 16 and the fifth dielectric line 20, the module can be used without disassembling and measuring each individual component. Both A ₁ and B ₁ can be measured in the state of Then, may be obtained a ratio of the two transmission coefficients _{S 21} for the center frequency of the millimeter-wave signal _Wa 2, Wb _2. For example, B ₁ is usually 10 tens dB larger than A ₁ , and in such a case, the branching ratio R may be set to −10 several dB as much as possible. In this way, Pa ₂ and Pb ₂ can be made substantially equal, and the millimeter wave signals Wa ₂ and Wb ₂ can be effectively interfered, so that the millimeter wave signals Wa ₂ and Wb ₂ are combined. The strength at the time of performing can be made significantly smaller than Pa ₂ + Pb ₂ , and the on / off ratio can be improved by, for example, about 6 dB as compared with the case of not doing so. In general, since A ₁ <B ₁ , a method of setting the branching ratio R to R <1 or R = A ₁ / (B ₁ · B ₂ · B ₃ ) is effective. Yes, but not otherwise.

Also, the line length between one output end 2 b of the branching device 2 and the pulse modulator 3 or the line between the other output end 2 c of the branching device 2 and the pulse modulator 3 passing through the mixer 6 and the circulator 4. The millimeter wave signal passing through the pulse modulator 3 in the OFF state is transmitted through Wa ₂ , the other output end 2 c of the branching device 2, the mixer 6 and the circulator 4, and the output end 3 b of the pulse modulator 3. the millimeter-wave signal reflected at the output end 3b of the pulse modulator 3 and Wb _2, when the phase difference was [delta] at the center frequency of these Wa ₂ and _{Wb 2, δ = (2N +} 1) · π become so When set to, these Wa ₂ and Wb ₂ are combined in antiphase between the output 3b of the pulse modulator 3 and the circulator 4, and cancel each other and attenuate most effectively. When the tuner 3 is in the off state, it is possible to more effectively suppress a part of the transmission millimeter wave signal from being transmitted as an unnecessary signal, and to increase the on / off ratio of the transmission output. The performance can be increased.

In the second high frequency transmitter / receiver of the present invention, the phase difference δ is not specifically set, but Wa ₂ and Wb ₂ always interfere except in a special case of δ = 2Nπ. matching attenuated, pulse modulator 3 but is to always output a low intensity millimeter wave signal than the sum of the intensity Pb ₂ of the intensity Pa ₂ and Wb ₂ of Wa ₂ when in the off state, the Wb ₂ The strength Pb ₂ is different from the strength Pa _{2 of} Wa ₂ (usually, Wb ₂ is stronger than Wa ₂ ), and this effect is not sufficiently obtained. In particular, if the intensity Pb ₂ of Wb ₂ and the intensity Pa _{2 of} Wa ₂ are made the same, the effect of attenuating and attenuating these Wa ₂ and Wb ₂ can be greatly increased. It is. In addition, if the phase difference δ is intentionally set as described above, the effect can be further increased. The principle is generally known in theory such as a Mach-Zehnder interferometer.

  If the branching ratio R is set as described above, a local signal having an appropriate strength is input to the mixer 6 from the other output terminal 2c of the branching device 2, so that reception sensitivity is improved and the branching device 2 is Since the intensity of the millimeter wave signal output from the one output terminal 2b of the branching device 2 to the pulse modulator 3 is increased, the transmission output of the transmitting millimeter wave signal can be increased.

  Next, an example of an embodiment of the third high-frequency transmitter / receiver of the present invention is the first terminal 2'a, 4a and the second terminal around the magnetic body as shown in the block circuit diagram of FIG. First and second circulators 2 'that have 2'b, 4b and third terminals 2'c, 4c, and output millimeter-wave signals input from one terminal in this order from other adjacent terminals. , 4, a millimeter wave oscillator 1 for generating a millimeter wave signal connected to a first terminal 2 ′ a of the first circulator 2 ′, a second terminal 2 ′ b of the first circulator 2 ′, The millimeter wave signal connected between the first circulator 4 and the first terminal 4a of the second circulator 4 is transmitted to the second circulator 4 side for transmission according to the pulse signal or reflected to the first circulator 2 'side. And a second terminal of the second circulator 4 Reflected by the pulse modulator 3 connected between the transmitting / receiving antenna 5 connected to b, the third terminal 2′c of the first circulator 2 ′, and the third terminal 4c of the second circulator 4 And a millimeter wave signal input from the third terminal 2 ′ c of the first circulator 2 ′ and a millimeter wave signal received by the transmission / reception antenna 5 and input from the third terminal 4 c of the second circulator 4. And a mixer 6 for outputting an intermediate frequency signal by mixing, and the millimeter wave signal transmitted through the pulse modulator 3 in the OFF state is Wa, and the third terminal 2′c of the first circulator 2 ′ is provided. Through the mixer 6 and the second circulator 4 and transmitted to the output end 3b of the pulse modulator 3 and reflected by the output end 3b of the pulse modulator 3, Wb is the center frequency of these Wa and Wb. Place in The difference is taken as δ, δ = (2N + 1) · π (although, N represents an integer.) Is configured to set such that the.

  Further, the third high-frequency transmitter / receiver of the present invention shown in FIG. 4 is a high-frequency for connecting the above-described components as in the example of the first high-frequency transmitter / receiver of the present invention shown in the plan view of FIG. A non-radiative dielectric line is used as a transmission line for use.

  That is, the third high-frequency transmitter / receiver of the present invention shown in the block circuit diagram of FIG. 4 specifically has an interval of 1/2 or less of the wavelength of the millimeter wave signal as shown in the plan view of FIG. Between the flat conductors 11 arranged in parallel (the other flat conductor is not shown), the peripheral portions of the ferrite plates 14 and 15 arranged in parallel to the flat conductor 11 are respectively input / output of millimeter wave signals. The first and second terminals 14a and 15a, the second terminals 14b and 15b, and the third terminals 14c and 15c are arranged in this order, and in this order, the millimeter wave signals input from one terminal are adjacent to each other. The first circulator 2 'and the second circulator 4 output from the terminals, the first dielectric line 46 having one end connected to the first terminal 14a of the first circulator 2', and the first dielectric The millimeter-wave signal output from the high-frequency diode connected to the other end of the line 46 is circulated. A millimeter-wave oscillator 1 that performs number modulation and propagates and outputs the first dielectric line 46 as a millimeter-wave signal, a second dielectric line 47 having one end connected to the second terminal 14b, and a second A pulse modulator 3 connected to the other end of the dielectric line 47 and reflecting the millimeter wave signal to the input end 3a side or transmitting to the output end 3b side according to the pulse signal, and the output of the pulse modulator 3 A third dielectric line 48 connected between the end 3b and the first terminal 15a of the second circulator 4, and a fourth end connected to the second terminal 15b of the second circulator 4 A dielectric line 49; a transmitting / receiving antenna 5 connected to the other end of the fourth dielectric line 49; and a fifth dielectric line 50 having one end connected to the third terminal 15c of the second circulator 4. , One end connected to the third terminal 14c of the first circulator 2 ', Between the other end of the fifth dielectric line 50 and the other end of the sixth dielectric line 51. The millimeter wave signal input from the sixth dielectric line 51 and the millimeter wave signal received by the transmission / reception antenna 5 and input from the second circulator 4 are mixed to output an intermediate frequency signal. A mixer 6 and a millimeter wave signal passing through the pulse modulator 3 in the OFF state Wa, and the mixer 6 and the second circulator 4 from the third terminal 2'c of the first circulator 2 '. When the millimeter wave signal passing through the output end 3b of the pulse modulator 3 and reflected by the output end 3b of the pulse modulator 3 is Wb, and the phase difference at the center frequency between these Wa and Wb is δ, δ = (2N + 1) · π is set.

  In the above configuration, an attenuator or a variable attenuator is preferably provided between the first circulator 2 ′ and the mixer 6.

  The third high frequency transmitter / receiver of the present invention configured as described above operates in the same manner as a conventional high frequency transmitter / receiver. However, at that time, the millimeter wave signal transmitted through the pulse modulator 3 in the OFF state is Wa, and the pulse modulation is performed from the third terminal 2'c of the first circulator 2 'through the mixer 6 and the second circulator 4. When the millimeter wave signal transmitted through the output terminal 3b of the modulator 3 and reflected by the output terminal 3b of the pulse modulator 3 is Wb, and the phase difference at the center frequency between these Wa and Wb is δ, δ = (2N + 1 ) · Π is set so that Wa and Wb are combined in opposite phases between the output end 3b of the pulse modulator 3 and the second circulator 4, and cancel each other to effectively attenuate. Therefore, when the pulse modulator 3 is in the off state, it is possible to suppress a part of the transmission millimeter-wave signal from being transmitted as an unnecessary signal, and to increase the on / off ratio of the transmission output. It can be increased.

  Further, the first circulator 2 ′ and the pulse modulator 3 cooperate with each other so that the local signal LO is not input to the mixer 6 while the pulse modulator 3 outputs the millimeter wave signal for transmission. Therefore, even if a part of the millimeter-wave signal for transmission leaks from the first terminal 4a of the second circulator 4 to the third terminal 4c due to insufficient isolation of the second circulator 4, the mixer 6 does not output an intermediate frequency signal corresponding to the leaked millimeter wave signal, so that the reception performance can be improved, and the on / off ratio of the transmission output, which is an improvement of the transmission system, is increased. In addition, the receiving system can be improved.

  Further, when an attenuator or a variable attenuator is provided between the first circulator 2 ′ and the mixer 6, the attenuator or the variable attenuator is connected to the third terminal 2′c (the first circulator 2 ′). Since the millimeter wave signal output from the two input terminals of the mixer 6 can be reduced by attenuating the millimeter wave signal output from the third terminal 14c), the second circulator 4 from the mixer 6 side can be reduced. And the intensity of the millimeter wave signal Wb that is transmitted to the pulse modulator 3 and reflected by the output terminal 3b of the pulse modulator 3, and the intensity of the millimeter wave signal Wa that is transmitted through the pulse modulator 3 in the OFF state are the same. Therefore, Wa and Wb are combined in opposite phases between the output end 3b of the pulse modulator 3 and the second circulator 4, and cancel each other to attenuate more effectively. Further, when the pulse modulator 3 is in the off state, a part of the transmission millimeter wave signal is further prevented from being transmitted as an unnecessary signal, and the on / off ratio of the transmission output can be increased. Can be further increased.

Next, in the high-frequency transmitter / receiver of the present invention, the first to sixth dielectric lines 16 to 21 and 46 to 51 are made of a resin such as ethylene tetrafluoride or polystyrene, or a cordier having a low relative dielectric constant. Ceramics such as light (2MgO · 2Al ₂ O ₃ · 5SiO ₂ ) ceramics, alumina (Al ₂ O ₃ ) ceramics, and glass ceramics are preferable, and these have low loss in the millimeter wave band.

  The cross-sectional shapes of the first to sixth dielectric lines 16 to 21 and 46 to 51 are basically rectangular, but may be rounded corners of the rectangular wave. Various cross-sectional shapes used for transmission can be used.

The ferrite plates 14 and 15 are preferably made of zinc, nickel, and iron oxide (Zn _a Ni _b Fe _c O _x ), for example, for millimeter wave signals among ferrites.

  Further, the shape of the ferrite plates 14 and 15 is usually a disc shape, but the planar shape may be a regular polygonal shape. In that case, when the number of dielectric lines to be connected is n (n is an integer of 3 or more), the planar shape is preferably a regular m-square (m is an integer greater than n of 3 or more).

  The flat conductors 11 and 12 are made of Cu, Al, Fe, Ag, Au, Pt, SUS (stainless steel), brass (Cu-Zn alloy) in terms of high electrical conductivity and good workability. A conductive plate such as) is suitable. Or what formed these conductor layers on the surface of the insulating board which consists of ceramics, resin, etc. may be used.

  Further, the non-reflecting terminator 22 is provided with a film-like resistor or the like on a plane parallel to the flat conductors 11 and (12) inside the dielectric line 13 with respect to the dielectric line 13 as shown in FIG. What is necessary is just to comprise a radio wave absorber. At that time, the material of the resistor is preferably a nickel chromium alloy or carbon. In addition, as the material of the radio wave absorber, permalloy or sendust is suitable. If these materials are used, the millimeter wave signal can be attenuated efficiently. Further, materials other than these that can attenuate the millimeter wave signal may be used.

  The substrate 30 is made of aluminum (Al), gold on one main surface of a plate-shaped substrate made of thermoplastic resin such as ethylene tetrafluoride, polystyrene, glass ceramics, glass epoxy resin, epoxy resin, so-called liquid crystal polymer. A choke-type bias supply line 31 formed of a strip conductor made of (Au), copper (Cu) or the like is used.

  In the high-frequency transmitter / receiver of the present invention, the circuit configuration shown in the block circuit diagram is important, and the high-frequency transmission line connecting each circuit element is not only a non-radiative dielectric line but also a conductive line. Select a wave tube, dielectric waveguide, strip line, microstrip line, coplanar line, slot line, coaxial line, or a modified high-frequency transmission line according to the frequency band and application to be used. It doesn't matter. Further, the frequency band to be used is effective not only in the millimeter wave band but also in the microwave band or lower frequency band.

  Further, a duplexer, a switch, a hybrid circuit, or the like may be used instead of the circulator 4 (second circulator 4). Further, for the high-frequency oscillator, the modulator, and the mixer, a bipolar transistor, a field effect transistor (FET), or an integrated circuit (CMOS, MMIC, etc.) in which these are integrated may be used instead of the diode.

  Next, a radar apparatus according to the present invention, a vehicle equipped with the radar apparatus and a small ship equipped with the radar apparatus will be described.

  An example of an embodiment of a radar apparatus according to the present invention is to detect by processing any one of the first to third high-frequency transmitter / receivers of the present invention having the above-described configuration and an intermediate frequency signal output from the high-frequency transmitter / receiver. A distance information detector for detecting distance information to the object.

  According to the radar apparatus of the present invention, since the above configuration is adopted, the high-frequency transmitter / receiver of the present invention transmits a good millimeter wave signal with a high transmission output on / off ratio. In addition, it is possible to provide a radar apparatus that can detect a detection object at a close distance or a distant object with certainty.

  The radar device-equipped vehicle of the present invention includes the above-described radar device of the present invention and is configured to use this radar device for detection of a detection target.

  Since the radar device-equipped vehicle of the present invention has such a configuration, the behavior of the vehicle can be controlled based on the distance information detected by the radar device, For example, the detection of obstacles on the road or other vehicles can be warned by sound, light or vibration. However, in the vehicle equipped with the radar device of the present invention, Since the radar apparatus detects other vehicles and the like quickly and reliably, it is possible to perform appropriate control of the vehicle and appropriate warning to the driver without causing the vehicle to make a sudden behavior.

  The radar device-equipped vehicle of the present invention is not limited to a vehicle for transporting passengers and cargo such as trains, trains, and automobiles, but also bicycles, motorbikes, amusement park vehicles, golf courses, etc. It can also be used for carts and the like.

  A small ship equipped with a radar apparatus according to the present invention includes the radar apparatus according to the present invention, and the radar apparatus is used to detect a detection target.

  Since the small ship equipped with the radar apparatus of the present invention has such a configuration, the behavior of the small ship is controlled based on the distance information detected by the radar apparatus in the small ship as in the conventional vehicle equipped with the radar apparatus. Or the operator is warned by sound, light or vibration that an obstacle such as a reef, another ship or other small ship has been detected. In a ship, the radar device quickly and reliably detects obstacles such as reefs, other ships or other small ships that are detection objects. Proper control and appropriate warning to the operator can be provided.

  The small-sized ship equipped with the radar device of the present invention is specifically a ship that can be operated without a license for a small ship or a license, and is a boat with a total tonnage of less than 20 tons. Motorcycles, small bass boats with outboard motors, inflatable boats (rubber boats) with outboard motors, fishing boats, recreational fishing boats, work boats, houseboats, towing boats, sports boats, fishing boats, yachts, open-sea yachts, cruisers or gross tonnage 20 It can be used for pleasure boats of tons or more.

  Thus, according to the present invention, the transmission output on / off ratio can be suppressed with a simple configuration by suppressing that a part of the high-frequency signal for transmission is transmitted as an unnecessary signal when the pulse modulator is in the off state. A high-performance high-frequency transmitter / receiver capable of improving transmission / reception performance, a radar device including the same, a vehicle equipped with the radar device equipped with the radar device, and a small ship equipped with the radar device Can do.

The first high-frequency transmitter / receiver of the present invention shown in FIG. 2 was configured as follows. Two parallel-plate conductors 11 and (12) with two 6 mm-thick Al plates are arranged at an interval of 1.8 mm, and a rectangular shape with a cross-sectional shape of 1.8 mm (height) x 0.8 mm (width) between them. The first to fifth dielectric lines 16 to 20 made of cordierite ceramics having a relative dielectric constant of 4.8 are arranged. At that time, the circulator 4 has a diameter of 2 mm and a thickness of 0.23 mm, one of the two ferrite plates 15 being in close contact with the upper plate conductor and the other being in close contact with the lower plate conductor, and the central axes thereof are Arranged so that they are on the same straight line and face each other, and the second dielectric line 17, the third dielectric line 18, and the fourth dielectric line 19 are arranged radially around the ferrite plate 15 did. Further, the branching device 2 brings the middle of the first dielectric line 16 and the middle of the fifth dielectric line 20 close to each other with a distance D = 2.1 mm between the nearest parts, and the millimeter of the fifth dielectric line 20 A reflection-free terminator 22 is connected to the end of the wave oscillator 1 side. The pulse modulator 3 includes an organic resin substrate (relative dielectric constant εr) made of a thermoplastic resin having a low dielectric constant of 0.2 mm between the first dielectric line 16 and the second dielectric line 17. = 3.0) and a millimeter wave modulation switch using the substrate 30 is arranged. A choke-type bias supply made of copper formed by alternately forming a wide line and a narrow line on one main surface (surface opposite to the first dielectric line 16) of the millimeter wave modulation switch The line 31 is formed, and the length of the wide line is λ ₁ /4=0.7 mm (λ ₁ is 2.8 mm for the wavelength of millimeter wave signal frequency 76.3 GHz, about 2.8 mm, and the dielectric substrate has a short wavelength. The length of the narrow line is λ ₁ /4=0.7 mm, the width of the wide line is 1.5 mm, and the width of the narrow line is 0.2 mm. Further, as the millimeter wave oscillator 1, a pill type voltage controlled oscillator (VCO) using a Gunn diode element is used, and a flat conductor having a strong standing electric field of a millimeter wave signal propagating through the first dielectric line 16 is used. 11 was connected to the other end of the waveguide whose one end was connected to the through hole provided in 11. Further, a metal horn antenna was connected to the end of the third dielectric line 18 opposite to the ferrite plate 15 as the transmitting / receiving antenna 5. In addition, the mixer 6 brings the middle of the fourth dielectric line 19 and the middle of the fifth dielectric line 20 close to each other with a distance D = 1.1 mm between the closest portions, and the ferrite of the fourth dielectric line 19 An organic resin substrate made of a thermoplastic resin having a low dielectric constant of 0.2 mm (dielectric constant) on each of the end opposite to the plate 15 and the end opposite to the branching device 2 of the fifth dielectric line 20 A millimeter wave detection unit using a substrate 30 having a rate εr = 3.0) was arranged to constitute a balanced mixer. One main surface (surface opposite to the fourth and fifth dielectric lines 19 and 20) of the millimeter wave detection section is made of copper formed by alternately forming wide lines and narrow lines. A choke-type bias supply line 31 is formed, and the length of the wide line is λ ₁ /4=0.7 mm (λ ₁ is 2.8 mm for a wavelength of about 4 mm at a frequency of 76.3 GHz of a millimeter wave signal, The length of the narrow line is λ ₁ /4=0.7 mm, the width of the wide line is 1.5 mm, and the width of the narrow line is 0.2 mm. .

  The ferrite plate 15 was made of a material having a relative dielectric constant of 13.5 and a saturation magnetization of 3,300 G (Gauss) (magnetic flux density Bm by JIS C2561 DC magnetic measurement).

Further, the branching ratio R of the branching device 2 was set to -14 dB. At that time, the intensity Pa ₂ of the millimeter-wave signal Wa ₂ transmitted through the pulse modulator 3 in the OFF state, the fifth dielectric line 20 to the mixer 6, the fourth dielectric line 19, the circulator 4 and the second The ratio Pa ₂ / Pb _{2 to} the intensity Pb ₂ of the millimeter wave signal Wb ₂ that passes through the dielectric line 17 to the output end 3b of the pulse modulator 3 and reflects from the output end 3b of the pulse modulator 3 is expressed by the frequency Was about 3 dB at 76.3 GHz. At this time, the mixer 6 had good conversion gain.

  Two types of samples were prepared for the high-frequency transceiver configured as described above. One of them is a sample X as an embodiment of the present invention, and the other is a sample Y as a comparative example. In the sample X, the phase difference δ at 76.3 GHz which is the center frequency of a millimeter wave signal for transmission is approximately ( 2N + 1) π, and in sample Y, the phase difference δ at 76.3 GHz, which is the center frequency of the millimeter wave signal for transmission, was significantly different from (2N + 1) π. Specifically, first, a sample Y having a phase difference δ of 1.31π + 2Nπ at a frequency of 76.3 GHz is obtained, and the phase difference δ at the same frequency is approximately π + 2Nπ for the same condition. A sample X in which the line lengths of the first and second dielectric lines 16 and 17 were adjusted was obtained. At that time, in the sample X, the line lengths of the first and second dielectric lines 16 and 17 are about −1 mm and +1 mm respectively with respect to the line lengths of the first and second dielectric lines 16 and 17 of the sample Y. The first and second dielectric lines 16 and 17 are not different except that the positions of the end portions on the pulse modulator 3 side and the positions of the pulse modulator 3 are different.

For samples X and Y, first, the phase difference δ was measured as follows using a vector network analyzer for the millimeter wave band. The first test terminal (test port 1) of the vector network analyzer is connected to the end of the waveguide to which the VCO is connected by removing the VCO, and the second test terminal (test port 2) is connected to the third test terminal. horn antenna of the dielectric waveguide 18 is connected to remove the horn antenna end connected to measure the transmission characteristic S ₂₁ between their first and second test terminals. At this time, when measuring the millimeter wave signal Wa ₂ transmitted through the pulse modulator 3 in the off state, a metal for shielding electromagnetic waves between the first dielectric line 16 and the fifth dielectric line 20 is used. insert the plate blocks the millimeter wave signal Wb _2, when measuring the millimeter wave signal Wb ₂ reflected at the output end 3b of the pulse modulator 3, a first dielectric waveguide 16 and the second dielectric guide 17 insert a metal plate for shielding electromagnetic waves instead of the millimeter wave modulation switch between blocked the millimeter-wave signal Wa _2. That is, the transmission characteristic S ₂₁ was measured independently for each of Wa ₂ and Wb ₂ . The difference between the phase of Wa _{2 and} the phase of Wb ₂ was obtained from the phase value among the measured values of the transmission characteristics S ₂₁ to obtain the phase difference δ. The results are shown in Table 1. In Table 1, the phase difference δ is shown with 2Nπ omitted.

  From the results shown in Table 1, in sample Y, the frequency difference of the millimeter wave signal is 76.3 GHz, and the phase difference δ is 1.31π shifted from π by 0.31π, whereas in sample X, the phase difference δ has the same frequency. It was found to be 1.05π, and it was confirmed that the phase difference δ in the sample X was approximately π.

  Next, samples X and Y were actually operated, and their on / off ratio characteristics were measured as follows. That is, the VCO is stably oscillated so that the oscillation output does not change, and the horn antenna is removed from the end of the third dielectric line 18 to which the horn antenna is connected. And the intensity of the millimeter wave signal output from the end thereof is measured for each of when the pulse modulator 3 is in the on state and when it is in the off state, and the ratio of those measured values is on / An off ratio was obtained. The results are shown in the diagram of FIG. The intensity (unit: watts) of the millimeter wave signal as the transmission output when the pulse modulator 3 is in the on state is W_on, and the millimeter wave signal as the transmission output when the pulse modulator 3 is in the off state. The intensity (unit: watts) was W_off.

  FIG. 9 is a diagram showing the on / off ratio characteristics of the transmission output for the example of the high-frequency transceiver of the present invention and the comparative example, where the horizontal axis is frequency (unit: GHz), and the vertical axis is the on / off of the transmission output. The off-ratio is represented by the reciprocal (−10 Log (W_on / W_off)) (unit: dB), and the black circle plot shows a representative measured value of the on / off ratio characteristic of the transmission output of the sample X. The plot shows representative measured values of the ON / OFF ratio characteristics of the transmission output of sample Y. In FIG. 9, the on / off ratio is represented by a reciprocal, and the smaller the actually measured value, the higher the on / off ratio and the better the on / off ratio characteristic of the transmission output. .

From the measurement results of the samples X and Y shown in FIG. 9, in the sample X, the phase difference δ of the millimeter wave signals Wa ₂ and Wb ₂ becomes approximately π at 76.3 GHz which is the center frequency of the millimeter wave signal for transmission. Thus, it can be seen that by setting the line lengths of the first and second dielectric lines 16 and 17, the on / off ratio is high before and after the frequency. That is, if the phase difference δ between Wa ₂ and Wb ₂ is (2N + 1) π, Wa ₂ and Wb ₂ are combined in opposite phases between the output end 3b of the pulse modulator 3 and the circulator 4, and are mutually In order to effectively attenuate each other by canceling each other, when the pulse modulator 3 is in an OFF state, a part of the transmission millimeter wave signal is suppressed from being transmitted as an unnecessary signal, and the ON / OFF ratio of the transmission output is increased. I can confirm that I can do it. Although omitted here, it was confirmed that the intensity of the millimeter wave signal output as the transmission output when the pulse modulator 3 is in the OFF state is smaller in the sample X than in the sample Y. Further, the intensity of the millimeter wave signal output as the transmission output when the pulse modulator 3 is in the OFF state is dominant in the ON / OFF ratio of the transmission output, and the ON / OFF ratio of the transmission output is reduced by reducing this. It was also confirmed that can be increased.

Further, from the measurement result of the phase difference δ of the sample X shown in Table 1 and the measurement result of the sample X shown in FIG. 9, the phase difference δ is δ <0.75π (π−π / 4) and 1.25π (π + π / 4) Since the on / off ratio of the transmission output is saturated when <δ (frequency is less than 75.9 GHz and exceeds 76.7 GHz), the phase difference δ is 0.75π (π−π / 4) ≦ δ ≦ 1.25π It can be seen that when (π + π / 4), Wa ₂ and Wb ₂ effectively cancel each other and attenuate, thereby increasing the on / off ratio of the transmission output. Therefore, it was found that the phase difference δ is preferably from δ = (2N + 1) π−1 / 4π to δ = (2N + 1) π + 1 / 4π. Of course, δ = (2N + 1) π is optimal among them as described above.

  When the same evaluation as above was performed for the second and third high-frequency transceivers of the present invention, a good result with a high on / off ratio of the transmission output was obtained.

  Finally, when a radar apparatus including the samples X and Y is configured and a radar detection test for detecting a detection object approaching the radar apparatus is performed, the radar apparatus including the sample X is fast and sure. Confirmed to output distance information.

  Thus, the high-frequency transmitter / receiver of the present invention has a simple configuration and suppresses that a part of the high-frequency signal for transmission is transmitted as an unnecessary signal when the pulse modulator is in the off state, thereby turning on / off the transmission output. It became a high-performance high-frequency transmitter / receiver that can increase the off-ratio and increase the transmission / reception performance. Further, the radar apparatus of the present invention has become a radar apparatus that can quickly and reliably detect a radar.

  Note that the present invention is not limited to the above-described embodiments and examples, and various modifications may be made without departing from the scope of the present invention. For example, as an adjustment for adjusting the phase difference δ, the first, second, fourth, and fifth dielectric lines 16, 17, 19, 20, 46, 47, 49, and 50 are shifted in the middle. A phaser may be provided. In this case, the phase difference δ can be dynamically set. For example, the phase difference δ can be dynamically changed according to the operation condition of the mixer 6 or can be synchronized with the operation of the pulse modulator 3. The phase difference δ can be changed.

It is a block circuit diagram showing typically the composition about an example of an embodiment of the 1st high frequency transceiver of the present invention. It is a top view which shows typically the structure about an example of embodiment of the 1st high frequency transmitter-receiver of this invention. It is a block circuit diagram which shows typically the structure about an example of embodiment of the 2nd high frequency transmitter-receiver of this invention. It is a block circuit diagram which shows typically the structure about an example of embodiment of the 3rd high frequency transmitter-receiver of this invention. It is a top view which shows typically the structure about an example of embodiment of the 3rd high frequency transmitter-receiver of this invention. It is a partially broken perspective view which shows the fundamental structure of a nonradiative dielectric track | line. It is a perspective view which shows typically an example of the board | substrate with which the diode used for a nonradiative dielectric track type pulse modulator was mounted. It is a perspective view which shows typically an example of the board | substrate with which the diode used for a nonradiative dielectric track type mixer was mounted. It is a diagram which shows the on / off ratio characteristic of transmission output about the Example and comparative example of the high frequency transmitter-receiver of this invention. It is a typical block circuit diagram which shows the example of the conventional high frequency transmitter-receiver.

Explanation of symbols

1: Millimeter wave oscillator 2: Branching device 2 ': First circulator 2a, 2'a: First terminal 2b, 2'b: Second terminal 2c, 2'c: Third terminal 3: Pulse modulation 3a: input terminal 3b: output terminal 4: circulator (second circulator)
4a: 1st terminal 4b: 2nd terminal 4c: 3rd terminal 5: Transmission / reception antenna 6: Mixer
11, 12: Flat conductor
13: Dielectric line
14, 15: Ferrite plate
14a, 15a: First terminal
14b, 15b: Second terminal
14c, 15c: Third terminal
16, 46: First dielectric line
17, 47: Second dielectric line
18, 48: Third dielectric line
19, 49: Fourth dielectric line
20, 50: Fifth dielectric line
21, 51: Sixth dielectric line
22: Non-reflective terminator
30: Board
31: Choke-type bias supply line
32: Connection terminal
33: Diode (element for high frequency modulation)
34: Diode (element for high frequency detection)

Claims (9)

A high-frequency oscillator for generating a high-frequency signal; a branching device connected to the high-frequency oscillator for branching the high-frequency signal and outputting the branched signal to one output end and the other output end; and connected to the one output end A modulator that modulates the high-frequency signal branched to the one output terminal and outputs a high-frequency signal for transmission; and a first terminal, a second terminal, and a third terminal around the magnetic body, A high-frequency signal input from one terminal in this order is output from the next adjacent terminal, and the output of the modulator is connected to the first terminal, and the circulator is connected to the second terminal of the circulator. A transmission / reception antenna, a high-frequency signal branched to the other output end connected between the other output end of the branching device and the third terminal of the circulator, and a high frequency received by the transmission / reception antenna. A mixer that mixes a wave signal and outputs an intermediate frequency signal, a line length between the branching device and the modulator, or between the branching device and the modulator on the mixer side. A high-frequency signal that transmits the line length through the modulator in an off state is Wa ₂ , and is transmitted from the other output end of the branching unit to the output end of the modulator through the mixer and the circulator, when a high-frequency signal reflected by the output of the modulator and Wb _2, which was the phase difference [delta] at the center frequency of these Wa ₂ and _{Wb 2, δ = (2N +} 1) · π ( although, N represents an integer A high-frequency transmitter / receiver characterized by being set to A high-frequency oscillator for generating a high-frequency signal; a branching device connected to the high-frequency oscillator for branching the high-frequency signal and outputting the branched signal to one output end and the other output end; and connected to the one output end A modulator that modulates the high-frequency signal branched to the one output terminal and outputs a high-frequency signal for transmission; and a first terminal, a second terminal, and a third terminal around the magnetic body, A high-frequency signal input from one terminal in this order is output from the next adjacent terminal, and the output of the modulator is connected to the first terminal, and the circulator is connected to the second terminal of the circulator. A transmission / reception antenna, a high-frequency signal branched to the other output end connected between the other output end of the branching device and the third terminal of the circulator, and a high frequency received by the transmission / reception antenna. Has and a mixer for outputting the intermediate frequency signal by mixing the waves signal, a high frequency signal to be output to the one output end of the divider Wa _1, the intensity Pa _1, wherein the branching unit of The high-frequency signal output to the other output terminal is Wb ₁ , its intensity is Pb _1, and the branching ratio of the branching unit is R = Pb ₁ / Pa ₁ (where R is a real number of 0 or more). A branching ratio R of the branching device is set to R <1. The transmission coefficient of the high-frequency signal that passes through the modulator in the off state is A ₁ , the transmission coefficient of the high-frequency signal that passes between the two input terminals of the mixer is B ₁ , the third terminal of the circulator, and the first Where the transmission coefficient of the high-frequency signal transmitted to and from the terminal 1 is B ₂ , and the reflection coefficient of the high-frequency signal reflected from the output end of the modulator is B ₃ , the branching ratio R is R = A ₁ / The high-frequency transmitter / receiver according to claim 2, wherein the high-frequency transmitter / receiver is set to be (B ₁ · B ₂ · B ₃ ). The line length between the one output terminal of the branching device and the modulator or the line length between the other output terminal of the branching device and the modulator passing through the mixer and the circulator is turned off. Wa ₂ , a high-frequency signal transmitted through the modulator in a state is transmitted from the other output terminal of the branching unit to the output terminal of the modulator through the mixer and the circulator, and the output of the modulator a high-frequency signal reflected by the end and Wb _2, when the phase difference was [delta] at the center frequency of these Wa ₂ and _{Wb 2, δ = (2N +} 1) · π ( although, N represents an integer.) becomes 4. The high frequency transmitter / receiver according to claim 2, wherein the high frequency transmitter / receiver is set as described above. A first terminal, a second terminal, and a third terminal are provided around the magnetic body, and a high frequency signal input from one terminal in this order is output from another adjacent terminal. A circulator; a high-frequency oscillator for generating a high-frequency signal connected to the first terminal of the first circulator; the second terminal of the first circulator; and the first terminal of the second circulator. And a modulator for transmitting the high-frequency signal to the second circulator for transmission or reflecting the first circulator in response to a pulse signal, and the second circulator A transmitting / receiving antenna connected to the second terminal, and the front terminal connected between the third terminal of the first circulator and the third terminal of the second circulator; The high-frequency signal reflected by the modulator and input from the third terminal of the first circulator, and the high-frequency signal received by the transmission / reception antenna and input from the third terminal of the second circulator; A high-frequency signal transmitted through the modulator in an off state Wa, and the mixer and the first circulator from the third terminal When the high-frequency signal transmitted through the circulator 2 to the output end of the modulator and reflected by the output end of the modulator is Wb, and the phase difference at the center frequency between these Wa and Wb is δ. , Δ = (2N + 1) · π (where N is an integer). 6. The high-frequency transceiver according to claim 5, wherein an attenuator or a variable attenuator is provided between the first circulator and the mixer. A high-frequency transmitter / receiver according to any one of claims 1 to 6, and a distance information detector for processing the intermediate frequency signal output from the high-frequency transmitter / receiver to detect distance information to a detection target. A radar apparatus comprising: A radar device-equipped vehicle comprising the radar device according to claim 7, wherein the radar device is used for detection of an object to be detected. 8. A small ship equipped with a radar apparatus, comprising the radar apparatus according to claim 7, wherein the radar apparatus is used for detection of a detection object.

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