JP2005110335A - Power converter - Google Patents

Power converter Download PDF

Info

Publication number
JP2005110335A
JP2005110335A JP2003336185A JP2003336185A JP2005110335A JP 2005110335 A JP2005110335 A JP 2005110335A JP 2003336185 A JP2003336185 A JP 2003336185A JP 2003336185 A JP2003336185 A JP 2003336185A JP 2005110335 A JP2005110335 A JP 2005110335A
Authority
JP
Japan
Prior art keywords
phase
voltage
output
inverter
power
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
JP2003336185A
Other languages
Japanese (ja)
Other versions
JP4401724B2 (en
Inventor
Toshiaki Oka
利明 岡
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Toshiba Mitsubishi Electric Industrial Systems Corp
Original Assignee
Toshiba Mitsubishi Electric Industrial Systems Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Toshiba Mitsubishi Electric Industrial Systems Corp filed Critical Toshiba Mitsubishi Electric Industrial Systems Corp
Priority to JP2003336185A priority Critical patent/JP4401724B2/en
Publication of JP2005110335A publication Critical patent/JP2005110335A/en
Application granted granted Critical
Publication of JP4401724B2 publication Critical patent/JP4401724B2/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Abstract

<P>PROBLEM TO BE SOLVED: To provide a power converter in which the distortion of an output current of each phase is removed by correcting a voltage variation and a large smoothing capacitor is not required. <P>SOLUTION: The power converter comprises a polyphase inverter where each phase is formed of at least one unit inverter 1 obtaining an AC single phase output from a DC power supply through a smoothing capacitor, a means 3 for controlling the output by imparting a voltage command to the polyphase inverter, a means for detecting each DC voltage of the unit inverter 1 directly or indirectly, and a means 4 for correcting the voltage command of each phase of the polyphase inverter. The voltage command correcting means 4 comprises a means for operating a variation in the DC voltage of each phase of the polyphase inverter using a signal obtained from the detecting means, and the power converter is arranged to correct the voltage command of the polyphase inverter based on operation results from the operating means. <P>COPYRIGHT: (C)2005,JPO&NCIPI

Description

本発明は電力変換装置に係わり、特に単位インバータの単相出力で各相を構成して多相交流電力を得る電力変換装置に関する。   The present invention relates to a power converter, and more particularly to a power converter that obtains multiphase AC power by configuring each phase with a single-phase output of a unit inverter.

3相電力を出力する電力変換装置においては、電力変換装置の大容量化、高電圧化を目的とし、また、その出力波形を改善するため、3相交流電源から2次側に複数の巻線を持った変圧器を介して3相交流電力を複数台の単位インバータへ供給し、これらの単位インバータを3グループに分割し、各グループの単相出力を夫々直列に接続し、その直列接続されたグループの一端を中性点として接続し、その他端を夫々3相の交流電動機の各相に接続することにより、交流電動機に3相交流電力を供給する手法が知られている(例えば、特許文献1参照。)。   In a power converter that outputs three-phase power, a plurality of windings are provided from the three-phase AC power source to the secondary side in order to increase the capacity and voltage of the power converter and to improve the output waveform. The three-phase AC power is supplied to multiple unit inverters via a transformer with a power supply, the unit inverters are divided into three groups, and the single-phase outputs of each group are connected in series, and the series connected A method of supplying three-phase AC power to an AC motor by connecting one end of each group as a neutral point and connecting the other end to each phase of a three-phase AC motor is known (for example, a patent) Reference 1).

この場合、前述の単位インバータの主回路は、変圧器の2次巻線からの電力をコンバータ及び直流平滑コンデンサで直流電力に変換し、この直流電力をインバータで任意の周波数、電圧を持った交流電力に変換するように構成されている。従って、この電力変換装置の直流リンク部は電力変換装置の出力の各相毎に独立した構成となっている。
特開平11−122943号公報(第14頁、図1)
In this case, the main circuit of the unit inverter described above converts the power from the secondary winding of the transformer into DC power with a converter and a DC smoothing capacitor, and this DC power is AC with an arbitrary frequency and voltage by the inverter. It is configured to convert to electric power. Therefore, the DC link part of this power converter has an independent configuration for each phase of the output of the power converter.
Japanese Patent Laid-Open No. 11-122943 (page 14, FIG. 1)

しかしながら、このような、独立した直流電源をもつ単位インバータの単相出力を多重接続した電力変換装置においては、各相の瞬時電力が変動することによって直流電圧変動が発生し、出力電流が正弦波から歪む。以下この原理について説明する。   However, in such a power conversion device in which single-phase outputs of unit inverters having independent DC power supplies are connected in multiples, DC voltage fluctuations occur due to fluctuations in the instantaneous power of each phase, and the output current is a sine wave. Distorted from. This principle will be described below.

3相インバータの時刻tにおける各相の出力電圧及電流は、角周波数をω、力率角をθとして、
Vu=√2・|V|・cos(ωt)
Vv=√2・|V|・cos(ωt−2π/3)
Vw=√2・|V|・cos(ωt+2π/3)
Iu=√2・|I|・cos(ωt−θ)
Iv=√2・|I|・cos(ωt−2π/3−θ)
Iw=√2・|I|・cos(ωt+2π/3−θ)
と記述できる。ここで、|V|及び|I|は夫々相電圧、相電流の実効値である。従って各相の瞬時電力は、以下となる。
The output voltage and current of each phase at the time t of the three-phase inverter are expressed as follows, where the angular frequency is ω and the power factor angle is θ:
Vu = √2 · | V | · cos (ωt)
Vv = √2 · | V | · cos (ωt−2π / 3)
Vw = √2 · | V | · cos (ωt + 2π / 3)
Iu = √2 · | I | · cos (ωt−θ)
Iv = √2 · | I | · cos (ωt−2π / 3−θ)
Iw = √2 · | I | · cos (ωt + 2π / 3−θ)
Can be described. Here, | V | and | I | are the effective values of the phase voltage and phase current, respectively. Therefore, the instantaneous power of each phase is as follows.

Pu=|V|・|I|・{cos(2ωt−θ)+cosθ}
Pv=|V|・|I|・{cos(2ωt−2π/3−θ)+cosθ}
Pw=|V|・|I|・{cos(2ωt+2π/3−θ)+cosθ}
また、全相の総電力は、これらを足し合わせた以下となる。
Pu = | V | · | I | · {cos (2ωt−θ) + cosθ}
Pv = | V | · | I | · {cos (2ωt−2π / 3−θ) + cos θ}
Pw = | V | · | I | · {cos (2ωt + 2π / 3−θ) + cos θ}
The total power of all phases is the sum of these.

P=Pu+Pv+Pw=3・|V|・|I|・cosθ
即ち、総電力には時間による変動成分はないが、各相の瞬時電力に着目すると、第1項が無効電力相当で、出力の2倍の周波数、1/2の力率角の位相差をもつ正弦波となる。直流電圧はこの無効電力に応じて変動する。
P = Pu + Pv + Pw = 3 · | V | · | I | · cos θ
That is, the total power has no time-dependent fluctuation component, but focusing on the instantaneous power of each phase, the first term is equivalent to reactive power, and the phase difference of twice the output frequency and half the power factor angle. It has a sine wave. The DC voltage varies according to this reactive power.

図8は特許文献1に示された電力変換装置の動作説明図であり、各相の出力電圧、出力電流及び出力瞬時電力の波形をU相の出力電圧位相を基準に示したものである。電力変換装置の出力電圧のU相、V相及びW相の各相は互いに120度の位相差を持っている。また各相の出力電流は各相の出力電圧に対して一定の位相差を持って出力される。各相の出力瞬時電力は各相の電圧と電流の積で求まる。この各相の出力瞬時電力は図8に示したように出力電圧位相によって大きく変動する。   FIG. 8 is an operation explanatory diagram of the power conversion device disclosed in Patent Document 1, and shows the waveforms of the output voltage, output current, and output instantaneous power of each phase with reference to the output voltage phase of the U phase. The U phase, V phase, and W phase of the output voltage of the power converter have a phase difference of 120 degrees. The output current of each phase is output with a certain phase difference with respect to the output voltage of each phase. The instantaneous output power of each phase is obtained by the product of the voltage and current of each phase. The output instantaneous power of each phase varies greatly depending on the output voltage phase as shown in FIG.

若し電力変換装置が共通の直流リンク部を持つ通常の電力変換装置であれば、各相毎の出力瞬時電力の和である電力変換装置全体の出力瞬時電力は一定となるため、コンバータ側から供給しなければならない電力は出力電圧位相によらず、一定となる。   If the power converter is a normal power converter with a common DC link, the output instantaneous power of the entire power converter, which is the sum of the output instantaneous power for each phase, is constant. The power to be supplied is constant regardless of the output voltage phase.

ところが、この特許文献1に示された電力変換装置の場合は、各相毎に独立した直流リンク部を持つ単位インバータで構成されているため、各相を構成する単位インバータの出力瞬時電力は各相の出力瞬時電力と等しくなり、出力電圧位相によって変圧器の2次巻線からコンバータ、直流リンク部を介して供給される単相インバータの出力瞬時電力は大きく変動する。   However, in the case of the power conversion device shown in Patent Document 1, since it is composed of unit inverters having independent DC link portions for each phase, the output instantaneous power of the unit inverters constituting each phase is The output instantaneous power of the single-phase inverter supplied from the secondary winding of the transformer via the converter and the DC link unit varies greatly depending on the output voltage phase.

直流電圧が各相で同一であると仮定しているPWM制御回路では、この直流電圧の変動により、出力電流が歪むこととなる。この電流歪みを抑えるために、従来は大きな平滑コンデンサが必要であった。しかし、このような大きな平滑コンデンサは、外形的にも、経済的にも問題があった。   In the PWM control circuit that assumes that the DC voltage is the same in each phase, the output current is distorted due to the fluctuation of the DC voltage. In order to suppress this current distortion, a large smoothing capacitor has been conventionally required. However, such a large smoothing capacitor has a problem in terms of appearance and economy.

本発明は上記問題点に鑑みて為されたもので、電圧変動を補正することにより、各相の出力電流の歪みを低減し、大きな平滑コンデンサを必要としない電力変換装置を提供することを目的とする。   The present invention has been made in view of the above problems, and an object of the present invention is to provide a power conversion device that reduces distortion of output current of each phase by correcting voltage fluctuation and does not require a large smoothing capacitor. And

上記目的を達成するため、本発明の第1の発明の電力変換装置は、直流電源から平滑コンデンサを介し、単相交流出力を得る少なくとも1台の単位インバータの出力で夫々各相を形成するように構成した多相インバータと、この多相インバータに電圧指令を与えて出力を制御する制御手段と、前記単位インバータの各々の直流電圧を直接または間接的に検出する検出手段と、前記多相インバータの各相の電圧指令に補正を加える電圧指令補正手段とを備え、前記電圧指令補正手段は、前記検出手段で検出された信号を用いて前記多相インバータの各相の直流電圧の変動分を求める演算手段を有し、この演算手段の演算結果により前記多相インバータの各相の電圧指令を補正することを特徴としている。   In order to achieve the above object, the power converter of the first invention of the present invention forms each phase with the output of at least one unit inverter that obtains a single-phase AC output from a DC power source through a smoothing capacitor. A multi-phase inverter configured as described above, a control means for giving a voltage command to the multi-phase inverter to control its output, a detection means for directly or indirectly detecting each DC voltage of the unit inverter, and the multi-phase inverter Voltage command correction means for correcting the voltage command of each phase of the multi-phase inverter using the signal detected by the detection means. It has a calculating means for obtaining, and the voltage command of each phase of the multiphase inverter is corrected by the calculation result of the calculating means.

また、本発明の第2の発明の電力変換装置は、直流電源から平滑コンデンサを介し、単相交流出力を得る少なくとも1台の単位インバータの出力で夫々各相を形成するように構成した多相インバータと、この多相インバータに電圧指令を与えて出力を制御する制御手段と、前記単位インバータの各々の出力電圧及び出力電流を、直接または間接的に検出する検出手段と、前記多相インバータの各相の電圧指令に補正を加える電圧指令補正手段とを備え、前記電圧指令補正手段は、前記検出手段により得られた信号を用いて前記多相インバータの各相の直流電圧の変動分に相当する無効電力を求める演算手段を有し、この演算手段の演算結果により前記多相インバータの各相の電圧指令を補正することを特徴としている。   The power conversion device according to the second aspect of the present invention is a polyphase that is configured so that each phase is formed by an output of at least one unit inverter that obtains a single-phase AC output from a DC power source through a smoothing capacitor. An inverter, a control means for giving a voltage command to the multi-phase inverter to control the output, a detection means for directly or indirectly detecting each output voltage and output current of the unit inverter, and the multi-phase inverter Voltage command correction means for correcting the voltage command of each phase, and the voltage command correction means corresponds to the variation of the DC voltage of each phase of the multiphase inverter using the signal obtained by the detection means And calculating a reactive power, and correcting a voltage command for each phase of the multi-phase inverter based on a calculation result of the calculation means.

本発明によれば、各相の直流電圧または無効電力の比例成分で、各相の電圧指令を補正するようにしているので、各相の出力電流の歪みを低減し、大きな平滑コンデンサを必要としない電力変換装置を提供することができる。   According to the present invention, since the voltage command of each phase is corrected with the proportional component of the DC voltage or reactive power of each phase, the distortion of the output current of each phase is reduced, and a large smoothing capacitor is required. It is possible to provide a power conversion device that does not.

以下、本発明の実施例を図面を参照して説明する。   Embodiments of the present invention will be described below with reference to the drawings.

以下に、本発明の実施例1に係る電力変換装置を図1乃至図3を参照して説明する。図1は本発明の電力変換装置の回路構成図である。   Below, the power converter concerning Example 1 of the present invention is explained with reference to Drawing 1 thru / or Drawing 3. FIG. 1 is a circuit configuration diagram of a power converter according to the present invention.

単位インバータ1U、1V及び1Wは単相出力インバータであり、その出力をY接続することにより3相インバータを構成し、交流電動機2に3相交流電力を供給している。単位インバータ1U、1V及び1Wは、詳細を後述する主制御回路3からの電圧指令によって、所望の周波数成分を持つ電圧を出力するように制御されている。また、電圧指令補正回路4は、各々の単位インバータ1U、1V及び1Wの直流電圧の変動分を求め、主制御回路3からの電圧指令を補正するための電圧補正指令を出力する。補正された電圧指令は、図示しないPWM制御回路を介して単位インバータ1U、1V及び1Wを制御している。   The unit inverters 1U, 1V, and 1W are single-phase output inverters. The outputs of the unit inverters 1U, 1V, and 1W are Y-connected to form a three-phase inverter, and supply three-phase AC power to the AC motor 2. The unit inverters 1U, 1V and 1W are controlled so as to output a voltage having a desired frequency component according to a voltage command from the main control circuit 3 which will be described in detail later. Further, the voltage command correction circuit 4 obtains a variation in the DC voltage of each unit inverter 1U, 1V, and 1W, and outputs a voltage correction command for correcting the voltage command from the main control circuit 3. The corrected voltage command controls the unit inverters 1U, 1V and 1W via a PWM control circuit (not shown).

単位インバータ1の内部回路構成を図2に示す。直流電源11の出力を平滑コンデンサ12を介し、スイッチング素子13AP、13AN、13BP及び13BNで構成される単相インバータ回路に供給する。各々のスイッチング素子13には逆並列にフライホイールダイオードが接続されている。上記単相インバータ回路の出力端子A、Bから交流出力が得られる。尚、直流電源11は図2に示されたようなバッテリーを用いても良いが、交流電源をコンバータを用いて整流して得るようにしても良い。   The internal circuit configuration of the unit inverter 1 is shown in FIG. The output of the DC power supply 11 is supplied through a smoothing capacitor 12 to a single-phase inverter circuit composed of switching elements 13AP, 13AN, 13BP, and 13BN. A flywheel diode is connected to each switching element 13 in antiparallel. An AC output is obtained from the output terminals A and B of the single-phase inverter circuit. The DC power source 11 may use a battery as shown in FIG. 2, but the AC power source may be rectified using a converter.

次に、主制御回路3の詳細構成ついて説明する。   Next, the detailed configuration of the main control circuit 3 will be described.

トルク設定器5で与えられたトルク基準T*は、磁束設定器6で設定された励磁指令Φ*で除算されてトルク電流基準Iq*に変換される。また、励磁指令Φ*は演算により励磁電流基準Id*に変換される。   The torque reference T * given by the torque setting device 5 is divided by the excitation command Φ * set by the magnetic flux setting device 6 and converted into a torque current reference Iq *. Further, the excitation command Φ * is converted into an excitation current reference Id * by calculation.

一方、3相2相変換器9は電流検出器8A、8B及び8Cで検出された交流電動機2の各相の電流を直交変換し、フィードバックトルク電流Iq及びフィードバック励磁電流Idを得る。これらのフィードバック電流Iq及びIdは上述のトルク電流基準Iq*及び励磁電流基準Id*と夫々比較され、夫々の偏差がゼロになるように、電流制御器7A及び7Bがq軸およびd軸の電圧基準Vq*及びVd*を夫々制御する。ここで得られたq軸およびd軸の電圧基準Vq*及びVd*は、2相3相変換器10により3相の電圧基準Vu*、Vv*及びVw*に変換される。   On the other hand, the three-phase to two-phase converter 9 orthogonally converts the currents of the respective phases of the AC motor 2 detected by the current detectors 8A, 8B and 8C to obtain a feedback torque current Iq and a feedback excitation current Id. These feedback currents Iq and Id are compared with the above-described torque current reference Iq * and excitation current reference Id *, respectively, and the current controllers 7A and 7B are connected to the q-axis and d-axis voltages so that the respective deviations become zero. References Vq * and Vd * are controlled. The q-axis and d-axis voltage references Vq * and Vd * obtained here are converted into three-phase voltage references Vu *, Vv * and Vw * by the two-phase / three-phase converter 10.

また、トルク基準T*と励磁指令Φ*から演算によりすべり角周波数ωsを求め、これにフィードバック角速度ωmを加えることにより電力変換装置の出力角周波数ω1を決定する。この出力角周波数ω1を積分して得られる出力位相基準θ1を、前述した3相2相変換器9の位相基準とするとともに、2相3相変換器10から3相の電圧基準Vu*、Vv*及びVw*を求めるための位相基準としている。   Further, the slip angular frequency ωs is obtained by calculation from the torque reference T * and the excitation command Φ *, and the output angular frequency ω1 of the power converter is determined by adding the feedback angular velocity ωm thereto. The output phase reference θ1 obtained by integrating the output angular frequency ω1 is used as the phase reference of the three-phase two-phase converter 9 described above, and the three-phase voltage references Vu * and Vv from the two-phase three-phase converter 10. * And Vw * are used as phase references.

次に電圧指令補正回路4の詳細について説明する。図3に電圧指令補正回路4のブロック構成図を示す。単位インバータ1U、1V及び1Wの夫々の直流電圧値VDCu、VDCv及びVDCwの平均値を、平均値回路41で得、得られた平均値と夫々の直流電圧値VDCu、VDCv及びVDCwの差に比例したeu,ev,ewを電圧指令の補正量として、元の電圧指令Vu*、Vv*及びVw*に夫々加算補正する。このようにして補正された電圧指令は、前述したように、図示しないPWM制御回路によりゲートパルスに変換され、単位インバータ1のスイッチング素子13に供給される。   Next, details of the voltage command correction circuit 4 will be described. FIG. 3 shows a block diagram of the voltage command correction circuit 4. The average value of the DC voltage values VDCu, VDCv and VDCw of the unit inverters 1U, 1V and 1W is obtained by the average value circuit 41, and is proportional to the difference between the obtained average value and the DC voltage values VDCu, VDCv and VDCw. The corrected eu, ev, and ew are used as correction amounts for the voltage command, and are added to the original voltage commands Vu *, Vv *, and Vw * for correction. The voltage command corrected in this way is converted into a gate pulse by a PWM control circuit (not shown) and supplied to the switching element 13 of the unit inverter 1 as described above.

以下に実施例1の作用効果について説明する。   The operational effects of the first embodiment will be described below.

通常、PWM制御は、時間平均電圧を制御するものであるので、図2に示す2レベルインバータを適用した場合、直流電圧をVdc、オン時間比率をTonとすると、
出力電圧の平均値Voutは以下となる。
Normally, PWM control is to control the time average voltage. Therefore, when the two-level inverter shown in FIG. 2 is applied, assuming that the DC voltage is Vdc and the on-time ratio is Ton,
The average value Vout of the output voltage is as follows.

Vout=Ton・Vdc (1)
オン時間比率Tonは、PWM回路に与える電圧指令V*に比例するので、比例係数αを用いて、
Vout=α・V*・Vdc (2)
と表せる。
Vout = Ton · Vdc (1)
Since the on-time ratio Ton is proportional to the voltage command V * given to the PWM circuit, the proportional coefficient α is used,
Vout = α · V * · Vdc (2)
It can be expressed.

一方、d、q軸上の制御量は、直流量として扱われ、各電圧、電流は、各相の実効値の平均値として扱われる。(2)式においてはVdcが一定であることを前提にしているが、実際のPWM出力Vout^は、変動する瞬時直流電圧によって出力電圧が決まり、この瞬時直流電圧をVdc^と書き直すと、次式となる。   On the other hand, the control amount on the d and q axes is treated as a direct current amount, and each voltage and current is treated as an average value of effective values of each phase. In the equation (2), it is assumed that Vdc is constant, but the actual PWM output Vout ^ is determined by the changing instantaneous DC voltage, and when this instantaneous DC voltage is rewritten as Vdc ^, It becomes an expression.

Vout^=α・V*・Vdc^ (3)
したがって、実電圧の不足分は、(2)−(3)式より次式となる。
Vout ^ = α · V * · Vdc ^ (3)
Accordingly, the shortage of the actual voltage is expressed by the following equation from equations (2)-(3).

Vout−Vout^=α・V*・(Vdc−Vdc^) (4)
ここで、(4)式を(α・Vdc^)で除算したものが補正分の電圧基準であるので、これをeとおくと、
e={(Vdc−Vdc^)/Vdc}・V* (5)
従ってeを用いて出力するべきVoutを記述すると、以下となる。
Vout−Vout ^ = α · V * · (Vdc−Vdc ^) (4)
Here, what is obtained by dividing equation (4) by (α · Vdc ^) is a voltage reference for correction.
e = {(Vdc−Vdc ^) / Vdc} · V * (5)
Therefore, Vout to be output using e is described as follows.

Vout=α・(V*+e)・Vdc^ (6)
以上のようにして、変動する各単相インバータの直流電圧Vdc^に応じて、電圧基準を補正することにより、出力すべき電圧が正しく得られ、電圧の変動に起因する電流の歪みを低減することが可能となる。
Vout = α · (V * + e) · Vdc ^ (6)
As described above, by correcting the voltage reference according to the varying DC voltage Vdc ^ of each single-phase inverter, the voltage to be output can be obtained correctly, and the distortion of the current due to the voltage fluctuation is reduced. It becomes possible.

尚、実施例1では、所謂ベクトル制御によって、電圧、電流指令値を与えたが、例えばV/F制御などによって電圧及び電流指令を与えるような他の制御システムにおいても、同様の効果が得られる。   In the first embodiment, the voltage and current command values are given by so-called vector control, but the same effect can be obtained in other control systems that give the voltage and current commands by V / F control, for example. .

また、本実施例では、単位インバータ1を3台用いて3相インバータを構成する例を示しているが、インバータは多相インバータとしても良く、多相インバータの各相は単位インバータ1の単相出力を複数台直列に接続するようにしても良い。   Further, in this embodiment, an example in which a three-phase inverter is configured by using three unit inverters 1 is shown, but the inverter may be a multi-phase inverter, and each phase of the multi-phase inverter is a single phase of the unit inverter 1. A plurality of outputs may be connected in series.

以上説明したように、本発明によれば、各相の直流電圧の比例成分で、各相の電圧指令を補正するようにしたので、出力電流の歪みを低減でき、平滑コンデンサの容量を低減することが可能となる。   As described above, according to the present invention, the voltage command of each phase is corrected by the proportional component of the DC voltage of each phase, so that distortion of output current can be reduced and the capacity of the smoothing capacitor can be reduced. It becomes possible.

図4は本発明の実施例2に係る電力変換装置の電圧指令補正回路のブロック構成図である。この実施例2の各部について、図3の実施例1に係る電力変換装置の電圧指令補正回路のブロック構成図と同一部分は同一符号で示し、その説明を省略する。この実施例2が実施例1と異なる点は、図3の平均値回路41に代えて、夫々の直流電圧値VDCu、VDCv及びVDCwの時間平均値を演算する時間平均回路42U、42V及び42Wを夫々設けた点である。   FIG. 4 is a block diagram of a voltage command correction circuit of the power conversion apparatus according to the second embodiment of the present invention. The same parts as those in the block configuration diagram of the voltage command correction circuit of the power conversion apparatus according to the first embodiment shown in FIG. The second embodiment is different from the first embodiment in that time average circuits 42U, 42V and 42W for calculating time average values of the respective DC voltage values VDCu, VDCv and VDCw are provided instead of the average value circuit 41 of FIG. It is a point that each provided.

図4の電圧指令補正回路4Aでは、このように各相の時間平均を用いるが、各相の直流電圧がバランスした状態を考えれば、図3の平均値回路41の出力と時間平均回路42U、42V及び42Wの出力は基本的に同一となる。従って、得られる補正電圧指令eu、ev及びewは実施例1で得られるものと等しくなり、直流電圧の変動に起因する電流の歪みを抑制することが可能となる。   In the voltage command correction circuit 4A of FIG. 4, the time average of each phase is used in this way, but considering the state in which the DC voltage of each phase is balanced, the output of the average value circuit 41 of FIG. The outputs of 42V and 42W are basically the same. Accordingly, the obtained correction voltage commands eu, ev, and ew are equal to those obtained in the first embodiment, and it is possible to suppress current distortion caused by fluctuations in DC voltage.

尚、時間平均を得る方法としては、変動の周波数よりも高い周波数を除去するローパスフィルタを用いる方法や、過去の一定時間の直流電圧値をメモリして平均を求める方法等がある。   As a method for obtaining the time average, there are a method using a low-pass filter that removes a frequency higher than the frequency of fluctuation, a method for obtaining an average by memorizing a DC voltage value of a past fixed time, and the like.

図5は本発明の実施例3に係る電力変換装置の回路構成図である。この実施例3の各部について、図1の実施例1係る電力変換装置の回路構成図と同一部分は同一符号で示し、その説明を省略する。この実施例3が実施例1と異なる点は、直流電圧値VDCu、VDCv及びVDCwを入力とする電圧指令補正回路4に代えて、各相の電圧指令値Vu*、Vv*及びVw*、並びに電流指令値Iu*、Iv*及びIw*を入力とする電圧指令補正回路4Bを設けた点と、d軸、q軸の電流基準Id*、Iq*を各相の電流基準Iu*、Iv*及びIw*に変換する2相3相変換器14を設けた点である。   FIG. 5 is a circuit configuration diagram of a power conversion apparatus according to Embodiment 3 of the present invention. In each part of the third embodiment, the same components as those in the circuit configuration diagram of the power conversion apparatus according to the first embodiment shown in FIG. The third embodiment differs from the first embodiment in that instead of the voltage command correction circuit 4 that receives the DC voltage values VDCu, VDCv, and VDCw, the voltage command values Vu *, Vv *, and Vw * for each phase, and The point that the voltage command correction circuit 4B that receives the current command values Iu *, Iv *, and Iw * is provided, and the d-axis and q-axis current references Id * and Iq * are the current references Iu * and Iv * for each phase. And a two-phase / three-phase converter 14 for converting to Iw *.

図6に電圧指令補正回路4Bのブロック構成図を示す。電圧指令補正回路4Bは、各相の電圧、電流指令値の積を、加算回路43で加算平均し、この加算平均した量と各相の瞬時電力との差分に比例した量を各相毎に電圧基準補正指令eu、ev及びewとして出力する。   FIG. 6 shows a block diagram of the voltage command correction circuit 4B. The voltage command correction circuit 4B adds and averages the product of the voltage and current command values of each phase by the adder circuit 43, and calculates an amount proportional to the difference between the added average amount and the instantaneous power of each phase for each phase. Output as voltage reference correction commands eu, ev and ew.

各相の直流電圧の変動は、各相の無効電力に比例する。上記のように加算平均して得られた量は有効電力であり、各相の瞬時電力からこの有効電力を減算した量が無効電力となる。従って、この無効電力に比例して電圧指令を補正することにより、実施例1と同様の効果が得られる。   The fluctuation of the DC voltage of each phase is proportional to the reactive power of each phase. The amount obtained by averaging as described above is active power, and the amount obtained by subtracting this active power from the instantaneous power of each phase is reactive power. Accordingly, by correcting the voltage command in proportion to the reactive power, the same effect as in the first embodiment can be obtained.

尚、実施例3では、瞬時電力の演算を電圧、電流指令を用いて行ったが、各相の出力電圧、あるいは出力電流を直接検出しても良く、また、指令値と直接検出された出力電流または電圧との組合せを用いて瞬時電力の演算を行っても、同様の効果が得られる。   In the third embodiment, the instantaneous power is calculated using the voltage and current commands. However, the output voltage or output current of each phase may be directly detected, or the output detected directly from the command value. The same effect can be obtained even when the instantaneous power is calculated using a combination of current or voltage.

また、実施例3では、3相の瞬時電力を加算することにより、有効電力を得たが、実施例2と同様に、各相の時間平均を用いて、各相の有効電力を求めても良い。   In Example 3, the effective power was obtained by adding the instantaneous power of the three phases. However, as in Example 2, the active power of each phase can be obtained using the time average of each phase. good.

以上説明したように、各相の直流電圧の比例成分に代えて各相の無効電力量の比例成分で各相の電圧指令を補正するようにしても、出力電流の歪みを低減でき、平滑コンデンサの容量を低減することができる。   As described above, even if the voltage command of each phase is corrected with the proportional component of the reactive power amount of each phase instead of the proportional component of the DC voltage of each phase, the distortion of the output current can be reduced, and the smoothing capacitor Capacity can be reduced.

図7は本発明の実施例4に係る電力変換装置の電圧指令補正回路のブロック構成図である。この実施例4の各部について、図6の実施例3に係る電力変換装置の電圧指令補正回路のブロック構成図と同一部分は同一符号で示し、その説明を省略する。この実施例4が実施例3と異なる点は、各相の無効電力を入力とし全相の2乗平均を演算する2乗平均回路44、この2乗平均回路44の出力である無効電力と加算回路43により加算平均して求めた有効電力から力率を求める正接角演算回路45、並びに2乗平均回路44の出力、前記力率角の1/2の値、及び出力角周波数の2倍の周波数を入力とし、各相の正弦波無効電力量に相当する出力を得る3相正弦波回路46が追加された点である。   FIG. 7 is a block diagram of the voltage command correction circuit of the power conversion apparatus according to the fourth embodiment of the present invention. The same parts as those in the block configuration diagram of the voltage command correction circuit of the power conversion device according to the third embodiment shown in FIG. The fourth embodiment is different from the third embodiment in that a reactive power of each phase is input and a square average circuit 44 that calculates a mean square of all phases, and a reactive power that is an output of the mean square circuit 44 is added. The tangent angle calculation circuit 45 for obtaining the power factor from the active power obtained by the averaging by the circuit 43, and the output of the square average circuit 44, the value of 1/2 of the power factor angle, and twice the output angular frequency A three-phase sine wave circuit 46 that adds an output corresponding to the sine wave reactive power amount of each phase with the frequency as an input is added.

電圧指令補正回路4Cでは、実施例3と同様、電圧、電流指令の積の総和により有効電力を得、有効電力と各相の瞬時電力との差により各相の無効電力を得る。各相の無効電力の実効値の平均値は、2乗平均回路44によって次式の演算を行うことにより得ることができる。尚、Qu、Qv及びQwは各相の無効電力を表し、Qは無効電力の実効値の平均値を表す。   In the voltage command correction circuit 4C, as in the third embodiment, the active power is obtained by the sum of products of the voltage and current commands, and the reactive power of each phase is obtained by the difference between the active power and the instantaneous power of each phase. The average value of the effective values of the reactive power of each phase can be obtained by calculating the following equation by the square average circuit 44. In addition, Qu, Qv, and Qw represent the reactive power of each phase, and Q represents the average value of the effective value of the reactive power.

Q={(Qu+Qv+Qw)/3}1/2 (7)
また、正接角演算回路45により、有効電力と無効電力の正接角を求め、3相正弦波回路46により、以下の式により、各相の電圧指令補正量を決定する。
Q = {(Qu 2 + Qv 2 + Qw 2 ) / 3} 1/2 (7)
The tangent angle calculation circuit 45 obtains the tangent angles of the active power and the reactive power, and the three-phase sine wave circuit 46 determines the voltage command correction amount for each phase by the following equation.

eu=G・Q・cos(ωet−θe) (8)
ev=G・Q・cos(ωet−2π/3−θe) (9)
ew=G・Q・cos(ωet+2π/3−θe) (10)
但し、Gは比例定数、θeは上記正接角の1/2の値であり、またωe=2ω1である。
eu = G · Q · cos (ωet−θe) (8)
ev = G · Q · cos (ωet−2π / 3−θe) (9)
ew = G · Q · cos (ωet + 2π / 3−θe) (10)
However, G is a proportionality constant, θe is a value ½ of the tangent angle, and ωe = 2ω1.

上記(8)乃至(10)式は、無効電力を瞬時値ではなく、振幅と位相で表している。従って、この実施例4によれば、瞬時無効電力を使って電圧基準を補正する実施例3と同様の作用効果が得られる。   In the above formulas (8) to (10), the reactive power is expressed not by an instantaneous value but by an amplitude and a phase. Therefore, according to the fourth embodiment, the same effect as that of the third embodiment in which the voltage reference is corrected using the instantaneous reactive power can be obtained.

尚、実施例4では、瞬時電力の演算を電圧、電流指令で行ったが、各相の出力電圧、あるいは出力電流を直接検出しても良く、また、指令値と直接検出された出力電流または電圧との組合せを用いて瞬時電力の演算を行っても、同様の効果が得られる。   In the fourth embodiment, the instantaneous power is calculated with the voltage and current commands. However, the output voltage or output current of each phase may be directly detected, or the command value and the directly detected output current or Even if the instantaneous power is calculated using a combination with the voltage, the same effect can be obtained.

また、実施例4では、3相の瞬時電力を加算して有効電力を得たが、実施例2と同様に、各相の時間平均を用いて、各相の有効電力を求めても良い。   In the fourth embodiment, the effective power is obtained by adding the instantaneous power of the three phases. However, as in the second embodiment, the active power of each phase may be obtained using the time average of each phase.

更に、実施例4では、総電力の1相あたりの平均電力と、各相の瞬時電力の差により、各相の無効電力を求めたが、例えば、U相については、
Pu=|V|・|I|・{cos(2ωt−θ)+cosθ}
であり、得られた1相あたりの平均電力は、|V|・|I|・cosθに相当する。この平均電力を力率cosθで割れば、皮相電力|V|・|I|が得られるので、これを振幅とし、電圧指令の2倍の周波数、1/2の力率角をもつ無効電力を求めても良い。
Furthermore, in Example 4, the reactive power of each phase was obtained from the difference between the average power per phase of the total power and the instantaneous power of each phase. For example, for the U phase,
Pu = | V | · | I | · {cos (2ωt−θ) + cosθ}
The obtained average power per phase corresponds to | V | · | I | · cos θ. By dividing this average power by the power factor cos θ, the apparent power | V | · | I | is obtained, and this is used as the amplitude, and the reactive power having a frequency twice the voltage command and a power factor angle of 1/2 is obtained. You may ask.

以上の実施例1乃至実施例4で用いる電力変換装置を、電動機制御に用いる場合、総電力を、電圧指令と電流指令の積で計算するのではなく、電圧指令とトルク成分電流の積で得ても、同様の効果が得られる。またこの場合の電圧指令を、電動機の磁束または励磁分電流と電動機の速度との積で得られる電動機誘起電圧を用いても、同様の効果が得られる。   When the power conversion device used in the first to fourth embodiments described above is used for motor control, the total power is not calculated by the product of the voltage command and the current command, but is obtained by the product of the voltage command and the torque component current. However, the same effect can be obtained. In addition, the same effect can be obtained by using a motor induced voltage obtained by the product of the motor magnetic flux or excitation current and the motor speed as the voltage command in this case.

更に、電圧、電流指令の代わりに、直接検出した各相の出力電圧、電流を用いても、同様の効果が得られる。   Further, the same effect can be obtained by using the directly detected output voltage and current of each phase instead of the voltage and current commands.

本発明の実施例1に係る電力変換装置の回路構成図。The circuit block diagram of the power converter device which concerns on Example 1 of this invention. 単位インバータの回路構成図。The circuit block diagram of a unit inverter. 本発明の実施例1に係る電力変換装置の電圧指令補正回路のブロック構成図。The block block diagram of the voltage command correction circuit of the power converter device which concerns on Example 1 of this invention. 本発明の実施例2に係る電力変換装置の電圧指令補正回路のブロック構成図。The block block diagram of the voltage command correction circuit of the power converter device which concerns on Example 2 of this invention. 本発明の実施例3に係る電力変換装置の回路構成図。The circuit block diagram of the power converter device which concerns on Example 3 of this invention. 本発明の実施例3に係る電力変換装置の電圧指令補正回路のブロック構成図。The block block diagram of the voltage command correction circuit of the power converter device which concerns on Example 3 of this invention. 本発明の実施例4に係る電力変換装置の電圧指令補正回路のブロック構成図。The block block diagram of the voltage command correction circuit of the power converter device which concerns on Example 4 of this invention. 電力変換装置の動作説明図。Operation | movement explanatory drawing of a power converter device.

符号の説明Explanation of symbols

1、1U、1V、1W 単位インバータ
2 交流電動機
3 主制御回路
4、4A、4B、4C 電圧指令補正回路
5 トルク設定器
6 磁束設定器
7A、7B 電流制御器
8A、8B、8C 電流検出器
9 3相2相変換器
10 2相3相変換器
11 直流電源
12 平滑コンデンサ
13、13AP、13AN、13BP、13BN スイッチング素子
41 平均値回路
42U、42V、42W 時間平均回路
43 加算回路
44 2乗平均回路
45 正接角演算回路
46 3相正弦波回路
1, 1U, 1V, 1W Unit inverter 2 AC motor 3 Main control circuit 4, 4A, 4B, 4C Voltage command correction circuit 5 Torque setting device 6 Magnetic flux setting device 7A, 7B Current controller 8A, 8B, 8C Current detector 9 Three-phase two-phase converter 10 Two-phase three-phase converter 11 DC power supply 12 Smoothing capacitor 13, 13AP, 13AN, 13BP, 13BN Switching element 41 Average value circuit 42U, 42V, 42W Time average circuit 43 Adder circuit 44 Square average circuit 45 Tangent angle calculation circuit 46 Three-phase sine wave circuit

Claims (10)

直流電源から平滑コンデンサを介し、単相交流出力を得る
少なくとも1台の単位インバータの出力で夫々各相を形成するように構成した多相インバータと、
この多相インバータに電圧指令を与えて出力を制御する制御手段と、
前記単位インバータの各々の直流電圧を直接または間接的に検出する検出手段と、
前記多相インバータの各相の電圧指令に補正を加える電圧指令補正手段と
を備え、
前記電圧指令補正手段は、
前記検出手段により得られた信号を用いて前記多相インバータの各相の直流電圧の変動分を求める演算手段を有し、
この演算手段の演算結果により前記多相インバータの各相の電圧指令を補正することを特徴とする電力変換装置。
A multi-phase inverter configured to form each phase with the output of at least one unit inverter that obtains a single-phase AC output from a DC power source through a smoothing capacitor;
Control means for controlling the output by giving a voltage command to the multi-phase inverter;
Detecting means for directly or indirectly detecting the DC voltage of each of the unit inverters;
Voltage command correction means for correcting the voltage command of each phase of the multi-phase inverter,
The voltage command correction means includes
Using a signal obtained by the detection means, calculating means for obtaining a variation in the DC voltage of each phase of the multi-phase inverter,
A power conversion device, wherein the voltage command of each phase of the multiphase inverter is corrected based on the calculation result of the calculation means.
前記演算手段は、
前記多相インバータの全相の直流電圧の平均値と、
前記多相インバータの各相の直流電圧との差分を夫々求めることを特徴とする請求項1に記載の電力変換装置。
The computing means is
An average value of DC voltages of all phases of the multi-phase inverter;
The power conversion device according to claim 1, wherein a difference from a DC voltage of each phase of the multiphase inverter is obtained.
前記演算手段は、
前記多相インバータの各相毎に、
直流電圧と直流電圧の時間平均値との差分を夫々求めることを特徴とする請求項1に記載の電力変換装置。
The computing means is
For each phase of the multiphase inverter,
The power converter according to claim 1, wherein a difference between the DC voltage and the time average value of the DC voltage is obtained.
直流電源から平滑コンデンサを介し、単相交流出力を得る
少なくとも1台の単位インバータの出力で夫々各相を形成するように構成した多相インバータと、
この多相インバータに電圧指令を与えて出力を制御する制御手段と、
前記単位インバータの各々の出力電圧及び出力電流を、直接または間接的に検出する検出手段と、
前記多相インバータの各相の電圧指令に補正を加える電圧指令補正手段と
を備え、
前記電圧指令補正手段は、
前記検出手段により得られた信号を用いて前記多相インバータの各相の直流電圧の変動分に相当する無効電力を求める演算手段を有し、
この演算手段の演算結果により前記多相インバータの各相の電圧指令を補正することを特徴とする電力変換装置。
A multi-phase inverter configured to form each phase with the output of at least one unit inverter that obtains a single-phase AC output from a DC power source through a smoothing capacitor;
Control means for controlling the output by giving a voltage command to the multi-phase inverter;
Detecting means for directly or indirectly detecting the output voltage and output current of each of the unit inverters;
Voltage command correction means for correcting the voltage command of each phase of the multi-phase inverter,
The voltage command correcting means is
Using arithmetic means for obtaining reactive power corresponding to the variation of the DC voltage of each phase of the multiphase inverter using the signal obtained by the detection means;
A power conversion device, wherein the voltage command of each phase of the multiphase inverter is corrected based on the calculation result of the calculation means.
前記演算手段は、
前記単位インバータの出力電圧と出力電流の積を全相分加算して得た瞬時電力の1相あたりの平均値と、
各相の瞬時電力との差分を夫々求めることを特徴とする請求項4に記載の電力変換装置。
The computing means is
Average value per phase of instantaneous power obtained by adding the product of the output voltage and output current of the unit inverter for all phases;
The power converter according to claim 4, wherein a difference from the instantaneous power of each phase is obtained.
前記演算手段は、
前記単相インバータの出力電圧と出力電流の積を全相分加算して得た瞬時電力の1相あたりの平均値と、各相の瞬時電力との差分を全相分2乗平均して得られる振幅と、
各相の出力電圧または出力電流の周波数の2倍の周波数と、
各相の出力電圧と出力電流から得られる力率角の半分の位相差と
を持つ正弦波の無効電力を各相に対し夫々変換して求めることを特徴とする請求項4に記載の電力変換装置。
The computing means is
Obtained by averaging the average of the instantaneous power per phase obtained by adding the product of the output voltage and output current of the single-phase inverter for all phases and the instantaneous power of each phase for all phases. Amplitude to be
Twice the frequency of the output voltage or output current of each phase;
5. The power conversion according to claim 4, wherein sine wave reactive power having an output voltage of each phase and a phase difference of half of the power factor angle obtained from the output current is obtained by converting each phase. apparatus.
前記演算手段は、
前記単相インバータの出力電圧と出力電流の積を全相分加算して得た瞬時電力の1相あたりの平均値を力率で除算して得られる振幅と、
各相の出力電圧または出力電流の周波数の2倍の周波数と、
各相の出力電圧と出力電流から得られる力率角の半分の位相差と
を持つ正弦波の無効電力を各相に対し夫々変換して求めることを特徴とする請求項4に記載の電力変換装置。
The computing means is
The amplitude obtained by dividing the average value per phase of instantaneous power obtained by adding the product of the output voltage and output current of the single-phase inverter for all phases, by the power factor;
Twice the frequency of the output voltage or output current of each phase;
5. The power conversion according to claim 4, wherein sine wave reactive power having an output voltage of each phase and a phase difference of half of the power factor angle obtained from the output current is obtained by converting each phase. apparatus.
直流電源から平滑コンデンサを介し、単相交流出力を得る
少なくとも1台の単位インバータの出力で夫々各相を形成するように構成した多相インバータと、
この多相インバータで駆動される交流電動機と、
前記多相インバータに電圧指令を与えて出力を制御する制御手段と、
前記単位インバータの各々の出力電圧及び出力電流を、直接または間接的に検出する検出手段と、
前記多相インバータの各相の電圧指令に補正を加える電圧指令補正手段と
を備え、
前記電圧指令補正手段は、
前記検出手段により得られた信号を用いて前記多相インバータの各相の直流電圧の変動分に相当する無効電力を求める演算手段を有し、
この演算手段の演算結果により前記多相インバータの各相の電圧指令を補正することを特徴とする電力変換装置。
A multi-phase inverter configured to form each phase with the output of at least one unit inverter that obtains a single-phase AC output from a DC power source through a smoothing capacitor;
AC motor driven by this multi-phase inverter,
Control means for controlling the output by giving a voltage command to the multi-phase inverter;
Detection means for directly or indirectly detecting the output voltage and output current of each unit inverter;
Voltage command correction means for correcting the voltage command of each phase of the multi-phase inverter,
The voltage command correction means includes
Using a signal obtained by the detecting means, and calculating means for obtaining reactive power corresponding to the fluctuation of the DC voltage of each phase of the multi-phase inverter,
A power conversion device, wherein the voltage command of each phase of the multiphase inverter is corrected based on the calculation result of the calculation means.
前記演算手段は、
前記単相インバータの出力電圧と前記交流電動機のトルク成分電流の積から得られる瞬時電力の1相あたりの平均値を力率で除算して得られる振幅と、
各相の出力電圧または出力電流の周波数の2倍の周波数と、
各相の出力電圧と出力電流から得られる力率角の半分の位相差と
を持つ正弦波の無効電力を各相に変換して求めることを特徴とする請求項8に記載の電力変換装置。
The computing means is
The amplitude obtained by dividing the average value per phase of instantaneous power obtained from the product of the output voltage of the single-phase inverter and the torque component current of the AC motor by the power factor;
Twice the frequency of the output voltage or output current of each phase;
9. The power conversion device according to claim 8, wherein a sine wave reactive power having an output voltage of each phase and a phase difference of half of the power factor angle obtained from the output current is obtained by converting each phase.
前記検出手段のうち、出力電圧を検出する検出手段は、
前記交流電動機の磁束または磁束分電流指令と、前記交流電動機の速度との積から得られる電動機誘起電圧によることを特徴とする請求項8に記載の電力変換装置。
Among the detection means, the detection means for detecting the output voltage is:
9. The power conversion device according to claim 8, wherein the power conversion device is based on a motor-induced voltage obtained from a product of a magnetic flux or magnetic flux component current command of the AC motor and a speed of the AC motor.
JP2003336185A 2003-09-26 2003-09-26 Power converter Active JP4401724B2 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP2003336185A JP4401724B2 (en) 2003-09-26 2003-09-26 Power converter

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP2003336185A JP4401724B2 (en) 2003-09-26 2003-09-26 Power converter

Publications (2)

Publication Number Publication Date
JP2005110335A true JP2005110335A (en) 2005-04-21
JP4401724B2 JP4401724B2 (en) 2010-01-20

Family

ID=34532400

Family Applications (1)

Application Number Title Priority Date Filing Date
JP2003336185A Active JP4401724B2 (en) 2003-09-26 2003-09-26 Power converter

Country Status (1)

Country Link
JP (1) JP4401724B2 (en)

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007322145A (en) * 2006-05-30 2007-12-13 Hioki Ee Corp Ac signal measuring instrument and its offset adjustment method
JP2008306805A (en) * 2007-06-06 2008-12-18 Mitsubishi Electric Corp Power conversion device
WO2009084097A1 (en) * 2007-12-27 2009-07-09 Mitsubishi Electric Corporation Controller for power converter
JP2011010476A (en) * 2009-06-26 2011-01-13 Panasonic Corp Motor drive device and electric apparatus employing the same
JP2014220943A (en) * 2013-05-09 2014-11-20 川崎重工業株式会社 Multilevel power conversion device and control method thereof
WO2018159274A1 (en) * 2017-02-28 2018-09-07 株式会社日立産機システム Ac electric motor control device
WO2020217764A1 (en) * 2019-04-23 2020-10-29 日立オートモティブシステムズ株式会社 Power conversion device, and electric vehicle system provided therewith

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007322145A (en) * 2006-05-30 2007-12-13 Hioki Ee Corp Ac signal measuring instrument and its offset adjustment method
JP4648243B2 (en) * 2006-05-30 2011-03-09 日置電機株式会社 AC signal measuring instrument and offset adjustment method thereof
JP2008306805A (en) * 2007-06-06 2008-12-18 Mitsubishi Electric Corp Power conversion device
WO2009084097A1 (en) * 2007-12-27 2009-07-09 Mitsubishi Electric Corporation Controller for power converter
US8750009B2 (en) 2007-12-27 2014-06-10 Mitsubishi Electric Corporation Controller of a power converter that uses pulse width modulation
JP2011010476A (en) * 2009-06-26 2011-01-13 Panasonic Corp Motor drive device and electric apparatus employing the same
JP2014220943A (en) * 2013-05-09 2014-11-20 川崎重工業株式会社 Multilevel power conversion device and control method thereof
WO2018159274A1 (en) * 2017-02-28 2018-09-07 株式会社日立産機システム Ac electric motor control device
JP2018143035A (en) * 2017-02-28 2018-09-13 株式会社日立産機システム Control device for AC motor
US11273712B2 (en) 2017-02-28 2022-03-15 Hitachi Industrial Equipment Systems Co., Ltd. AC electric motor control device
WO2020217764A1 (en) * 2019-04-23 2020-10-29 日立オートモティブシステムズ株式会社 Power conversion device, and electric vehicle system provided therewith
JPWO2020217764A1 (en) * 2019-04-23 2020-10-29

Also Published As

Publication number Publication date
JP4401724B2 (en) 2010-01-20

Similar Documents

Publication Publication Date Title
EP1705789B1 (en) Power inverter system and method of correcting supply voltage of the same
RU2392732C1 (en) Device for control of asynchronous motor vector, method for control of asynchronous motor vector and device for control of asynchronous motor drive
CN101647186B (en) Power conversion system
JP4529113B2 (en) Voltage source inverter and control method thereof
US20140268970A1 (en) Matrix converter and method for controlling matrix converter
JP4401724B2 (en) Power converter
JP2001145398A (en) Inverter control method and inverter control apparatus
EP2763301B1 (en) Power converter control method
JP6503277B2 (en) Controller and AC motor drive
JP5351390B2 (en) Power converter
JP3773794B2 (en) Power converter
JP2733724B2 (en) Current control device for multi-winding AC motor
US10622930B2 (en) Motor control device and control method
JP3236985B2 (en) Control device for PWM converter
JP2006166664A (en) Control method of voltage type inverter
JP2011217575A (en) Power conversion apparatus
JP4581508B2 (en) Control device for voltage source inverter
WO2018061546A1 (en) Control device for power converter
JPH10127056A (en) Pulse width modulation converter device
JP2702936B2 (en) Method and apparatus for controlling voltage source inverter
JP2003088141A (en) Power converter for system linkage
WO2021079919A1 (en) Power conversion device
JP5399955B2 (en) Power converter and control method of power converter
JP6340970B2 (en) Control device
JPH089646A (en) Controller for voltage pwm converter

Legal Events

Date Code Title Description
A621 Written request for application examination

Free format text: JAPANESE INTERMEDIATE CODE: A621

Effective date: 20060623

A977 Report on retrieval

Free format text: JAPANESE INTERMEDIATE CODE: A971007

Effective date: 20090220

A131 Notification of reasons for refusal

Free format text: JAPANESE INTERMEDIATE CODE: A131

Effective date: 20090224

A521 Written amendment

Free format text: JAPANESE INTERMEDIATE CODE: A523

Effective date: 20090424

TRDD Decision of grant or rejection written
A01 Written decision to grant a patent or to grant a registration (utility model)

Free format text: JAPANESE INTERMEDIATE CODE: A01

Effective date: 20091013

A01 Written decision to grant a patent or to grant a registration (utility model)

Free format text: JAPANESE INTERMEDIATE CODE: A01

A61 First payment of annual fees (during grant procedure)

Free format text: JAPANESE INTERMEDIATE CODE: A61

Effective date: 20091028

R150 Certificate of patent or registration of utility model

Ref document number: 4401724

Country of ref document: JP

Free format text: JAPANESE INTERMEDIATE CODE: R150

Free format text: JAPANESE INTERMEDIATE CODE: R150

FPAY Renewal fee payment (event date is renewal date of database)

Free format text: PAYMENT UNTIL: 20121106

Year of fee payment: 3

FPAY Renewal fee payment (event date is renewal date of database)

Free format text: PAYMENT UNTIL: 20121106

Year of fee payment: 3

FPAY Renewal fee payment (event date is renewal date of database)

Free format text: PAYMENT UNTIL: 20131106

Year of fee payment: 4

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250