JP2002518971A - Power supply method for electronically rectified polyphase motor and power supply circuit for implementing the method - Google Patents

Abstract

SUMMARY OF THE INVENTION The present invention is directed to passive electrical filtering downstream of a power supply (A) for attenuating rapid fluctuations in a power flow supplied from the power supply (A), and a command indicating a passing state and a blocking state. Using a flexible switch unit, each combination of the states of the switch defines a conversion arrangement, the conversion of the voltage supplied by the power supply (A) for powering the phases of the motor (M) and the current command ( Motor (M) initiated by phase excitation and demagnetization commands, with regulation of the supply current before and after (Icons) and a plurality of sequencing periods in which each cycle does not change the excitation and demagnetization commands. And a method for feeding an electronically rectified multi-phase motor (M) from a sequencing power supply (A) in a cycle of excitation and demagnetization of the phase. The method further comprises a plurality of translation arrangement pairs such that during at least one sequencing period per cycle, the average current of the current adheres to the current command (Icons) as closely as possible.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001] The present invention relates to a power supply method for an electronically rectified polyphase motor. And a feed circuit using the method.

BACKGROUND OF THE INVENTION The power supply from a single-phase network of an electronically commutated polyphase motor is generally operated on the basis of position commands and information issued by a pickup in order to supply each phase of the motor. The rectification stage and the converter stage, including the means for electronic rectification, are implemented. The present invention relates to, but is not limited to, the case of an electronically rectified variable reluctance motor powered by an output converter.

In an actual power supply method of an electronic commutation motor, a current generated from a power supply is subjected to disturbances that affect various frequencies in a frequency domain. This obstruction caused CEI 610
The high frequency value of the current approved in 00-3-2 may be exceeded. The actual solution to this problem is to select the power supply current in order to remove the disturbance caused by the tuning of the current above the frequency in that region. For example, a passive (mainly composed of filters L and C) or active (PFC "power factor correction" type) filter is inserted between the rectification stage and the converter stage. The addition of the filter PFC upstream of the converter stage requires a great deal of additional expense, resulting in operating powers in excess of several hundred watts, an unacceptable wattage of electronics.

According to document FR2 744 577 in the name of the applicant of the present invention, a method for powering a polyphase motor with an electronically rectified variable reluctance from a rectified power supply comprises an excitation sequence during which the rectified voltage is applied to its phase. The degaussing sequence during which the rectified reverse voltage affects its phase, ie the detection of the disturbance affects the current generated from the rectified power supply, and is currently stored in at least one phase corresponding to this detection. It has been found that the magnetic energy involves a sequence of free rings during which it is significantly conserved.

Therefore, the actual power supply method cannot make the motor function over a wide range,
Obviously, it is not satisfactory because of the need for expensive filter equipment. In particular, no economically satisfactory solution exists in providing an efficient control of the converter supply current.

DISCLOSURE OF THE INVENTION It is an object of the present invention to propose a method for powering an electronically commutated motor with more flexible controls than current methods and remedying this drawback, The present invention clears the practical constraints on electromagnetic compatibility without the need for a powerful filter device such as a PFC. These objects are to provide a method of feeding an electronically rectified multi-phase motor from a power supply,-a passive electrical filtering downstream of the power supply to attenuate rapid fluctuations of the power supply current supplied by said power supply; The conversion of the voltage supplied by the power supply for powering the phases of the motor, using a commandable switch unit indicating a blocking state, each combination of the states of said switch defining a conversion arrangement (conversion configuration) -Adjustment of the supply current before and after the current command, using the alternation of the two conversion arrangements;-determination of the average supply current;-a plurality in each cycle in which the excitation and demagnetization commands do not change. And a sequence of motor phase excitation and demagnetization cycles initiated by the phase excitation and demagnetization instructions having a sequencing period of .

According to the invention, the method uses a plurality of pairs of conversion arrangements such that during at least one sequencing cycle per cycle, the average current of the current obeys the current command as closely as possible.

Therefore, this power supply method minimizes the cost of efficiently controlling the power supply current, and contributes to optimizing the power factor and satisfying the electromagnetic compatibility constraint. Furthermore, the supply method according to the invention makes it possible to considerably attenuate the abnormal noise generated by the motor thus supplied.

Here, for each sequencing cycle, a cycle during which a command or instruction issued by the sequencer does not change is defined. It is worth noting that in a sequencing cycle, two consecutive arrangement pairs can have the same or equivalent arrangement (configuration).

In a preferred form in carrying out the method according to the invention, it further selects an arrangement pair which makes it possible to generate two values of the supply current which enclose the current command as closely as possible, It is configured to select a pair of arrangements that are combined to take into account excitation or demagnetization commands.

The power supply method according to the present invention is configured to use a series of arrangement pairs defined in advance in response to an excitation or demagnetization command.

[0012] Furthermore, when two power supply currents surrounding the current command can no longer be generated by the current configuration pair, a transition from the current configuration pair to the next configuration pair can be planned.

Each time the period is initialized, the first configuration pair belonging to the continuation of the predefined pair is determined according to the last active configuration pair of the previous period, and then the first configuration pair is used. It is advantageous to plan the configuration.

For example, one of the selected arrangement pairs may include at least one freewheel state.

In particular, when the power supply method according to the present invention is implemented, two consecutive arrangement pairs have the same or equivalent arrangement that generates substantially the same potential difference with respect to the motor phase in the sequencing cycle. You can plan.

In a first implementation, the power supply is a rectified AC voltage source, and the current command exhibits a nearly rectified limit with the power supply.

In a second method of realization, the power supply is a substantially constant power supply and has a substantially continuous current command.

In considering the invention from another aspect, a circuit has been proposed for powering an electronically rectified polyphase motor from a power supply implementing the method according to the invention, comprising: -A passive electrical filtering means in series with the power supply for attenuating rapid fluctuations of the power supply current supplied from-a commandable switch unit indicating a pass state and a blocking state, each combination of said switch states A converter for supplying power from a filtered power supply for supplying power to the motor phases, which defines the conversion arrangement; means for determining the average supply current of the converter; Means for adjusting the supply current arranged to generate an adjustment logic signal enabling an alternation between the two conversion arrangements responsive to the signals; Le is decomposed into a plurality of sequences cycle instructions transmitted by the sequencer does not change throughout the phase, a phase sequencer for generating a logic signal of instructions defining a cycle of excitation and demagnetization phase consists.

According to the invention, this circuit is arranged between the phase sequencer and the converter and is arranged in such a way that, during each sequencing cycle defined by the phase sequencer, the average current of the converter adheres to the current command as closely as possible. A selection device configured to use the arrangement pairs in succession.

From the phase sequencer, a logic signal is generated which defines the excitation and demagnetization cycles of the phase, depending on the direction of rotation of the motor and the average machine required counter-direction. .

[0021] The selection device is specially configured to select an arrangement pair which allows to generate two values of the supply current, which enclose the current command as closely as possible, and to take into account the phase excitation and demagnetization commands. I have.

DETAILED DESCRIPTION OF THE INVENTION Other features and advantages of the present invention will be described in the following description, but the accompanying drawings for illustration do not limit the scope of the present invention. Absent.

Now, an example in which the power supply circuit according to the present invention is executed will be described with reference to FIG. The power supply circuit 1 includes a power conversion chain provided with a filter device 2 connected to a power supply A at an inlet, and a conventional power converter 3 for supplying power to the phase of an electronically rectified multiphase motor M. The power supply circuit 1 further includes an average current regulator 6, a modulation logic signal generator circuit 5 attached to the converter 3, a phase sequencer 7, and a selection device 100 for selecting a pair of arrangements attached to the converter 3. Includes control and command circuits, including:

Next, it will be explained that logic state 1 must correspond to the generation of a power supply current exceeding the current generated by logic state 0 within the same pair of arrangements.

As an example of a case where a power supply circuit is created based on the present invention, the filter 2 is a filter of the type (L, C) when the reference values are L = 1 mH and C = 4.7 μF. . The filter is set such that the average current upstream of the filter is approximately equal to the average current downstream of the filter.

The phase 7 sequencer receives a rotation direction command, a pair code command, and data of a period generator generated from a position pickup or the like. The regulator 6 is a converter 3
Of the power supply current and the current command information Icons. These two pieces of information are equally applied to the selection device 100 connected to the phase 7 sequencer.

A form that may be better implemented is that the average current regulator includes a component extractor 21, in particular, between the converter's power supply current meter and the current command, FIG. 2A
And a frequency limiter 24 for generating a logic signal associated with the periodic variable MLI directly from the outlet, a first structure 20 as shown in FIG.

In another implementation, the regulator comprises an averaging circuit 31 of type R, C, etc. for presenting the average value of the power supply current measurement of the converter, a comparator circuit 32 between the current commands, and a frequency Another structure shown in FIG. 2B may be presented, including a limiter 24.

The most important steps in implementing the most common power supply method in the selection device will now be described with reference to FIG. 3 according to the present invention.

From the sequencer 7, SL of the entire logic signal that defines the cycle of the sequencing T is generated within a period in which the excitation and demagnetization commands do not change. Selection device 10
0 (FIG. 1) takes into account these logical requirements, and Conf1,
Selecting the entire configuration M, Conf2... ConfM, enables compliance with the sequencer requirements. For each selected arrangement, the power supply currents IConf1, IConf2... IConfM of the converter are calculated, in particular using the measured values of the phase currents. Further calculated current IConf and current command ICons
Calculate the error of the current Ierreur equal to the difference between If the current error is positive, select an arrangement that minimizes | Ierreur |
This arrangement is combined with LI logic state 1. If the current error is negative,
The arrangement that minimizes | Ierreur | is combined with the logic level 0 of the command MLI. Both configurations selected in this way are the configuration pair [ConFX,
[CnF Y] is assembled.

When using the power supply method according to the invention corresponding to the version shown in simplified form in FIG. 4, the actual execution takes into account each new request of the sequencer 7 corresponding to the new cycle. , The last paired configuration used is stored. Compatible with this new request pre-defined in memory, pair 1 = Conf1 / Conf2, pair 2 = Conf3 / Conf4,. , Pair C = Conf P / Conf Q. The first pair following this is selected, and the power supply current of converter 3 is measured when the required MLI becomes a new logic 0. If the power supply current of the converter is less than or equal to the current ICons command, the selected pair is maintained. Conversely, if the power supply current exceeds the current command, the next pair in the continuation of the pair is selected to modify the selected arrangement pair.

Referring to FIG. 5 to FIG. 13 and FIG. 17 to FIG. 19, there are several examples in which a pair of the conventional structure of the converter and the arrangement corresponding to the usual power supply method from the motor to the variable reluctance are actually selected. Let me show you. It is worth noting that for FIGS. 5-13 and 17-19 common references to the same components or pairs are used systematically.

First, referring to FIGS. 5A to 7D, consider an output converter 50 including six transistors T 1 to T 6 for supplying power to a three-phase motor. This output converter is connected upstream of the continuous power supply E and is constituted by a type (L, C) filtering layer. This converter presents an asymmetrical conventional three-half bridge structure, each possessing two free-wheeling diodes, to provide a three-phase supply.

The first table shown in FIG. 5A shows an arrangement pair of units used in a direct direction for this feed structure. This means that the three phases U, V W
, And a table consisting of six rows corresponding to the characteristic sequence, in which the state of the transistor of the converter and the percentage of the circulating type change between 0 and 100%, and are represented by the coefficient α. The 18 sequence pairs corresponding to the unique combinations with the command MLI have been rearranged.

As described above, in the case of (W, 4), the power supply current is −Iu−αIv + Iw
It is expressed by the following equation. In this case, Iu, Iv, and Iw represent currents applied to phases U, V, and W, respectively, and coefficient α represents a current that continuously changes between 0 and 1. A coefficient α equal to 1 corresponds to excitation (+ I) or demagnetization (−I), but coefficient α does not correspond to a free wheel state.

The transition to another column occurs at each new cycle of sequencing,
Receive control of sequencer 7.

When it is detected that the current alignment pair is not appropriate, the selection device initiates a transition to each next row in the column.

The arrow in each table indicates the arrangement pair selected first when there is a change in the period. It should be noted that the average power supply current of the converter is continuous whenever the arrangement pairs transition.

In the case of the opposite direction to the sequencer request, reference is made to the corresponding table in an example such as FIG. 5B. It is possible to define such a paired sequence that can be used in both directions of rotation. In this case, only the table shown in FIG. 5C is referred to.

Now, a description will be given of the case where a series of arrangement pairs in the direct direction of rotation shown in FIGS. 6 and 7A to 7D are actually used.

For example, using the equation of current −Iu + αIv−Iw, look at the first arrangement pair of V5 at the intersection of the Vth column and the fifth row in the table of FIG. In the first arrangement pair, the magnetism is removed from the other two phases U and W, while the phase V of the motor is excited by MLI modulation. While the branch line V of the converter keeps passing the T4 low-order transistor, the high-order transistor of T3 is the MLI.
It is controlled by modulation (FIG. 7).

When the sequencer 7 commands a new cycle of sequencing corresponding to the commutation from the phase V to the phase W, the table of FIG. 6 indicates that the transition from the pair V5 to the pair W3 shown in FIG. Indicated by In this second arrangement, phase U is demagnetized and phase W is always powered, but phase V is under the influence of the excitation controlled by the MLI command of the T3 higher order transistor. ing. This transition from the second arrangement pair W3 to the arrangement pair W4 following the same row of the table is operated by a selection device based on the condition of minimizing current errors. In the new arrangement pair W4 (FIG. 7), the T3 high order transistor on branch line V remains open, while the T4 low order transistor is operated in MLI mode;
Thus, the winding V is arranged in a demagnetized state by the free wheel. in this case,
It is noteworthy that the commands of the T3 and T4 transistors can be reversed, thereby forming an equivalent arrangement pair. Next, the selection device 1
The 00 instruction sufficiently removes the magnetism from the two phases U and V and places W5 (FIG. 7) in an excitation situation controlled by the MLI command of the T5 higher order transistor on branch W. Move to Sequencer 7 has phase W
Until it commands a new sequencing cycle corresponding to the commutation of the phase U.

The power supply method according to the present invention can be applied to an output converter 60 having four transistors and four diodes based on the conventional structure shown in FIG. The arrangement pair corresponding to this figure corresponds to the logic state [10
11] and a second arrangement pair associated with the logical state [1001]. In this power supply method, only six arrangement pairs flow in each rotation direction as shown in FIGS. 9A and 9B. Referring to the table of the arrangement pair shown in FIG. 10, the symmetric three-phase power supply of the four-transistor converter structure can also be predicted.

It is also possible to use the method according to the invention for powering a two-phase motor with electronic commutation. With reference to FIGS. 11 and 12, in a first example of application to an output converter 70 consisting of two half-bridges corresponding to asymmetric and necessarily symmetrical feeds, the arrangement pair continues In the case of two rotation directions, it includes eight arrangement pairs that will flow continuously based on the transition indicated by the arrow. FIG.
Is a pair V2 corresponding to the equation of current -αIu + Iv.

In addition, it is possible to consider a two-phase power supply method that is inevitably left and right by connecting to three transistors. This feeding method draws out the four arrangement pairs shown in FIG.

For example, the asymmetry realized by the eight transistor converters T1 to T8 consisting of two complete bridges, which may be used in the operation of an electronic commutation motor with a magnet or a non-periodic motor as shown in FIG. In this case, a series of 16 arrangement pairs shown in FIGS. 15 and 16 are combined with each rotation direction.
In this power supply method, the windings of the two-phase motor are supplied with power in one direction or the other. This results in the cycles of the tables of FIGS. 15 and 16, ie the four columns U +, V +, corresponding to the different combinations applying the supply voltage in the two phases.
Four cycles indicated by U- and V- will be generated. The arrangement pair shown in FIG. 14 is thus shown in the pair V + 2 term and corresponds to the formula of the current -αIu ⁺ + Iv ⁺ .

The performance specific to the power supply method according to the present invention is shown in the time-series charts of FIGS. 17 and 19. Accordingly, the power supply current waveform associated with the converter structure shown in FIG. 17 and shown in the table of FIG. 6 includes the first region of MLI rectification of the current corresponding to the placement pair V5, during a new cycle of sequencing. A second region corresponding to the first pair of arrangements of W3 in that period, starting when the current measured at the level of MLI = 0 exceeds the current command;
Starting when the current measured at the level of MLI = 0, the third area corresponding to the W4 arrangement pair, exceeds the current command, there is a fourth area corresponding to the W5 arrangement.
As soon as a phase commutation command is issued by the sequencer 7, this arrangement pair is stopped in order to carry out the sequence U3, U4, U5 of the new arrangement pair. Due to the rectification process of this arrangement pair, the current command ICo
The power supply average current Ialim can be effectively controlled around ns.

The command C (for the higher and lower order transistors of the same branch line of the converter)
Observing the logic signals TL), C (TH), in this case the branch line W, that the higher and lower order transistors remain commanded to the MLI separately from the end of the sequencing period T I understand.

Next, referring to FIG. 18, when observing a characteristic electric waveform of the output converter instructed by the power supply method according to the present invention, a command C (
The TL) logic signal is in the form of a conventional slot, while the associated higher order IGBT transistor command C (TH) logic signal has an uncut first portion and high frequency modulation. It is in the form of a slot divided into a second part corresponding to the MLI.

The Iphase current in phase shows the first decay region of “controlled MLI” followed by the remaining duration of the lower transistor command cycle after the appearance of an uncut up front at the beginning of the cycle. Followed by the "controlled" MLI region at the end of the command of the upper transistor, and the decay region in the controlled MLI outside the command region of the two transistors, and finally the current release region at the end of the cycle. The appearing electric waveform is shown. Since the power supply current Ialim of the converter is always well controlled around the current command, it has been found that the power supply scheme according to the invention is effective.

As shown in the chronogram of FIG. 19, the effectiveness of the power feeding method according to the present invention is as follows.
It is also effective in the case of a power supply current that needs to comply with the sine curve current command. Thus, the measured power supply current Ialim shows a remarkable sine curve state with a relatively weak amplitude modulation MLI, while the current in the Iphase phase shows a significantly irregular waveform. Is observed.

When simplifying the power supply method according to the present invention, it should be noted that a series of three arrangements of only one switched converter with modulation of the impulse width (MLI) must be selected. is there. However, if this is used, when the instruction sent from the sequencer suddenly changes and an exception occurs, a problem occurs that the arrangement pairs become discontinuous. As an example, there is a case of a request to reverse the rotation direction. In that case, the arrangement pair sequence has no time to operate normally and the first
In this arrangement pair, the continuity of the current consumed by the converter cannot be guaranteed.

In general, the power supply scheme according to the invention can be used with any type of electronically commutated motor (MCE), such as a magnet synchronous motor or a cage asynchronous motor. The number of motor phases is 2, 3, 4 or 5.

If the signal MLI is applied to a switch IGBT, the typical frequency range of this signal will be between 10 and 50 KHz.

It should be noted that the description given here relates only to a very specific example of operation and that each of the three phases can be in a state producing some energy independently. In particular, the phase hysteresis difference can be considered.

Of course, the present invention is not limited to the examples described here, but many modifications can be made to the present invention without departing from the scope of the present invention. Therefore, the phase and the number of electrode pairs of the electronic commutation motor supplied by the present method can be arbitrarily set. Besides, the scheme according to the invention can accept any customary law of adjusting the angle at the start of the excitation and demagnetization sequence. The output switch is not limited to the transistor IBGT proposed in this description, but can be selected to include any other transistor technology. further,
The logic of the commands of the higher and lower order switches can of course be interchanged.

[Brief description of the drawings]

FIG. 1 is a block diagram of a supply circuit according to the present invention.

FIG. 2A shows two methods for performing a feed average current adjustment of a converter.

2A and 2B illustrate two methods of performing a converter average feed current adjustment.

FIG. 3 is a flowchart corresponding to using a power supply method in the most general method according to the present invention.

FIG. 4 is a block diagram corresponding to a particular use of the power supply method according to the invention.

FIG. 5A is a table showing characteristic transitions between configuration pairs for an asymmetric three-phase power supply with six transistors in the direct direction of rotation.

FIG. 5B is a table showing characteristic transitions between pairs of arrangements in the case of an asymmetric three-phase power supply having six transistors in the reverse direction of rotation.

FIG. 5C is a table showing characteristic transitions between a pair of arrangements in the case of a symmetric three-phase power supply having six transistors in both directions of rotation.

FIG. 6 is an example of an actual series of arrangement pairs performed in the case of an asymmetric three-phase power supply with six transistors in the direct direction of rotation.

FIG. 7A is a pair of arrangements of V5, W3, W4 and W5 corresponding to the series of pairs shown in FIG.

7B is a pair of arrangements of V5, W3, W4 and W5 corresponding to the series shown in FIG. 6;

7C is a pair of arrangements of V5, W3, W4 and W5 corresponding to the series shown in FIG. 6;

FIG. 7D is a pair of V5, W3, W4 and W5 arrangements corresponding to the series shown in FIG.

FIG. 8 is an example of an arrangement pair in the case of an asymmetric three-phase power supply including four transistors.

FIG. 9A is a table showing characteristic transitions between pairs of arrangements for an asymmetric three-phase feed with four transistors in each of the direct and reverse directions of rotation.

FIG. 9B is a table showing characteristic transitions between pairs of arrangements for an asymmetric three-phase power supply with four transistors in each of the direct and reverse directions of rotation.

FIG. 10 is a table showing a characteristic transition between a pair of arrangements in the case of a symmetric three-phase power supply including four transistors in both directions of rotation.

FIG. 11 shows an example of an arrangement pair in the case of two-phase power supply with four transistors.

FIG. 12 is a table showing a characteristic transition between a pair of arrangements in the case of two-phase power supply including four transistors in both directions of rotation.

FIG. 13 is a table showing a characteristic transition between a pair of arrangements in the case of two-phase power supply including three transistors in both directions of rotation.

FIG. 14 is an example of a pair of arrangements for an asymmetric two-phase two-way power supply with eight transistors.

FIG. 15 is a table showing characteristic transitions between pairs of arrangements for an asymmetric two-phase two-way power supply with eight transistors in the direct direction of rotation.

FIG. 16 is a table showing a characteristic transition between a pair of arrangements for an asymmetric two-phase two-way feed with eight transistors in reverse rotation.

FIG. 17 is a chronogram showing in detail the control signals of the switches operated from the converter in the power supply circuit, the current in the phase of the motor and the power supply current of the converter according to the invention.

FIG. 18 is a chronogram showing control signals of a switch operated by a converter in a power supply circuit, a current in a phase of a motor, and a power supply current in the case of a constant power supply according to the present invention.

FIG. 19 is a chronogram showing a switch operated by a converter in a power supply circuit according to the present invention, a current in a motor phase in the case of an AC power supply, and a control signal of a power supply current.

──────────────────────────────────────────────────続 き Continuation of the front page (72) Inventors Le Roux, Misiel, Philippe, Josef F-14200, France France, Muline, Cilleman de la Baylier (No address) F term (reference) 5H560 BB03 BB04 BB12 BB16 DC12 EB01 RR04 TT07 TT08 TT15 UA02 XA02

Claims (14)

[Claims] 1. A power supply method for an electronically rectified multi-phase motor (M) from a power supply (A), comprising:-a power supply (A) for attenuating a rapid fluctuation of a power supply flow supplied from the power supply (A);
A) passive electric filtering downstream of: feeding a phase of the motor (M), using a commandable switch unit indicating a pass state and a blocking state, each combination of said switch states defining a conversion arrangement; Conversion of the voltage supplied by the power supply (A) to adjust the power supply current before and after the current command (Icons), using an alternation of the two conversion arrangements; Determining a motor (M) initiated by a phase excitation and demagnetization command, wherein each cycle has a plurality of sequencing periods in which the excitation and demagnetization commands do not change;
) And the sequencing of cycles of demagnetization, and furthermore, during at least one sequencing period of each cycle, a plurality of conversions such that the average current of the current obeys the current command (Icons) as closely as possible. A method characterized by using arrangement pairs. 2. A pair of arrangements (Conf) configured to generate two values of the supply current which further enclose the current command (Icons) as closely as possible and to take into account the phase excitation and demagnetization commands. 2. The method of claim 1, comprising selecting (X, CONf Y). 3. The method according to claim 2, further comprising a continuation of a pair of predefined arrangements in response to excitation and demagnetization commands. 4. The provision of a transition from a current configuration pair to a next configuration pair when the current configuration pair can no longer generate two supply currents that enclose the current command (Icons) as closely as possible. The method according to claim 3, characterized in that: 5. Furthermore, each time the period is initialized, the first arrangement pair belonging to the continuation of the predefined pair according to the last active arrangement pair of the previous period is determined, and then the first arrangement pair is used. 5. The method according to claim 3, further comprising: 6. The method according to claim 2, wherein one of the selected arrangement pairs comprises at least one free-wheel state. 7. A method according to claim 2, wherein during one sequencing period, two consecutive arrangement pairs have an equivalent arrangement that generates substantially the same potential difference with respect to the motor phase.
The method according to any one of the preceding claims. 8. The power supply (A) is a rectified AC voltage source, and the current command (Icons) has a form close to a sine whose phase is almost rectified with the supply voltage.
The method according to any one of the preceding claims. 9. The method according to claim 1, wherein the power supply is a substantially constant voltage source and the current command is in a substantially continuous form. 10. A circuit (1) for powering an electronically rectified multi-phase motor (M) from a power supply (A), comprising:-attenuating rapid fluctuations in the power supply supplied by said power supply (A). Power supply (A
) A passive electrical filtering means in series with: a filter for the phase of the motor (M), comprising a commandable switch unit indicating a pass state and a blocking state, each combination of said switch states defining a conversion arrangement. A converter (3) for supplying power from the power supply subjected to the above-mentioned operation;-means for determining a supply average current of the converter (3);-a response to a logic signal in response to a current command (Icons) and a current measurement; Power supply current adjustment means (6) configured to generate an adjustment logic signal enabling alternating between the two conversion arrangements (Conf X, Conf Y);-each cycle comprises a sequencer ( 7) A phase sequencer for generating a logic signal of an instruction defining a cycle of phase excitation and demagnetization, wherein the instruction issued by 7) is decomposed into a plurality of unchanging sequence periods. (7) and using a method according to any one of the preceding claims, further comprising a cycle arranged between the phase sequencer (7) and the converter (3) and defined by the phase sequencer (7). A selection device arranged to successively use a plurality of conversion arrangement pairs such that the average current of the converter (3) adheres as much as possible to the current command (Icons) during at least one sequencing period of each (1
00). 11. Selecting a pair of arrangements which allows the selection device (100) to generate two values of the supply current which enclose the current command (Icons) as closely as possible, taking into account the commands of phase excitation and demagnetization. The circuit of claim 10, wherein the circuit is configured to: 12. The circuit according to claim 10, wherein the selection device is configured to use a continuation of a predefined pair of arrangements in response to excitation and demagnetization commands. . 13. When the selection device (100) can no longer generate two supply currents which enclose the current command (Icons) as closely as possible, the transition from the current arrangement pair to the next arrangement pair is made. 13. It is configured to order.
The circuit according to claim 1. 14. The selection device (100) determines, each time a period is initialized, the first configuration pair belonging to the continuation of the predefined pair according to the last active configuration pair of the previous period, and then determines the first configuration pair. 14. The circuit according to any one of claims 10 to 13, wherein the circuit is configured to use the following arrangement pairs.