EP4423902A1 - Procédé et système de régulation d'une machine électrique - Google Patents

Procédé et système de régulation d'une machine électrique

Info

Publication number
EP4423902A1
EP4423902A1 EP22808802.7A EP22808802A EP4423902A1 EP 4423902 A1 EP4423902 A1 EP 4423902A1 EP 22808802 A EP22808802 A EP 22808802A EP 4423902 A1 EP4423902 A1 EP 4423902A1
Authority
EP
European Patent Office
Prior art keywords
stator
phase
orthogonal
determined
fluxes
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP22808802.7A
Other languages
German (de)
English (en)
Inventor
Mohamed Ayeb
Florian Bethke
Ludwig Brabetz
Thomas Waldmann
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Volkswagen AG
Original Assignee
Volkswagen AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Volkswagen AG filed Critical Volkswagen AG
Publication of EP4423902A1 publication Critical patent/EP4423902A1/fr
Pending legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/13—Observer control, e.g. using Luenberger observers or Kalman filters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/141—Flux estimation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/18—Estimation of position or speed
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/20—Estimation of torque
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H02P21/28—Stator flux based control
    • H02P21/30—Direct torque control [DTC] or field acceleration method [FAM]
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation

Definitions

  • the invention relates to a method and a system for controlling an electrical machine using measuring coils which are arranged in an air gap between a stator and a rotor of the electrical machine, with a number of phase windings being present which have different to which electrical phases are assigned.
  • electromobility In many industrial areas of application and increasingly also in mobile applications (“electromobility”), electrical machines are used as drive motors with a high level of efficiency and high specific power and power density.
  • control methods which take into account a measured rotor position.
  • optical, inductive position sensors or position sensors based on the Hall effect are used, which i. i.e. R. are arranged outside of the electrical machine and measure a rotation angle of the rotor relative to the stator on the rotor axis.
  • approaches for controlling the electrical machine are also known which do not require a position sensor. According to the state of the art, they are based on an estimate of the position of the rotor relative to the stator using mathematical calculation models of the electrical machine and some easily measurable machine variables, such as voltage setpoints and measured phase currents.
  • the publication WO 2013/079502 A describes, for example, a Hall magnetic field sensor using thin-film technology, which is applied to a surface of a stator pole.
  • the sensor can be used to measure a magnetic flux density in the air gap, which can be used as a control variable for a flux-supported, model-based control.
  • a Hall magnetic field sensor using thin-film technology
  • the sensor can be used to measure a magnetic flux density in the air gap, which can be used as a control variable for a flux-supported, model-based control.
  • Even a production-related fluctuation in the parameters from machine to machine makes a sufficiently accurate estimate of the position of the rotor inadequate for many applications.
  • many of the parameters included in the mathematical calculation model are subject to the influence of different operating conditions, above all the influence of the operating temperature.
  • the operating condition cannot be adequately taken into account in the mathematical calculation model in all cases, or the operating condition cannot be measured with sufficient accuracy in order to be able to be taken into account.
  • the latter applies, for example, to the rotor temperature, which can only be determined precisely during operation with a great deal of technical effort.
  • a measuring coil within an air gap between the rotor and stator of an electrical machine is known in order to determine various properties of the electrical machine during operation.
  • the property of the electrical machine is determined on the one hand using a measured impedance of the measuring coil and on the other hand using an induced voltage in the measuring coil.
  • a rotational position and/or a rotational speed of the rotor relative to the stator can be determined.
  • Magnetic fields from permanent magnets in the rotor can also be determined in permanently excited synchronous or asynchronous machines, which indirectly allow conclusions to be drawn about temperatures in the rotor.
  • the variables obtained in this way can be used within the framework of a model-based control method for the electrical machine.
  • the measuring coil arranged in the air gap can be formed, for example, by a film conductor with imprinted induction loops.
  • a control method can thus advantageously be implemented with a simple and inexpensive sensor.
  • the disadvantage is that a stored computational model of the electrical machine must also be used here, on the basis of which the controlled variables can be approximately determined using the measured values.
  • the consideration e.g. B. a determined rotor temperature improves the quality of the approximation, but does not make it unavoidable.
  • a further object is to describe a system with an electrical machine and such a controller.
  • a method according to the invention of the type mentioned at the outset has the following steps: Magnetic linkage fluxes in the air gap are measured using the measuring coils and magnetic linkage fluxes of the multiple phase windings of the different phases are determined.
  • the magnetic linkage fluxes determined in this way are transformed into a stator-fixed orthogonal coordinate system in order to obtain orthogonal magnetic linkage fluxes.
  • phase currents flowing through the multiple phase windings are measured and transformed into the orthogonal coordinate system fixed to the stator in order to obtain orthogonal phase currents. From this, an instantaneous torque and/or a flux-forming component is determined and the electric machine is controlled based on the instantaneous torque and/or the flux-forming component.
  • the magnetic interlinkage fluxes of the multiple phase windings of the different phases are determined from the measured values of the plurality of measuring coils, preferably taking into account a previously known winding scheme of the phase windings around the stator teeth.
  • the electric machine can be controlled without requiring a position sensor to measure the rotor position and without these variables being estimated using models and possibly being inaccurate.
  • the instantaneous torque is determined using the cross product of the orthogonal magnetic chain flows and the orthogonal phase currents are determined.
  • the instantaneous torque can be compared with a specified torque setpoint value for the purpose of regulation.
  • the flux-forming component of the phase current vector is determined by projecting the phase current vector onto a phase-to-phase flux vector formed from the orthogonal magnetic phase-to-phase fluxes.
  • the flux-forming component of the phase current vector can be compared with a target value for this component, which is determined using the target value of the torque, for example using a specified table.
  • the control can be designed as a field-oriented control or as a direct torque control. These two methods are known in principle--with a different determination of the controlled variables--which means that established control circuits can advantageously be used.
  • a rotor position and/or a rotor speed can also be determined from the orthogonal magnetic linkage fluxes.
  • a plurality of measuring coils are used, each of which is arranged on a stator tooth of the stator.
  • the measuring coils can preferably be planar coils that are applied to foils.
  • Such measuring coils can be made so thin that they can be used in electrical machines with typical air gap widths.
  • the measured phase currents and/or magnetic linkage fluxes are compared with one another, with expected values and/or with previously determined values for diagnostic purposes. In this way, a diagnosis of the electrical machine or its activation can also be carried out while the control method is being executed.
  • the magnitude of the interlinking magnetic fluxes result from the interaction of the energization of the stator windings and the magnetization of the rotor. If there are differences in the relationship between the values or in comparison to earlier measurements, this can indicate errors in the measurement of the currents and/or changes in the rotor magnetization, eg demagnetization. Asymmetries with regard to the various phases can also indicate faults, eg possible interturn faults or line breaks.
  • a system according to the invention for controlling an electrical machine using measuring coils which are arranged in an air gap between a stator and a rotor of the electrical machine, has an evaluation unit for evaluating measured values of the measuring coils and a controller that is value inputs is connected to the evaluation unit.
  • the system is characterized in that the evaluation unit and the controller are set up to carry out an aforementioned method.
  • 1a shows a schematic representation of the principle of an electrical machine
  • FIG. 1b shows a more detailed schematic representation of a pole pitch of the electrical machine shown in FIG. 1;
  • FIG. 2a shows the pole pitch according to FIG. 1b in a representation with magnetic field lines
  • FIG. 2b shows a detail from FIG. 2a with a more detailed representation of the field lines
  • FIG. 3 shows an oblique view of a stator tooth with a measuring coil
  • FIG. 4 shows a schematic representation of a winding diagram of an electrical machine
  • FIG. 6 shows an electrical machine with a control system for carrying out field-oriented control in a block diagram
  • FIG. 7 shows an electrical machine with a control system for carrying out field-oriented control in a block diagram for direct torque control.
  • Figures 1a, b and 2a, b first show an electrical machine 1, which can be controlled with the control method according to the invention.
  • FIG. 1a shows the electrical machine 1 in a cross section in a very schematic representation.
  • the electrical machine 1 has a stator 2, which is designed approximately in the form of a hollow cylinder. Within the stator 2, a rotor 4 is rotatably mounted, with an air gap 3 running around between the stator 2 and the rotor 4.
  • the electrical machine 1 is designed as an internal rotor - the stator 2 is stationary and is outside, while the rotor 4 is rotatably mounted inside the stator 2 .
  • the control method presented as part of this application can also be used for an external rotor machine in which the stator is on the inside in a rotationally fixed manner and the rotor is on the outside in the form of a hollow cylinder and rotates around the stator.
  • the rotor 4 rotates relative to the stator 2 by a magnetic interaction between a magnetic rotor field and a magnetic stator field.
  • the rotor and stator fields are superimposed in the air gap 3 , as a result of which a torque is built up on the rotor 4 in relation to the stator 2 .
  • Stray fields in the rotor 4 or stator 2 which do not close via the air gap 3 and the respective other component, ie the stator 2 and rotor 4, do not contribute to the formation of a torque.
  • control method described below is suitable for an electrical machine 1 designed as a three-phase machine, for example an asynchronous machine or a synchronous machine.
  • FIG. 1a a segment of the electric machine 1 is shown, which is referred to as the pole pitch 5.
  • This pole pitch 5 is shown in more detail in FIG. 1b.
  • FIG. 1b shows that the stator 2 includes a stator yoke 21 and has a plurality of stator teeth 22 directed radially inwards, between which grooves 23 are correspondingly formed.
  • Stator windings 24 which generate the stator magnetic field are arranged in these slots 23 .
  • a stator winding 24 is only indicated in one of the slots 23 in FIG. 1b.
  • the rotor 4 has a rotor yoke 41 in which permanent magnets 42 are embedded.
  • the permanent magnets 42 are surrounded by cavities 43 in the rotor yoke 41 in the radial direction.
  • the electric machine 1 shown is a permanently excited synchronous machine with embedded magnets. This is purely exemplary. It is noted that the control method according to the application can also be used for other types of three-phase machines, for example synchronous machines with separate excitation, synchronous machines with embedded magnets and surface magnets, reluctance machines and asynchronous machines.
  • stator windings 24 are used, which are arranged over the circumference of the stator 2 in the slots 23.
  • Each of the three windings which are also called phase windings, can include several coils.
  • the three phase windings are azimuthally offset from one another, although they can partially overlap.
  • magnetic poles are formed along the circumference of the stator 2, specifically at least one pooled pair, usually a plurality of pole pairs. The azimuthal extent of half a pair of poles corresponds precisely to the pole pitch 5 indicated in FIG. 1a and reproduced in FIG. 1b.
  • FIG. 2a shows pole pitch 5 from FIG. 1b in a representation with magnetic field lines during operation of electrical machine 1.
  • Stator field lines 20 in stator 2 and rotor field lines 40 in rotor 4 can be seen.
  • FIG. 2b shows a detail from FIG. 2a in the area of three stator teeth 22.
  • the stator field lines 20 and the rotor field lines 40 are drawn in with greater density and in more detail.
  • the figure clearly shows the bundling of the rotor field lines 40 by the permanent magnet 42 and the routing of the rotor field lines 40 around the cavities 43 .
  • the guidance of the stator field lines 20 through the stator teeth 22 can also be seen.
  • FIG. 2b also shows flat measuring coils 31 arranged on the stator teeth 22, specifically on their tooth flanks. The extend in the axial direction Measuring coils 31 preferably over the entire length of the stator tooth 22. As the air gap field lines 30 in the air gap 3 show, the measuring coils 31 essentially detect all, but at least all, torque-relevant magnetic fields.
  • a stator tooth 22 is shown separately in a schematic representation in FIG. 3 in order to clarify the arrangement of the measuring coil 31 on the tooth flank of the stator tooth 22 .
  • the measuring coil 31 is designed as a so-called “radial coil”, ie a coil with a number of turns that lie within one plane.
  • the measuring coil 31 preferably has a thin (plastic) film as the carrier material, onto which the conductor loops that form the coil are vapour-deposited.
  • the measuring coil 31 can thus use the technology and the established manufacturing processes of flexible printed circuit boards (FPC—Flexible Printed Circuits).
  • a single coil is formed, which essentially extends over the entire surface of the tooth flank of the stator tooth 22 .
  • FIG. 4 illustrates a winding diagram of the electrical machine 1 shown above. It is noted that the winding scheme shown is purely exemplary and serves to derive and explain the method according to the application. The relationships shown below can be transferred to any other winding scheme, e.g. B. also to those that have multi-layer or long-stretched windings. Purely by way of example, the stator 2 of the electrical machine 1 shown in FIG. 4 has exactly one pair of poles with twelve stator teeth. However, the method according to the application described below can also be transferred analogously to electrical machines with a plurality of pole pairs.
  • FIG. 4 shows the twelve stator teeth 22 with stator windings 24.
  • the stator 2 of the electrical machine 1 is shown unrolled, so that the stator teeth 22 are shown linearly along a line.
  • the twelve stator teeth 22 are assigned to the one pair of poles mentioned and thus to two pole pitches 5 .
  • the electrical machine 1 is a three-phase machine operated on three electrical phases u, v and w. It has three phase windings 24 accordingly.
  • the designation of the phases u, v, w is used as an index for identifying the three phase windings 24 and all measured or calculated parameters that depend on the respective phase winding 24 or the respective electrical phase u, v , w are.
  • the phase windings 24 of the three phases u, v, w each consist of two concentric coils with a number of turns N 1 and N 2 .
  • the stator windings 24 belonging to one coil are connected to a box labeled N 1 or N 2 in FIG. 4 in order to indicate the association of the corresponding stator windings 24 (shown in section) with one another.
  • the stator teeth 22 of the pole pair are numbered consecutively from 1-12 in FIG. 4, the numbering being used below to indicate the stator teeth 22 . Due to the linearly unwound representation of the stator 2, the connecting lines starting from the phase windings 24 of the phase w on the left in FIG .
  • An outer coil of the phase u thus includes the stator teeth 22 with the index 1-7 and an inner coil of the phase u the stator teeth 22 with the index 2-6.
  • the phase v and w coils are each offset by four teeth, which corresponds to one third of the number of teeth in a pole pair.
  • the coils of phase w are in turn offset by four teeth compared to phase v (their outgoing conductors are in slots 9 and 10 and the return conductors in slots 3 and 4). They are formed with windings of adjacent pairs of poles, not shown in FIG. 4, if the machine has several pairs of poles.
  • a measuring coil 31 (not shown in FIG. 4) is arranged on each of the twelve stator teeth 22, with which a magnetic linkage flux ⁇ can be measured in each case.
  • the individually measured linkage fluxes ⁇ , which are measured on the respective stator tooth 22, are referred to below as ⁇ 1 - ⁇ 12 using the index of the stator tooth 22.
  • the factor k indicates the ratio of the linkage flux ⁇ 1 - ⁇ 12 to the (actual) magnetic flux in the respective stator tooth 22 .
  • the factor k depends on the geometry of the measuring coil 31 on the stator tooth 22, for example on the number of windings and the associated area. It can be determined, for example, in a no-load test with stator windings 24 without current by comparing induced voltages at connections of the electrical machine 1 with calculated voltages according to the formulas given above, induced voltages being used in the formulas instead of the magnetic fluxes .
  • ⁇ a 2/3 ( ⁇ u + ⁇ v cos(2/3 ⁇ ) + ⁇ w cos(4/3 ⁇ ))
  • ⁇ b 2/3 ( ⁇ v sin(2/3 ⁇ ) + ⁇ w sin(4/3 ⁇ ))
  • M actual 3/2 p ( ⁇ a xl b - ⁇ b xl a ) where p indicates the number of pole pairs of the electric machine 1.
  • stator fluxes which are referred to below as “stator fluxes” for the sake of simplicity, only represent a main flux of the stator 2 .
  • a stray flux component is not determined, since the magnetic fields measured by the measuring sensors 31 do not detect stray fluxes.
  • the leakage flux component does not contribute to the torque either, it can be neglected for the control purposes explained below. It is noted that for other purposes, e.g. B. to calculate a terminal voltage on the electrical machine 1 in motor or generator operation, the contribution of the leakage flux component would have to be taken into account. This is to be distinguished from no-load operation, in which no stator stray fluxes occur without a stator current, which is why the method given above can be used to find k.
  • the instantaneous torque M actual determined in this way can be used as a controlled variable in a control method for the electrical machine 1 and, for example, currents can be controlled in such a way that a specified torque M setpoint is achieved.
  • each of the twelve stator teeth 22 shown is provided with a measuring coil 31 .
  • every stator tooth 22 of the electrical machine 1 needs to be equipped with a measuring coil 31, since the symmetrical structure of the electrical machine 1 allows the magnetic field in the air gap 3 to be determined by measurements on a few selected stator teeth 22 over the entire circumference of the Stators 2 to reconstruct.
  • the number of required measuring coils 31 can be reduced to two, which are then attached to two stator teeth 22 offset by half a pole pitch 5 should.
  • the components of the stator flux ⁇ a , ⁇ b and the phase currents la , lb are shown as examples of a snapshot over the axes a, b.
  • the current position of the vector of the stator flux ⁇ is specified as the angular position ⁇ relative to the coordinate axis a. Compared to the coordinate system fixed to the stator (i.e.
  • the resulting vectors of the stator flux ⁇ and the phase current I have different phase positions, which are at an angle ⁇ between the vector of the phase current I and the vector of the stator flux ⁇ utter.
  • FIG. 5 also shows the projection of the vector of the phase current I onto the vector of the stator flux ⁇ , in other words the vector of the phase current I has been divided into a component parallel to the vector of the stator flux ⁇ and a component perpendicular thereto.
  • the abbreviation I d ( ⁇ ) is assigned to the parallel component and the abbreviation l q ( ⁇ ) to the vertical component. Since only the vertical component l q ( ⁇ ) results in a torque, it is also referred to below as the “torque-generating component l q ( ⁇ ) ”.
  • the component I d ( ⁇ ) aligned parallel to the direction of the stator flux vector ⁇ represents a flux-forming component of the current vector I.
  • the two components of the current vector I, the flux-forming component I d ( ⁇ ) and the torque-forming component l q ( ⁇ ) can thus be measured in the method described above without further approximations using the measuring coils 31 on the stator teeth 22 and a measurement of the phase currents l u , l v , I w can be determined.
  • variables are also manipulated variables in known control methods for electrical machines.
  • the previously indicated way of directly determining these variables correspondingly allows an electric machine to be controlled without the need to determine these variables from a rotor position measured using a position sensor or without the inadequacy of determining these variables from model-based estimates.
  • FIG. 6 shows an arrangement for controlling an electrical machine 1 using the direct measurement of torque M and stator flux ⁇ .
  • the arrangement includes a converter 6 with phase current outputs 61, via which the stator windings 24 of the electrical machine 1 are energized.
  • the String current outputs 61 are followed by string current sensors 62 which record (time-dependent) measured values for the string currents l u , l v , l w .
  • the evaluation unit 7 includes inputs 71 for the measuring coils 31 and inputs 72 for the phase currents l u , l v , l w .
  • An instantaneous (actual) torque M actual and the speed n are output at outputs 73, as well as an instantaneous stator flux vector T'actual, present in the form of its absolute value
  • control arrangement 8 which includes the actual controller 81 and a coordinate transformer 85 .
  • controller 81 the supplied actual values of torque M actual and stator flux
  • the torque setpoint value M setpoint is supplied directly and represents the control specification for the electric machine 1.
  • the setpoint value for the stator flux ⁇ setpoint is calculated from the torque setpoint value M setpoint and with the aid of a specification unit 9 of the speed n is calculated, the specification unit 9 including a desired speed-dependent relationship between the torque setpoint value M setpoint and the stator flux setpoint value ⁇ setpoint in a predefined and stored family of characteristics.
  • controller 81 outputs voltages U d , U q for the phase windings of the electrical machine as manipulated variables. These voltages are output in the d/q coordinate system at the control outputs 84 and are converted in the coordinate transformer 85 into the actual defaults for phase voltages U u , U v , U w for the inverter 6 , which are made available at phase control outputs 86 become.
  • FIG. 6 thus shows a field-oriented control for the electrical machine 1 based on a direct measurement of the controlled variables.
  • FIG. 7 shows a modification of this field-oriented control, the control principle of which is known as direct torque control (DTC—Direct Torque Control).
  • DTC Direct Torque Control
  • the same reference symbols identify elements that are the same or have the same effect as in FIG.
  • the converter 6 is not controlled via specifications for the phase voltages U u , U v , U w for the phase windings 24, but rather via switching states S u , S v , S w , which directly control switching elements Which control the phase windings 24 in a pulse width modulation process.
  • a switching table 87 is provided instead of the coordinate transformer 85, with the switching states S u , S v , S w being selected on the basis of the control output 84 of the controller 81 .
  • the actual value of the torque M is and the actual value of the stator flux ⁇ is determined directly from the measured values of the measuring sensors 31 and the measured winding currents l u , l v , l w . It is not necessary to estimate these values or to take into account other machine parameters that could change during operation.
  • I phase current (in vector representation) ⁇ 1 - ⁇ 12 measured magnetic interlinking flux ⁇ u , ⁇ v , ⁇ w magnetic interlinking flux
  • ⁇ is instantaneous magnetic linkage flux (in vectorial

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

L'invention concerne un procédé de régulation d'une machine électrique (1) en ayant recours à des bobines de mesure (31) disposées dans un entrefer (3) situé entre un stator (2) et un rotor (4) de la machine électrique, plusieurs enroulements de ligne (24) étant présents, lesquels sont associés à différentes phases électriques (u, v, w). Ledit procédé comprend les étapes qui consistent à : - mesurer des flux de concaténation magnétiques (Ψ1 - Ψ12) dans l'entrefer (3) à l'aide de bobine de mesure (31); - déterminer des flux de concaténation magnétiques (Ψu, Ψv, Ψw) de la pluralité d'enroulements de ligne (24) des différentes phases (u, v, w); - transformer les flux de concaténation magnétiques (Ψu, Ψv, Ψw) déterminés dans un système de coordonnées orthogonal solidaire du stator pour obtenir des flux de concaténation magnétiques orthogonaux (Ψa, Ψb); - mesurer des courants de ligne (Iu, Iv, Iw) qui circulent à travers la pluralité de bobines de ligne (24); - transformer les courants de ligne (Iu, Iv, Iw) mesurées dans le système de coordonnées orthogonal solidaire du stator pour obtenir des courants de ligne orthogonaux (Ia, Ib); - déterminer un couple de rotation instantané (Mist) et/ou une composante formant flux (Id) d'un vecteur de courant de ligne (I) formé à partir des courants de ligne orthogonaux (Ia, Ib) et ce, à partir des flux de concaténation magnétiques orthogonaux (Ψa, Ψb) et des courants de ligne orthogonaux (Ia, Ib); et – réguler la machine électrique (1) sur la base du couple de rotation instantané (Mist) et/ou de la composante formant flux (Id) ainsi déterminée. L'invention concerne en outre un système de régulation d'une machine électrique (1) par ce procédé.
EP22808802.7A 2021-10-29 2022-10-24 Procédé et système de régulation d'une machine électrique Pending EP4423902A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102021128353.1A DE102021128353A1 (de) 2021-10-29 2021-10-29 Verfahren und System zur Regelung einer elektrischen Maschine
PCT/EP2022/079629 WO2023072848A1 (fr) 2021-10-29 2022-10-24 Procédé et système de régulation d'une machine électrique

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EP4423902A1 true EP4423902A1 (fr) 2024-09-04

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US (1) US20240283382A1 (fr)
EP (1) EP4423902A1 (fr)
CN (1) CN118202569A (fr)
DE (1) DE102021128353A1 (fr)
WO (1) WO2023072848A1 (fr)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR3114454B1 (fr) * 2020-09-22 2023-01-06 Ntn Snr Roulements Machine électrique à N phases

Citations (1)

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