EP3846588A1 - Verfahren zur steuerung der leistung und kochfeld, das dieses verfahren umsetzt - Google Patents

Verfahren zur steuerung der leistung und kochfeld, das dieses verfahren umsetzt Download PDF

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Publication number
EP3846588A1
EP3846588A1 EP20217187.2A EP20217187A EP3846588A1 EP 3846588 A1 EP3846588 A1 EP 3846588A1 EP 20217187 A EP20217187 A EP 20217187A EP 3846588 A1 EP3846588 A1 EP 3846588A1
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EP
European Patent Office
Prior art keywords
com
switching element
power
threshold
sub
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EP20217187.2A
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English (en)
French (fr)
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EP3846588B1 (de
Inventor
Antonio ALVES
Xavier André
Serge Boyer
Cédric GOUMY
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Groupe Brandt SAS
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Groupe Brandt SAS
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Publication of EP3846588A1 publication Critical patent/EP3846588A1/de
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/06—Control, e.g. of temperature, of power
    • H05B6/062—Control, e.g. of temperature, of power for cooking plates or the like
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B2213/00—Aspects relating both to resistive heating and to induction heating, covered by H05B3/00 and H05B6/00
    • H05B2213/07—Heating plates with temperature control means

Definitions

  • the invention relates to a method for controlling the power of an induction hob comprising several inductors in operation.
  • induction means or inductors integrated into a resonant circuit are supplied from an inverter power supply device comprising a switching element.
  • the switching elements power the inductors according to a setpoint power.
  • the switching elements are subject to overheating, which can affect the correct functioning of the hob.
  • cooktops comprising temperature sensors as well as methods for controlling the power of cooktops comprising a temperature regulation step on the basis of the information collected by said temperature sensors.
  • each power supply device is equipped with a temperature sensor for each switching element.
  • the object of the present invention is to resolve at least one of the aforementioned drawbacks.
  • the invention relates to a power control method for an induction hob comprising several operating inductors, each inductor being controlled in power by a switching element according to a setpoint power associated with said inductor, and a suitable temperature sensor. in measuring a temperature representative of the temperature of all of said switching elements.
  • Such a power control method makes it possible, thanks to a temperature sensor, to detect a rise in temperature in the switching elements, to identify said at least one switching element generating heating and to act on the latter.
  • the method according to the invention makes it possible to identify and act individually on the source of the heating.
  • the steps of determining, identifying and reducing the control method are only implemented when the measured temperature is greater than or equal to the alert threshold. This avoids having to repeat the control process continuously, even when there is no heating in the switching elements.
  • the identification of said at least one switching element generating a heating is made possible by determining the number of switchings at a high current or voltage value exceeding the preset maximum current or voltage threshold. The higher the said number of switchings, the greater the heating.
  • the control method according to the invention thus makes it possible to regulate efficiently and at a lower cost, the temperature of the switching elements.
  • the threshold ratio is predefined, that is to say fixed beforehand. The comparison for each switching element of the ratio calculated with the threshold ratio makes it possible to identify the switching element or elements generating heating and to act rapidly on the latter.
  • the threshold ratio decreases when the number of switching elements in operation in the induction hob increases.
  • the threshold ratio decreases when the measured temperature value increases.
  • the threshold ratio can thus be recalculated during operation of the hob, as a function of the number of switching elements in operation and / or of the measured temperature value. This allows very precise identification of the switching elements generating overheating.
  • the threshold frequency decreases when the number of switching elements in operation in said induction hob increases.
  • the threshold frequency decreases when said measured temperature value increases.
  • the threshold frequency can thus be recalculated during operation of the hob, as a function of the number of switching elements in operation and / or of the measured temperature value.
  • the amplitude of the decrease in said setpoint power is defined as a function of the threshold ratio or of the threshold frequency, said amplitude increasing when said threshold ratio or said frequency threshold increases.
  • the determination and identification steps are reiterated over predefined time periods sliding over time.
  • the determination and identification steps are repeated over periods smaller than said predefined period of time.
  • each inductor is driven by a single switching element, preferably an IGBT ( Insulated Gate Bipolar Transistor).
  • IGBT Insulated Gate Bipolar Transistor
  • the invention also relates to an induction hob comprising several inductors, each inductor being controlled in power by a switching element according to a setpoint power associated with said inductor, and a temperature sensor suitable for measuring a temperature. representative of the temperature of all of said switching elements.
  • the hob comprises power control means configured to implement the power control method having the preceding characteristics.
  • the induction hob has characteristics and advantages similar to those described above in relation to the control method.
  • the figure 1 shows an induction hob suitable for implementing the present invention.
  • this hob may be an induction hob 10 comprising at least one cooking zone associated with induction means.
  • the hob 10 has predefined cooking zones.
  • the hob 10 comprises four cooking zones F1, F2, F3, F4, each cooking zone being associated with one or more inductors.
  • This hob 10 conventionally comprises a power phase of an electrical supply 11, typically a mains supply.
  • the hob 10 is supplied with 32 A, which can supply a maximum power of 7200 W to the hob 10, ie a power of 3600 W per phase.
  • a control and power control card 12 makes it possible to support all the electronic and computer means necessary for controlling the hob 10.
  • the cooking zones can also be identified by silkscreen printing opposite the inductors placed under the cooking surface.
  • the hob 10 also includes control and interface means 14 with the user, in particular allowing the user to control the power and duration of the operation of each hotplate F1, F2, F3, F4.
  • control and interface means 14 assign a setpoint power P c to each cooking zone covered with a receptacle.
  • the figure 2 shows another type of induction hob suitable for implementing the present invention.
  • the cooking hob 15 is in this exemplary embodiment a so-called matrix hob, that is to say without predefined cooking zones.
  • This hob 15 comprises heating means consisting of inductors 17 distributed in a hob 16.
  • These inductors 17 are distributed in a two-dimensional grid under the cooking surface 16 of the cooking hob 15.
  • the inductors 17 are staggered.
  • the inductors can be arranged in a distribution in rows and columns, that is to say in a matrix arrangement.
  • a heating zone Z is formed from the detection of the inductors 17 covered by the receptacle.
  • the heating zones Z are defined on a case-by-case basis by the position of the receptacle facing a subassembly of inductors 17 arranged under the cooking surface 16.
  • a heating zone Z can thus be formed by 'one or more inductors.
  • Each inductor 17 of the hob 15 can thus be controlled independently and put into operation only when a receptacle covers at least part of this inductor.
  • the hob 15 comprises in a known manner, as in the embodiment of the figure 1 , both a control and power command card adapted to support all the electronic and computer means necessary for the control of the hob 15, and control and interface means with the user, allowing in particular the user to control the power and duration of the operation of each Z heating zone.
  • the invention also applies to flexible tables, that is to say comprising a matrix part or without a predefined focus, and a part with predefined focal points.
  • the figure 3 illustrates an embodiment of an inverter power supply device adapted to power an inductor.
  • an inductance L represents both the inductance of the inductors and that of the vessel to be heated placed opposite.
  • the system constituted by the receptacle and the inductor (s) of the hearth can thus be schematized by an inductor L.
  • the resonant circuit also comprises a capacitor C mounted in parallel with the inductor L.
  • the resonant circuit thus formed is supplied by an inverter power supply device comprising here a single switching element Com or power element.
  • Each inductor is for example controlled in power by a switching element Com according to a setpoint power P c associated with said inductor.
  • the switching element Com is here a switch of the type of a voltage-controlled transistor, in particular an IGBT or IGBT switch (acronym for the English term " Insulated Gate Bipolar Transistors ”) .
  • the switching element is connected in series with the resonant circuit L, C and a freewheeling diode D is connected in parallel with the switching element.
  • Such an inverter power supply device operates at a switching frequency corresponding to the switching frequency of the switching element.
  • the switching frequency of the power supply device corresponds to a control or switching period T.
  • inverter power supply device comprising the IGBT switch and the freewheeling diode D, and controlled according to a switching frequency (or switching period or control T) is commonly used in the field of appliances. induction cooking and does not need to be described in more detail here.
  • the switching element Com may be of another type, for example an insulated gate field effect transistor (MOSFET), or else a bipolar transistor.
  • MOSFET insulated gate field effect transistor
  • the present invention applies particularly to tables in which each inductor is associated with a single switching element Com, for example to mono IGBT tables.
  • the invention can be applied in the case of different assemblies, for example a half-bridge assembly.
  • the hob according to the invention further comprises a temperature sensor C T (not shown here).
  • the temperature sensor C T can for example be placed near the switching elements Com, the motherboard and / or the heat exchanger of the hob.
  • the temperature sensor C T is suitable for measuring a temperature T m representative of the temperature of all the switching elements Com.
  • the hob operates according to a control method making it possible, during a heating in the switching elements Com, to identify the switching element (s) Com at the origin of said heating and to act on them in order to reduce the temperature.
  • temperature T m The ordering method comprises several steps.
  • a first step consists in detecting when the temperature value T m measured by the temperature sensor C T is greater than or equal to a warning threshold T s .
  • This first step is performed by the temperature sensor C T which for example can send a signal when the alert threshold T s is exceeded.
  • a second step of the control method is then carried out. This second step consists in determining, for each switching element Com, over a predefined period of time Tf, a number of switching operations N c at a current or voltage value greater than or equal respectively to a maximum current threshold I s or of voltage U s prefixed. For example, for an IGBT switch, these are the high current switching which are determined. For a MOSFET, the determination is aimed at high voltage switching.
  • the aim of the second step is to detect the switching elements Com exposed to high currents or voltages during switching. The more the Com switching element is exposed to current or voltage spikes, the more likely it is to heat up.
  • the detection of switching elements Com with high currents or voltages can be carried out by any known means.
  • a third step of the control method then consists in identifying at least one switching element Com generating a heating as a function of the number of switching operations N c determined in the second step for each one switching element Com.
  • a fourth step of the control method consists in reducing the setpoint power P c associated with the inductor controlled by the switching element or elements Com generating a heating identified in the third step.
  • the setpoint power P c can be reduced one or more times until an acceptable temperature of the switching elements Com is obtained and / or an acceptable number of switching operations of the controlled switching element (s) Com having generated warming up.
  • the reduction in the setpoint power P c can be carried out by any known means, for example by chopping.
  • the amplitude of the decrease in the setpoint power P c can be constant.
  • the setpoint power P c can be reduced by 12.5W for each inductor controlled by a switching element Com generating heating.
  • the amplitude of the decrease in the setpoint power P c can be a function of the number of inductors in operation.
  • the amplitude of the setpoint power P c can decrease when the number of operating inductors increases.
  • the switching element Com can return to power. initial setpoint. This step can be done either gradually or instantly.
  • the third step or identification step is described in more detail below, according to two exemplary embodiments.
  • the identification step consists firstly in acquiring a total number of switchings N T , for each switching element Com, over the predefined period of time Tf.
  • a ratio R c is calculated between the determined number of switchings N c and the total number of switchings N T for each switching element Com.
  • a ratio R c is calculated over the predefined period of time Tf between the number of switchings N c where the switching element Com has been exposed to a current or voltage peak and the total number of switchings N T.
  • This calculated ratio R c is then compared with a threshold ratio R s .
  • the threshold ratio R s is predefined, for example by test.
  • the calculation of the ratio R c can be carried out on a sliding average over the predefined period of time Tf. In other words, the calculation can be done on periods of time less than the predefined period of time, said periods of time overlapping.
  • the ratio R c can be calculated every 3.3 seconds by considering the number of switchings over the last 15 seconds.
  • the number of switchings is 450,000 over the sliding measurement period of 15 seconds. If in this period of time, the number of switchings N c at a current or voltage value greater than or equal respectively to a maximum threshold of current I s or of voltage U s prefixed is 420,000, the ratio R c is then equal 0.93.
  • the threshold ratio R s can be between 0.90 and 0.95. This range of values has a good value between a reduction in acceptable inductor performance and a significant effect on the temperature of the switching element Com.
  • the threshold ratio R s can be fixed or variable.
  • the threshold ratio R s can decrease when the number of switching elements Com in operation in the induction hob increases.
  • the threshold ratio R s may be 0.95 when two Com switching elements are active, 0.93 when three Com switching elements are active, and 0.90 when four Com switching elements are active.
  • the threshold ratio R s can decrease when the value of the temperature T m measured in the switching elements Com increases.
  • the threshold ratio can be equal to 0.95 when the measured temperature T m is between 70 ° C and 80 ° C, 0.93 when the measured temperature T m is between 80 ° C and 90 ° C , and 0.91 when the measured temperature T m is greater than 90 °.
  • the calculation of the threshold ratio R s as a function of the number of switching elements Com as a function of the temperature T m measured can be carried out in two distinct embodiments or can be combined. In the latter case, the calculation of the threshold ratio R s can take into account both the variation in the number of switching elements Com and the variation in the temperature T m measured.
  • the setpoint power P c of the inductor controlled by the switching element Com generating a heating is then reduced.
  • the identification step consists firstly in the calculation for each switching element Com of a frequency of occurrence F c of switching at a current or voltage value greater than or equal respectively at a maximum current I s or voltage U s threshold from the number of switchings N c determined over the predefined period of time Tf.
  • the number of switchings N c at a high current or voltage value is determined for each switching element Com over the predefined period of time T f . This makes it possible to calculate the frequency of switching at a high current or voltage value over the predefined period of time T f .
  • the calculated frequency of appearance F c is compared with a threshold frequency F s .
  • the threshold frequency F s is prefixed, for example by test.
  • the threshold frequency F s can be between 27,000 and 28,500. This value range has a good range between a reduction in the acceptable performance of the inductor and a significant effect on the temperature of the switching element Com.
  • the threshold frequency F s can be fixed or variable.
  • the threshold frequency F s can decrease when the number of switching elements Com in operation increases.
  • the threshold frequency F s can be 28,500 when two inductors are active, 27 750 when three Com switching elements are active and 27,000 when four Com switching elements are active.
  • the threshold frequency F s can also decrease when the value of the temperature T m measured in the switching elements Com increases.
  • the threshold frequency F s can be equal to 28,500 when the measured temperature T m is between 70 ° C and 80 ° C, 27,500 when the measured temperature T m is between 80 ° C and 90 ° C , and 26,500 when the measured temperature T m is greater than 90 °.
  • the calculation of the threshold frequency F s as a function of the number of switching elements Com and of the temperature T m measured can be carried out in two distinct embodiments or can be combined. In the latter case, the calculation of the threshold frequency F s can take into account both the variation in the number of switching elements Com and the variation in the temperature T m measured.
  • the setpoint power P c of the inductor controlled by the switching element Com generating a heating is then reduced.
  • the amplitude of the decrease in the setpoint power P c can be defined as a function of the threshold ratio R s or of the threshold frequency F s . Indeed, said amplitude can increase when said threshold ratio R s or said threshold frequency F s increases.
  • the values of the threshold ratio R s and of the threshold frequency F s can be calculated respectively with respect to an initial ratio value or initial frequency of appearance to which one or more correction coefficients are applied.
  • the correction coefficients depend in particular on the number of elements in operation and / or on the temperature of the switching elements Com.
  • the coefficients applicable as a function of the number of active switching elements Com and / or of the temperature of the electronics can also be stored by means of storage means of the hob, and applied as needed.
  • the decrease in the associated setpoint power P c may be greater when the calculated ratio R c or the calculated frequency of occurrence F c reaches the highest threshold ratios. In other words, the more the switching element Com heats up, the greater the amplitude of reduction of the associated setpoint power P c.
  • the setpoint power P c is reduced only for the inductor (s) controlled by the switching element (s) Com generating l 'warming up.
  • the overall reduction in the setpoint power P c of all the inductors in operation can be effected when the measured temperature T m reaches a critical temperature value.
  • the critical temperature is greater than the alert threshold T s and may constitute additional safety for the hob.
  • the control method may include a step of reducing the setpoint power P c of all the inductors in operation.
  • the figure 4 illustrates a determination device comprising in particular means for measuring the current i flowing in an IGBT switch and a freewheeling diode D.
  • this determination device makes it possible to determine when the current in the IGBT switch exceeds the maximum threshold of pre-set current I s (second step of the control method according to the invention).
  • the means for measuring the current are produced by means of a current transformer 20.
  • the value of the voltage at the terminals of a load resistor R1, placed at the output of the current transformer 20, corresponds to the image of the current i flowing in the IGBT switch or the freewheeling diode D.
  • These measuring means 20 are associated with means 30 for detecting a peak of the current i flowing in the IGBT switch.
  • These detection means 30 notably comprise a diode of the Zener type D1 connected in parallel with the current transformer 20.
  • the avalanche voltage of the Zener type diode D1 is approximately equal to the value of the voltage at the output of the current transformer 20 when the current i flowing in the IGBT switch is approximately equal to a maximum current threshold I s prefixed, admissible in the IGBT switch.
  • the detection means 30 further comprise a second diode D2 connected in series with the Zener diode D1 and in opposition with respect to the Zener diode D1.
  • the detection means 30 further include a resistor R2, mounted in series with the two diodes D1, D2.
  • Means 40 for generating a SWITCH level signal are associated with the detection means 30.
  • the generation means 40 are configured to generate a SWITCH level signal intended to inform control means, typically produced by a microprocessor 50, if the current i flowing in the switching element has or has not reached the preset maximum current threshold.
  • the generation means 40 comprise a second switching element T1 controlled by a control signal FREQUENCY having a period equal to the switching period T and being representative of the control of the switch IGBT.
  • the second switching element T1 is connected in series with the resistor R2 and the two diodes D1, D2 forming a circuit in parallel with the current transformer 20.
  • the second switching element T1 is here a bipolar transistor of the NPN type.
  • the generation means 40 further include delay means 41 mounted between the control signal FREQUENCY and the second switching element T1.
  • the delay means 41 are connected to the base b of the second transistor T1.
  • the delay means 41 are configured to generate a period of time Tr (illustrated on figure 4 ) at the start of a switching period T of the IGBT switch.
  • the delay means 41 comprise a delay resistor R3 connected by a first terminal to the base of the second transistor T1, and a delay capacitor C1 mounted between the base and the emitter of the second transistor T1.
  • the FREQUENCY control signal is applied to the second terminal of the delay resistor R3.
  • the generation means 40 further include a third switching element T2, being here a bipolar transistor of the same type as the second transistor T1, that is to say of the NPN type.
  • the third transistor T2 is mounted between a pull-up resistor R5 and the reference potential.
  • the base of the third transistor T2 is connected to the collector of the second transistor T1 and to the resistor R2 of the detection means 30.
  • the SWITCH level signal is taken between the third transistor T2 (its collector) and the pull-up resistor R5.
  • an output capacitor C2 is connected at the output of the third transistor T2, in parallel.
  • the output capacitor C2 forms with the pull-up resistor R5 means for maintaining 42 the level signal SWITCH in a predefined state indicating that the current i flowing in the switch IGBT has a value equal to the maximum preset current threshold.
  • the output capacitor C2 and the pull-up resistor R5 have values such that the level signal SWITCH remains in the predefined state during a switching (or chopping) period of the IGBT switch.
  • the detection means 30 are configured to detect a current i whose value is substantially equal to the maximum preset current threshold I s , corresponding to the admissible current value in the IGBT switch.
  • This predetermined maximum threshold value is strictly positive.
  • this predetermined maximum threshold value is greater than or equal to 40 A, and preferably greater than 60 A.
  • the generation means 40 are configured to generate a SWITCH level signal indicating whether or not the detection means 30 have detected a current peak equal to the maximum current threshold I s prefixed.
  • the level signal SWITCH is intended to inform the control means 50, whether the current i circulating in the switch IGBT reaches or not the maximum threshold of current I s prefixed.
  • the level signal SWITCH is in the low state. Otherwise, the SWITCH level signal is high.
  • control signal FREQUENCY is indicative of the command or set to ON of the IGBT switch.
  • the FREQUENCY control signal has a first state when the switch is driven or turned on, and a second state when the IGBT switch is not conducting.
  • the first state can be a high state and the second state can be a low state.
  • the control signal FREQUENCY goes high after the activation of the freewheeling diode D and at the latest at the instant which the freewheeling diode D stops driving. Indeed, the IGBT switch is controlled or deviates passing at an instant between the start and the end of the conduction of the freewheeling diode D.
  • the control signal FREQUENCY is here a signal having a period equal to the switching period T and corresponds to the control signal of the switch IGBT.
  • control signal FREQUENCY is in the first state when the IGBT switch is in the ON state and in the second state when it is in the OFF state.
  • this diode D2 is blocked.
  • Zener type diode D1 then turns on.
  • the IGBT switch is on for a period of time called the conduction period Tc.
  • the level signal FREQUENCY is high.
  • the delay means 41 comprising the capacitor C1 and the resistor R3, introduce a delay time on the control signal FREQUENCY which controls the operation of the second switching element or transistor. T1.
  • resistor R3 and of capacitor C1 are selected so that the second transistor T1 does not turn on until after a predefined delay relative to the passage to the high state of the control signal FREQUENCY.
  • the delay means 41 introduce a delay on the control signal FREQUENCY.
  • This delay time corresponds to the time period Tr (visible on the figure 6 ) at the start of the control period T of the IGBT switch (in the case shown in figure 6 , the conduction period Tc of the IGBT switch begins at the same time as the switching period T).
  • the time period Tr is less than the conduction period Tc of the IGBT switch.
  • the first current peak generated in the switching element when it is turned ON generally takes place within 0.5 microseconds after switching on. set to ON. This is seen by those skilled in the art knowing inverter power supply devices such as that shown in figure 3 .
  • Tpic This period during which the first current peak takes place is called Tpic (visible on the figure 6 ) and corresponds to the minimum value of the time period Tr at the start of the control period.
  • the time period Tr is between a minimum value corresponding to the minimum period Tpic, and a maximum value corresponding to the conduction period Tc of the IGBT switch.
  • the minimum period Tpic corresponds to the period of time during which the first current peak generated in the switching element when it is turned ON can take place.
  • This third transistor T2 thus becomes on and the level signal SWITCH goes low, this state indicating that the current i flowing in the switch IGBT has a value equal to the maximum current threshold I s prefixed.
  • the microprocessor 50 can, from the state of the level signal SWITCH, detect the current peak in the IGBT switch, corresponding to a current value reaching the maximum preset current threshold I s , generated during the period time Tr at the start of the control period T of the IGBT switch.
  • the figure 5 illustrates the image of the voltage across the load resistor R1, the current flowing through the Zener type diode D1, the collector-emitter voltage of the second transistor T1 and the level signal SWITCH.
  • the voltage across the load resistor R1 is greater than the avalanche voltage of the Zener type diode D1 at the end of the conduction period Tc of the IGBT switch.
  • the collector-emitter voltage of the second transistor T1 remains zero due to the fact that the control signal FREQUENCY is in the high state, the second transistor T1 being on.
  • the rising edge of the FREQUENCY signal corresponding to the control of the IGBT switch corresponds to the instant at which the freewheeling diode D stops its conduction.
  • This example thus represents a case in which the conduction period Tc of the IGBT switch is minimal.
  • the figure 6 illustrates the same parameters when the voltage across the load resistor R1 exceeds the avalanche voltage of the Zener diode D1 at the start of the control period T.
  • a current peak occurs when turned ON of the IGBT switch over a minimum period of time Tr or Tpic.
  • the peak of the current observed in the IGBT switch when it is turned ON is independent of the receptacle placed opposite the induction means. Indeed, this current peak is due to the discharge of the capacitor C in the resonance circuit as indicated above.
  • the Zener type diode D1 is conducting, that is to say that a current flows through it.
  • the collector-emitter voltage of the second transistor T1 has a value greater than zero.
  • the level signal SWITCH goes low as can be seen at figure 6 .
  • this method given by way of non-limiting example can be applied to the control method can determine the number of switchings where the switching elements generate a SWITCH signal and thus identify the switching elements generating heating.
  • the individualized regulation that is to say for each switching element generating heating, carried out by means of the control method described above can also be associated with regulation by measuring the temperature of the ambient temperature. all the components of the hob.
  • the present invention thus proposes a method for controlling the power of a hob making it possible to detect heating in the switching elements, to identify the switching elements generating said heating and to regulate the temperature by acting precisely on the latter.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Induction Heating (AREA)
  • Control Of High-Frequency Heating Circuits (AREA)
EP20217187.2A 2019-12-31 2020-12-24 Verfahren zur steuerung der leistung und kochfeld, das dieses verfahren umsetzt Active EP3846588B1 (de)

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FR1915790A FR3105908B1 (fr) 2019-12-31 2019-12-31 Procédé de commande en puissance et table de cuisson mettant en œuvre ledit procédé

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EP3846588A1 true EP3846588A1 (de) 2021-07-07
EP3846588B1 EP3846588B1 (de) 2022-10-12

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2726704A1 (fr) * 1994-11-07 1996-05-10 Breda Jean Pierre Generateur haute frequence a resonance pour un appareil de chauffage a induction
EP1679938A1 (de) * 2003-10-30 2006-07-12 Matsushita Electric Industrial Co., Ltd. Induktionsheiz-kocheinrichtung
WO2013064396A1 (en) * 2011-11-04 2013-05-10 Arcelik Anonim Sirketi An induction heating cooker

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2726704A1 (fr) * 1994-11-07 1996-05-10 Breda Jean Pierre Generateur haute frequence a resonance pour un appareil de chauffage a induction
EP1679938A1 (de) * 2003-10-30 2006-07-12 Matsushita Electric Industrial Co., Ltd. Induktionsheiz-kocheinrichtung
WO2013064396A1 (en) * 2011-11-04 2013-05-10 Arcelik Anonim Sirketi An induction heating cooker

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FR3105908B1 (fr) 2022-01-14
FR3105908A1 (fr) 2021-07-02
EP3846588B1 (de) 2022-10-12

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