EP2420107A1 - Régulation de la puissance de del, à l'aide de la moyenne du courant des del et d'un compteur bidirectionnel - Google Patents

Régulation de la puissance de del, à l'aide de la moyenne du courant des del et d'un compteur bidirectionnel

Info

Publication number
EP2420107A1
EP2420107A1 EP10711663A EP10711663A EP2420107A1 EP 2420107 A1 EP2420107 A1 EP 2420107A1 EP 10711663 A EP10711663 A EP 10711663A EP 10711663 A EP10711663 A EP 10711663A EP 2420107 A1 EP2420107 A1 EP 2420107A1
Authority
EP
European Patent Office
Prior art keywords
switch
led
circuit
current
value
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP10711663A
Other languages
German (de)
English (en)
Other versions
EP2420107B1 (fr
Inventor
Eduardo Pereira
Michael Zimmermann
Alexander Barth
Markus Mayrhofer
Günter MARENT
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Tridonic GmbH and Co KG
Tridonic AG
Original Assignee
Tridonic GmbH and Co KG
Tridonic AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Family has litigation
First worldwide family litigation filed litigation Critical https://patents.darts-ip.com/?family=42226646&utm_source=google_patent&utm_medium=platform_link&utm_campaign=public_patent_search&patent=EP2420107(A1) "Global patent litigation dataset” by Darts-ip is licensed under a Creative Commons Attribution 4.0 International License.
Priority claimed from DE102009017139A external-priority patent/DE102009017139A1/de
Application filed by Tridonic GmbH and Co KG, Tridonic AG filed Critical Tridonic GmbH and Co KG
Priority to PL10711663T priority Critical patent/PL2420107T3/pl
Publication of EP2420107A1 publication Critical patent/EP2420107A1/fr
Application granted granted Critical
Publication of EP2420107B1 publication Critical patent/EP2420107B1/fr
Revoked legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light
    • H05B45/14—Controlling the intensity of the light using electrical feedback from LEDs or from LED modules
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/375—Switched mode power supply [SMPS] using buck topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/38—Switched mode power supply [SMPS] using boost topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/385—Switched mode power supply [SMPS] using flyback topology

Definitions

  • the present invention relates to a circuit arrangement for operating light emitting diodes (LED), in particular of inorganic light emitting diodes or organic light emitting diodes, which is used in electronic ballasts for corresponding light emitting diodes.
  • LED light emitting diodes
  • the invention also relates to a lighting system.
  • the switch-off time of the switch is determined by the fact that the LED current reaches a fixed predetermined Ausschaltschwellenwert. This leads to inaccuracies, since the negative current flow range can vary immediately after switching on the switch, which makes the power control inaccurate.
  • the object of the invention is now to make the power control of an LED in a converter such as a boost converter (boost converter), buck converter (also called step-down) or buck-boost converter (flyback converter or inverter called) to make more accurate.
  • a converter such as a boost converter (boost converter), buck converter (also called step-down) or buck-boost converter (flyback converter or inverter called) to make more accurate.
  • a first aspect of the invention relates to a method for regulating, in particular for controlling the power of an LED in a converter with a switch.
  • the invention can be applied equally to:
  • the converter is formed by an active clocked switch and passive energy storage elements with, for example, an inductor.
  • a converter can be a buck converter, buck-boost converter or flyback converter (isolated flyback converter).
  • the LED is connected in the output circuit.
  • An inductance is magnetized if the switch is actively clocked and a current flow takes place via the closed switch and the inductance.
  • the feedback variable used for the control is a measured actual value representative of the mean value of the LED current, which is compared with a reference value as setpoint. Depending on a difference between the actual value and the setpoint value, the duty ratio of the current switch-on operation of the actively-clocked switch and / or a subsequent switch-on operation can be set.
  • the duty cycle of the active clocked switch can be changed only every n-th switch-on, where n is greater than or equal to 2.
  • the duty cycle of the active clocked switch can be changed, for example, over the time of switching off the active clocked switch as a control line.
  • the duty cycle can be adjusted by adaptively specifying a turn-off level of a measured, representative of the LED current size, which is switched off when the switch-off level of the active clocked switch.
  • the level of the DC bus voltage supplying the converter can alternatively or additionally be used in addition to the clocking of the active clocked switch.
  • the bus voltage can be generated by means of an active PFC circuit, wherein the level of the generated bus voltage is carried out by changing the timing of a switch of the PFC circuit.
  • a sample of the LED current may be obtained, preferably measured at half the Einschatzeitdauer the active clocked switch.
  • the actual value representative of the mean value of the LED current can be determined by a continuous measurement of the LED current (or a quantity representative thereof).
  • the continuously measured LED current may be compared to a reference value, and the actual value representative of the mean value may be the duty cycle of the comparison value over the on period of the active switch.
  • the duty cycle can be determined using a bidirectional digital payer.
  • the reference value may depend on a predetermined dimming value and / or the measured LED voltage.
  • the LED power can be through one of the following operating modes
  • a dimming of the LED (s) can be done by PWM, wherein the LED current preferably in Continous Conduction Mode in the ON time of a PWM pulse is generated.
  • the invention also relates to an integrated circuit, in particular ASIC or microcontroller or hybrid thereof, which is designed to carry out a method as stated above.
  • the invention relates to an operating device for an LED, comprising such an integrated circuit.
  • a circuit for power control of an LED which has a converter with a switch, wherein the LED in the output circuit can be connected.
  • a control unit activates the switch, whereby the switch takes over the current flow and magnetizes the inductance, whereby the LED is supplied with a high-frequency voltage.
  • the control unit is fed back a measured actual value representative of the mean value of the LED current, which is compared with a reference value.
  • control unit can set the duty cycle of the current switch-on operation of the actively switched switch and / or a subsequent switch-on operation.
  • the control unit can change the duty cycle of the active clocked switch only every n-th switch-on, where n is greater than or equal to 2.
  • the control unit may change the duty cycle of the active clocked switch over the time of switching off the active clocked switch as a control variable.
  • the control unit may adjust the duty cycle by adaptively specifying a turn-off level of a measured magnitude representative of the LED current, the control unit turning off the actively-pulsed switch upon reaching the turn-off level.
  • control unit can also control a DC link circuit and obtain feedback signals from the DC link circuit, the DC link voltage generating the DC bus voltage supplying the converter.
  • the control unit can be used as a control line of the power control alternatively or in addition to the
  • an active PFC circuit may be provided, wherein the control unit carries out the level of the generated bus voltage by changing the timing of a switch of the PFC circuit.
  • the control unit may be fed back as a measured actual value representative of the mean value of the LED current, a sample of the LED current, preferably measured at half the on-time of the active clocked switch.
  • the control unit may continuously measure the LED current (or a quantity representative thereof) for determining the actual value representative of the mean value of the LED current.
  • the control circuit may comprise a comparator which compares the continuously measured LED current with a reference value, and the control circuit uses the duty cycle of the comparator output signal as the actual value representative of the mean value.
  • the output of the comparator may be fed to a bidirectional digital counter of the control circuit.
  • the control circuit may set the reference value depending on an externally or internally predetermined dimming value and / or the measured and the control circuit supplied LED voltage.
  • FIG. 1 shows an operating device according to the invention for LEDs connected in a buck converter
  • FIG. 2 shows in detail a circuit according to the invention for LEDs connected in a buck-boost converter and the measurement signals which can be tapped off therefrom.
  • FIG. 3 shows the profile of drive signals from a switch of the half bridge as well as the center point voltage U L3 and the LED current I LED ,
  • FIG. 4 shows the structure of a regulation of the LED current
  • FIG. 5 shows the time profile of signals of the control of FIG. 4
  • Fig. 1 shows an electronic ballast for operating LED.
  • Fig. 1 shows a converter for operating at least one LED and a power factor correction circuit, both circuits being controlled by a control unit IC.
  • the electronic ballast On the input side, the electronic ballast has a mains voltage supplied - not shown rectifier - to which the active power factor correction circuit adjoins, which acts as a boost converter.
  • the PFC circuit substantially comprises a coil L ⁇ which is magnetized when the switch (transistor) S6 is closed in response to a drive command S ⁇ D from the integrated circuit IC.
  • the bus voltage Uout at the pin can be measured at the pin ST2 when the switch S ⁇ is open.
  • the time of demagnetization of the coil L6 can also be determined.
  • the converter has a further switch Sl and is designed as a buck converter.
  • the current through the switch Sl can be supplied to the control circuit IC by means of a measuring resistor (shunt) Rl at a pin CS.
  • a control signal for the switch Sl is output by the control circuit IC.
  • the reconnection of the active clocked switch Sl can be determined by the monitoring of the current flowing through the inductor Ll branch current iLl. For example, it can be monitored whether the branch current i L1 flowing through the inductance L 1 has again fallen to zero or whether the inductance L 1 has been demagnetized (critical conduction mode). This can be done by means of a secondary winding to the inductor Ll or by means of monitoring the voltage across the switch Sl. In Continuous Conduction Mode it is monitored whether one of the branch currents has reached a lower switch-on threshold (greater than zero). In the Discontinous Conduction Mode, it is monitored whether the branch current has already been at zero for a predetermined period of time before switching on. In this discontinuous conduction mode, the off time period T off is included to calculate the average time value of the current.
  • the switch-on of the switch S1 can be advantageous before complete demagnetization of the inductance L1, especially if no or only a very small capacitor C1 is present. In this case, so-called non-gap current operation can be achieved.
  • the control circuit IC drives the converter and can continue to perform the PFC control.
  • the control unit can be fed back feedback signals from the range of the PFC intermediate circuit voltage, such as.: - The input voltage via a tap STl, the current through the inductor L ⁇ by means of a voltage divider ST2 (or monitoring the voltage across the inductance L6), and the bus voltage Uout via the voltage divider ST2.
  • the control unit can adjust the level of the output voltage by clocking the switch S6 and preferably digitally control it by means of the returned bus voltage.
  • the control unit can feedback signals from the range of the load circuit containing the LED are returned to the converter: the LED voltage V LED (for example, determined by means of a comparison of the returned bus voltage with the voltage at the voltage divider
  • the LED voltage V LED can be evaluated, for example, as a parameter for the control of the LED operation or for error detection.
  • the switch-off time period T O ff of the switch S1 can be included in order to calculate the time-average value of the current through the LED.
  • the switch-off time T Off can be determined, for example, by monitoring the voltage across the switch Sl. In this case, it can be recognized over which period of time there is a demagnetization of the inductance L 1 (which is the case) Switch off period T off corresponds).
  • the switch-off duration T Off can, however, also be determined or detected, for example, by an evaluation of the drive signal for the switch S1.
  • a capacitor Cl is connected in parallel with the LED as a filter or smoothing capacitor in parallel.
  • This can smooth the LED voltage during operation and maintain the LED voltage during demagnetization of the inductance Ll.
  • the current determined via the shunt Rl does not exactly correspond to the current flowing through the LED, but additionally also contains a current component flowing through the capacitor C1.
  • This total current can also be used for the power control according to the invention, since the current through the shunt Rl again represents a measure of the actual power in the output circuit, if it is assumed that the bus voltage Uout is constant (eg due to the regulation of the PFC) or due a measurement is known. This total current is therefore referred to below as LED current.
  • a low-impedance shunt Rl is interposed, which, however, serves only for the measurement of currents and has no measurable influence on the voltages in the circuit.
  • a brightness change (dimming) of the LED is preferably by a pulsed operation (periods with nearly constant LED current are due to periods without
  • Fig. 2 shows a converter for operating at least one LED, which circuit is controlled by a control unit IC.
  • the converter may be preceded by a circuit for power factor correction.
  • the converter has a further switch Sl and is designed as a buck-boost converter.
  • the current through the switch Sl can be supplied to the control circuit IC by means of a measuring resistor (shunt) Rl at a pin CS.
  • a control signal for the switch Sl is output by the control circuit IC.
  • the switch S1 When the switch S1 is closed, the current flows through an inductance L1 and increases substantially linearly with the magnetization of the inductance L1.
  • the LEDs are powered by the capacitor Cl during this phase.
  • the switch Sl When the switch Sl is turned off, the energy of the inductance Ll is reduced by a current flow through the LEDs and the freewheeling diode Dl substantially linearly until the switch Sl is finally turned on again.
  • the time can be determined in which the magnetization of the inductance Ll is substantially degraded and thus the current through the freewheeling path (diode Dl, LED path, inductance Ll) not more is driven on.
  • the reconnection of the active clocked switch Sl can be determined by the monitoring of the current flowing through the inductor Ll branch current iLl. For example, it can be monitored whether the branch current i L1 flowing through the inductance L 1 has fallen back to zero or whether the inductance L 1 has been demagnetized. This can be done by means of a secondary winding to the inductor Ll or by means of monitoring the voltage across the switch Sl. But it can also be a reconnection due to the expiration of a certain period of direct current measurement in the path of the LED.
  • the control circuit IC drives the converter and can continue to perform the PFC control.
  • the control unit can feedback signals from the range of the load circuit containing the LED are returned to the converter: the LED voltage V LED by means of a voltage divider, not shown, arranged parallel to the LED, the LED current I LED (for example by means of shunt Rl), and the voltage across the switch Sl by means of a tap A2 (inductive or by tapping over the switch Sl).
  • a capacitor Cl is connected in parallel with the LED as a filter or smoothing capacitor in parallel. This can smooth the LED voltage during operation and maintain the LED voltage during the magnetization or even during the demagnetization of the inductance Ll.
  • a low-impedance shunt Rl is interposed, which, however, serves only for the measurement of currents and has no measurable influence on the voltages in the circuit.
  • FIG. 3 signal curves during the switching on and off of the switch S1 are shown.
  • the switch S1 is actively clocked and switched on between the times T31 and T32 (time duration t 0N ).
  • the linearly increasing LED current I LED can only be detected during the time period t 0 N at the shunt Rl, during which the switch Sl is turned on.
  • the LED current can not be detected by means of the shunt Rl.
  • the switch-on time of the high-frequency clocked switch Sl can be determined by monitoring the branch current i L1 flowing through the inductance L 1. For example, it can be monitored whether the branch current i L1 flowing through the inductance L 1 has again dropped to zero or whether the inductance L 1 has been demagnetized. This can be done by means of a secondary winding to the inductor L2 or by means of monitoring the voltage across the switch Sl.
  • the turn-off timing of the high-frequency clocked switch Sl is thereby set when the LED current reaches a predetermined threshold value Ipeak. As already explained at the outset, any fluctuations in the maximum negative current level ⁇ I at the reversal point T31 and in that case are disregarded, which makes this type of power regulation inaccurate.
  • the turn-off instant of the actively-timed switch (in the example of FIG. 2, switch S1) is now made adaptive, so that as a result the turn-on time t.sub.N is variable.
  • This can be achieved, for example, by adapting the turn-off threshold for the LED current and / or adaptively adjusting the turn-on time duration of the actively-timed switch.
  • the adaptation takes place on the basis of a feedback signal which is representative of the mean value of the LED current (averaging over one or more switch-on durations of the actively-timed switch). By controlling the average of the LED current, the lamp power control is much more accurate.
  • the mean value of the LED current can be detected by a sample is detected and evaluated at the time t on / 2, ie half of the on time t ON of the active clocked switch. If this is higher than the setpoint mean value, the switch-on time period or the switch-off current threshold can be reduced, in the current order, in a subsequent switch-on operation of the actively-timed switch.
  • the LED current I LED is compared with a reference value lavg soii by a comparator Kl.
  • This reference value I aV g soll is therefore the nominal mean value for the LED current and can, for example, depend on an external or internal dimming value specification and / or the level of the LED voltage.
  • This reference value l a vg so ii is a measure of the target power.
  • the purpose of the control is that the duty cycle of the output of the comparator Kl during a turn-on period t 0N of the active clocked switch is 50%.
  • the output signal of the comparator is supplied to a digital up / down counter COUNTER, which is clocked by a timer of the control unit (clock signal CNT_CLK).
  • the COUNTER counter counts in one direction as long as the LED current I LED is below the reference value Iavg_setpoint, and in the opposite direction as soon as the LED current I LED reaches the reference value l avg so ii exceeds.
  • the duty cycle of the comparison signal supplied to the counter COUNTER will be 50% and thus at the end of a switch-on period the counter reading will correspond exactly to its initial level.
  • This deviation signal ERROR is fed to a preferably digital regulator REGULATOR, which is also clocked by a timer of the control unit by a signal reg_clk.
  • REGULATOR controller implements a control strategy (eg PI controller) and controls a manipulated variable that influences the power of the LED depending on the input signal ERROR and the control strategy.
  • This manipulated variable may, for example, be one or more of:
  • the manipulated variable (s) can be changed in the current switch-on process, in each subsequent switch-on process or in every n-th switch-on process, where n is an integer greater than or equal to 2.
  • the output signal of the further comparator K2 controls the switching off gate_off of the switch.
  • the converter for the LED may, for example, also be a boost converter or a flyback converter.

Landscapes

  • Circuit Arrangement For Electric Light Sources In General (AREA)
  • Led Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un circuit de régulation de la puissance d'une DEL, comprenant un convertisseur muni d'un commutateur (51), ladite DEL étant connectée dans le circuit de sortie. Une unité de commande (1C) commande la magnétisation d'une inductance (L1) par activation du commutateur (S1) de manière cadencée. L'unité de commande (1C) reçoit en retour une valeur réelle mesurée, représentative de la moyenne du courant parcourant la DEL, qui est comparée à une valeur de référence.
EP10711663.4A 2009-04-14 2010-03-26 Régulation de la puissance de del, à l'aide de la moyenne du courant des del et d'un compteur bidirectionnel Revoked EP2420107B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PL10711663T PL2420107T3 (pl) 2009-04-14 2010-03-26 Regulacja mocy led, za pomocą średniej wartości prądu led i dwukierunkowych liczników

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
AT2292009 2009-04-14
DE102009017139A DE102009017139A1 (de) 2009-04-14 2009-04-15 Leistungsregelung von LED
DE102010003054 2010-03-19
PCT/EP2010/054014 WO2010118944A1 (fr) 2009-04-14 2010-03-26 Régulation de la puissance de del, à l'aide de la moyenne du courant des del et d'un compteur bidirectionnel

Publications (2)

Publication Number Publication Date
EP2420107A1 true EP2420107A1 (fr) 2012-02-22
EP2420107B1 EP2420107B1 (fr) 2015-07-08

Family

ID=42226646

Family Applications (1)

Application Number Title Priority Date Filing Date
EP10711663.4A Revoked EP2420107B1 (fr) 2009-04-14 2010-03-26 Régulation de la puissance de del, à l'aide de la moyenne du courant des del et d'un compteur bidirectionnel

Country Status (6)

Country Link
US (1) US9060406B2 (fr)
EP (1) EP2420107B1 (fr)
CN (1) CN102396295B (fr)
DE (1) DE112010001622A5 (fr)
PL (1) PL2420107T3 (fr)
WO (1) WO2010118944A1 (fr)

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CN102396295B (zh) 2015-06-10
US20120133295A1 (en) 2012-05-31
EP2420107B1 (fr) 2015-07-08
US9060406B2 (en) 2015-06-16
PL2420107T3 (pl) 2015-12-31
CN102396295A (zh) 2012-03-28
DE112010001622A5 (de) 2012-08-30
WO2010118944A1 (fr) 2010-10-21

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